CN110112921B - Zero-current soft-switching PWM full-bridge converter - Google Patents

Zero-current soft-switching PWM full-bridge converter Download PDF

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Publication number
CN110112921B
CN110112921B CN201910413719.0A CN201910413719A CN110112921B CN 110112921 B CN110112921 B CN 110112921B CN 201910413719 A CN201910413719 A CN 201910413719A CN 110112921 B CN110112921 B CN 110112921B
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auxiliary
diode
current
switching
switching tube
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CN110112921A (en
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秦岭
周磊
段冰莹
田民
沈家鹏
高娟
尹铭
韩启萌
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Zhenjiang Huiqiao Electric Co ltd
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Nantong University
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/3353—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having at least two simultaneously operating switches on the input side, e.g. "double forward" or "double (switched) flyback" converter
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/02—Conversion of ac power input into dc power output without possibility of reversal
    • H02M7/04—Conversion of ac power input into dc power output without possibility of reversal by static converters
    • H02M7/12—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/21—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/217—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M7/219—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only in a bridge configuration
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0048—Circuits or arrangements for reducing losses
    • H02M1/0054—Transistor switching losses
    • H02M1/0058—Transistor switching losses by employing soft switching techniques, i.e. commutation of transistors when applied voltage is zero or when current flow is zero
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Inverter Devices (AREA)
  • Dc-Dc Converters (AREA)

Abstract

The invention discloses a zero current soft switch PWM full-bridge converter, which comprises a full-bridge switch circuit, a first soft switch auxiliary circuit, a second soft switch auxiliary circuit, a transformer and a rectification filter circuit, wherein the first soft switch auxiliary circuit and the second soft switch auxiliary circuit respectively comprise an auxiliary switch tube, an auxiliary series branch formed by an auxiliary resonant inductor and an auxiliary resonant capacitor in series, and an auxiliary diode used for connecting the auxiliary series branch with the full-bridge switch circuit, the full-bridge switch network on the primary side of the transformer realizes the zero current switching-on and switching-off of all switch tubes including the auxiliary switch tube and the natural switching-off of all diodes including the diodes of the secondary side rectifier network, further, the loss of the zero-current soft-switching PWM full-bridge converter is further reduced, the working efficiency is further improved, and the zero-current soft-switching PWM full-bridge converter is particularly suitable for high-power working conditions.

Description

Zero-current soft-switching PWM full-bridge converter
Technical Field
The application relates to the technical field of electricity, in particular to a zero-current soft-switching PWM full-bridge converter.
Background
In order to promote the rapid development of the electric automobile industry, governments and enterprises of various countries continuously increase the investment and construction strength of electric automobile charging facilities. The direct current charging pile is a main charging device of a charging station and a battery replacement station, and generally adopts a two-stage structure of a three-phase rectifying circuit and a charging interface full-bridge converter. In order to achieve a smaller and lighter system, the switching frequency of the charging interface converter needs to be increased, but the switching loss increases sharply, and the heat dissipation requirement for the power supply is also increased. For this reason, the charging interface full-bridge converter needs to implement soft switching to improve the conversion efficiency of the system.
Soft switches include Zero Voltage Switches (ZVS) and Zero Current Switches (ZCS). The zero voltage switching technique refers to a technique of dropping a voltage of a switch to zero before the switch is turned on or off, and the zero current switching technique refers to a technique of dropping a current of the switch to zero before the switch is turned on or off. The traditional zero-voltage soft-switching PWM phase-shifted full-bridge converter has an internal circulating current stage, so that the system loss is large, and a bridge arm is difficult to realize ZVS after light load time lag. In addition, the ZVS power circuit is more suitable for using a Metal-Oxide-Semiconductor Field-Effect Transistor (MOSFET) as a switching tube, but the on-resistance of the MOSFET is proportional to the voltage rating, so the ZVS power circuit is not very suitable for the dc charging occasion of the electric vehicle with the characteristics of high voltage and large current. In contrast, an Insulated Gate Bipolar Transistor (IGBT) with a larger energy density and a lower on-state loss is more suitable as a switching tube of a full-bridge charging interface converter. However, when the IGBT is turned off, a current tail phenomenon occurs, which results in a large turn-off loss. An effective measure to solve this problem is to implement zero current soft switching of the IGBT. Therefore, a method for ensuring that the zero-current soft switching of all the switching tubes and the natural turn-off of the diodes can be realized in the whole range of input and output voltage and load variation is needed.
Disclosure of Invention
In view of this, the present application provides a zero current soft switching PWM full bridge converter, all switching tubes of the converter can realize zero current soft switching, and all diodes can be naturally turned off, thereby improving the system efficiency.
In order to achieve the purpose, the technical scheme provided by the invention is as follows:
in a first aspect, the present invention provides a zero current soft switching PWM full bridge converter, including a full bridge switching circuit, a transformer and a rectifying and filtering circuit, where the full bridge switching circuit includes a first bridge arm and a second bridge arm, the first bridge arm is formed by connecting a first switching tube and a third switching tube in series, the second bridge arm is formed by connecting a second switching tube and a fourth switching tube in series, collectors of the first switching tube and the second switching tube are respectively connected to an anode of an input power supply, a primary side of the transformer is connected to midpoints of the first bridge arm and the second bridge arm, the rectifying and filtering circuit includes a bridge rectifying circuit composed of four diodes and a filtering circuit composed of a filtering capacitor and a filtering inductor, a secondary side of the transformer is connected to the bridge rectifying circuit, and the zero current soft switching PWM full bridge converter further includes:
a first soft-switching auxiliary circuit, the first soft-switching auxiliary circuit including a first auxiliary switching tube, a first auxiliary resonant branch and a first auxiliary diode, the first auxiliary switching tube being connected in series with the first auxiliary resonant branch, wherein, the collector of the first auxiliary switch tube is connected with the anode of the input power supply, the emitter of the first auxiliary switch tube is connected with the first end of the first auxiliary resonance branch, the second end of the first auxiliary resonance branch is connected with the negative electrode of the input power supply, the first auxiliary resonance branch is formed by connecting a first auxiliary resonance inductor and a first auxiliary resonance capacitor in series, the cathode of the first auxiliary diode is respectively connected with the emitter of the first switching tube and the collector of the third switching tube, the anode of the first auxiliary diode is respectively connected with the emitter of the first auxiliary switching tube and the first end of the first auxiliary resonance branch;
a second soft switching auxiliary circuit, the second soft switching auxiliary circuit including a second auxiliary switching tube, a second auxiliary resonant branch and a second auxiliary diode, the second auxiliary switching tube being connected in series with the second auxiliary resonant branch, wherein, the collector of the second auxiliary switch tube is connected with the anode of the input power supply, the emitter of the second auxiliary switch tube is connected with the first end of the second auxiliary resonance branch, the second end of the second auxiliary resonance branch is connected with the negative electrode of the input power supply, the second auxiliary resonance branch is formed by connecting a second auxiliary resonance inductor and a second auxiliary resonance capacitor in series, the cathode of the second auxiliary diode is respectively connected with the emitter of the second switch tube and the collector of the fourth switch tube, the anode of the second auxiliary diode is respectively connected with the emitter of the second auxiliary switching tube and the first end of the second auxiliary resonance branch;
according to the symmetrical design of the circuit, the inductance of the second auxiliary resonance inductor is equal to the inductance of the first auxiliary resonance inductor, and the capacitance of the second auxiliary resonance capacitor is equal to the capacitance of the first auxiliary resonance capacitor.
The zero current soft switching PWM full bridge converter further comprises: the first diode and the first switch tube are connected in reverse parallel, and the second diode and the second switch tube are connected in reverse parallel.
Further, the first switch tube, the second switch tube, the third switch tube, the fourth switch tube, the first auxiliary switch tube and the second auxiliary switch tube are all IGBTs.
In a second aspect, the present application also provides a method for protecting a switch, which is applied to the zero-current soft-switching PWM full-bridge converter of the first aspect, and the method includes: after the first switch tube and the fourth switch tube are switched on, a first auxiliary switch tube is switched on; and after the second switching tube and the third switching tube are switched on, switching on the second auxiliary switching tube. By this implementation, in the on state of the first switch tube and the fourth switch tube, within the on time of the first auxiliary switch tube, the first auxiliary switch unit performs half-period resonance, and the first auxiliary switch tube can be regarded as zero-current on and zero-current off. After the first auxiliary switching tube is turned off, the current passing through the first switching tube is gradually reduced, and zero current turn-off of the first switching tube can be realized when the current is reduced to zero, so that the loss of the first switching tube is reduced. After the first switching tube is turned off, the current passing through the fourth switching tube is also gradually reduced, and zero current turn-off of the fourth switching tube can be realized when the current is reduced to zero, so that the loss of the fourth switching tube is reduced. Similarly, in the on state of the second switch tube and the third switch tube, the second auxiliary switch unit performs half-period resonance within the on time of the second auxiliary switch tube, and the second auxiliary switch tube can be regarded as zero current on and zero current off. After the second auxiliary switching tube is switched off, the current passing through the second switching tube is gradually reduced, and zero current switching-off of the second switching tube can be realized when the current is reduced to zero, so that the loss of the second switching tube is reduced. After the second switching tube is turned off, the current passing through the third switching tube is also gradually reduced, and zero current turn-off of the third switching tube can be realized when the current is reduced to zero, so that the loss of the third switching tube is reduced.
Furthermore, a calculation formula of the on-time of the first auxiliary switch tubeIs composed of
Figure BDA0002063659740000021
The calculation formula of the on-time of the second auxiliary switch tube is
Figure BDA0002063659740000022
According to the symmetrical design of the circuit, Ton,Sa＝Ton,Sb。Ton,SaFor the first auxiliary switch tube is turned on for a time period Ton,SbThe switching-on time of the second auxiliary switching tube is set; l isaIs the inductance of the first auxiliary resonant inductor, LbThe inductance of the second auxiliary resonant inductor is La＝Lb；CaIs the capacitance of the first auxiliary resonant capacitor, CbThe capacitance of the second auxiliary resonant capacitor is Ca＝Cb. In turn, the turn-on duration of the first auxiliary switch tube and the second auxiliary switch tube may be set to implement zero-current turn-on and turn-off of all switch tubes in the converter.
Compared with the prior art, the technical scheme of the invention has the following advantages:
according to the zero-current soft-switching PWM full-bridge converter, the soft-switching auxiliary branch circuit comprising the resonant inductor, the resonant capacitor, the auxiliary switching tube and the auxiliary diode is added in the basic circuit of the full-bridge switch, so that the full-bridge switching network on the primary side of the transformer realizes zero-current switching-on and switching-off of all switching tubes including the auxiliary switching tube and natural switching-off of all diodes including the diodes of the secondary side rectification network, further the loss of the zero-current soft-switching PWM full-bridge converter is further reduced, the working efficiency is further improved, and the zero-current soft-switching PWM full-bridge converter is particularly suitable for high-power working conditions.
Drawings
Fig. 1 is a schematic circuit diagram of a zero-current soft-switching PWM full-bridge converter according to an embodiment of the present application;
FIGS. 2(a) to (n) are equivalent diagrams of 14 operation modes of the circuit of FIG. 1 in one switching period;
fig. 2(o) is a diagram of main operation waveforms of fig. 1 in one switching period.
Detailed Description
The technical solutions in the embodiments of the present application will be described clearly and completely with reference to the drawings in the embodiments of the present application, and it is obvious that the described embodiments are only a part of the embodiments of the present application, and not all of the embodiments. All other embodiments, which can be derived by a person skilled in the art from the embodiments given herein without making any creative effort, shall fall within the protection scope of the present invention.
Fig. 1 shows a schematic circuit structure diagram of a zero-current soft-switching PWM full-bridge converter according to an embodiment of the present application. As an exemplary and non-limiting embodiment, the zero current soft-switching PWM full-bridge converter comprises a full-bridge switching circuit, a first soft-switching auxiliary circuit, a second soft-switching auxiliary circuit, a transformer T, a rectifying circuit and a filtering circuit, wherein the input end of the zero current soft-switching PWM full-bridge converter is connected with an input power supply VinConnected to an output terminal of a DC load RoConnection for direct current load RoProviding an output voltage.
Wherein, the full-bridge switch network comprises a first switch tube S1A second switch tube S2A third switch tube S3And a fourth switching tube S4A first switch tube S1And a third switching tube S3A first bridge arm and a second switching tube S connected in series2And a fourth switching tube S4The first bridge arm and the second bridge arm are connected in parallel. First to fourth switching tubes S1-S4An Insulated Gate Bipolar Transistor (IGBT) is adopted, and the IGBT has high energy density and extremely low on-state loss, so that the IGBT is suitable for occasions with high voltage and large current.
For the first bridge arm, the first switching tube S1Collector electrode of the power supply is connected with an input power supply VinThe emitter is connected with the midpoint A of the first bridge arm, and the first switching tube S1Further comprises a first diode D connected in inverse parallel therewith1A third switching tube S3The collector of the first bridge arm is connected with the midpoint A of the first bridge arm, and the emitter of the first bridge arm is connected with the input power supply VinOf the negative electrode. It should be noted that, in this embodiment, the bridge arm midpoint a is not necessarily limited to a midpoint on a physical scale, but may be located in the first switch tube S1And a third switching tube S3At any point on the connecting line between them.
For the second bridge arm, the second switching tube S2Collector electrode of the power supply is connected with an input power supply VinThe emitter of the second switch tube S is connected with the midpoint B of the second bridge arm2Further comprises a first diode D connected in inverse parallel therewith2Fourth switch tube S4The collector of the first bridge arm is connected with the midpoint B of the second bridge arm, and the emitter of the first bridge arm is connected with the input power supply VinThe negative electrode of (1). It should be noted that, in this embodiment, the bridge arm midpoint B is not necessarily limited to a midpoint on a physical scale, but may be located on the second switch tube S2And a fourth switching tube S4At any point on the connecting line between them.
In this embodiment, the primary winding of the transformer T has one end connected to the midpoint a of the first leg and the other end connected to the midpoint B of the second leg.
In this embodiment, the first soft switch auxiliary circuit is a first auxiliary switch tube SaA first auxiliary resonant inductor LaA first auxiliary resonant capacitor CaAnd a first auxiliary diode DaFirst auxiliary resonant inductor LaAnd a first auxiliary resonant capacitor CaA first auxiliary resonant branch consisting of a first auxiliary switch tube SaCollector electrode of the power supply is connected with an input power supply VinPositive pole of (1), first auxiliary switching tube SaIs connected to a first end of a first auxiliary resonant branch, a second end of which is connected to an input power supply VinNegative pole of (1), first auxiliary diode DaRespectively with the first switching tube S1The third switch tube S3Is connected to the collector of a first auxiliary diode DaRespectively with the first auxiliary switching tube SaIs connected with the first end of the first auxiliary resonance branch.
In this embodiment, the second soft switch auxiliary circuit is a second auxiliary switch tube SbSecond auxiliary harmonicVibration inductance LbA second auxiliary resonant capacitor CbAnd a second auxiliary diode DbSecond auxiliary resonant inductor LbAnd a second auxiliary resonance capacitor CbA second auxiliary resonant branch formed by connecting in series, a second auxiliary switch tube SbCollector electrode of the power supply is connected with an input power supply VinPositive pole of (2), second auxiliary switching tube SbIs connected to a first end of a second auxiliary resonant branch, a second end of which is connected to an input power supply VinNegative pole of (2), a second auxiliary diode DbRespectively with the second switching tube S2Emitter of, the fourth switching tube S4Is connected to the collector of a second auxiliary diode DbRespectively with the second auxiliary switch tube SbIs connected with the first end of the second auxiliary resonance branch.
In this embodiment, the second auxiliary resonant inductor LbInductance of and the first auxiliary resonant inductor LaThe inductance of the second auxiliary resonant capacitor C is equalbAnd the first auxiliary resonant capacitor CaAre equal.
In this embodiment, the first auxiliary switch tube SaAnd a second auxiliary switch tube SbInsulated Gate Bipolar Transistors (IGBTs) are used.
In this embodiment, the secondary side of the transformer T is connected to a rectifying and smoothing circuit comprising a third diode D3A fourth diode D4A fifth diode D5A sixth diode D6Filter inductor LoAnd a filter capacitor CoA third diode D3And a fifth diode D5A first diode series branch and a fourth diode D4And a sixth diode D6A second diode series branch formed by series connection, a first diode series branch connected in parallel with the second diode series branch, and a filter inductor LoOne end of the first diode is connected to the third diode D3And a fourth diode D5Is connected with the cathode of the filter capacitor C, and the other end of the filter capacitor C is connected with the cathode of the filter capacitor CoIs connected to a filter capacitor CoTo another one ofTerminals are respectively connected with a fifth diode D5A sixth diode D6The anode of the transformer T is connected, one end of the secondary winding of the transformer T is respectively connected with the anode of the third diode and the cathode of the fifth diode, and the other end of the secondary winding of the transformer T is respectively connected with the anode of the fourth diode and the cathode of the sixth diode.
The operation of the zero-current soft-switching PWM full-bridge converter according to the present application will be described with reference to the circuit connection of fig. 1.
The working process of the converter can be divided into 14 modes in one switching period, and the filter inductor LoSufficiently large, flows through the filter inductance LoCan be regarded as a constant current IoSuch that the filter inductance LoFilter capacitor CoAnd an output load RoCan be regarded as a current IoThe equivalent circuits of the modes of the constant current source of (1) are respectively shown in fig. 2(a) to 2 (n); the main waveform diagram in one switching cycle is shown in fig. 2 (o).
The following are distinguished:
at the beginning of a cycle, the first switch tube S1A second switch tube S2The third switch tube S3, the fourth switch tube S4, the first auxiliary switch tube Sa and the second auxiliary switch tube Sb are all in an off state, S1、S2Withstand voltage UinOutput a load current IoFreewheeling via a resonant rectifier network, D3、D6The magnitude of the medium current is (I)o-kim)/2，D4、D5The magnitude of the medium current is (I)o+kim) And/2, wherein k is the original secondary side turn ratio.
Mode 1: the equivalent circuit diagram is shown in FIG. 2(a) [ t0～t1]And (5) stage.
t0At the moment, the first switch tube S is switched on1And a fourth switching tube S4Due to transformer leakage inductance L in the transformer TsLimiting sudden change of current, first switch tube S1And a fourth switching tube S4For zero current switching-on, primary side current i of transformerpAnd (4) increasing linearly. Fourth diode D4A fifth diode D5Medium electricityThe flow decreases linearly at the same time. At t1At the moment, the primary side current i of the transformerpRises to ip＝Io/k+imFourth diode D4A fifth diode D5The intermediate freewheeling current drops to zero and turns off naturally, and this phase ends.
Primary side current of the transformer:
Figure BDA0002063659740000041
modality 1 duration:
Δt1＝(Io/k+im)Ls/Uin (2)
mode 2: the equivalent circuit diagram is shown in FIG. 2(b) [ t1～t2]And (5) stage.
First switch tube S1And a fourth switching tube S4Maintain conduction, primary side current i of transformerpIs clamped at a stable value. t is t2At the moment, the first auxiliary switch tube SaAnd conducting.
Primary side current of the transformer:
ip(t)＝Io/k+im
modality 3: the equivalent circuit diagram is shown in FIG. 2(c) [ t2～t3]And (5) stage.
t2At the moment, the first auxiliary switch tube SaConducting, first auxiliary resonant inductor LaA first auxiliary resonant capacitor CaResonance occurs, at which stage the first auxiliary switch tube SaCurrent value and first auxiliary resonant inductor LaThe current values are equal, so the first auxiliary switch tube SaTurning on for zero current. t is t3At the moment, the first auxiliary resonant inductor LaThe current drops to zero. At this time, the first auxiliary switch tube S can be realizedaZero current turn-off, turn-off first auxiliary switch tube SaAnd the stage ends.
First auxiliary resonant inductor LaCurrent:
iLa(t)＝-{[Uin-uCa(t6)]sinωr(t-t2)}/Zr (4)
first auxiliary resonant capacitor CaVoltage:
uCa(t)＝Uin-[Uin-uCa(t6)]cosωr(t-t2) (5)
wherein the resonant angular frequency
Figure BDA0002063659740000042
Resonant frequency
Figure BDA0002063659740000043
Characteristic impedance
Figure BDA0002063659740000044
Modal 3 duration (first auxiliary switching tube S)aOn duration of time):
Δt3＝π/ωr (6)
modality 4: the equivalent circuit diagram is shown in FIG. 2(d) [ t3～t4]And (5) stage.
t3At the moment, the first auxiliary resonant inductor LaA first auxiliary resonant capacitor CaReverse resonance, first auxiliary diode DaAnd conducting. The first auxiliary diode D at this stageaCurrent value and first auxiliary resonant inductor LaThe current values are equal, the first switch tube S1The current gradually decreases. t is t4At the moment, the first auxiliary diode DaCurrent iLaUp to the primary current i of the transformerpEqual in size, switch tubes S1The current drops to zero and the phase ends.
First auxiliary resonant inductor LaCurrent:
iLa(t)＝{[Uin-uCa(t6)]sinωr(t-t3)}/Zr (7)
first auxiliary resonant capacitor CaVoltage:
uCa(t)＝Uin+[Uin-uCa(t6)]cosωr(t-t3) (8)
modality 4 duration:
Δt4＝{arcsin[(Io/k+im)/(Uin-uCa(t6))]}/ωr (9)
mode 5: the equivalent circuit diagram is shown in FIG. 2(e) [ t4～t5]And (5) stage.
t4At the moment of time, with the first switching tube S1Antiparallel-connected first diode D1And conducting. t is t4At time, the first auxiliary resonant inductor LaCurrent iLaA peak is reached. t is t5At the moment, the first auxiliary resonant inductor LaCurrent iLaDrops to the primary side current i of the transformer againpEqual size, first diode D1The current drops to zero and turns off naturally. The first switch tube S is turned off at any time in this stage1Its zero current turn off can be achieved and the phase ends.
Modality 5 duration:
Δt5＝π/ωr-2Δt4 (10)
modality 6: the equivalent circuit diagram is shown in FIG. 2(f) [ t5～t6]And (5) stage.
t5At the moment, the first diode D1Off, first auxiliary resonant capacitor CaA first auxiliary resonant inductor LaThe resonance continues. At this stage, the voltage u at the S1 end of the first switch tubeS1＝Uin-UABThe voltage u at the third switch tube S3S3＝UAB. Primary side current i of transformerpGradually falling, fourth diode D4A fifth diode D5And simultaneously, opening the circuit and performing follow current. t is t6At the moment, the primary side current i of the transformerpDown to 0, the first auxiliary diode DaNaturally shut off and the phase ends.
First auxiliary resonant inductor LaCurrent:
iLa(t)＝{uCa(t5)sin[ωr(t-t5)]}/Zr+(Io/k+im)cosωr(t-t5) (11)
first auxiliary resonant capacitor CaVoltage:
uCa(t)＝uCa(t5)cos[ωr(t-t5)]-(Io/k+im)Zr sin[ωr(t-t5)] (12)
AB terminal voltage of transformer T:
uAB(t)＝-2(Io/k+im)Zrsin[ωr(t-t5)] (13)
modality 6 duration:
Δt6＝{arctan[-(Io/k+im)/uCa(t5)]}/ωr (14)
modality 7: the equivalent circuit diagram is shown in FIG. 2(g) [ t6～t7]And (5) stage.
In this stage, the current i in the primary side circuit of the transformerpWhen the current is zero, the secondary side continues the current through the rectifier bridge, and the fourth switching tube S is turned off at any time4Its zero current turn-off can be achieved. t is t7At the moment, the second switch tube S is switched on2A third switch tube S3。
Third diode D3A sixth diode D6Current:
iD3＝iD6＝(Io-kim)/2 (15)
fourth diode D4A fifth diode D5Current:
iD4＝iD5＝(Io+kim)/2 (16)
modality 8: the equivalent circuit diagram is shown in FIG. 2(h) [ t7，t8]And (5) stage.
t7At the moment, the second switch tube S2A third switch tube S3And conducting. Due to the leakage inductance L of the transformersLimiting sudden change of current, second switch tube S2A third switch tube S3Zero current open, transformer primary sideCurrent ipThe inverse rises linearly. Third diode D3A sixth diode D6The medium current decreases linearly at the same time. t is t8Time of day, current ipRises reversely to (I)o/k-im) A third diode D3A sixth diode D6The intermediate freewheeling current drops to zero and turns off naturally, and this phase ends.
Primary side current of the transformer:
Figure BDA0002063659740000051
modality 8 duration:
Δt8＝(Io/k-im)Ls/Uin (18)
modality 9: FIG. 2(i) shows an equivalent circuit diagram, [ t ]8，t9]And (5) stage.
A second switch tube S2A third switch tube S3Maintain conduction, primary side current i of transformerp' clamped at a constant value. t is t9At the moment, the second auxiliary switch tube SbConduction, this phase ends.
Primary side current of the transformer:
i'p(t)＝Io/k-im (19)
modality 10: the equivalent circuit diagram is shown in FIG. 2(j) [ t9，t10]And (5) stage.
t9At the moment, the second auxiliary switch tube SbConducting, second auxiliary resonant inductor LbA second auxiliary resonant capacitor CbResonance occurs, at which stage the second auxiliary switch tube SbThe current value is equal to the second auxiliary resonant inductor current value, so that the second auxiliary switch tube SbTurning on for zero current. t is t10At that time, the second auxiliary resonant inductor current drops to zero. At the moment, the second auxiliary switch tube S is turned offbIts zero current turn-off can be achieved and the phase ends.
Second auxiliary resonant inductor LbCurrent:
iLb(t)＝-{[Uin-uCb(t13)]sinωr2(t-t9)}/Zr2 (20)
second auxiliary resonant capacitor CbVoltage:
uCb(t)＝Uin-[Uin-uCb(t13)]cosωr2(t-t9) (21)
wherein the resonant angular frequency
Figure BDA0002063659740000061
Resonant frequency
Figure BDA0002063659740000062
Characteristic impedance
Figure BDA0002063659740000063
Modal 10 duration (second auxiliary switch tube S)bOn duration of time):
Δt10＝π/ωr2 (22)
modality 11: the equivalent circuit diagram is shown in FIG. 2(k) [ t10，t11]And (5) stage.
t10At the moment, the second auxiliary resonant inductor LbA second auxiliary resonant capacitor CbReverse resonant, second auxiliary diode DbAnd conducting. The second auxiliary diode D at this stagebThe current value is equal to the current value of the resonant inductor, and the second switch tube S2The current gradually decreases. t is t11At the moment, the second auxiliary diode DbCurrent iLbUp to the primary current i of the transformerpEqual size, switch tubes S2The current drops to zero and the stage ends.
Second auxiliary resonant inductor LbCurrent:
iLb(t)＝{[Uin-uCb(t13)]sinωr2(t-t10)}/Zr2 (23)
second auxiliary resonant capacitor CbVoltage:
uCb(t)＝Uin+[Uin-uCb(t13)]cosωr2(t-t10) (24)
modality 11 duration:
Δt11＝{arcsin[(Io/k-im)/(Uin-uCb(t13))]}/ωr2 (25)
modality 12: FIG. 2(l) shows an equivalent circuit diagram, [ t ]11，t12]And (5) stage.
t11At the moment of time, with the second switching tube S2A second diode D connected in reverse parallel2And conducting. t is t11' time, second auxiliary resonant inductor LbCurrent iLbA peak is reached. t is t12At the moment, the second auxiliary resonant inductor LbCurrent iLbDrops to the primary side current i of the transformer againp' equal size, second diode D2The current drops to zero and turns off naturally. The second switch tube S is turned off at any time in the stage2Its zero current turn off can be achieved and the phase ends.
Modality 12 duration:
Δt12＝π/ωr2-2Δt11 (26)
mode 13: the equivalent circuit diagram is shown in FIG. 2(m) [ t12，t13]And (5) stage.
t12At the moment of time, with the second switching tube S2A second diode D connected in reverse parallel2Turn-off, second auxiliary resonant inductor LbA second auxiliary resonant capacitor CbThe resonance continues. The second switch tube S at this stage2And a fourth switching tube S4Terminal voltage of (c): u. ofS2＝Uin-uBA，uS4＝uBA. Primary side current i of transformerp' gradually falling, secondary side third diode D3A sixth diode D6And simultaneously, opening the circuit and performing follow current. t is t13At the moment, the primary side current i of the transformerp' go down to 0. Second auxiliary diode DbNaturally shut off and the phase ends. From this moment until the end of this switching cycleThe third switch tube S is turned off at any time3Its zero current turn-off can be achieved.
Second auxiliary resonant inductor LbCurrent:
iLb(t)＝{uCb(t12)sin[ωr2(t-t12)]}/Zr2+(Io/k-im)cosωr2(t-t12) (27)
second auxiliary resonant capacitor CbVoltage:
uCb(t)＝uCb(t12)cos[ωr2(t-t12)]-(Io/k-im)Zr2sin[ωr2(t-t12)] (28)
BA terminal voltage of transformer T:
uBA(t)＝-2(Io/k-im)Zr2sin[ωr2(t-t12)] (29)
modality 13 duration:
Δt13＝{arctan[-(Io/k-im)/uCb(t12)]}/ωr2 (30)
modality 14: the equivalent circuit diagram is shown in FIG. 2(n) [ t13，t14]And (5) stage.
At this stage, the primary side current i of the transformerp' zero, secondary side freewheeling via rectifier bridge, at t14The time goes to the next switching cycle.
Third diode D3A sixth diode D6Current:
iD3＝iD6＝(Io-kim)/2 (31)
fourth diode D4A fifth diode D5Current:
iD4＝iD5＝(Io+kim)/2 (32)
based on the above analysis of the operating principle of the zero-current soft-switching PWM full-bridge converter shown in fig. 1, the following method for protecting the switch is introduced:
at the first switchPipe S1And a fourth switching tube S4After a period of time, the first auxiliary switch tube S is switched onaIn the first auxiliary switch tube SaFirst auxiliary resonant inductor L in turn-on timeaAnd a first auxiliary resonant capacitor CaResonance occurs, and a resonance current is generated. After half a resonance period, the first auxiliary switching tube SaThe current is reduced to zero, and a first auxiliary switch tube S can be realizedaThe zero current of (c) is turned off. Then the first auxiliary resonant inductor LaAnd a first auxiliary resonant capacitor CaReverse resonance, first auxiliary diode DaOn, the first switch tube S1The current of the first switch tube S is gradually reduced, and when the current is reduced to zero, the first switch tube S can be realized1Is turned off at zero current, the first switching tube S1After being turned off, the first auxiliary resonant inductor LaAnd a first auxiliary resonant capacitor CaThrough a first auxiliary diode DaContinue to resonate, pass through the fourth switch tube S4When the current is reduced to 0, the fourth switch tube S can be realized4The zero current of (c) is turned off.
In the second switch tube S2And a third switching tube S3After a period of time, the second auxiliary switch tube S is switched onbIn the second auxiliary switch tube SbSecond auxiliary resonant inductor L in turn-on timebAnd a second auxiliary resonance capacitor CbResonance occurs, and a resonance current is generated. After half a resonance period, the second auxiliary switching tube SbThe current is reduced to zero, and a second auxiliary switch tube S can be realizedbThe zero current of (c) is turned off. And then the second auxiliary resonant inductor LbAnd a second auxiliary resonant capacitor CbReverse resonant, second auxiliary diode DbOn, the second switch tube S2The current of the first switch tube S gradually decreases, and when the current decreases to zero, the second switch tube S can be realized2Is turned off at zero current, and the second switching tube S2After being turned off, the second auxiliary resonant inductor LbAnd a second auxiliary resonance capacitor CbThrough a second auxiliary diode DbContinuing to resonate, passing through a third switch tube S3When the current is reduced to 0, the third switch tube S can be realized3The zero current of (c) is turned off.
It should be noted that, turning on the switch means providing a high level driving signal to the switch tube, and turning off the switch means providing a low level driving signal to the switch tube. Specifically, the switch control unit transmits a Pulse signal to the controllable switch tube through a Pulse Width Modulation (PWM) technique.
It is noted that, herein, relational terms such as first and second, and the like may be used solely to distinguish one entity or action from another entity or action without necessarily requiring or implying any actual such relationship or order between such entities or actions. Also, the terms "comprises," "comprising," or any other variation thereof, are intended to cover a non-exclusive inclusion, such that a process, method, article, or apparatus that comprises a list of elements does not include only those elements but may include other elements not expressly listed or inherent to such process, method, article, or apparatus. Without further limitation, an element defined by the phrase "comprising an … …" does not exclude the presence of other identical elements in a process, method, article, or apparatus that comprises the element.
The above description of the embodiments is only intended to facilitate the understanding of the method of the invention and its core idea, and not to limit it. It should be noted that, for those skilled in the art, without departing from the principle of the present invention, several improvements and modifications can be made to the present invention, and these improvements and modifications also fall into the protection scope of the present invention.

Claims (4)

1. The utility model provides a zero current soft switch PWM full-bridge converter, includes full-bridge switch circuit, transformer, rectification filter circuit, full-bridge switch circuit includes first bridge arm and second bridge arm, first bridge arm is established ties by first switch tube and third switch tube and is constituted, the second bridge arm is established ties by second switch tube and fourth switch tube and is constituted, the primary side of transformer with first bridge arm with the midpoint connection of second bridge arm, the secondary side of transformer with rectification filter circuit connects, its characterized in that, zero current soft switch PWM full-bridge converter still includes:
a first soft-switching auxiliary circuit, the first soft-switching auxiliary circuit including a first auxiliary switching tube, a first auxiliary resonant branch and a first auxiliary diode, the first auxiliary switching tube being connected in series with the first auxiliary resonant branch, wherein, the collector of the first auxiliary switch tube is connected with the anode of the input power supply, the emitter of the first auxiliary switch tube is connected with the first end of the first auxiliary resonance branch, the second end of the first auxiliary resonance branch is connected with the negative electrode of the input power supply, the first auxiliary resonance branch is formed by connecting a first auxiliary resonance inductor and a first auxiliary resonance capacitor in series, the cathode of the first auxiliary diode is respectively connected with the emitter of the first switching tube and the collector of the third switching tube, the anode of the first auxiliary diode is respectively connected with the emitter of the first auxiliary switching tube and the first end of the first auxiliary resonance branch;
a second soft switching auxiliary circuit, which includes a second auxiliary switching tube, a second auxiliary resonant branch and a second auxiliary diode, the second auxiliary switching tube is connected in series with the second auxiliary resonant branch, wherein a collector of the second auxiliary switching tube is connected to an anode of the input power supply, an emitter of the second auxiliary switching tube is connected to a first end of the second auxiliary resonant branch, a second end of the second auxiliary resonant branch is connected to a cathode of the input power supply, the second auxiliary resonant branch is formed by connecting a second auxiliary resonant inductor and a second auxiliary resonant capacitor in series, a cathode of the second auxiliary diode is connected to an emitter of the second switching tube and a collector of the fourth switching tube, and an anode of the second auxiliary diode is connected to an emitter of the second auxiliary switching tube and a first end of the second auxiliary resonant branch, the inductance of the second auxiliary resonant inductor is equal to the inductance of the first auxiliary resonant inductor, and the capacitance of the second auxiliary resonant capacitor is equal to the capacitance of the first auxiliary resonant capacitor;
the zero current soft switching PWM full bridge converter further comprises: the first diode and the first switching tube are connected in reverse parallel, and the second diode and the second switching tube are connected in reverse parallel;
the rectification filter circuit comprises a third diode, a fourth diode, a fifth diode, a sixth diode, a filter inductor and a filter capacitor, wherein the cathode of the third diode is connected with the cathode of the fourth diode and the first end of the filter inductor, the second end of the filter inductor is connected with the anode of the filter capacitor, the cathode of the filter capacitor is connected with the anode of the fifth diode and the anode of the sixth diode, the anode of the third diode is connected with the cathode of the fifth diode and the first end of the secondary side of the transformer, and the anode of the fourth diode is connected with the cathode of the sixth diode and the second end of the secondary side of the transformer;
the working process of the zero-current soft-switching PWM full-bridge converter in one switching period comprises the following 14 modes:
(1) mode 1, t0～t1Stage (2): t is t0The first switching tube and the fourth switching tube are switched on at any time, the primary current of the transformer rises linearly from zero, the first switching tube and the fourth switching tube are switched on for zero current, the current in the fourth diode and the fifth diode drops to zero and is naturally switched off, and the mode 1 is finished;
(2) mode 2, t1～t2Stage (2): the first switching tube and the fourth switching tube are kept conducted, the primary side current of the transformer is kept unchanged, and t2At the moment, the first auxiliary switching tube is switched on, and the mode 2 is ended;
(3) mode 3, t2～t3Stage (2): the first auxiliary resonance inductor resonates with the first auxiliary resonance capacitor, the first auxiliary switch tube is switched on for zero current, and t3At the moment, the current of the first auxiliary resonant inductor is reduced to zero, the first auxiliary switching tube is turned off by the zero current, and the mode 3 is ended;
(4) mode 4, t3～t4Stage (2): the first auxiliary resonance inductor and the first auxiliary resonance capacitor pass throughAn auxiliary diode performs reverse resonance, the current of the first switch tube begins to fall, and t4At the moment, the current of the first switching tube is reduced to zero, the first switching tube is turned off, and the mode 4 is ended;
(5) mode 5, t4～t5Stage (2): the first diode is conducted, the first auxiliary resonant inductor current continues to rise and then falls after reaching the peak value, and t5At the moment, the current of the first auxiliary resonant inductor is reduced to be equal to the primary current of the transformer, the current of the first diode is reduced to zero and is naturally turned off, and the mode 5 is ended;
(6) mode 6, t5～t6Stage (2): the first auxiliary resonance inductor and the first auxiliary resonance capacitor continue to perform reverse resonance, the fourth diode and the fifth diode are simultaneously switched on, and t6At the moment, the primary side current of the transformer drops to 0, the first auxiliary diode is naturally turned off, and the mode 6 is ended;
(7) mode 7, t6～t7Stage (2): the primary current of the transformer is kept at zero, the third diode, the fourth diode, the fifth diode and the sixth diode follow current, t7At the moment, the second switching tube and the third switching tube are switched on by zero current, and the mode 7 is ended;
(8) mode 8, t7～t8Stage (2): the primary side current of the transformer is linearly increased from zero in a reverse direction, the currents in the third diode and the sixth diode are simultaneously linearly decreased, and t8At the moment, the currents in the third diode and the sixth diode are reduced to zero and are naturally turned off, and the mode 8 is ended;
(9) mode 9, t8～t9Stage (2): the second switching tube and the third switching tube are kept conducted, the primary side current of the transformer is kept unchanged, and t9At the moment, the second auxiliary switching tube is switched on, and the mode 9 is ended;
(10) mode 10, t9～t10Stage (2): the second auxiliary resonance inductor resonates with the second auxiliary resonance capacitor, the second auxiliary switch tube is switched on for zero current, and t10At the moment, the current of the second auxiliary resonant inductor is reduced to zero, the second auxiliary switching tube is turned off by the zero current, and the mode 10 is ended;
(11) mode 11, t10～t11Stage (2): the second auxiliary resonance inductor and the second auxiliary resonance capacitor perform reverse resonance through the second auxiliary diode, the current of the second switching tube begins to fall, and t11At the moment, the current of the second switching tube is reduced to zero, the second switching tube is turned off, and the mode 11 is ended;
(12) mode 12, t11～t12Stage (2): the second diode is conducted, the current of the second auxiliary resonance inductor continuously rises and falls after reaching the peak value, and t12At the moment, the current of the second auxiliary resonant inductor is reduced to be equal to the primary current of the transformer, the current of the second diode is reduced to zero and is naturally turned off, and the mode 12 is ended;
(13) mode 13, t12～t13Stage (2): the second auxiliary resonance inductor and the second auxiliary resonance capacitor continue to perform reverse resonance, the third diode and the sixth diode are simultaneously switched on, and t13At the moment, the primary current of the transformer drops to 0, the second auxiliary diode is naturally turned off, and the mode 13 is ended;
(14) modality 14, t13～t14Stage (2): the current of the primary circuit of the transformer is zero, and the third diode, the fourth diode, the fifth diode and the sixth diode follow current and flow at t14At that point, the modality 14 ends and the next switching cycle is entered.
2. The zero current soft-switching PWM full-bridge converter according to claim 1, wherein each switching tube of said zero current soft-switching PWM full-bridge converter is an IGBT.
3. A method of protecting switches, applied to a zero current soft switching PWM full bridge converter according to any of claims 1 or 2, the method comprising:
after the first switch tube and the fourth switch tube are switched on, the first auxiliary switch tube is switched on;
and after the second switching tube and the third switching tube are switched on, switching on the second auxiliary switching tube.
4. The method of claim 3,
the calculation formula of the on-time of the first auxiliary switch tube is as follows:
Figure FDA0002984830290000021
the calculation formula of the on-time of the second auxiliary switch tube is as follows:
Figure FDA0002984830290000022
wherein, Ton,SaFor the first auxiliary switch tube is turned on for a time period Ton,SbThe switching-on time of the second auxiliary switching tube is set; l isaIs the inductance of the first auxiliary resonant inductor, LbThe inductance of the second auxiliary resonance inductor; caIs the capacitance of the first auxiliary resonant capacitor, CbIs the capacitance of the second auxiliary resonant capacitor.
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