CN116169796B - Soft-switch battery wireless charger, charging method and soft-switch charging control method - Google Patents

Soft-switch battery wireless charger, charging method and soft-switch charging control method Download PDF

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Publication number
CN116169796B
CN116169796B CN202310225583.7A CN202310225583A CN116169796B CN 116169796 B CN116169796 B CN 116169796B CN 202310225583 A CN202310225583 A CN 202310225583A CN 116169796 B CN116169796 B CN 116169796B
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auxiliary
current
switch tube
soft
voltage
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CN116169796A (en
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刘洪臣
王有政
周祺堃
赵诗雨
于惠缨
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Harbin Institute of Technology
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Harbin Institute of Technology
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J50/00—Circuit arrangements or systems for wireless supply or distribution of electric power
    • H02J50/10—Circuit arrangements or systems for wireless supply or distribution of electric power using inductive coupling
    • H02J50/12—Circuit arrangements or systems for wireless supply or distribution of electric power using inductive coupling of the resonant type
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0048—Circuits or arrangements for reducing losses
    • H02M1/0054—Transistor switching losses
    • H02M1/0058—Transistor switching losses by employing soft switching techniques, i.e. commutation of transistors when applied voltage is zero or when current flow is zero
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
    • H02M1/083—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters for the ignition at the zero crossing of the voltage or the current
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/01—Resonant DC/DC converters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/3353—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having at least two simultaneously operating switches on the input side, e.g. "double forward" or "double (switched) flyback" converter

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Computer Networks & Wireless Communication (AREA)
  • Inverter Devices (AREA)

Abstract

A soft switch battery wireless charger, a charging method and a soft switch charging control method belong to the technical field of battery wireless charging. The invention aims at the problems that the composite topological structure of the existing battery wireless charger is complex, and the parameter requirements on the compensation element are harsh when soft switching is realized. The soft switch battery wireless charger comprises an energy transmitting end and an energy receiving end, wherein the energy transmitting end is provided with an auxiliary circuit on the basis of a high-frequency single-phase full-bridge inverter circuit and is arranged on a transmitting coil L P Is connected with primary compensation capacitor C in series at the same name end P The method comprises the steps of carrying out a first treatment on the surface of the The energy receiving end is added with a secondary side compensation network on the basis of an active rectifier, and a mode change-over switch Q is arranged to control the change-over of a charging mode. The switching tube in the high-frequency single-phase full-bridge inverter circuit can realize zero-voltage soft-on action and zero-current soft-off action simultaneously in a full-load range, so that the switching loss in the high-frequency inverter is reliably eliminated, and the mode of realizing soft switching has the capacity of resisting compensation parameter offset.

Description

Soft-switch battery wireless charger, charging method and soft-switch charging control method
Technical Field
The invention relates to a soft switch battery wireless charger, a charging method and a soft switch charging control method, and belongs to the technical field of battery wireless charging.
Background
At present, various intelligent equipment is powered by an internal battery of the system. The traditional electric energy supply mode has two major types of pluggable wired power supply and battery replacement, and has the defects of dependence on manual operation, frequent recovery and charging, plugging of devices, easy abrasion, contact electric spark generation and the like. The wireless charging technology effectively solves the defects of the traditional wired power supply mode, and is widely applied to the fields of portable electronic equipment, deep sea aircrafts, electric vehicles and the like.
At present, a mainstream battery charging mode adopts a two-stage charging mode, namely' constant current and constant voltage. In order to realize a constant-current charging mode and a constant-voltage charging mode required by battery charging, researchers at home and abroad have made more beneficial searches in recent years. Mainly comprises three technical means: i.e. adding DC/DC converters, frequency switching techniques and designing new composite topologies. The introduction of a DC/DC converter not only increases the power density of the system but also increases the losses of the system; the frequency switching technology needs to construct a wireless communication link between a transmitter and a receiver, which increases the complexity of a system controller, and in addition, frequency bifurcation phenomenon is caused, which also has negative influence on the stability of the system; the composite topology can effectively avoid the defects of frequency conversion and the addition of a DC/DC converter, so that the composite topology is constructed as a research hot spot in recent years. However, existing composite topologies suffer from a large number of devices. Therefore, it is desirable to construct a composite topology that contains a small number of components.
In addition, battery wireless chargers typically operate at higher frequencies, with the switching losses of the power switching devices being a greater proportion of the total losses of the system. Therefore, it is important to improve the efficiency of the system to have as many power switches as possible operate in soft switching conditions. At present, the most main mode of the battery wireless charger for realizing the soft switch is to adjust parameters of the compensation element, so that the input impedance of the system presents inductance, and zero-voltage soft switch-on is realized. However, this approach is demanding on parameters, and drift of parameters has a large influence on the magnitude of the soft switch and the reactive power, resulting in poor stability of the soft switch.
Disclosure of Invention
Aiming at the problems that the composite topological structure of the existing battery wireless charger is complex and the parameter requirements on the compensation element are harsh when soft switching is realized, the invention provides the soft switching battery wireless charger, a charging method and a soft switching charging control method.
The invention providesA soft switch battery wireless charger comprises a DC power supply V in Auxiliary circuit, high-frequency single-phase full-bridge inverter circuit and primary compensation capacitor C P A coupler, a secondary compensation network, a mode change-over switch Q and an active rectifier,
DC power supply V in The positive pole of the high-frequency single-phase full-bridge inverter circuit is connected with the positive pole input end of the direct-current side of the high-frequency single-phase full-bridge inverter circuit, and the direct-current power supply V in The negative electrode of the high-frequency single-phase full-bridge inverter circuit is connected with the negative electrode input end of the direct-current side of the high-frequency single-phase full-bridge inverter circuit;
the coupler comprises a transmitting coil L P And a receiving coil L S ；
The reference positive pole A of the alternating current side of the high-frequency single-phase full-bridge inverter circuit passes through the primary compensation capacitor C P Connecting transmitting coils L P Is the same name as the transmitting coil L P The different name end of the high-frequency single-phase full-bridge inverter circuit is connected with a reference negative pole B on the alternating current side;
the auxiliary circuit comprises an auxiliary resonant inductor L A Auxiliary resonance capacitor C A Auxiliary switch tube S A1 And an auxiliary switching tube S A2 Auxiliary switch tube S A1 And an auxiliary switching tube S A2 After being connected in series, the high-frequency single-phase full-bridge inverter circuit is connected between a positive input end and a negative input end on the direct current side, and an auxiliary resonance inductance L A Is connected with a DC power supply V in Auxiliary resonance capacitor C between the positive electrode of the high-frequency single-phase full-bridge inverter circuit and the positive electrode input end of the direct current side A Is connected with an auxiliary switch tube S A1 And an auxiliary switching tube S A2 The connection point between the two is connected with the reference positive pole A;
the secondary compensation network comprises a compensation capacitor C S1 Compensating capacitor C S2 And compensating inductance L S1 ；
The AC input side reference positive pole C of the active rectifier is connected with the compensation inductance L through the mode change-over switch Q S1 Is one end of compensating inductance L S1 The other end of (C) is connected with a compensation capacitor S2 Compensating capacitor C S2 The other end of the first power supply is connected with an alternating current input side reference negative pole D of the active rectifier; positive terminal of DC output side of active rectifier and DC inputThe battery load is connected between the outlet side negative electrode ends for charging;
compensating inductance L S1 The other end of (C) is connected with a compensation capacitor S1 Compensating capacitor C S1 Is connected with the receiving coil L at the other end S Is the same name end of the receiving coil L S The opposite terminal of the active rectifier is connected with the negative terminal of the direct current output side of the active rectifier.
The soft-switching battery wireless charger according to the invention, the active rectifier comprises a switching tube S 5 Switch tube S 6 Diode D 1 Diode D 2 And output capacitance C O ，
Switch tube S 5 Drain of (D) diode D 1 Cathode and output capacitance C of (2) O One end of the switch tube S is connected and then used as the positive end of the direct current output side of the active rectifier 6 Source of (D) diode D 2 Anode and output capacitance C of (2) O The other end of the active rectifier is connected and then used as the negative end of the direct current output side of the active rectifier;
switch tube S 5 Source electrode of (C) is connected with switch tube S 6 A drain electrode of (2); diode D 1 Anode-connected diode D of (c) 2 A cathode of (a);
diode D 1 The anode connection terminal of (2) is used as a reference positive pole C, a switch tube S 6 As a reference negative pole D.
According to the soft-switching battery wireless charger of the invention, the mode changeover switch Q is formed by two MOSFETs in reverse series connection.
The soft switch battery wireless charger of the invention, the high-frequency single-phase full-bridge inverter circuit comprises a switch tube S 1 Switch tube S 2 Switch tube S 3 And a switch tube S 4 ，
Switch tube S 1 And a switch tube S 3 The drains of the two are connected together to serve as the positive input end of the direct current side of the high-frequency single-phase full-bridge inverter circuit, and the switch tube S 2 And a switch tube S 4 The sources of the two are connected together to serve as the negative input end of the direct current side of the high-frequency single-phase full-bridge inverter circuit; switch tube S 1 Source electrode of (C) is connected with switch tube S 2 Is provided with a drain electrode of (c),switch tube S 3 Source electrode of (C) is connected with switch tube S 4 A drain electrode of (2);
switch tube S 1 The source electrode of the (B) is used as a reference positive pole A and a switching tube S of an alternating current side of a high-frequency single-phase full-bridge inverter circuit 4 The drain electrode of the (C) is used as a reference negative pole B of the alternating current side of the high-frequency single-phase full-bridge inverter circuit.
The invention also provides a charging method of the soft-switch battery wireless charger, which is realized based on the soft-switch battery wireless charger and comprises the steps of carrying out constant current and then constant voltage wireless charging on a battery load:
firstly, constant current charging is carried out on a battery load: the mode change-over switch Q is in an off state, and the diode D 1 And diode D 2 Cut-off, compensating inductance L S1 The active rectifier is equivalent to a half-bridge active rectifier when not in operation;
when the charging voltage of the battery load reaches the rated voltage, the battery load is subjected to constant voltage charging: the mode change-over switch Q is in a conducting state, and the switch tube S 6 Conduction and switch tube S 5 The active rectifier is equivalent to a half-bridge uncontrollable rectifier, which is turned off until the charging is completed.
The invention also provides a soft switch charging control method of the soft switch battery wireless charger, which is used for controlling the charging of the soft switch battery wireless charger and comprises the following steps:
the high-frequency single-phase full-bridge inverter circuit adopts a unipolar SPWM modulation method to realize zero-voltage soft-on and zero-current soft-off of the switching tube.
According to the soft switch charging control method of the soft switch battery wireless charger, the process of realizing zero voltage soft on and zero current soft off by the high-frequency single-phase full-bridge inverter circuit comprises the following steps:
if the output current of the high-frequency single-phase full-bridge inverter circuit is in the positive direction, a switch tube S 1 In a high-frequency switching state, switch tube S 2 And a switch tube S 3 Turn-off, switch tube S 4 Conducting; if the output current of the high-frequency single-phase full-bridge inverter circuit is in a negative direction, a switch tube S 2 In a high-frequency switching state, switch tube S 3 Conduction and switch tube S 1 And a switch tube S 4 And (5) switching off.
According to the soft switch charging control method of the soft switch battery wireless charger, the high-frequency single-phase full-bridge inverter circuit is controlled in 10 working phases in one switching period:
stages 1[0 to t 0 ]: in the initial stage of the switching period, the auxiliary switching tube S is made A1 And an auxiliary switching tube S A2 Turn-off, switch tube S 1 And a switch tube S 4 Conduction, DC power supply V in By auxiliary resonant inductance L A Switch tube S 1 And a switch tube S 4 Compensating capacitance C towards primary side P And a transmitting coil L P Powering up to t at the end of the initial phase 0 Time; auxiliary resonance capacitor C in stage 1 A Voltage v across CA =0, auxiliary resonant inductance L A Current i in (a) LA ＝I P ，I P Is a fixed value;
stage 2[t 0 ～t 1 ]：t 0 At moment, the auxiliary switching tube S is turned on A2 Auxiliary resonant inductance L A Obstruction auxiliary switch tube S A2 Current rising rate at turn-on time to make auxiliary switch tube S A2 Realizing zero-voltage soft-on; auxiliary resonant inductance L A And auxiliary resonance capacitor C A Resonance, auxiliary resonance inductance L A Current i in (a) LA From I P Start to increase, auxiliary resonance capacitance C A Voltage v across CA Increase in reverse from 0 when the auxiliary resonance capacitance C A The voltage across it increases inversely to-V in When equal, auxiliary resonant inductance L A Current i in (a) LA The auxiliary resonance capacitance C starts to decrease after increasing to the maximum value in this stage A Voltage v across CA Continue to increase reversely when the auxiliary resonant inductance L A Current i in (a) LA Again equal to I P When in use, the auxiliary switch tube S A2 The current in (a) is equal to 0 and reaches t 1 At the moment, the stage 2 ends;
stage 3[t 1 ～t 2 ]：t 1 Time of day, auxiliary switching tube S A2 In (a) and (b)The current is equal to 0, and the auxiliary switch tube S is turned off A2 Zero-current soft turn-off is completed; auxiliary resonant inductance L A And auxiliary resonance capacitor C A Continuously in a resonance state, auxiliary resonance inductance L A Current i in (a) LA From I P Start to decrease, auxiliary resonance capacitance C A Voltage v across CA Reverse decrease; auxiliary resonant inductance L A Current i in (a) LA When changing to 0, reach t 2 At the moment, the stage 3 ends;
stage 4[t 2 ～t 3 ]：t 2 At the moment, flows through the switching tube S 1 The current of (2) is zero, and the switch tube S is turned off 1 Zero-current soft turn-off is completed; auxiliary resonant inductance L A And auxiliary resonance capacitor C A Resonance, auxiliary resonance inductance L A Current i in (a) LA Non-linear increase in reverse direction from 0, auxiliary resonance capacitance C A Voltage v across CA Continuing to reversely reduce; as auxiliary resonance capacitor C A Voltage v across CA Equal to V in Auxiliary resonant inductance L A Current i in (a) LA Reaching the reverse maximum; then, the auxiliary resonance capacitor C A Voltage v across CA And auxiliary resonant inductance L A Current i in (a) LA All in the process of reverse reduction, when the auxiliary resonant inductance L A Current i in (a) LA Changing to 0 again to reach t 3 At the moment, the stage 4 ends;
stage 5[t 3 ～t 4 ]：t 3 Time of day, I P By auxiliary resonance capacitor C A The branch is freewheeling and the auxiliary resonance capacitor C A Voltage v across CA The inverse linearity decreases when the auxiliary resonance capacitance C A Voltage v across CA When equal to 0, the auxiliary switch tube S A2 The body diode of (1) is naturally turned off to t 4 At the moment, the stage 5 ends;
stage 6[t 4 ～t 5 ]：t 4 At moment, the auxiliary switching tube S is turned on A1 Auxiliary resonant inductance L A Obstruction auxiliary switch tube S A1 Current rising rate during on to enable auxiliary switch tube S A1 Realizing zero-voltage soft-on; then, the auxiliary resonant inductance L A And auxiliary resonance capacitor C A Resonance, auxiliary resonance inductance L A Current i in (a) LA And auxiliary resonance capacitor C A Voltage v across CA Increasing positively from 0 when the auxiliary resonant inductance L A Current i in (a) LA Increase to I P Reach t 5 At the moment, the stage 6 ends;
stage 7[t 5 ～t 6 ]: from t 5 Starting at the moment, the auxiliary resonant inductance L A Current i in (a) LA Always equal to I P When the auxiliary resonance capacitor C A Voltage v across CA Equal to V in When it reaches t 6 At the moment, the stage 7 ends;
stage 8[t 6 ～t 7 ]: from t 6 Starting at the moment, the current starts to flow through the switching tube S 2 Body diode of (2), auxiliary resonant inductance L A Current i in (a) LA Forward reduction, auxiliary resonance capacitance C A Voltage v across CA Positive increase, in the auxiliary resonance inductance L A Current i in (a) LA T changing to zero 7 Time, auxiliary resonance capacitor C A Voltage v across CA Reaching the positive maximum value, and ending the stage 8;
stage 9[t 7 ～t 8 ]：t 7 Time of day, auxiliary switching tube S A1 The current in (a) is equal to 0, and the auxiliary switching tube S is turned off A1 Zero-current soft turn-off is completed; the current starts to flow through the auxiliary switching tube S A1 The body diode of (1), auxiliary resonant inductance L A And auxiliary resonance capacitor C A Resonance, auxiliary resonance inductance L A Current i in (a) LA Increase in reverse from 0, auxiliary resonance capacitance C A Voltage v across CA Starts to decrease in the forward direction when the auxiliary resonance capacitance C A Voltage v across CA And V is equal to in When equal, auxiliary resonant inductance L A Current i in (a) LA Reversely increasing to the maximum value, reversely decreasing, and the auxiliary resonance capacitor C A Voltage v across CA Forward direction decreases; when the auxiliary resonant inductance L A Current i in (a) LA Equal to 0, auxiliary switching tube S A1 The body diode in the capacitor is naturally turned off, and the auxiliary resonance capacitor C A Voltage v across CA Changing to 0 to reach t 8 At the moment, stage 9 ends;
stage 10[ t ] 8 ～t 9 ]：t 8 At the moment, switch tube S 1 The voltage at two ends is equal to 0, and the switching tube S is turned on 1 Completing zero voltage soft-on; auxiliary resonant inductance L at this time A Current i in (a) LA Positive linear increase, when the auxiliary resonant inductance L A Current i in (a) LA Increase to I P When flowing through the switch tube S 2 The current change of the body diode is 0, so that zero-current soft turn-off is realized, and the stage 10 is finished; continuing to the next switching cycle.
The invention has the beneficial effects that: the switching tube in the high-frequency single-phase full-bridge inverter circuit in the soft-switching battery wireless charger with the low-energy consumption auxiliary circuit can realize zero-voltage soft-on action and zero-current soft-off action in a full-load range at the same time, so that the switching loss in the high-frequency inverter is reliably eliminated, and the mode of realizing soft switching has the capacity of resisting compensation parameter deviation.
The auxiliary circuit has the characteristic of low energy consumption, and the auxiliary switching tube can realize zero-voltage soft-on and zero-current soft-off actions within the full load range, and is simple to control.
In the method, the high-frequency single-phase full-bridge inverter circuit adopts a limited monopole SPWM (sinusoidal pulse Width modulation) strategy, which is beneficial to further improving the efficiency of the charger.
The rectification link of the invention adopts an active rectification circuit composed of two MOSFETs and two diodes, and has the advantage of high efficiency compared with the traditional uncontrollable rectification circuit (composed of four diodes). The invention can complete the switching of the constant-current charging mode and the constant-voltage charging mode by only using one mode change-over switch and a small amount of compensation elements under the condition of no need of frequency switching and complex control.
Drawings
FIG. 1 shows a soft-switching battery according to the inventionA structural schematic diagram of the charger; v in the figure AB Representing the voltage between AB points, V CD Representing the voltage between CD spots, i CS1 Compensating for the flow through capacitor C S1 I is the current of (i) P Compensating capacitance C for flow through primary P I is the current of (i) CS2 Compensating for the flow through capacitor C S2 I is the current of (i) LS1 Compensating inductance L for flow S1 Current of V BAT Indicating the charging voltage, I BAT Represents charging current, M PS Representing the transmitting coil L P And a receiving coil L S Mutual inductance between the two;
fig. 2 is an equivalent circuit diagram of the charging method of the soft-switching battery wireless charger in the constant-current charging mode;
fig. 3 is an equivalent circuit diagram of a charging method of the soft-switching battery wireless charger in a constant voltage charging mode according to the present invention;
fig. 4 to 13 are equivalent circuit diagrams of soft-switching commutation of the soft-switching battery wireless charger operating at 10 stages of one switching cycle in the soft-switching charge control method of the soft-switching battery wireless charger; wherein fig. 4 is an equivalent circuit diagram of the commutation working phase 1; fig. 5 is an equivalent circuit diagram of the commutation working phase 2; fig. 6 is an equivalent circuit diagram of the commutation working phase 3; fig. 7 is an equivalent circuit diagram of the commutation working phase 4; fig. 8 is an equivalent circuit diagram of the commutation working phase 5; fig. 9 is an equivalent circuit diagram of the commutation working phase 6; fig. 10 is an equivalent circuit diagram of the commutation working phase 7; fig. 11 is an equivalent circuit diagram of the commutation working phase 8; fig. 12 is an equivalent circuit diagram of the commutation working phase 9; fig. 13 is an equivalent circuit diagram of the commutation operating phase 10;
FIG. 14 is a characteristic operational waveform diagram of a soft-switch charge control method for a soft-switch battery wireless charger at 10 stages in a switching cycle; i in the figure S1 Is a switching tube S 1 V of (2) S1 Is a switching tube S 1 Is a voltage of (2);
fig. 15 shows a switching tube S in a soft switch charge control method of a soft switch battery wireless charger 1 Voltage and current experimental waveforms during switching;
fig. 16 is a soft-switching batteryIn the soft switch charging control method of the wireless charger, an auxiliary switch tube S A1 Voltage and current experimental waveforms during switching; i in the figure SA1 Is an auxiliary switch tube S A1 V of (2) SA1 Is an auxiliary switch tube S A1 Is a voltage of (2);
fig. 17 shows a soft-switching charge control method of a soft-switching battery wireless charger, in which an auxiliary switching tube S A2 Voltage and current experimental waveforms during switching; i in the figure SA2 Is an auxiliary switch tube S A2 V of (2) SA2 Is an auxiliary switch tube S A2 Is a voltage of (2);
fig. 18 is an experimental waveform of a soft-switch battery wireless charger in a constant current charging mode in a charging method of the soft-switch battery wireless charger;
fig. 19 is an experimental waveform of a soft-switch battery wireless charger in a constant voltage charging mode in a charging method of the soft-switch battery wireless charger.
Detailed Description
The following description of the embodiments of the present invention will be made clearly and completely with reference to the accompanying drawings, in which it is apparent that the embodiments described are only some embodiments of the present invention, but not all embodiments. All other embodiments, which can be made by those skilled in the art based on the embodiments of the invention without making any inventive effort, are intended to be within the scope of the invention.
It should be noted that, without conflict, the embodiments of the present invention and features of the embodiments may be combined with each other.
The invention is further described below with reference to the drawings and specific examples, which are not intended to be limiting.
Detailed description of the inventionreferring to fig. 1, this embodiment provides a soft-switching battery wireless charger, which includes a dc power supply V in Auxiliary circuit, high-frequency single-phase full-bridge inverter circuit and primary compensation capacitor C P A coupler, a secondary compensation network, a mode change-over switch Q and an active rectifier,
DC power supplySource V in The positive pole of the high-frequency single-phase full-bridge inverter circuit is connected with the positive pole input end of the direct-current side of the high-frequency single-phase full-bridge inverter circuit, and the direct-current power supply V in The negative electrode of the high-frequency single-phase full-bridge inverter circuit is connected with the negative electrode input end of the direct-current side of the high-frequency single-phase full-bridge inverter circuit;
the coupler comprises a transmitting coil L P And a receiving coil L S ；
The reference positive pole A of the alternating current side of the high-frequency single-phase full-bridge inverter circuit passes through the primary compensation capacitor C P Connecting transmitting coils L P Is the same name as the transmitting coil L P The different name end of the high-frequency single-phase full-bridge inverter circuit is connected with a reference negative pole B on the alternating current side;
the auxiliary circuit comprises an auxiliary resonant inductor L A Auxiliary resonance capacitor C A Auxiliary switch tube S A1 And an auxiliary switching tube S A2 Auxiliary switch tube S A1 And an auxiliary switching tube S A2 After being connected in series, the high-frequency single-phase full-bridge inverter circuit is connected between a positive input end and a negative input end on the direct current side, and an auxiliary resonance inductance L A Is connected with a DC power supply V in Auxiliary resonance capacitor C between the positive electrode of the high-frequency single-phase full-bridge inverter circuit and the positive electrode input end of the direct current side A Is connected with an auxiliary switch tube S A1 And an auxiliary switching tube S A2 The connection point between the two is connected with the reference positive pole A;
the secondary compensation network comprises a compensation capacitor C S1 Compensating capacitor C S2 And compensating inductance L S1 ；
The AC input side reference positive pole C of the active rectifier is connected with the compensation inductance L through the mode change-over switch Q S1 Is one end of compensating inductance L S1 The other end of (C) is connected with a compensation capacitor S2 Compensating capacitor C S2 The other end of the first power supply is connected with an alternating current input side reference negative pole D of the active rectifier; the positive electrode end of the direct current output side and the negative electrode end of the direct current output side of the active rectifier are connected with a battery load for charging;
compensating inductance L S1 The other end of (C) is connected with a compensation capacitor S1 Compensating capacitor C S1 Is connected with the receiving coil L at the other end S Is the same name end of the receiving coil L S The opposite terminal of the active rectifier is connected with the negative terminal of the direct current output side of the active rectifier.
In the present embodiment, the active rectifier includes a switching tube S 5 Switch tube S 6 Diode D 1 Diode D 2 And output capacitance C O ，
Switch tube S 5 Drain of (D) diode D 1 Cathode and output capacitance C of (2) O One end of the switch tube S is connected and then used as the positive end of the direct current output side of the active rectifier 6 Source of (D) diode D 2 Anode and output capacitance C of (2) O The other end of the active rectifier is connected and then used as the negative end of the direct current output side of the active rectifier;
switch tube S 5 Source electrode of (C) is connected with switch tube S 6 A drain electrode of (2); diode D 1 Anode-connected diode D of (c) 2 A cathode of (a);
diode D 1 The anode connection terminal of (2) is used as a reference positive pole C, a switch tube S 6 As a reference negative pole D.
The mode changeover switch Q is composed of two MOSFETs in reverse series.
The high-frequency single-phase full-bridge inverter circuit comprises a switching tube S 1 Switch tube S 2 Switch tube S 3 And a switch tube S 4 ，
Switch tube S 1 And a switch tube S 3 The drains of the two are connected together to serve as the positive input end of the direct current side of the high-frequency single-phase full-bridge inverter circuit, and the switch tube S 2 And a switch tube S 4 The sources of the two are connected together to serve as the negative input end of the direct current side of the high-frequency single-phase full-bridge inverter circuit; switch tube S 1 Source electrode of (C) is connected with switch tube S 2 Drain electrode of (d), switch tube S 3 Source electrode of (C) is connected with switch tube S 4 A drain electrode of (2);
switch tube S 1 The source electrode of the (B) is used as a reference positive pole A and a switching tube S of an alternating current side of a high-frequency single-phase full-bridge inverter circuit 4 The drain electrode of the (C) is used as a reference negative pole B of the alternating current side of the high-frequency single-phase full-bridge inverter circuit.
The soft-switching battery wireless charger provided by the embodiment is provided with a low-energy consumption auxiliary circuit, and can realize high-efficiency charging of a battery load.
The second embodiment, as shown in fig. 2, 3, 18 and 19, provides a charging method of a soft-switch battery wireless charger, which is implemented based on the first embodiment and includes performing constant-current and constant-voltage wireless charging on a battery load:
firstly, constant current charging is carried out on a battery load: the mode change-over switch Q is in an off state, and the diode D 1 And diode D 2 If it is in the cut-off state, the compensating inductance L S1 The active rectifier is equivalent to a half-bridge active rectifier when not in operation; the structure of the soft switch battery wireless charger can be equivalent to the traditional S-S (Series-Series) topological structure, and the working principle is similar.
When the charging voltage of the battery load reaches the rated voltage, the battery load is subjected to constant voltage charging: the mode change-over switch Q is in a conducting state, and the switch tube S 6 If it is in the conducting state, the switch tube S 5 The active rectifier is equivalent to a half-bridge uncontrollable rectifier until the charging is finished. At this time, the structure of the soft switch battery wireless charger can be equivalent to an S-LCC (Series-Inductor Capacitor Capacitor) topological structure, and the working principle is similar.
In a third embodiment, as shown in fig. 4 to 17, the present embodiment provides a soft switch charging control method in a full load range of a soft switch battery wireless charger, where the soft switch battery wireless charger in the first embodiment is subjected to charging control, so that a high frequency inverter switching tube realizes zero voltage soft on and zero current soft off simultaneously, and the method includes:
and the high-frequency single-phase full-bridge inverter circuit adopts a limited unipolar SPWM modulation method to realize zero-voltage soft-on and zero-current soft-off of the switching tube. Since the soft switching operation principle in the constant-current charging mode and the constant-voltage charging mode is the same, the soft switching method of the present embodiment focuses only on the high-frequency single-phase full-bridge inverter circuit. Therefore, only the soft switching principle of the system energy emission side will be described in the present embodiment.
Further, the process of realizing zero-voltage soft-on and zero-current soft-off by the high-frequency single-phase full-bridge inverter circuit comprises the following steps:
if the output current of the high-frequency single-phase full-bridge inverter circuit is in the positive direction, a switch tube S 1 In a high-frequency switching state, switch tube S 2 And a switch tube S 3 Turn-off, switch tube S 4 Conducting; if the output current of the high-frequency single-phase full-bridge inverter circuit is in a negative direction, a switch tube S 2 In a high-frequency switching state, switch tube S 3 Conduction and switch tube S 1 And a switch tube S 4 And (5) switching off. This approach may reduce system losses.
Still further, taking an example when the output current of the high-frequency single-phase full-bridge inverter circuit is in the positive direction, in combination with fig. 4 to 14, the high-frequency single-phase full-bridge inverter circuit is controlled by dividing 10 working phases in one switching cycle:
stages 1[0 to t 0 ]: in the initial stage of the switching cycle, as shown in FIG. 4, the auxiliary switching tube S is made A1 And an auxiliary switching tube S A2 Turn-off, switch tube S 1 And a switch tube S 4 Conduction, DC power supply V in By auxiliary resonant inductance L A Switch tube S 1 And a switch tube S 4 Compensating capacitance C towards primary side P And a transmitting coil L P Powering up to t at the end of the initial phase 0 Time; auxiliary resonance capacitor C in stage 1 A Voltage v across CA =0, auxiliary resonant inductance L A Current i in (a) LA ＝I P ，I P Is a fixed value;
I P the values are determined according to known parameters in a specific application scenario, including the input voltage, the rated charge voltage and charge current of the battery, and the mutual inductance of the coupler.
Stage 2[t 0 ～t 1 ]: shown in FIG. 5, t 0 At moment, the auxiliary switching tube S is turned on A2 Auxiliary resonant inductance L A Obstruction auxiliary switch tube S A2 Current rising rate at turn-on time to make auxiliary switch tube S A2 Realizing zero-voltage soft-on; auxiliary resonant inductance L A And auxiliary resonance capacitor C A Resonance, auxiliary resonance inductance L A Current i in (a) LA From I P Start to increase, auxiliary resonance capacitance C A Voltage v across CA Increase in reverse from 0 when the auxiliary resonance capacitance C A The voltage across it increases inversely to-V in When equal, auxiliary resonant inductance L A Current i in (a) LA The auxiliary resonance capacitance C starts to decrease after increasing to the maximum value in this stage A Voltage v across CA Continue to increase reversely when the auxiliary resonant inductance L A Current i in (a) LA Again equal to I P When in use, the auxiliary switch tube S A2 The current in (a) is equal to 0 and reaches t 1 At the moment, the stage 2 ends; switching tube S in this stage 1 And a switch tube S 4 Continuing to be in a conducting state;
stage 3[t 1 ～t 2 ]: FIG. 6 shows t 1 Time of day, auxiliary switching tube S A2 The current in (a) is equal to 0, and the auxiliary switching tube S is turned off A2 Zero-current soft turn-off is completed; auxiliary resonant inductance L A And auxiliary resonance capacitor C A Continues to be in a resonance state, and resonance current starts to flow through the auxiliary switching tube S A2 Auxiliary resonant inductance L in the body diode of (1) A Current i in (a) LA From I P Start to decrease, auxiliary resonance capacitance C A Voltage v across CA Reverse decrease; auxiliary resonant inductance L A Current i in (a) LA When changing to 0, reach t 2 At the moment, the stage 3 ends;
stage 4[t 2 ～t 3 ]: FIG. 7 shows t 2 At the moment, flows through the switching tube S 1 The current of (2) is zero, and the switch tube S is turned off 1 Zero-current soft turn-off is completed; auxiliary resonant inductance L A And auxiliary resonance capacitor C A Resonance, resonance current starts to flow through the auxiliary switching tube S A2 Body diode and switching tube S 1 Body diode of (2), auxiliary resonant inductance L A Current i in (a) LA Non-linear increase in reverse direction from 0, auxiliary resonance capacitance C A Voltage v across CA Continuing to reversely reduce; as auxiliary resonance capacitor C A Voltage v across CA Equal to V in Auxiliary resonant inductance L A Current i in (a) LA Reaching the reverse maximum; then, the auxiliary resonance capacitor C A Voltage v across CA And auxiliary resonant inductance L A Current i in (a) LA All in the process of reverse reduction, when the auxiliary resonant inductance L A Current i in (a) LA Changing to 0 again to reach t 3 At the moment, the stage 4 ends;
stage 5[t 3 ～t 4 ]: FIG. 8 shows t 3 Time of day, I P By auxiliary resonance capacitor C A The branch is freewheeling and the auxiliary resonance capacitor C A In a discharge state, the electric energy passes through the auxiliary switch tube S A2 Body diode of (2), auxiliary resonance capacitor C A And a switch tube S 4 Compensating capacitance C towards primary side P And a transmitting coil L P Supplying power; auxiliary resonance capacitor C A Voltage v across CA The inverse linearity decreases when the auxiliary resonance capacitance C A Voltage v across CA When equal to 0, the auxiliary switch tube S A2 The body diode of (1) is naturally turned off to t 4 At the moment, the stage 5 ends;
stage 6[t 4 ～t 5 ]: as shown in FIG. 9, t 4 At moment, the auxiliary switching tube S is turned on A1 Auxiliary resonant inductance L A Obstruction auxiliary switch tube S A1 Current rising rate during on to enable auxiliary switch tube S A1 Realizing zero-voltage soft-on; then, the auxiliary resonant inductance L A And auxiliary resonance capacitor C A Resonance, auxiliary resonance inductance L A And auxiliary resonance capacitor C A Is started to flow through the switching tube S 2 Body diode of (2), auxiliary resonant inductance L A Current i in (a) LA And auxiliary resonance capacitor C A Voltage v across CA Increasing positively from 0 when the auxiliary resonant inductance L A Current i in (a) LA Increase to I P Reach t 5 At the moment, the stage 6 ends;
stage 7[t 5 ～t 6 ]: from t, as shown in FIG. 10 5 Starting at the moment, the auxiliary resonant inductance L A Current i in (a) LA Always equal to I P When the auxiliary resonance capacitor C A Voltage v across CA Equal to V in When it reaches t 6 At the moment, the stage 7 ends; in stage 7, the electrical energy is supplied via a DC power supply V in Auxiliary resonant inductance L A Auxiliary switch tube S A1 Auxiliary resonance capacitor C A And a switch tube S 4 The loop in which it is located is towards the transmitter (primary compensation capacitance C P And a transmitting coil L P ) Providing electric energy;
stage 8[t 6 ～t 7 ]: FIG. 11 shows the same principle as stage 6, from t 6 Starting at the moment, the auxiliary resonant inductance L A And auxiliary resonance capacitor C A Is started to flow through the switching tube S 2 Body diode of (2), auxiliary resonant inductance L A Current i in (a) LA Forward reduction, auxiliary resonance capacitance C A Voltage v across CA Positive increase, in the auxiliary resonance inductance L A Current i in (a) LA T changing to zero 7 Time, auxiliary resonance capacitor C A Voltage v across CA Reaching the positive maximum value, and ending the stage 8;
stage 9[t 7 ～t 8 ]: FIG. 12, t 7 Time of day, auxiliary switching tube S A1 The current in (a) is equal to 0, and the auxiliary switching tube S is turned off A1 Zero-current soft turn-off is completed; auxiliary resonant inductance L A And auxiliary resonance capacitor C A Is started to flow through the auxiliary switching tube S A1 The body diode of (1), auxiliary resonant inductance L A And auxiliary resonance capacitor C A Resonance, auxiliary resonance inductance L A Current i in (a) LA Increase in reverse from 0, auxiliary resonance capacitance C A Voltage v across CA Starts to decrease in the forward direction when the auxiliary resonance capacitance C A Voltage v across CA And V is equal to in When equal, auxiliary resonant inductance L A Current i in (a) LA Reversely increasing to the maximum value, reversely decreasing, and the auxiliary resonance capacitor C A Voltage v across CA Forward direction decreases; when the auxiliary resonant inductance L A Current i in (a) LA Equal to 0, auxiliary switching tube S A1 The body diode in the capacitor is naturally turned off, and the auxiliary resonance capacitor C A Voltage v across CA Changing to 0 to reach t 8 At the moment, stage 9 ends;
stage 10[ t ] 8 ～t 9 ]: FIG. 13 shows t 8 At the moment, switch tube S 1 The voltage at two ends is equal to 0, and the switching tube S is turned on 1 Completing zero voltage soft-on; auxiliary resonance capacitor C A Does not work; the electric energy passes through a direct current power supply V in Auxiliary resonance capacitor L A Switch tube S 1 And a switch tube S 4 The loop in which the transmitter is located supplies power to the transmitter; at the same time, the electric energy also passes through the switch tube S 2 Body diode and switching tube S 4 Is provided to power the transmitter; switch tube S 1 After being turned on, the direct-current power supply voltage is directly applied to the auxiliary resonant inductor L A Two ends, the auxiliary resonance inductance L A Current i in (a) LA Positive linear increase, when the auxiliary resonant inductance L A Current i in (a) LA Increase to I P When flowing through the switch tube S 2 The current change of the body diode is 0, so that zero-current soft turn-off is realized, and the stage 10 is finished; continuing to the next switching cycle.
Specific examples: in order to verify the effectiveness of a soft-switching battery wireless charger with a low-energy consumption auxiliary circuit, a lithium battery with rated current of 3A and rated voltage of 100V is selected for experiments, and the working frequency of the system is 85kHz. The experimental results are shown in fig. 15 to 19.
Under the soft-switching battery wireless charger with the low-energy consumption auxiliary circuit provided by the embodiment, the switching tube S 1 The current and voltage waveforms of (a) are shown in FIG. 15, and it can be seen that the switching tube S 1 The zero voltage soft-on and zero current soft-off actions are completed. Thus switching tube S 1 The switching loss of (2) is thoroughly reduced to zero, which is of great significance in improving the efficiency of the system.
Under the soft-switch battery wireless charger with the low-energy consumption auxiliary circuit provided by the embodiment, the auxiliary switch tube S A1 The current and voltage waveforms of (a) are shown in FIG. 16, and it can be seen that the auxiliary switching tube S A1 Complete zero voltage soft-on andzero current soft off action.
Under the soft-switch battery wireless charger with the low-energy consumption auxiliary circuit provided by the embodiment, the auxiliary switch tube S A1 The current and voltage waveforms of (a) are shown in FIG. 17, and it can be seen that the auxiliary switching tube S A2 The zero voltage soft-on and zero current soft-off actions are completed.
Under the soft-switch battery wireless charger with the low-energy consumption auxiliary circuit provided by the embodiment, the auxiliary switch tube S A1 The current and voltage waveforms of (a) are shown in FIG. 17, and it can be seen that the auxiliary switching tube S A2 The zero voltage soft-on and zero current soft-off actions are completed.
Under the soft-switching battery wireless charger with the low-energy consumption auxiliary circuit provided by the embodiment, key experimental waveforms of the system in the constant-current mode are shown in fig. 18, and it can be seen that the output current of the system is 3A the same as the rated current of the battery.
In the soft-switching battery wireless charger with the low-energy consumption auxiliary circuit provided in this embodiment, key experimental waveforms of the system in the constant voltage mode are shown in fig. 19, and it can be seen that the output voltage of the system is 100V the same as the rated voltage of the battery.
Although the invention herein has been described with reference to particular embodiments, it is to be understood that these embodiments are merely illustrative of the principles and applications of the present invention. It is therefore to be understood that numerous modifications may be made to the illustrative embodiments and that other arrangements may be devised without departing from the spirit and scope of the present invention as defined by the appended claims. It should be understood that the different dependent claims and the features described herein may be combined in ways other than as described in the original claims. It is also to be understood that features described in connection with separate embodiments may be used in other described embodiments.

Claims (6)

1. A soft switch battery wireless charger is characterized by comprising a direct current power supply V in Auxiliary circuit, high-frequency single-phase full-bridge inverter circuit and primary compensation capacitor C P A coupler, a,A secondary side compensation network, a mode changeover switch Q and an active rectifier,
DC power supply V in The positive pole of the high-frequency single-phase full-bridge inverter circuit is connected with the positive pole input end of the direct-current side of the high-frequency single-phase full-bridge inverter circuit, and the direct-current power supply V in The negative electrode of the high-frequency single-phase full-bridge inverter circuit is connected with the negative electrode input end of the direct-current side of the high-frequency single-phase full-bridge inverter circuit;
the coupler comprises a transmitting coil L P And a receiving coil L S ；
The reference positive pole A of the alternating current side of the high-frequency single-phase full-bridge inverter circuit passes through the primary compensation capacitor C P Connecting transmitting coils L P Is the same name as the transmitting coil L P The different name end of the high-frequency single-phase full-bridge inverter circuit is connected with a reference negative pole B on the alternating current side;
the auxiliary circuit comprises an auxiliary resonant inductor L A Auxiliary resonance capacitor C A Auxiliary switch tube S A1 And an auxiliary switching tube S A2 Auxiliary switch tube S A1 And an auxiliary switching tube S A2 After being connected in series, the high-frequency single-phase full-bridge inverter circuit is connected between a positive input end and a negative input end on the direct current side, and an auxiliary resonance inductance L A Is connected with a DC power supply V in Auxiliary resonance capacitor C between the positive electrode of the high-frequency single-phase full-bridge inverter circuit and the positive electrode input end of the direct current side A Is connected with an auxiliary switch tube S A1 And an auxiliary switching tube S A2 The connection point between the two is connected with the reference positive pole A;
the secondary compensation network comprises a compensation capacitor C S1 Compensating capacitor C S2 And compensating inductance L S1 ；
The AC input side reference positive pole C of the active rectifier is connected with the compensation inductance L through the mode change-over switch Q S1 Is one end of compensating inductance L S1 The other end of (C) is connected with a compensation capacitor S2 Compensating capacitor C S2 The other end of the first power supply is connected with an alternating current input side reference negative pole D of the active rectifier; the positive electrode end of the direct current output side and the negative electrode end of the direct current output side of the active rectifier are connected with a battery load for charging;
compensating inductance L S1 The other end of (C) is connected with a compensation capacitor S1 Is compensated for byCapacitor C S1 Is connected with the receiving coil L at the other end S Is the same name end of the receiving coil L S The different name end of the active rectifier is connected with the direct current output side negative end of the active rectifier;
the active rectifier comprises a switching tube S 5 Switch tube S 6 Diode D 1 Diode D 2 And output capacitance C O ，
Switch tube S 5 Drain of (D) diode D 1 Cathode and output capacitance C of (2) O One end of the switch tube S is connected and then used as the positive end of the direct current output side of the active rectifier 6 Source of (D) diode D 2 Anode and output capacitance C of (2) O The other end of the active rectifier is connected and then used as the negative end of the direct current output side of the active rectifier;
switch tube S 5 Source electrode of (C) is connected with switch tube S 6 A drain electrode of (2); diode D 1 Anode-connected diode D of (c) 2 A cathode of (a);
diode D 1 The anode connection terminal of (2) is used as a reference positive pole C, a switch tube S 6 The drain electrode connecting end of (2) is used as a reference negative pole D;
the high-frequency single-phase full-bridge inverter circuit comprises a switching tube S 1 Switch tube S 2 Switch tube S 3 And a switch tube S 4 ，
Switch tube S 1 And a switch tube S 3 The drains of the two are connected together to serve as the positive input end of the direct current side of the high-frequency single-phase full-bridge inverter circuit, and the switch tube S 2 And a switch tube S 4 The sources of the two are connected together to serve as the negative input end of the direct current side of the high-frequency single-phase full-bridge inverter circuit; switch tube S 1 Source electrode of (C) is connected with switch tube S 2 Drain electrode of (d), switch tube S 3 Source electrode of (C) is connected with switch tube S 4 A drain electrode of (2);
switch tube S 1 The source electrode of the (B) is used as a reference positive pole A and a switching tube S of an alternating current side of a high-frequency single-phase full-bridge inverter circuit 4 The drain electrode of the (C) is used as a reference negative pole B of the alternating current side of the high-frequency single-phase full-bridge inverter circuit.
2. The soft-switching battery wireless charger of claim 1, wherein the mode switch Q is formed by two MOSFETs in anti-series connection.
3. A charging method of a soft-switching battery wireless charger, based on the soft-switching battery wireless charger of claim 2, characterized by comprising the steps of performing constant current and then constant voltage wireless charging on a battery load:
firstly, constant current charging is carried out on a battery load: the mode change-over switch Q is in an off state, and the diode D 1 And diode D 2 Cut-off, compensating inductance L S1 The active rectifier is equivalent to a half-bridge active rectifier when not in operation;
when the charging voltage of the battery load reaches the rated voltage, the battery load is subjected to constant voltage charging: the mode change-over switch Q is in a conducting state, and the switch tube S 6 Conduction and switch tube S 5 The active rectifier is equivalent to a half-bridge uncontrollable rectifier, which is turned off until the charging is completed.
4. A soft-switching battery wireless charger charging control method for the soft-switching battery wireless charger of claim 2, comprising:
the high-frequency single-phase full-bridge inverter circuit adopts a unipolar SPWM modulation method to realize zero-voltage soft-on and zero-current soft-off of the switching tube.
5. The soft-switching battery wireless charger soft-switching charge control method of claim 4, wherein,
the process for realizing zero-voltage soft-on and zero-current soft-off by the high-frequency single-phase full-bridge inverter circuit comprises the following steps:
if the output current of the high-frequency single-phase full-bridge inverter circuit is in the positive direction, a switch tube S 1 In a high-frequency switching state, switch tube S 2 And a switch tube S 3 Turn-off, switch tube S 4 Conducting; if the output current of the high-frequency single-phase full-bridge inverter circuit is in a negative direction, a switch tube S 2 In a high-frequency switching state, switch tube S 3 Conduction and switch tube S 1 And a switch tube S 4 And (5) switching off.
6. The soft-switching charge control method of a soft-switching battery wireless charger of claim 5, wherein,
the high-frequency single-phase full-bridge inverter circuit is controlled by dividing 10 working phases in one switching period:
stages 1[0 to t 0 ]: in the initial stage of the switching period, the auxiliary switching tube S is made A1 And an auxiliary switching tube S A2 Turn-off, switch tube S 1 And a switch tube S 4 Conduction, DC power supply V in By auxiliary resonant inductance L A Switch tube S 1 And a switch tube S 4 Compensating capacitance C towards primary side P And a transmitting coil L P Powering up to t at the end of the initial phase 0 Time; auxiliary resonance capacitor C in stage 1 A Voltage v across CA =0, auxiliary resonant inductance L A Current i in (a) LA ＝I P ，I P Is a fixed value;
stage 2[t 0 ～t 1 ]：t 0 At moment, the auxiliary switching tube S is turned on A2 Auxiliary resonant inductance L A Obstruction auxiliary switch tube S A2 Current rising rate at turn-on time to make auxiliary switch tube S A2 Realizing zero-voltage soft-on; auxiliary resonant inductance L A And auxiliary resonance capacitor C A Resonance, auxiliary resonance inductance L A Current i in (a) LA From I P Start to increase, auxiliary resonance capacitance C A Voltage v across CA Increase in reverse from 0 when the auxiliary resonance capacitance C A The voltage across it increases inversely to-V in When equal, auxiliary resonant inductance L A Current i in (a) LA The auxiliary resonance capacitance C starts to decrease after increasing to the maximum value in this stage A Voltage v across CA Continue to increase reversely when the auxiliary resonant inductance L A Current i in (a) LA Again equal to I P When in use, the auxiliary switch tube S A2 The current in (a) is equal to 0 and reaches t 1 At the moment, the stage 2 ends;
stage 3[t 1 ～t 2 ]：t 1 Time of day, auxiliary switching tube S A2 The current in (a) is equal to 0, and the auxiliary switching tube S is turned off A2 Zero-current soft turn-off is completed; auxiliary resonant inductance L A And auxiliary resonance capacitor C A Continuously in a resonance state, auxiliary resonance inductance L A Current i in (a) LA From I P Start to decrease, auxiliary resonance capacitance C A Voltage v across CA Reverse decrease; auxiliary resonant inductance L A Current i in (a) LA When changing to 0, reach t 2 At the moment, the stage 3 ends;
stage 4[t 2 ～t 3 ]：t 2 At the moment, flows through the switching tube S 1 The current of (2) is zero, and the switch tube S is turned off 1 Zero-current soft turn-off is completed; auxiliary resonant inductance L A And auxiliary resonance capacitor C A Resonance, auxiliary resonance inductance L A Current i in (a) LA Non-linear increase in reverse direction from 0, auxiliary resonance capacitance C A Voltage v across CA Continuing to reversely reduce; as auxiliary resonance capacitor C A Voltage v across CA Equal to V in Auxiliary resonant inductance L A Current i in (a) LA Reaching the reverse maximum; then, the auxiliary resonance capacitor C A Voltage v across CA And auxiliary resonant inductance L A Current i in (a) LA All in the process of reverse reduction, when the auxiliary resonant inductance L A Current i in (a) LA Changing to 0 again to reach t 3 At the moment, the stage 4 ends;
stage 5[t 3 ～t 4 ]：t 3 Time of day, I P By auxiliary resonance capacitor C A The branch is freewheeling and the auxiliary resonance capacitor C A Voltage v across CA The inverse linearity decreases when the auxiliary resonance capacitance C A Voltage v across CA When equal to 0, the auxiliary switch tube S A2 The body diode of (1) is naturally turned off to t 4 At the moment, the stage 5 ends;
stage 6[t 4 ～t 5 ]：t 4 At moment, the auxiliary switching tube S is turned on A1 Auxiliary resonant inductance L A Obstruction auxiliary switch tube S A1 Current rising rate during on to enable auxiliary switch tube S A1 Realizing zero-voltage soft-on; then, the auxiliary resonant inductance L A And auxiliary resonance capacitor C A Resonance, auxiliary resonance inductance L A Current i in (a) LA And auxiliary resonance capacitor C A Voltage v across CA Increasing positively from 0 when the auxiliary resonant inductance L A Current i in (a) LA Increase to I P Reach t 5 At the moment, the stage 6 ends;
stage 7[t 5 ～t 6 ]: from t 5 Starting at the moment, the auxiliary resonant inductance L A Current i in (a) LA Always equal to I P When the auxiliary resonance capacitor C A Voltage v across CA Equal to V in When it reaches t 6 At the moment, the stage 7 ends;
stage 8[t 6 ～t 7 ]: from t 6 Starting at the moment, the current starts to flow through the switching tube S 2 Body diode of (2), auxiliary resonant inductance L A Current i in (a) LA Forward reduction, auxiliary resonance capacitance C A Voltage v across CA Positive increase, in the auxiliary resonance inductance L A Current i in (a) LA T changing to zero 7 Time, auxiliary resonance capacitor C A Voltage v across CA Reaching the positive maximum value, and ending the stage 8;
stage 9[t 7 ～t 8 ]：t 7 Time of day, auxiliary switching tube S A1 The current in (a) is equal to 0, and the auxiliary switching tube S is turned off A1 Zero-current soft turn-off is completed; the current starts to flow through the auxiliary switching tube S A1 The body diode of (1), auxiliary resonant inductance L A And auxiliary resonance capacitor C A Resonance, auxiliary resonance inductance L A Current i in (a) LA Increase in reverse from 0, auxiliary resonance capacitance C A Voltage v across CA Starts to decrease in the forward direction when the auxiliary resonance capacitance C A Voltage v across CA And V is equal to in When equal, auxiliary resonant inductance L A Current i in (a) LA Reversely increasing to the maximum value, then reversely decreasing again, and assistingAuxiliary resonance capacitor C A Voltage v across CA Forward direction decreases; when the auxiliary resonant inductance L A Current i in (a) LA Equal to 0, auxiliary switching tube S A1 The body diode in the capacitor is naturally turned off, and the auxiliary resonance capacitor C A Voltage v across CA Changing to 0 to reach t 8 At the moment, stage 9 ends;
stage 10[ t ] 8 ～t 9 ]：t 8 At the moment, switch tube S 1 The voltage at two ends is equal to 0, and the switching tube S is turned on 1 Completing zero voltage soft-on;
auxiliary resonant inductance L at this time A Current i in (a) LA Positive linear increase, when the auxiliary resonant inductance L A Current i in (a) LA Increase to I P When flowing through the switch tube S 2 The current change of the body diode is 0, so that zero-current soft turn-off is realized, and the stage 10 is finished; continuing to the next switching cycle.
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CN109660029A (en) * 2019-02-18 2019-04-19 浙江万安亿创电子科技有限公司 It enjoys a double blessing bridge radio energy transmission system soft switch circuit
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