CN107231129B - Harmonic control CMOS mixer based on transformer structure - Google Patents

Harmonic control CMOS mixer based on transformer structure Download PDF

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CN107231129B
CN107231129B CN201710334207.6A CN201710334207A CN107231129B CN 107231129 B CN107231129 B CN 107231129B CN 201710334207 A CN201710334207 A CN 201710334207A CN 107231129 B CN107231129 B CN 107231129B
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transformer
nmos transistor
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harmonic
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CN107231129A (en
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伍晶
刘智卿
罗文玲
裘华英
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Chengdu Tongliang Technology Co ltd
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    • H03—ELECTRONIC CIRCUITRY
    • H03D—DEMODULATION OR TRANSFERENCE OF MODULATION FROM ONE CARRIER TO ANOTHER
    • H03D7/00—Transference of modulation from one carrier to another, e.g. frequency-changing
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Abstract

The invention discloses a harmonic control CMOS (complementary metal oxide semiconductor) mixer based on a transformer structure, which comprises a transconductance stage, a harmonic control transformer network, a switching stage and an output stage; the transconductance stage converts an input radio frequency signal into radio frequency current, the converted radio frequency current contains fundamental wave and harmonic components due to nonlinearity of a transistor, the fundamental wave and the harmonic components are suppressed by a transformer harmonic control network, second harmonic is generated and filtered, third harmonic is injected into the switching stage, and an intermediate frequency signal is finally output by the output stage through modulation and mixing of the switching stage. The harmonic control network with the transformer structure is introduced between the transconductance stage and the switching stage of the mixer, so that the linearity, the isolation degree and the noise performance of the mixer are improved, and the working voltage and the static power consumption are reduced.

Description

Harmonic control CMOS mixer based on transformer structure
Technical Field
The invention belongs to the technical field of microelectronics, and particularly relates to a harmonic control CMOS mixer based on a transformer structure.
Background
The mixer is an important module in a radio frequency transceiving link, completes the function of converting signals from radio frequency to intermediate frequency, and the performance of the whole system link is directly influenced by the design of the mixer. In recent years, with the rapid development of wireless communication technology, the operating frequency is higher and higher, the modulation mode is more and more complex, and the phase array, MIMO and other multi-channel technologies are widely applied to communication systems, which puts a severe demand on the design of mixers. On one hand, the working frequency is increased, and the output power of the local oscillator LO is difficult to be increased in millimeter waves, particularly in the THz frequency band, so that the frequency mixer cannot provide a good gain; on the other hand, in the existing circuit structure, although the active mixer can meet the gain requirement and has better port isolation compared with the passive mixer, there is a natural problem that the linearity is not high, and the too low input P1dB cannot meet the requirement of the current multi-channel design; in addition, the active mixer with the traditional structure has the problems of larger power consumption, higher working voltage and the like.
The harmonic control theory appears in the design of a high-efficiency radio frequency power amplifier at the earliest time, and the main idea is that the impedance control of a harmonic terminal, namely the control of a frequency domain, enables the drain voltage waveform and the current waveform to be staggered on a time domain, so that the purpose of improving the power amplifier efficiency is achieved. The harmonic control is carried out on the load impedance, theoretically, all higher harmonics are required to be controlled to achieve an ideal effect, and in practice, the harmonic component after the harmonic component exceeds the third harmonic is very weak, so that the third harmonic can be controlled.
Therefore, based on the related thought of harmonic control, the invention is different from the waveform adjustment in power amplifier design and eliminates the influence of higher harmonics, and by constructing a passive transformer network, the invention fully utilizes the advantages of a six-port transformer structure, and creates a mixer which can improve the linearity, the isolation and the noise performance and simultaneously reduce the working voltage and the power consumption.
The designer actively makes research and innovation to create a harmonic control CMOS mixer based on a transformer structure, so that the harmonic control CMOS mixer has industrial utilization value.
Disclosure of Invention
To solve the above problems, it is an object of the present invention to provide a transformer structure-based harmonic-controlled CMOS mixer, which is capable of improving linearity, isolation, and noise performance, while reducing operating voltage and power consumption.
The invention relates to a harmonic control CMOS mixer based on a transformer structure, which comprises:
the radio frequency signal is amplified by the transconductance stage and then output to the harmonic control network, the harmonic control network controls second and third harmonics in the harmonic of the amplified radio frequency signal, the second and third harmonics pass through the switch stage to generate an intermediate frequency signal, and finally the intermediate frequency signal is output through the output stage.
Further, the transconductance stage includes: NMOS tube MN1 and NMOS tube MN2, wherein the gates of NMOS tube MN1 and NMOS tube MN2 are used as two radio frequency input ends and are respectively connected with two ends of a differential radio frequency voltage signal, the sources of NMOS tube MN1 and NMOS tube MN2 are connected together, and the drain of NMOS tube MN1 and NMOS tube MN2 are used as two output ends of the transconductance stage to output differential radio frequency current signals.
Further, the harmonic control network based on the six-port transformer comprises: primary inductance LP1, inductance LP2, and inductance LC at the primary center tap; a transformer secondary inductor LS1, an inductor LS2 and a secondary grounding center tap; the six-port transformer is of a fully differential structure, a primary inductor LP1, an inductor LP2 and an inductor LC at a primary center tap are used for forming a primary coil part of the transformer, a secondary inductor LS1 and an inductor LS2 of the transformer form a secondary coil part of the transformer, an inductor LT1, an inductor LT2, a capacitor CT1 and a capacitor CT2 are third harmonic control networks of a secondary output end of the transformer, and differential signals output by a transconductance stage are coupled to a secondary inductor through the primary inductor.
Further, the switching stage includes: the NMOS transistor MN3, the NMOS transistor MN4, the NMOS transistor MN5 and the NMOS transistor MN6 which form a double-balanced structure switch stage and have the same size; differential inductors L1, L2 and capacitors C1, C2 serving as mixer loads, the two poles of the differential inductor are illustrated with inductors L1 and L2, the center tap portion is powered by the supply voltage, and the capacitors C1, C2 are illustrated as capacitors connected across the differential inductor;
the NMOS transistor MN3 and the NMOS transistor MN4 form a first switch branch, and the NMOS transistor MN5 and the NMOS transistor MN6 form a second switch branch; the grid electrodes of the first switch branch and the second switch branch are respectively connected with LOP and LON at two ends of a differential local oscillator signal; the sources of the first switching branch MN3 and MN4 are connected together, and the sources of the second switching branch MN5 and MN6 are connected together and respectively connected with a secondary differential signal end of a harmonic control network; the drains of the NMOS transistor MN3 and the NMOS transistor MN5 are connected together, the drains of the NMOS transistor MN4 and the NMOS transistor MN6 are connected together, and the drains of the NMOS transistor MN4 and the NMOS transistor MN6 are respectively connected with the L1 and C1 part and the L2 and C2 part of a differential load and are used as differential output ends connected to an output stage;
a six-port transformer connected between the transconductance stage and the switching stage for coupling the radio frequency signal; the center tap of the primary coil of the transformer provides power supply for the transconductance stage, and the center tap of the secondary coil of the transformer provides source grounding for the switching stage; the port impedance characteristics of the transformer are obtained by modeling the transformer, namely, the second harmonic impedance looking into the primary differential port of the transformer from the drain of the transconductance stage is in a high-impedance state, and the third harmonic impedance is short-circuited to the ground at the secondary differential port of the transformer.
Further, the output stage is based on a TIA amplifier structure, and includes: a PMOS tube MP1, a PMOS tube MP2, an NMOS tube MN7, an NMOS tube MN8, a resistor R1, a resistor R2, a capacitor CP and a capacitor CN;
radio frequency coupling capacitors CP and CN are connected between the output stage and the switch stage to play a role of blocking, and radio frequency signals output by the switch stage are coupled to the output stage; the source electrodes of the PMOS tube MP1 and the PMOS tube MP2 are connected with power voltage, and the drain electrodes are respectively connected with the drain electrodes of the NMOS tube MN7 and the NMOS tube MN 8; the source electrodes of the NMOS transistor MN7 and the NMOS transistor MN8 are grounded, and the grid electrodes are respectively connected with the grid electrodes of the PMOS transistor MP1 and the PMOS transistor MP 2; two ends of the resistor R1 and the resistor R2 are respectively connected with the grid and the drain of the PMOS tube and the NMOS tube, the radio frequency coupling capacitors CP and CN are connected between the output stage and the switch stage to play a role of blocking, and the radio frequency signals output by the switch stage are coupled to the output stage.
By the above scheme, the harmonic control CMOS mixer based on the transformer structure at least has the following advantages:
the adoption of a transformer for harmonic control can not only improve the linearity and the leakage efficiency of the transconductance stage, but also realize free control of two-stage bias because the transconductance amplifier stage is coupled with the switch stage through the transformer, so that when the transconductance stage works in Class-AB, a tube can generate the maximum fundamental wave component, the static effect is lower than that in Class-A, and the V of the switch stage is adjustedgs-VthThe voltage makes the switch work fully, and the output noise can be reduced to a great extent. In addition, the transformer is positioned between the transconductance stage and the switch stage in the layout structure, so that the distance between the transconductance stage and the switch stage is naturally increased, a direct path between the transconductance stage and the switch stage is cut off, the isolation is improved, and LO-RF leakage is reduced.
The foregoing description is only an overview of the technical solutions of the present invention, and in order to make the technical solutions of the present invention more clearly understood and to implement them in accordance with the contents of the description, the following detailed description is given with reference to the preferred embodiments of the present invention and the accompanying drawings.
Drawings
FIG. 1 is a schematic circuit diagram of a transformer structure based harmonic controlled CMOS mixer of the present invention;
fig. 2 is a schematic diagram of a network structure of a harmonic control transformer in a harmonic control CMOS mixer based on a transformer structure according to the present invention.
Detailed Description
The following examples are given to further illustrate the embodiments of the present invention. The following examples are intended to illustrate the invention but are not intended to limit the scope of the invention.
The invention relates to a harmonic control CMOS mixer based on a transformer structure, which comprises:
the radio frequency signal is amplified by the transconductance stage and then output to the harmonic control network, the harmonic control network controls second and third harmonics in the harmonic of the amplified radio frequency signal, the second and third harmonics pass through the switch stage to generate an intermediate frequency signal, and finally the intermediate frequency signal is output through the output stage.
According to the invention, the second harmonic and the third harmonic of the output signal of the transconductance stage are adjusted by adopting the harmonic control network with the transformer structure, so that the linearity, the isolation, the noise performance and the leakage efficiency of the transconductance stage are effectively improved, and the working voltage and the static power consumption are reduced.
The invention discloses a better embodiment of a harmonic control CMOS mixer based on a transformer structure, which comprises the following steps: the harmonic control CMOS mixer comprises:
the radio frequency signal is amplified by the transconductance stage and then output to the harmonic control network, the harmonic control network controls second and third harmonics in the harmonic of the amplified radio frequency signal, the second and third harmonics pass through the switch stage to generate an intermediate frequency signal, and finally the intermediate frequency signal is output through the output stage.
The transconductance stage comprises: NMOS tube MN1 and NMOS tube MN2, wherein the gates of NMOS tube MN1 and NMOS tube MN2 are used as two radio frequency input ends and are respectively connected with two ends of a differential radio frequency voltage signal, the sources of NMOS tube MN1 and NMOS tube MN2 are connected together, and the drain of NMOS tube MN1 and NMOS tube MN2 are used as two output ends of the transconductance stage to output differential radio frequency current signals.
The harmonic control network based on the six-port transformer comprises: primary inductance LP1, inductance LP2, and inductance LC at the primary center tap; a transformer secondary inductor LS1, an inductor LS2 and a secondary grounding center tap; the six-port transformer is of a fully differential structure, a primary inductor LP1, an inductor LP2 and an inductor LC at a primary center tap are used for forming a primary coil part of the transformer, a secondary inductor LS1 and an inductor LS2 of the transformer form a secondary coil part of the transformer, an inductor LT1, an inductor LT2, a capacitor CT1 and a capacitor CT2 are third harmonic control networks of a secondary output end of the transformer, and differential signals output by a transconductance stage are coupled to a secondary inductor through the primary inductor.
The switching stage comprises: the NMOS transistor MN3, the NMOS transistor MN4, the NMOS transistor MN5 and the NMOS transistor MN6 which form a double-balanced structure switch stage and have the same size; the frequency mixer comprises differential inductors L1 and L2 and capacitors C1 and C2 which are used as loads of the frequency mixer, wherein the inductors L1 and L2 are used for indicating two poles of the differential inductor, a center tap part is powered by power supply voltage, the capacitors C1 and C2 are used for indicating capacitors connected with two ends of the differential inductor, and only one capacitor is used in actual design; the LC load network has the band-pass frequency selection characteristic, and can obtain relatively pure intermediate-frequency signal output;
the NMOS transistor MN3 and the NMOS transistor MN4 form a first switch branch, and the NMOS transistor MN5 and the NMOS transistor MN6 form a second switch branch; the grid electrodes of the first switch branch and the second switch branch are respectively connected with LOP and LON at two ends of a differential local oscillator signal; the sources of the first switching branch MN3 and MN4 are connected together, and the sources of the second switching branch MN5 and MN6 are connected together and respectively connected with a secondary differential signal end of a harmonic control network; the drains of the NMOS transistor MN3 and the NMOS transistor MN5 are connected together, the drains of the NMOS transistor MN4 and the NMOS transistor MN6 are connected together, and the drains of the NMOS transistor MN4 and the NMOS transistor MN6 are respectively connected with the L1 and C1 part and the L2 and C2 part of a differential load and are used as differential output ends connected to an output stage;
a six-port transformer connected between the transconductance stage and the switching stage for coupling the radio frequency signal; the center tap of the primary coil of the transformer provides power supply for the transconductance stage, and the center tap of the secondary coil of the transformer provides source grounding for the switching stage; the port impedance characteristics of the transformer are obtained by modeling the transformer, namely, the second harmonic impedance looking into the primary differential port of the transformer from the drain of the transconductance stage is in a high-impedance state, and the third harmonic impedance is short-circuited to the ground at the secondary differential port of the transformer.
The output stage is based on a TIA amplifier structure and comprises: a PMOS tube MP1, a PMOS tube MP2, an NMOS tube MN7, an NMOS tube MN8, a resistor R1, a resistor R2, a capacitor CP and a capacitor CN;
radio frequency coupling capacitors CP and CN are connected between the output stage and the switch stage to play a role of blocking, and radio frequency signals output by the switch stage are coupled to the output stage; the source electrodes of the PMOS tube MP1 and the PMOS tube MP2 are connected with power voltage, and the drain electrodes are respectively connected with the drain electrodes of the NMOS tube MN7 and the NMOS tube MN 8; the source electrodes of the NMOS transistor MN7 and the NMOS transistor MN8 are grounded, and the grid electrodes are respectively connected with the grid electrodes of the PMOS transistor MP1 and the PMOS transistor MP 2; two ends of the resistor R1 and the resistor R2 are respectively connected with the grid and the drain of the PMOS tube and the NMOS tube, the radio frequency coupling capacitors CP and CN are connected between the output stage and the switch stage to play a role of blocking, and the radio frequency signals output by the switch stage are coupled to the output stage.
Fig. 2 is a schematic structural diagram of a harmonic control transformer network according to the present invention, in an actual design, the transformer wire is made of the uppermost metal, and the top metal is thick, so that an optimal Q value can be obtained. The topmost metal trace 1 in fig. 2 includes an inductor LT1\ LT2 and a capacitor CT1/CT2 connected in parallel to connect the primary coil of the transconductance stage transistor and the differential output end of the secondary coil, respectively, wherein the capacitor CT1/CT2 is a metal plate capacitor formed by the topmost metal trace 1 and the ground metal plane 3. In fig. 2, the second top metal routing portion 2 forms the source of the output differential switch stage of the transformer.
The working principle of the invention is as follows:
the drain current of the common source transistor can be expressed by a Taylor-series expansion as:
Figure GDA0002642471850000071
wherein v isgsIs the gate-source voltage of the transistor, gm(n)Is the nth order transconductance of the transistor. Analysis of the nonlinear model of the transistor may be thought of as the fundamental voltage applied across the nonlinear element producing harmonics, which in turn cause the associated nodes to produce harmonic voltages, where gm3Is a major factor in generating third order intermodulation distortion of the amplifier. Therefore, the drain and the source are well grounded, harmonic current can directly flow into the alternating current ground, the third harmonic voltage formed on each nonlinear element can be reduced as much as possible, and the third-order intermodulation component formed by the fundamental voltage is avoided. Based on the idea, the invention constructs an inductance-capacitance series network resonance at the third harmonic frequency at the secondary differential end of the transformer to provide good ground for the third harmonic component.
For the second harmonic component, the transformer can naturally suppress the second harmonic component generated from the transconductance stage from entering the switching stage. In order to further inhibit the second harmonic component, a small inductor LS is connected in series at the primary center tap of the transformer, so that the secondary harmonic is high in resistance, and the transmission of the secondary harmonic is further inhibited.
The above description is only a preferred embodiment of the present invention and is not intended to limit the present invention, it should be noted that, for those skilled in the art, many modifications and variations can be made without departing from the technical principle of the present invention, and these modifications and variations should also be regarded as the protection scope of the present invention.

Claims (3)

1. A transformer structure based harmonic controlled CMOS mixer, comprising: the radio frequency signal is amplified by the transconductance stage and then output to the harmonic control network, and the harmonic control network controls second and third harmonics in the harmonic of the amplified radio frequency signal, generates an intermediate frequency signal through the switch stage and finally outputs the intermediate frequency signal through the output stage;
the harmonic control network based on the six-port transformer comprises: primary inductance LP1, inductance LP2, and inductance LC at the primary center tap; a transformer secondary inductor LS1, an inductor LS2 and a secondary grounding center tap; the six-port transformer is of a fully differential structure, a primary inductor LP1, an inductor LP2 and an inductor LC at a primary center tap are used for forming a primary coil part of the transformer, a secondary inductor LS1 and an inductor LS2 of the transformer form a secondary coil part of the transformer, an inductor LT1, an inductor LT2, a capacitor CT1 and a capacitor CT2 are triple harmonic control networks at the secondary output end of the transformer, and differential signals output by a transconductance stage are coupled to a secondary inductor through the primary inductor;
the switching stage comprises: the NMOS transistor MN3, the NMOS transistor MN4, the NMOS transistor MN5 and the NMOS transistor MN6 which form a double-balanced structure switch stage and have the same size; differential inductors L1 and L2 and capacitors C1 and C2 which are used as mixer loads, wherein the inductors L1 and L2 are used as two poles of the differential inductor, a center tap part is powered by a power supply voltage, and capacitors C1 and C2 are used for illustrating capacitors connected to two ends of the differential inductor;
the NMOS transistor MN3 and the NMOS transistor MN4 form a first switch branch, and the NMOS transistor MN5 and the NMOS transistor MN6 form a second switch branch; the grid electrodes of the first switch branch and the second switch branch are respectively connected with LOP and LON at two ends of a differential local oscillator signal; the sources of the first switching branch MN3 and MN4 are connected together, and the sources of the second switching branch MN5 and MN6 are connected together and respectively connected with a secondary differential signal end of a harmonic control network; the drains of the NMOS transistor MN3 and the NMOS transistor MN5 are connected together, the drains of the NMOS transistor MN4 and the NMOS transistor MN6 are connected together, and the drains of the NMOS transistor MN4 and the NMOS transistor MN6 are respectively connected with the L1 and C1 part and the L2 and C2 part of a differential load and are used as differential output ends connected to an output stage;
a six-port transformer connected between the transconductance stage and the switching stage for coupling the radio frequency signal; the center tap of the primary coil of the transformer provides power supply for the transconductance stage, and the center tap of the secondary coil of the transformer provides source grounding for the switching stage; the port impedance characteristic of the transformer is obtained by modeling the transformer, namely, the second harmonic impedance seen from the drain of the transconductance stage to the primary differential port of the transformer is in a high-impedance state, an inductance-capacitance series network resonance is constructed at the secondary differential end of the transformer, and the third harmonic impedance is short-circuited to the ground at the secondary differential end of the transformer.
2. The transformer structure based harmonically controlled CMOS mixer of claim 1, wherein the transconductance stage comprises: NMOS transistor MN1 and NMOS transistor MN2, wherein the gates of NMOS transistor MN1 and NMOS transistor MN2 are used as two radio frequency input ends and are respectively connected with two ends of a differential radio frequency voltage signal, the sources of NMOS transistor MN1 and NMOS transistor MN2 are connected together, and the drains of NMOS transistor MN1 and NMOS transistor MN2 are used as two output ends of the transconductance stage to output differential radio frequency current signals.
3. The transformer structure based harmonically controlled CMOS mixer of claim 1, wherein the output stage is based on a TIA amplifier structure, comprising: a PMOS tube MP1, a PMOS tube MP2, an NMOS tube MN7, an NMOS tube MN8, a resistor R1, a resistor R2, a capacitor CP and a capacitor CN;
radio frequency coupling capacitors CP and CN are connected between the output stage and the switch stage to play a role of blocking, and radio frequency signals output by the switch stage are coupled to the output stage; the source electrodes of the PMOS tube MP1 and the PMOS tube MP2 are connected with power voltage, and the drain electrodes are respectively connected with the drain electrodes of the NMOS tube MN7 and the NMOS tube MN 8; the source electrodes of the NMOS transistor MN7 and the NMOS transistor MN8 are grounded, and the grid electrodes are respectively connected with the grid electrodes of the PMOS transistor MP1 and the PMOS transistor MP 2; two ends of the resistor R1 are respectively connected with the grid of the PMOS tube MP1 and the drain of the NMOS tube MN7, and two ends of the resistor R2 are respectively connected with the grid of the PMOS tube MP2 and the drain of the NMOS tube MN 8.
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