CN105932881A - Full-bridge LLC resonant converter and synchronous rectification driving method thereof - Google Patents
Full-bridge LLC resonant converter and synchronous rectification driving method thereof Download PDFInfo
- Publication number
- CN105932881A CN105932881A CN201610533700.6A CN201610533700A CN105932881A CN 105932881 A CN105932881 A CN 105932881A CN 201610533700 A CN201610533700 A CN 201610533700A CN 105932881 A CN105932881 A CN 105932881A
- Authority
- CN
- China
- Prior art keywords
- network circuit
- synchronous
- primary side
- resonant
- tube
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Pending
Links
- 230000001360 synchronised effect Effects 0.000 title claims abstract description 154
- 238000000034 method Methods 0.000 title claims abstract description 34
- 239000003990 capacitor Substances 0.000 claims description 12
- 230000005284 excitation Effects 0.000 claims description 11
- 238000001514 detection method Methods 0.000 claims description 10
- 238000002955 isolation Methods 0.000 claims description 6
- 238000004364 calculation method Methods 0.000 abstract description 2
- 101100283936 Caenorhabditis elegans gsr-1 gene Proteins 0.000 abstract 2
- 238000010586 diagram Methods 0.000 description 8
- 238000012795 verification Methods 0.000 description 4
- 230000003111 delayed effect Effects 0.000 description 3
- 230000003044 adaptive effect Effects 0.000 description 2
- 230000009286 beneficial effect Effects 0.000 description 2
- 238000001914 filtration Methods 0.000 description 2
- 238000012545 processing Methods 0.000 description 2
- 238000011160 research Methods 0.000 description 2
- 238000004088 simulation Methods 0.000 description 2
- 230000007547 defect Effects 0.000 description 1
- 238000013461 design Methods 0.000 description 1
- 238000002474 experimental method Methods 0.000 description 1
- 230000002349 favourable effect Effects 0.000 description 1
- 238000005259 measurement Methods 0.000 description 1
- 238000011084 recovery Methods 0.000 description 1
Classifications
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/33507—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters
- H02M3/33515—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters with digital control
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/33507—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters
- H02M3/33523—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters with galvanic isolation between input and output of both the power stage and the feedback loop
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/33569—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
- H02M3/33576—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements having at least one active switching element at the secondary side of an isolation transformer
- H02M3/33592—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements having at least one active switching element at the secondary side of an isolation transformer having a synchronous rectifier circuit or a synchronous freewheeling circuit at the secondary side of an isolation transformer
-
- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
-
- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02P—CLIMATE CHANGE MITIGATION TECHNOLOGIES IN THE PRODUCTION OR PROCESSING OF GOODS
- Y02P80/00—Climate change mitigation technologies for sector-wide applications
- Y02P80/10—Efficient use of energy, e.g. using compressed air or pressurized fluid as energy carrier
Landscapes
- Engineering & Computer Science (AREA)
- Power Engineering (AREA)
- Rectifiers (AREA)
Abstract
The invention relates to a full-bridge LLC resonant converter and a synchronous rectification driving method thereof. The resonant converter comprises an input end (Vin), an inversion network circuit (11), a resonant network circuit (13), a transformer (T), a rectification filter network circuit (15), an output load (R0) and an output end (Vout) and also comprises a synchronous driving device (17), wherein the synchronous driving device (17) is used for obtaining a resonant period (t<r>) through calculation according to a resonant current (i<Lr>) extracted from the resonant network circuit (13), comparing switching frequency (f<s>) with resonant frequency (f<r>) to obtain a comparison result, determining driving signals (u<g1>&u<g4> and u<g2>&u<g3>) of a primary-side switching tube and driving signals (u<gSR1> and u<gSR1>) of a secondary-side synchronous rectification tube according to the comparison result, and separately sending the driving signals to the inversion network circuit (11) and the rectification filter network circuit (15) so as to control the working of the inversion network circuit (11) and the rectification filter network circuit (15). According to the embodiment of the invention, the synchronous rectification on/off time is determined by comparing the switching frequency with the resonant frequency, the working of the full-bridge LLC resonant converter is flexibly controlled, and the full-bridge LLC resonant converter has the advantages of the simplicity, practicability, high implementability, low cost and the like.
Description
Technical Field
The invention relates to the technical field of digital circuits, in particular to a full-bridge LLC resonant converter and a synchronous rectification driving method.
Background
In recent years, the full-bridge LLC resonant converter has gradually received wide attention from the industry because it can realize the switching on of the primary switching tube ZVS and the switching off of the secondary rectifier diode ZCS in a wide load range, and has the advantages of no reverse recovery problem, capability of replacing the resonant inductor with the leakage inductance of the transformer, and the like.
However, when a large low-voltage current is output, the forward conduction voltage drop of the secondary diode of the full-bridge LLC resonant converter is increased, so that the rectification loss occupies a considerable proportion of the total loss, which is not favorable for improving the efficiency. Therefore, to improve this situation and increase the converter efficiency, it is common to choose to replace the diode with a MOSFET with a very low on-resistance, i.e. a synchronous rectification technique.
Although the MOSFET has a very low on-resistance, which is beneficial to reduce the rectification loss, another problem is introduced, namely that the driving time of the synchronous rectifier can directly affect the loss of the system. When the driving time of the synchronous rectifier tube is equal to the current duration, the driving signal of the synchronous rectifier tube is completely synchronous with the rectifying current, and the rectifying loss is minimum; when the driving time of the synchronous rectifier tube is less than the current duration, the rectified current flows through a body diode of the synchronous rectifier tube after the driving signal disappears, and the efficiency is not optimal; when the driving time of the synchronous rectifier tube is longer than the current duration, a circulation problem is inevitably formed, and energy flows reversely. Therefore, how to drive the synchronous rectifier rapidly and effectively becomes a research object of scholars again.
According to the principle of the full-bridge LLC resonant converter, the energy transferred from the primary side to the secondary side is resonant current iLrWith excitation current iLmDifference of (a), current i flowing through the synchronous rectifierSRComprises the following steps:
iSR＝n·(iLr-iLm) (1)
as can be seen from equation (1), the phase of the current of the synchronous rectifier is closely related to the primary resonant current and the excitation current, so that the turn-off time of the synchronous rectifier cannot be determined by simply relying on the resonant current, which brings great difficulty to the driving of the synchronous rectifier.
Referring to fig. 1, fig. 1 is a schematic diagram of a synchronous rectification driving signal of an ideal full-bridge LLC resonant converter, when a synchronous rectifier tube is just turned on, the driving signal is at a high level, the synchronous rectifier tube is turned on, and a current flows through a channel of the synchronous rectifier tube; when the current in the synchronous rectifier is about to drop to zero, the driving signal is low level, and the synchronous rectifier is turned off, so that the residual current will flow through the body diode of the synchronous rectifier.
Currently, the driving signal of the synchronous rectifier can be generated by the following two methods:
the method comprises the following steps: the energy transmitted to the rear stage of the full-bridge LLC resonant converter is the difference value of the resonant current and the exciting current, so that the output current signal of the rear stage and the exciting current are out of phase, the exciting inductor is integrated in the transformer, the exciting current cannot be detected, and the means for detecting the primary side signal is relatively complex.
The second method comprises the following steps: and detecting a secondary side signal, and detecting a zero crossing point of secondary side current through a CT or a current sensor at the secondary side so as to control the on-off of the switching tube. However, the bandwidth, delay and CPU processing time of the detection device may cause the turn-on timing of the synchronous rectifier to be delayed, and the turn-off time to be delayed. The on-delay affects efficiency, and the off-delay causes circulating current and energy to flow in reverse.
Therefore, many efforts and attempts are made by students in the aspect of synchronous rectification driving of a full-bridge LLC resonant converter, for example, in the document, "LLC resonant converter synchronous rectification strategy research" that a current transformer CT is used to drive a synchronous rectification tube, but this ignores that the current transformer CT itself will bring large loss, inevitably increases the PCB wiring difficulty of the secondary side, and limits the improvement of power density. Meanwhile, the turn-on timing of the synchronous rectifier is also affected by the bandwidth, delay and CPU processing time of the detection device, so that the turn-off time is delayed accordingly.
In the document "a Universal Adaptive Driving Scheme for synchronous rectification in LLC Resonant Converters", an FPGA is used to implement Adaptive control of synchronous rectification tubes in a full-bridge LLC Resonant converter, and this method has a high utilization rate, but has a high requirement on the anti-interference design of a circuit board, and the cost is also very high.
In summary, the current methods for driving synchronous rectifiers all have limitations in different aspects such as cost, computational complexity, power density and measurement accuracy.
Disclosure of Invention
Therefore, in order to solve the technical defects and shortcomings in the prior art, the invention provides a full-bridge LLC resonant converter and a synchronous rectification driving method.
Specifically, an embodiment of the invention proposes a full-bridge LLC resonant converter (10), comprising an input terminal (V)in) The inverter network circuit (11), the resonant network circuit (13), the transformer (T), the rectifier filter network circuit (15) and the output load (R)O) And an output terminal (V)out) And also comprises a synchronous drive device (17); wherein,
the synchronous driving device (17) comprises a resonant frequency detection module (171), a synchronous driving module (173) and an isolation driving module (175);
wherein the resonant frequency detection module (171) is based on a resonant current (i) extracted from the resonant network circuit (13)Lr) Calculating to obtain the resonance period (t)r) (ii) a The synchronous drive module (173) is coupled to the switching frequency (f)s) And said resonance period (t)r) The converted resonance frequency (f)r) Comparing to obtain a comparison result; the isolation driving module (175) determines a driving signal (u) of the primary side switching tube according to the comparison resultg1&ug4、ug2&ug3) Drive signal (u) of synchronous rectifier with secondary sidegSR1、ugSR1) And a drive signal (u) of the primary side switching tubeg1&ug4、ug2&ug3) And a drive signal (u) of the secondary synchronous rectifiergSR1、ugSR1) Respectively sent to the inverter network circuit (11) and the rectification filter network circuit (15).
In one embodiment of the invention, the inverter network circuit (11) comprises a first primary side switching tube (Q)1) A second primary side switch tube (Q)2) And a third primary side switch tube (Q)3) And the fourth primary side switch tube (Q)4) And an input capacitance (C)in1) (ii) a Wherein the first primary side switching tube (Q)1) And said third primary side switching tube (Q)3) The second primary side switching tube (Q)2) And said fourth primary side switching tube (Q)4) After being respectively connected in seriesIs connected in parallel to the input terminal (V)in) Two terminals and the input capacitance (C)in1) Is also connected in parallel to said input (V)in) Two ends;
wherein the synchronous drive device (17) drives a drive signal (u) of the primary side switching tubeg1&ug4、ug2&ug3) Respectively sent to the first primary side switching tubes (Q)1) And said fourth primary side switching tube (Q)4) The third primary side switching tube (Q)3) And said second primary side switching tube (Q)2) The control terminal of (1).
In one embodiment of the invention, the resonant network circuit (13) comprises a resonant inductance (L)r) Resonant capacitor (C)r) Excitation inductor (L)m) (ii) a The resonance inductance (L)r) The resonant capacitor (C)r) And said excitation inductance (L)m) Are sequentially connected in series with the first primary side switching tube (Q)1) And said third primary side switching tube (Q)3) A node (A) and the second primary side switching tube (Q) which are formed in series2) And said fourth primary side switching tube (Q)4) Nodes (B) formed in series; and the excitation inductance (L)m) Is also electrically connected to both sides of the transformer (T) input;
wherein the synchronous drive (17) is driven from the resonant inductance (L)r) And the resonance capacitance (C)r) The resonant current (i) is obtained at a node formed by the series connectionLr)。
In one embodiment of the invention, the rectifying filter network circuit (15) comprises a first secondary Synchronous Rectifier (SR)1) And a second secondary Synchronous Rectifier (SR)2) And an output filter capacitor (C)O) (ii) a The first secondary synchronous rectifier tube (SR)1) And the second secondary Synchronous Rectifier (SR)2) The two ends of the output end of the transformer (T) are connected in series; the output filter capacitor (C)O) Are electrically connected to the sliding end of the transformer (T) and the first secondary synchronous rectifier tube (SR) respectively1) And the second secondary Synchronous Rectifier (SR)2) Nodes formed by concatenation;
wherein the synchronous drive device (17) drives a drive signal (u) of the secondary synchronous rectifier tubegSR1、ugSR1) Respectively sent to the first secondary Synchronous Rectifier (SR)1) The second secondary synchronous rectifier tube (SR)2) The control terminal of (1).
In one embodiment of the invention, the synchronous drive means (17) is a DSP processor.
Another embodiment of the present invention provides a synchronous rectification driving method applied to a full-bridge LLC resonant converter, where the full-bridge LLC resonant converter includes an inverter network circuit (11), a resonant network circuit (13), a transformer (T), and a rectification filter network circuit (15), and the method includes:
step one, according to the resonance current (i) obtained by the resonance network circuit (13)Lr) Calculating to obtain the resonance period (t)r)；
Step two, comparing the switching frequency (f)s) And said resonance period (t)r) The converted resonance frequency (f)r) Obtaining a comparison result and determining a synchronous rectification off-time (t) based on said comparison resultoff)；
Triggering the switch link of the inverter network circuit (11) and the rectification filter network circuit (15) to be synchronously switched on according to the synchronous rectification switching-off time (t)off) And controlling the switch-off of a switch tube of the inverter network circuit (11).
In one embodiment of the invention, the resonance period (t) is calculated in step oner) The formula of (1) is:
in one embodiment of the invention, the synchronous rectification off-time (t) is determined on the basis of the comparison resultoff) The method comprises the following steps:
if the comparison result is the switching frequency (f)s) Greater than the resonance frequency (f)r) Then the synchronous rectification off time (t)off) The turn-off time of the switching tube of the inverter network circuit (11) is equal;
if the comparison result is the switching frequency (f)s) Less than or equal to the resonance frequency (f)r) And is greater than the resonance frequency (f)r) 90%, then the synchronous rectification off-time (t)off) Is half of said resonance period (t)r)；
If the comparison result is the switching frequency (f)s) Less than the resonance frequency (f)r) According to said switching frequency (f)s) Looking up the synchronous rectification off-time (t) from a databaseoff)。fs
In one embodiment of the invention, said synchronous rectification off-time (t) in said databaseoff) Is calculated according to different working frequencies, LLC resonant frequency, load current, tolerance of resonant parameters and input voltage.
According to the embodiment of the invention, the determination of the synchronous rectification turn-off time is determined by comparing the switching frequency with the resonant frequency, the work of the full-bridge LLC resonant converter is flexibly controlled, and the method has the advantages of simplicity, feasibility, strong realizability, low cost and the like. The method has the following specific beneficial effects:
1. the cost is low, and auxiliary circuits such as a current sensor and an intelligent chip are not needed when the synchronous rectifier tube is driven;
2. the driving method is simple and can be directly completed by writing a program through the DSP;
3. the power density can be higher, and most detection circuits are saved;
4. the flexibility is strong, and the off-line calculation of the turn-off time t of the synchronous rectifier tube under the condition of different resonant frequencies can be realizedoff。
Other aspects and features of the present invention will become apparent from the following detailed description, which proceeds with reference to the accompanying drawings. It is to be understood, however, that the drawings are designed solely for purposes of illustration and not as a definition of the limits of the invention, for which reference should be made to the appended claims. It should be further understood that the drawings are not necessarily drawn to scale and that, unless otherwise indicated, they are merely intended to conceptually illustrate the structures and procedures described herein.
Drawings
FIG. 1 is a schematic diagram of a synchronous rectification driving signal of an ideal full-bridge LLC resonant converter;
fig. 2 is a schematic circuit block diagram of a full-bridge LLC resonant converter according to an embodiment of the present invention;
fig. 3 is a circuit structure diagram of a full-bridge LLC resonant converter according to an embodiment of the present invention;
FIG. 4 is a flow chart of a synchronous rectification digital driving method according to an embodiment of the present invention; and
fig. 5 is a schematic diagram illustrating an operating principle of a synchronous rectification digital driving apparatus according to an embodiment of the present invention.
Detailed Description
In order to make the aforementioned objects, features and advantages of the present invention comprehensible, embodiments accompanied with figures are described in detail below.
Example one
Referring to fig. 2 and fig. 3 together, fig. 2 is a schematic circuit block diagram of a full-bridge LLC resonant converter according to an embodiment of the present invention; fig. 3 is a circuit configuration diagram of a full-bridge LLC resonant converter according to an embodiment of the present invention. The full bridge LThe LC resonant converter comprises an input terminal (V)in) The inverter network circuit (11), the resonant network circuit (13), the transformer (T), the rectifier filter network circuit (15) and the output load (R)O) And an output terminal (V)out) And a synchronous driving device (17). Specifically, the method comprises the following steps:
the synchronous driving device (17) comprises a resonant frequency detection module (171), a synchronous driving module (173) and an isolation driving module (175); wherein the resonant frequency detection module (171) is based on a resonant current (i) extracted from the resonant network circuit (13)Lr) Calculating to obtain the resonance period (t)r) (ii) a The synchronous drive module (173) is coupled to the switching frequency (f)s) And said resonance period (t)r) The converted resonance frequency (f)r) Comparing to obtain a comparison result; the isolation driving module (175) determines a driving signal (u) of the primary side switching tube according to the comparison resultg1&ug4、ug2&ug3) Drive signal (u) of synchronous rectifier with secondary sidegSR1、ugSR1) And a drive signal (u) of the primary side switching tubeg1&ug4、ug2&ug3) And a drive signal (u) of the secondary synchronous rectifiergSR1、ugSR1) Respectively sent to the inverter network circuit (11) and the rectification filter network circuit (15).
Further, the inverter network circuit (11) comprises a first primary side switching tube (Q)1) A second primary side switch tube (Q)2) And a third primary side switch tube (Q)3) And the fourth primary side switch tube (Q)4) And an input capacitance (C)in1) (ii) a Wherein the first primary side switching tube (Q)1) And said third primary side switching tube (Q)3) The second primary side switching tube (Q)2) And said fourth primary side switching tube (Q)4) Are respectively connected in series and then are connected in parallel with the input end (V)in) Two terminals and the input capacitance (C)in1) Is also connected in parallel to said input (V)in) Two ends;
wherein the synchronous driving device (17) drives the primary side switching tube with a driving signal (C:)ug1&ug4、ug2&ug3) Respectively sent to the first primary side switching tubes (Q)1) And said fourth primary side switching tube (Q)4) The third primary side switching tube (Q)3) And said second primary side switching tube (Q)2) The control terminal of (1).
Further, the resonant network circuit (13) comprises a resonant inductance (L)r) Resonant capacitor (C)r) Excitation inductor (L)m) (ii) a The resonance inductance (L)r) The resonant capacitor (C)r) And said excitation inductance (L)m) Are sequentially connected in series with the first primary side switching tube (Q)1) And said third primary side switching tube (Q)3) A node (A) and the second primary side switching tube (Q) which are formed in series2) And said fourth primary side switching tube (Q)4) Nodes (B) formed in series; and the excitation inductance (L)m) Is also electrically connected to both sides of the transformer (T) input;
wherein the synchronous drive (17) is driven from the resonant inductance (L)r) And the resonance capacitance (C)r) The resonant current (i) is obtained at a node formed by the series connectionLr)。
Further, the rectifying and filtering network circuit (15) comprises a first secondary Synchronous Rectifier (SR)1) And a second secondary Synchronous Rectifier (SR)2) And an output filter capacitor (C)O) (ii) a The first secondary synchronous rectifier tube (SR)1) And the second secondary Synchronous Rectifier (SR)2) The two ends of the output end of the transformer (T) are connected in series; the output filter capacitor (C)O) Are electrically connected to the sliding end of the transformer (T) and the first secondary synchronous rectifier tube (SR) respectively1) And the second secondary Synchronous Rectifier (SR)2) Nodes formed by concatenation;
wherein the synchronous drive device (17) drives a drive signal (u) of the secondary synchronous rectifier tubegSR1、ugSR1) Respectively sent to the first secondary Synchronous Rectifier (SR)1) The second secondary synchronous rectifier tube (SR)2) The control terminal of (1).
Further, the synchronous drive device (17) may be a DSP processor.
In the above embodiment, the synchronous driving device compares the resonant frequency determined by the resonant current with the preset switching frequency, determines the operating states of the inverter network circuit and the rectifier filter network circuit according to the comparison result, can well control the synchronous rectification digital driving of the full-bridge LLC resonant converter, and has the advantages of simplicity, feasibility, strong realizability, low cost, and the like.
Example two
Referring to fig. 4 and 5 together, fig. 4 is a flowchart of a synchronous rectification digital driving method according to an embodiment of the present invention; fig. 5 is a schematic diagram illustrating an operating principle of a synchronous rectification digital driving apparatus according to an embodiment of the present invention. The method is applied to a full-bridge LLC resonant converter, the full-bridge LLC resonant converter comprises an inverter network circuit (11), a resonant network circuit (13), a transformer (T) and a rectifying and filtering network circuit (15), wherein the method comprises the following steps:
step one, according to the resonance current (i) obtained by the resonance network circuit (13)Lr) Calculating to obtain the resonance period (t)r)；
Step two, comparing the switching frequency (f)s) And said resonance period (t)r) The converted resonance frequency (f)r) Obtaining a comparison result and determining a synchronous rectification off-time (t) based on said comparison resultoff)；
Triggering the switch link of the inverter network circuit (11) and the rectification filter network circuit (15) to be synchronously switched on according to the synchronous rectification switching-off time (t)off) And controlling the switch-off of a switch tube of the inverter network circuit (11).
Specifically, the method comprises the following steps:
for step one, firstly, the resonant current iLrAs the input quantity of the resonant frequency detection module, obtaining the resonant frequency f of the output quantityr. Calculating to obtain a resonance period t according to the reciprocal relation between the resonance period and the resonance frequencyr. Wherein the resonance period (t) is calculatedr) The formula of (1) is:
for step two, determining the synchronous rectification turn-off time (t) according to the comparison resultoff) One of the criteria may be:
fsif the comparison result is the switching frequency (f)s) Greater than the resonance frequency (f)r) Then the synchronous rectification off time (t)off) The turn-off time of the switching tube of the inverter network circuit (11) is equal;
if the comparison result is the switching frequency (f)s) Less than or equal to the resonance frequency (f)r) And is greater than the resonance frequency (f)r) 90%, then the synchronous rectification off-time (t)off) Is half of said resonance period (t)r)；
If the comparison result is the switching frequency (f)s) Less than the resonance frequency (f)r) According to said switching frequency (f)s) Looking up the synchronous rectification off-time (t) from a databaseoff)fs。
Determining a synchronous rectification off-time (t) from said comparison resultoff) Another actual judgment criterion may be: comparing the switching frequency fsTo the resonance frequency frThe correspondence can be divided into three cases, namely a first case: when the switching frequency is less than or equal to the resonance frequency, the synchronous rectifier and the primary side switching tube can be driven and conducted at the same time, but the difference is that the switching frequency is half of the resonance period (t)rAnd/2) the synchronous rectifier tube is firstly switched off after the synchronous rectifier tube is switched off, and the primary side switching tube is continuously switched on. In addition, theFor safety considerations, a certain safety margin may be reserved here. Wherein, trAt a resonance frequency frThe corresponding resonance time.
In the second case: when the switching frequency is higher than the resonant frequency, the primary side switching tube and the synchronous rectifier tube of the transformer can be synchronously driven, namely, the switching-on and the switching-off are simultaneously carried out, and the same driving signal can be applied to the primary side switching tube and the synchronous rectifier tube of the transformer.
In the third case: when the system is under a relatively serious light load or switching frequency fsWell below the resonance frequency frIn the meantime, the turn-off time of the synchronous rectifier cannot be simply set to tr2, a synchronous rectification off-time t is calculated according to the current working frequency, LLC resonant frequency, load current, tolerance of resonant parameters and input voltageoffAnd reserving enough time allowance or performing an off-line experiment to form a corresponding table, recording the turn-off time under different conditions, performing table lookup to obtain the turn-off time when the system works, and then generating a corresponding driving signal to drive the synchronous rectifier tube by using the turn-off time obtained by table lookup.
That is to say, before the full-bridge LLC resonant converter leaves factory, a database is stored in a storage module of the synchronous drive device, and in the product verification process, after the turn-off time of the synchronous rectifier tube is obtained from the above three conditions, a group of drive signals, i.e., the drive signal u of the primary side switching tube, is obtained by the isolated drive circuitg1&ug4、ug2&ug3Driving signal u of secondary side synchronous rectifiergSR1And ugSR2. And (4) performing simulation analysis and verification on the on-off conditions of the synchronous rectifier tube at the moment, comparing the on-off conditions of the synchronous rectifier tube with the on-off conditions of the primary side switching tube, and observing the current conditions flowing through the synchronous rectifier tube. Synchronous rectification off time toffIf the ZCS turn-off of the synchronous rectifier tube cannot be realized, the reserved safety margin of the driving signal needs to be adjusted again, the turn-off time of the synchronous rectifier tube is changed, and then the synchronous rectifier tube is turned off againAnd (6) carrying out verification.
Further, for the synchronous rectification off-time (t) in the databaseoff) Is calculated according to different working frequencies, LLC resonant frequency, load current, tolerance of resonant parameters and input voltage. In practical application, the idea of driving the synchronous rectifier tube when the switching frequency is less than or equal to the resonant frequency provided by the invention can be applied, and the off time of the synchronous rectifier tube is simulated by a simulation means, the standard is whether the synchronous rectifier tube can be turned off at zero current, different off times can be tested by trial and error for different switching frequencies, a table is formed by selecting proper off time, the synchronous rectifier tube can be driven by selecting approximate off time through the switching frequency when needed, and particularly, repeated experimental verification can be carried out to update the table.
In this embodiment, the determination of the time of the synchronous rectification pipe section is determined by comparing the switching frequency with the resonant frequency, and the operation of the full-bridge LLC resonant converter is flexibly controlled, that is, under a general condition, it is desirable that the full-bridge LLC resonant converter operates in a working mode in which the switching frequency is less than or equal to the resonant frequency and the deviation from the resonant frequency is less than a certain range, so that ZVS switching-on of the primary side switching tube and ZCS switching-off of the synchronous rectification pipe can be realized, and the efficiency is improved while the loss is reduced. Therefore, the method has the advantages of simplicity, feasibility, strong realizability, low cost and the like.
In summary, the principle and the implementation of the full-bridge LLC resonant converter and the synchronous rectification driving method thereof according to the present invention are explained herein by applying specific examples, and the above description of the examples is only used to help understanding the method and the core idea of the present invention; meanwhile, for a person skilled in the art, according to the idea of the present invention, there may be variations in the specific embodiments and the application scope, and in summary, the content of the present specification should not be construed as a limitation to the present invention, and the scope of the present invention should be subject to the appended claims.
Claims (9)
1. A full bridge LLC resonant converter (10) comprises an input terminal (V)in) The inverter network circuit (11), the resonant network circuit (13), the transformer (T), the rectifier filter network circuit (15) and the output load (R)0) And an output terminal (V)out) Characterized in that it also comprises a synchronous drive (17); wherein,
the synchronous driving device (17) comprises a resonant frequency detection module (171), a synchronous driving module (173) and an isolation driving module (175);
wherein the resonance frequency detection module (171) is based on the harmonicA resonance current (i) extracted by the network circuit (13)Lr) Calculating to obtain the resonance period (t)r) (ii) a The synchronous drive module (173) is coupled to the switching frequency (f)s) And said resonance period (t)r) The converted resonance frequency (f)r) Comparing to obtain a comparison result; the isolation driving module (175) determines a driving signal (u) of the primary side switching tube according to the comparison resultg1&ug4、ug2&ug3) Drive signal (u) of synchronous rectifier with secondary sidegSR1、ugSR1) And a drive signal (u) of the primary side switching tubeg1&ug4、ug2&ug3) And a drive signal (u) of the secondary synchronous rectifiergSR1、ugSR1) Respectively sent to the inverter network circuit (11) and the rectification filter network circuit (15).
2. Full bridge LLC resonant converter (10) as claimed in claim 1, characterized in that the inverter network circuit (11) comprises a first primary side switching tube (Q)1) A second primary side switch tube (Q)2) And a third primary side switch tube (Q)3) And the fourth primary side switch tube (Q)4) And an input capacitance (C)in1) (ii) a Wherein the first primary side switching tube (Q)1) And said third primary side switching tube (Q)3) The second primary side switching tube (Q)2) And said fourth primary side switching tube (Q)4) Are respectively connected in series and then are connected in parallel with the input end (V)in) Two terminals and the input capacitance (C)in1) Is also connected in parallel to said input (V)in) Two ends;
wherein the synchronous drive device (17) drives a drive signal (u) of the primary side switching tubeg1&ug4、ug2&ug3) Respectively sent to the first primary side switching tubes (Q)1) And said fourth primary side switching tube (Q)4) The third primary side switching tube (Q)3) And said second primary side switching tube (Q)2) The control terminal of (1).
3. Full bridge LL as claimed in claim 2C resonant converter (10), characterized in that the resonant network circuit (13) comprises a resonant inductance (L)r) Resonant capacitor (C)r) Excitation inductor (L)m) (ii) a The resonance inductance (L)r) The resonant capacitor (C)r) And said excitation inductance (L)m) Are sequentially connected in series with the first primary side switching tube (Q)1) And said third primary side switching tube (Q)3) A node (A) and the second primary side switching tube (Q) which are formed in series2) And said fourth primary side switching tube (Q)4) Nodes (B) formed in series; and the excitation inductance (L)m) Is also electrically connected to both sides of the transformer (T) input;
wherein the synchronous drive (17) is driven from the resonant inductance (L)r) And the resonance capacitance (C)r) The resonant current (i) is obtained at a node formed by the series connectionLr)。
4. A full bridge LLC resonant converter (10) as claimed in claim 3, characterized in that said rectifying filter network circuit (15) comprises a first secondary Synchronous Rectifier (SR)1) And a second secondary Synchronous Rectifier (SR)2) And an output filter capacitor (C)0) (ii) a The first secondary synchronous rectifier tube (SR)1) And the second secondary Synchronous Rectifier (SR)2) The two ends of the output end of the transformer (T) are connected in series; the output filter capacitor (C)0) Are electrically connected to the sliding end of the transformer (T) and the first secondary synchronous rectifier tube (SR) respectively1) And the second secondary Synchronous Rectifier (SR)2) Nodes formed by concatenation;
wherein the synchronous drive device (17) drives a drive signal (u) of the secondary synchronous rectifier tubegSR1、ugSR1) Respectively sent to the first secondary Synchronous Rectifier (SR)1) The second secondary synchronous rectifier tube (SR)2) The control terminal of (1).
5. A full bridge LLC resonant converter (10) as claimed in claim 1, characterized in that said synchronous drive means (17) is a DSP processor.
6. A synchronous rectification driving method is applied to a full-bridge LLC resonant converter, the full-bridge LLC resonant converter comprises an inverter network circuit (11), a resonant network circuit (13), a transformer (T) and a rectification filter network circuit (15), and the method comprises the following steps:
step one, according to the resonance current (i) obtained by the resonance network circuit (13)Lr) Calculating to obtain the resonance period (t)r)；
Step two, comparing the switching frequency (f)s) And said resonance period (t)r) The converted resonance frequency (f)r) Obtaining a comparison result and determining a synchronous rectification off-time (t) based on said comparison resultoff)；
Triggering the switch link of the inverter network circuit (11) and the rectification filter network circuit (15) to be synchronously switched on according to the synchronous rectification switching-off time (t)off) And controlling the switch-off of a switch tube of the inverter network circuit (11).
7. Method according to claim 6, characterized in that the resonance period (t) is calculatedr) The formula of (1) is:
8. method according to claim 6, characterized in that a synchronous rectification off-time (t) is determined on the basis of the comparison resultoff) The method comprises the following steps:
if the comparison result is the switching frequency (f)s) Greater than the resonance frequency (f)r) Then the synchronous rectification off time (t)off) The turn-off time of the switching tube of the inverter network circuit (11) is equal;
if the comparison result is the switching frequency (f)s) Less than or equal to the resonance frequency (f)r) And is greater than the resonance frequency (f)r) 90%, then the synchronous rectificationOff time (t)off) Is half of said resonance period (t)r)；
If the comparison result is the switching frequency (f)s) Less than the resonance frequency (f)r) According to said switching frequency (f)s) Looking up the synchronous rectification off-time (t) from a databaseoff)。
9. Method according to claim 8, characterized in that the synchronous rectification off-time (t) in the databaseoff) Is calculated according to different working frequencies, LLC resonant frequency, load current, tolerance of resonant parameters and input voltage.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN201610533700.6A CN105932881A (en) | 2016-07-08 | 2016-07-08 | Full-bridge LLC resonant converter and synchronous rectification driving method thereof |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN201610533700.6A CN105932881A (en) | 2016-07-08 | 2016-07-08 | Full-bridge LLC resonant converter and synchronous rectification driving method thereof |
Publications (1)
| Publication Number | Publication Date |
|---|---|
| CN105932881A true CN105932881A (en) | 2016-09-07 |
Family
ID=56827684
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CN201610533700.6A Pending CN105932881A (en) | 2016-07-08 | 2016-07-08 | Full-bridge LLC resonant converter and synchronous rectification driving method thereof |
Country Status (1)
| Country | Link |
|---|---|
| CN (1) | CN105932881A (en) |
Cited By (14)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN106655837A (en) * | 2016-11-20 | 2017-05-10 | 徐云鹏 | NEXT series AC-DC power switching circuit |
| CN107612346A (en) * | 2017-09-28 | 2018-01-19 | 西安图为电气技术有限公司 | A kind of two-way DC/DC power inverters |
| CN108274096A (en) * | 2018-03-20 | 2018-07-13 | 华南理工大学 | A kind of parallel great power welding power source system based on LLC resonant converter |
| CN108880274A (en) * | 2017-05-15 | 2018-11-23 | 赤多尼科两合股份有限公司 | A kind of output current detection circuit of controlled resonant converter |
| CN108988648A (en) * | 2018-07-06 | 2018-12-11 | 华南理工大学 | A kind of LLC resonant converter synchronous rectification forecast Control Algorithm |
| CN111193403A (en) * | 2019-12-31 | 2020-05-22 | 苏州浪潮智能科技有限公司 | Synchronous rectification method, system, terminal and storage medium based on CRPS |
| CN111600489A (en) * | 2020-03-28 | 2020-08-28 | 青岛鼎信通讯股份有限公司 | DAB switching frequency self-adaption method applied to energy router |
| CN113691140A (en) * | 2021-09-09 | 2021-11-23 | 安徽大学 | Bidirectional synchronous rectification control device and method for LLC converter |
| CN113708644A (en) * | 2021-08-30 | 2021-11-26 | 易事特集团股份有限公司 | Simplified synchronous rectification method and device for CLLC resonant converter |
| CN114123802A (en) * | 2022-01-25 | 2022-03-01 | 常州索维尔电子科技有限公司 | Secondary side synchronous rectification method of LLC circuit |
| CN114337290A (en) * | 2021-02-07 | 2022-04-12 | 华为数字能源技术有限公司 | Driving circuit of secondary rectifying circuit in power circuit |
| CN114337310A (en) * | 2022-03-10 | 2022-04-12 | 浙江日风电气股份有限公司 | Control method, device and medium for reducing voltage stress |
| WO2022094928A1 (en) * | 2020-11-06 | 2022-05-12 | Telefonaktiebolaget Lm Ericsson (Publ) | Circuit and method for controlling rectifier, and circuit including the rectifier |
| CN116545270A (en) * | 2023-06-28 | 2023-08-04 | 广东省洛仑兹技术股份有限公司 | Resonant converter, control method thereof and switching power supply |
Citations (7)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US20060187686A1 (en) * | 2005-02-21 | 2006-08-24 | Chaoqun Sun | LLC series resonant converter and the driving method for the synchronous rectification power switches thereof |
| CN101425751A (en) * | 2007-11-02 | 2009-05-06 | 台达电子工业股份有限公司 | Resonance converter system and control method thereof |
| US20090244934A1 (en) * | 2008-03-28 | 2009-10-01 | Delta Electronics Inc. | Synchronous rectification circuit having burst mode controller and controlling method thereof |
| CN102148568A (en) * | 2010-02-08 | 2011-08-10 | 成功 | Drive strategy for LLC (logic link control) synchronous rectifier tube based on current detection |
| US20120026755A1 (en) * | 2007-10-16 | 2012-02-02 | Delta Electronics, Inc. | Resonant converter system having synchronous control circuit and controlling method thereof |
| CN103518317A (en) * | 2011-05-12 | 2014-01-15 | 株式会社村田制作所 | Switching power supply device |
| WO2015067202A2 (en) * | 2013-11-07 | 2015-05-14 | Huawei Technologies Co., Ltd. | Startup method and system for resonant converters |
-
2016
- 2016-07-08 CN CN201610533700.6A patent/CN105932881A/en active Pending
Patent Citations (7)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US20060187686A1 (en) * | 2005-02-21 | 2006-08-24 | Chaoqun Sun | LLC series resonant converter and the driving method for the synchronous rectification power switches thereof |
| US20120026755A1 (en) * | 2007-10-16 | 2012-02-02 | Delta Electronics, Inc. | Resonant converter system having synchronous control circuit and controlling method thereof |
| CN101425751A (en) * | 2007-11-02 | 2009-05-06 | 台达电子工业股份有限公司 | Resonance converter system and control method thereof |
| US20090244934A1 (en) * | 2008-03-28 | 2009-10-01 | Delta Electronics Inc. | Synchronous rectification circuit having burst mode controller and controlling method thereof |
| CN102148568A (en) * | 2010-02-08 | 2011-08-10 | 成功 | Drive strategy for LLC (logic link control) synchronous rectifier tube based on current detection |
| CN103518317A (en) * | 2011-05-12 | 2014-01-15 | 株式会社村田制作所 | Switching power supply device |
| WO2015067202A2 (en) * | 2013-11-07 | 2015-05-14 | Huawei Technologies Co., Ltd. | Startup method and system for resonant converters |
Non-Patent Citations (3)
| Title |
|---|
| 刘军，等: "高压静电除尘用电源调压特性的分析", 《高电压技术》 * |
| 王建新，等: "SLR式软开关充电电源的设计", 《电源学报》 * |
| 胡群力: "TEA CO_2激光器充电电源及其数字控制", 《中国优秀硕士学位论文全文数据库 信息科技辑》 * |
Cited By (20)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN106655837A (en) * | 2016-11-20 | 2017-05-10 | 徐云鹏 | NEXT series AC-DC power switching circuit |
| CN108880274A (en) * | 2017-05-15 | 2018-11-23 | 赤多尼科两合股份有限公司 | A kind of output current detection circuit of controlled resonant converter |
| CN107612346A (en) * | 2017-09-28 | 2018-01-19 | 西安图为电气技术有限公司 | A kind of two-way DC/DC power inverters |
| CN108274096B (en) * | 2018-03-20 | 2023-06-16 | 华南理工大学 | Parallel high-power welding power supply system based on LLC resonant converter |
| CN108274096A (en) * | 2018-03-20 | 2018-07-13 | 华南理工大学 | A kind of parallel great power welding power source system based on LLC resonant converter |
| CN108988648A (en) * | 2018-07-06 | 2018-12-11 | 华南理工大学 | A kind of LLC resonant converter synchronous rectification forecast Control Algorithm |
| CN111193403A (en) * | 2019-12-31 | 2020-05-22 | 苏州浪潮智能科技有限公司 | Synchronous rectification method, system, terminal and storage medium based on CRPS |
| CN111600489B (en) * | 2020-03-28 | 2022-10-14 | 青岛鼎信通讯股份有限公司 | DAB switching frequency self-adaption method applied to energy router |
| CN111600489A (en) * | 2020-03-28 | 2020-08-28 | 青岛鼎信通讯股份有限公司 | DAB switching frequency self-adaption method applied to energy router |
| WO2022094928A1 (en) * | 2020-11-06 | 2022-05-12 | Telefonaktiebolaget Lm Ericsson (Publ) | Circuit and method for controlling rectifier, and circuit including the rectifier |
| CN114337290A (en) * | 2021-02-07 | 2022-04-12 | 华为数字能源技术有限公司 | Driving circuit of secondary rectifying circuit in power circuit |
| CN113708644A (en) * | 2021-08-30 | 2021-11-26 | 易事特集团股份有限公司 | Simplified synchronous rectification method and device for CLLC resonant converter |
| CN113708644B (en) * | 2021-08-30 | 2023-12-08 | 易事特集团股份有限公司 | Simplified synchronous rectification method and device for CLLC resonant converter |
| CN113691140B (en) * | 2021-09-09 | 2023-06-30 | 安徽大学 | Control method for bidirectional synchronous rectification control device of LLC converter |
| CN113691140A (en) * | 2021-09-09 | 2021-11-23 | 安徽大学 | Bidirectional synchronous rectification control device and method for LLC converter |
| CN114123802A (en) * | 2022-01-25 | 2022-03-01 | 常州索维尔电子科技有限公司 | Secondary side synchronous rectification method of LLC circuit |
| CN114337310B (en) * | 2022-03-10 | 2022-08-16 | 浙江日风电气股份有限公司 | Control method, device and medium for reducing voltage stress |
| CN114337310A (en) * | 2022-03-10 | 2022-04-12 | 浙江日风电气股份有限公司 | Control method, device and medium for reducing voltage stress |
| CN116545270A (en) * | 2023-06-28 | 2023-08-04 | 广东省洛仑兹技术股份有限公司 | Resonant converter, control method thereof and switching power supply |
| CN116545270B (en) * | 2023-06-28 | 2024-02-27 | 广东省洛仑兹技术股份有限公司 | Resonant converter, control method thereof and switching power supply |
Similar Documents
| Publication | Publication Date | Title |
|---|---|---|
| CN105932881A (en) | Full-bridge LLC resonant converter and synchronous rectification driving method thereof | |
| WO2021077757A1 (en) | Wide gain control method for variable topology llc resonant converter | |
| US9991811B1 (en) | Control method and control apparatus for flyback circuit | |
| US9537401B2 (en) | Push-pull converter and modulation method for controlling a push-pull converter | |
| CN112087147B (en) | Converter wide gain control method and application thereof | |
| CN101562399B (en) | Full-bridge double-output direct current-alternating current converter | |
| CN105896986B (en) | A kind of controlled resonant converter and its control method | |
| CN205081686U (en) | Variable turn ratio output direct current - direct -current converter | |
| JP2010252450A (en) | Power conversion apparatus | |
| US20230113753A1 (en) | Dc/dc converter and method for controlling output voltage thereof | |
| TW201838303A (en) | Control device and control method thereof | |
| KR20180004675A (en) | Bidirectional Converter with Auxiliary LC Resonant Circuit and Operating Method thereof | |
| CN104753356B (en) | A kind of bi-directional half bridge three level DC DC converter current virtual value minimizes control method | |
| CN111262442A (en) | Resonance converter based ON ON/OFF control | |
| CN113937988A (en) | Asymmetric half-bridge flyback converter and control method thereof | |
| TWI683513B (en) | Power converter and control method | |
| CN113676060B (en) | Self-adaptive synchronous rectification control method and system of CLLC resonant converter | |
| CN102857103A (en) | Three-level LLC (Logical Link Control) direct-current converter and control method thereof | |
| CN112067886A (en) | Current detection circuit of switching power supply device | |
| CN112491277A (en) | Method for improving efficiency of power electronic transformer through dead time self-adaption | |
| TW201427263A (en) | DC to AC power conversion apparatus and method thereof | |
| CN205725498U (en) | A kind of inverter power supply device | |
| CN201409088Y (en) | Full-bridge twin-output direct current to direct current converter | |
| CN104852590A (en) | Novel three-level logical link control (LLC) resonant converter | |
| CN103956922A (en) | Switch power supply and control method thereof |
Legal Events
| Date | Code | Title | Description |
|---|---|---|---|
| C06 | Publication | ||
| PB01 | Publication | ||
| C10 | Entry into substantive examination | ||
| SE01 | Entry into force of request for substantive examination | ||
| RJ01 | Rejection of invention patent application after publication |
Application publication date: 20160907 |
|
| RJ01 | Rejection of invention patent application after publication |