CN102857103A - Three-level LLC (Logical Link Control) direct-current converter and control method thereof - Google Patents
Three-level LLC (Logical Link Control) direct-current converter and control method thereof Download PDFInfo
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Abstract
The invention relates to the technical field of circuits, and discloses a three-level LLC direct-current converter and a control method of the three-level LLC direct-current converter. The method comprises the following steps of: controlling the converter by a hybrid control manner of a PFM (Pulse Frequency Modulation) and a PWM (Pulse Width Modulation); adjusting the duty ratio of a switch tube of the converter under a PWM state, carrying out synchronous adjusting on the second switch tube and the first switch tube in four switch tubes which are sequentially connected in series, and carrying out synchronous adjusting on a third switch tube and a fourth switch tube. By utilizing the three-level LLC direct-current converter and the control method of the three-level LLC direct-current converter, the consumption of a clamping diode in a clamping circuit can be reduced, and the cost can be further lowered by selecting a diode in a smaller size as well.
Description
Technical field
The present invention relates to the circuit engineering field, be specifically related to a kind of three-level LLC DC converter and control method thereof.
Background technology
The diode clamping tri-level topology is widely used in the every field of power electronic technology through nearly 30 years development.The advantage of diode clamping tri-level topology is that the reverse voltage that each switching tube bears is half of DC bus-bar voltage, can use the switching tube of low voltage grade, forms the converter of high voltage grade.
From three-level converter, three Level Technology can be expanded to again buck, boost, Cuk etc. above the topology, can reduce the voltage stress of FET (Field Effect Transistor, field effect transistor).
In the three-level LLC DC converter, usually adopt PFM (Pulse Frequence Modulation, frequency modulation(FM)) and PWM (Pulse Width Modulation, pulse-width modulation) control mode, such as, adopt PFM to raise the efficiency during normal operation, in low pressure underloading situation, adopt PWM to realize pressure regulation.
In the three-level LLC DC converter, traditional PWM mode adopts inner tube to keep 50% duty ratio (not considering Dead Time) constant, and the duty that changes outer tube is recently controlled the output energy.As shown in Figure 1, wherein, V
GsThe grid of expression switching tube S1, S2, S3, S4 is to source voltage.In half-bridge three-level LLC DC converter, inner tube S2, S3 keep 50% duty ratio (not considering Dead Time) constant, recently reduce output voltage gain by the duty that shortens outer tube S1, S4.This control mode can prevent bridge arm direct pass, improves reliability.But the time that shortcoming is inner tube to be opened, outer tube turn-offs is oversize, during this period of time in, freewheel current flows through clamping diode for a long time, can strengthen the loss of diode.
Summary of the invention
The embodiment of the invention provides a kind of three-level LLC DC converter and control method thereof for the problem that above-mentioned prior art exists, to reduce the loss of clamping diode in the clamp circuit.
For this reason, the embodiment of the invention provides following technical scheme:
A kind of three-level LLC DC converter comprises: dividing potential drop electric capacity, converter, clamp circuit, resonant circuit, isolating transformer, rectification circuit, filter circuit; Wherein: described converter comprises at least one group of switch, is used for direct voltage is reverse into a square wave or staircase voltage; Every group of switch comprises four successively switching tubes (S1, S2, S3, S4) of series connection, wherein, and second switch pipe (S2) and the first switching tube (S1) adjusted in concert, the 3rd switching tube (S3) and the 4th switching tube (S4) adjusted in concert.
Preferably, described second switch pipe (S2) has the identical edge of opening with the first switching tube (S1), and the first switching tube (S1) is carried previous setting-up time than second switch pipe (S2) and turn-offed; The 3rd switching tube (S3) has the identical edge of opening with the 4th switching tube (S4), and the 4th switching tube (S4) is carried previous setting-up time than the 3rd switching tube (S3) and turn-offed;
Preferably, described setting-up time is a Dead Time.
Alternatively, described rectification circuit is zero formula rectification circuit or bridge rectifier.
Alternatively, described filter circuit is an electric capacity, π type filter circuit or multi-stage filter circuit.
A kind of control method of three-level LLC DC converter comprises:
Adopt PFM and PWM mixed-control mode that described converter is controlled;
At the PWM state, regulate the duty ratio of switching tube in the described converter, and second switch pipe and the first switching tube in four switching tubes of successively series connection carried out adjusted in concert, the 3rd switching tube and the 4th switching tube are carried out adjusted in concert.
Preferably, described duty ratio is between 0 to 50%.
Preferably, described second switch pipe and the first switching tube in four switching tubes of successively series connection are carried out adjusted in concert, the 3rd switching tube and the 4th switching tube are carried out adjusted in concert comprise:
Four switching tubes to successively series connection apply respectively driving signal PWM1, PWM2, PWM3 and PWM4, and make these four driving signals have following relation:
Drive signal PWM1, phase place or duty ratio that PWM2, PWM3 are identical with the PWM4 synchronous change, and PWM1 shifts to an earlier date setting-up time of PWM2 and turn-off, PWM4 shifts to an earlier date setting-up time of PWM3 and turn-offs.
Preferably, described setting-up time is a Dead Time.
Preferably, when the PWM state, the described successively switching frequency of four switching tubes of series connection is fixed value or changes between the peak frequency of setting and minimum frequency.
A kind of three-level LLC DC converter and control method thereof that the embodiment of the invention provides, adopt PFM and PWM mixed-control mode that the three-level LLC DC converter is controlled, and at the PWM state, regulate the duty ratio of switching tube in the described converter, inner tube and outer tube in the converter are regulated synchronously, particularly, making outer tube drive only to drive than inner tube turn-offs a very little time in advance, such as a Dead Time, thereby the ON time of the clamping diode in the minimizing clamp circuit, the average current that clamping diode is born is very little, effectively reduces the loss of clamping diode.
Description of drawings
In order to be illustrated more clearly in the embodiment of the present application or technical scheme of the prior art, the below will do to introduce simply to the accompanying drawing of required use among the embodiment, apparently, the accompanying drawing that the following describes only is some embodiment that put down in writing among the present invention, for those of ordinary skills, can also obtain according to these accompanying drawings other accompanying drawing.
Fig. 1 is that prior art is half-bridge three-level LLC DC converter PWM control mode schematic diagram;
Fig. 2 is the circuit topology figure of embodiment of the invention half-bridge three-level LLC DC converter;
Fig. 3 is the sequential chart of the driving signal of four switching tubes in the embodiment of the invention half-bridge three-level LLC DC converter;
Fig. 4 is each signal output waveform schematic diagram under the PFM mode in the embodiment of the invention half-bridge three-level LLC DC converter;
Fig. 5 is embodiment of the invention half-bridge three-level LLC DC converter PWM control mode schematic diagram;
Fig. 6 is the circuit topology figure of embodiment of the invention full-bridge three-level LLC DC converter;
Fig. 7 is the flow chart of embodiment of the invention three-level LLC DC converter control method.
Embodiment
In order to make those skilled in the art person understand better the scheme of the embodiment of the invention, below in conjunction with drawings and embodiments the embodiment of the invention is described in further detail.
The embodiment of the invention provides a kind of three-level LLC DC converter and control method thereof, adopt PFM and PWM mixed-control mode that the three-level LLC DC converter is controlled, and at the PWM state, inner tube and outer tube in the converter are regulated synchronously, particularly, making outer tube drive only to drive than inner tube turn-offs a very little time in advance, such as a Dead Time, thereby the ON time of the clamping diode in the minimizing clamp circuit, the average current that clamping diode is born is very little, effectively reduces the loss of clamping diode.
The three-level LLC DC converter that the embodiment of the invention provides comprises: dividing potential drop electric capacity, converter, clamp circuit, resonant circuit, isolating transformer, rectification circuit, filter circuit; Wherein: described converter comprises at least one group of switch, is used for direct voltage is reverse into a square wave or staircase voltage; Every group of switch comprises four successively switching tube S1, S2, S3, the S4 of series connection, wherein, second switch pipe S2 and the first switching tube S1 adjusted in concert, the 3rd switching tube S3 and the 4th switching tube S4 adjusted in concert, particularly, described second switch pipe S2 has the identical edge of opening with the first switching tube S1, and the first switching tube S1 carries previous setting-up time than second switch pipe S2 and turn-offs; The 3rd switching tube S3 has the identical edge of opening with the 4th switching tube S4, and the 4th switching tube S4 carries previous setting-up time than the 3rd switching tube S3 and turn-offs.
Above-mentioned setting-up time can be the time that is lower than the ns level of 1us, such as, can be a Dead Time.Described Dead Time refers to PWM when output, a protective time slot that can not arrange because simultaneously conducting occurs the switching speed problem for the switching tube that makes in the converter.
The below is elaborated to embodiment of the invention three-level LLC DC converter as an example of half-bridge three-level LLC DC converter example.
As shown in Figure 2, be the circuit topology figure of half-bridge three-level LLC DC converter in the embodiment of the invention.
Wherein, dividing potential drop capacitor C 1, C2 are used for input voltage vin is divided equally, and producing two only is half voltage source of input voltage; Converter is composed in series by four switching tube S1, S2, S3, S4, is used for direct voltage is reverse into a square wave or staircase voltage; Clamp circuit is comprised of two diode D1, D2, wherein, diode D1 is connected between the contact of the mid point of dividing potential drop electric capacity and switching tube S1 source electrode and second switch pipe S2 drain electrode, and diode D2 is connected between the contact of the mid point of dividing potential drop electric capacity and switching tube S4 drain electrode and switching tube S3 source electrode; Resonant circuit comprises resonant capacitance Cr, resonant inductance Lr and the magnetizing inductance Lm that is connected in series, and this resonant circuit is connected between the output of the mid point of dividing potential drop electric capacity and converter; The magnetizing inductance Lm of the simple and above-mentioned resonant circuit of isolating transformer TR is in parallel, secondaryly links to each other with rectification circuit, and described rectification circuit adopts by rectifier diode D
R1And D
R2Consist of centre tapped zero formula rectification circuit, certainly, also can adopt other forms of rectification circuit, such as bridge rectifier.Rectifier diode links to each other with the filter circuit that connects load, and described filter circuit can be capacitor, and capacitor Co as shown in FIG. also can be other forms of filter circuit, such as π type filter circuit or multi-stage filter circuit.
In embodiments of the present invention, four switching tubes in the above-mentioned converter can be the parasitic diodes that MOSFET has reverse parallel connection, and outermost two switching tube S1, S4 are called outer tube, and the inside two switching tube S2, S3 are called inner tube.These four switching tubes need four tunnel driving signals to finish PFM, PWM control.The high accuracy that above-mentioned four switching tube S1～S4 are corresponding drives signal and is designated as PWM1～PWM4.
Fig. 3 is the sequential chart of above-mentioned four tunnel driving signal PWM1～PWM4.
As shown in Figure 3, above-mentioned four tunnel driving signal PWM1～PWM4 have following relation:
(1) do not considering Dead Time Td2 and judging in advance in the situation of time T d1, PWM1 and PWM4, PWM2 and PWM3 phase place are complementary.
Above-mentioned Dead Time refers to PWM when output, a protective time slot that can not arrange because simultaneously conducting occurs the switching speed problem for the switching tube that makes in the converter.On the other hand, within this period, primary current is forced to transfer to the switching tube that namely will open, parasitic capacitance discharge to the switching tube that namely will open, so that the drain-source voltage of this switching tube reduces to 0 or very low, this switching tube just can realize that no-voltage is open-minded, reduces the turn-on consumption of switching tube greatly like this.
As shown in Figure 2, after S1, S2 turn-off, during this period of time interval before S3, S4 open is exactly the dead band, S3 just opened suddenly cause straight-through when this dead band both can prevent that S2 from also not turn-offing fully, and primary current is forced to transfer to S3 and S4 in this section period, to the parasitic capacitance discharge of S3 and S4, then S3, S4 just can realize that no-voltage is open-minded.
In circuit shown in Figure 2, outer tube S1 and inner tube S2 can not turn-off simultaneously, and outer tube S1 is turn-offed first, the loop by C1 → D1 → S1 → C1 to inner tube S1 charging and charge to the same voltage Vin/2 of C1 till.At this moment, the voltage of outer tube S1 is clamped at Vin/2, can begin afterwards to turn-off inner tube S2, otherwise the voltage of inner tube S2 just may be charged to greater than Vin/2 and cause inner tube S2 to damage.Outer tube S1 begins to turn-off that inner tube S2 begins to turn-off is during this period of time turn-off time Td1 in advance.
(2) PWM1 shifts to an earlier date the Td1 shutoff than PWM2, and PWM4 shifts to an earlier date Td1 than PWM3 and turn-offs Td1 very little (about hundreds of ns).
(3) under two kinds of state of a controls (PFM and PWM), the output waveform of PWM1～PWM4 in a switch periods as shown in Figure 3, take high level as significant level, when PWMx (x=1～4) when being high by corresponding drive circuit so that Sx (x=1～4) conducting, when PWMx when low by corresponding drive circuit so that Sx disconnect.
Characteristic under two kinds of operating conditions of PFM, PWM is respectively:
(1) when the PFM state, by loop control break switching frequency f (in other words Ts), switching frequency f regulates between setting peak frequency and minimum frequency, and duty ratio is fixed as 50% (do not consider Dead Time Td2 and shift to an earlier date turn-off time Td1), and phase shift Tps is 0;
(2) when the PWM state, by loop control break duty ratio, duty ratio is regulated between 0～50%, and f is fixed as a certain characteristic frequency or also corresponding change of frequency.When changing duty ratio, PWM1, PWM2, PWM3, PWM4 change identical phase place or duty ratio together, do not change but PWM1 shifts to an earlier date the turn-off time Td1 of PWM2, and in like manner, the turn-off time Td1 that PWM4 shifts to an earlier date PWM3 does not change yet.
Fig. 4 is each signal output waveform schematic diagram under the PFM mode in the embodiment of the invention half-bridge three-level LLC DC converter, wherein:
V
GsThe grid of expression switching tube S1, S2, S3, S4 is to source voltage;
V
Ds1, V
Ds2, V
Ds3, V
Ds4Represent that respectively the drain electrode of switching tube S1, S2, S3, S4 is to source voltage;
i
pRepresent the resonant slots electric current, namely flow through the electric current of resonant inductance Lr;
i
LMThe electric current of expression magnetizing inductance Lm;
i
DExpression catching diode electric current;
i
DRExpression output rectifier diode (D
R1/ D
R2) electric current;
V
DR1Expression output rectifier diode voltage.
Below with reference to Fig. 2 and Fig. 4, the course of work of embodiment of the invention half-bridge three-level LLC DC converter under the PFM mode is elaborated.
As shown in Figure 4, half switch periods of this DC converter can be divided into following a few part:
1) mode 1[t0, t1]
Within this time period, t0 opens switching tube S1, S2 constantly, and the DC converter primary current flows through switching tube S1, S2, at this moment, energy by transformer to secondary transmission.Primary current rises with sinusoidal rule.Secondary diode DR1 conducting, output voltage is clamped at output voltage with transformer secondary output.Resonant inductance Lr and resonance capacitor C r resonance, the electric current that flows through magnetizing inductance Lm rises according to linearity.The DC converter secondary current is that the difference of primary current and exciting curent is converted secondary value.
2) mode 2[t1, t2]
Along with the linearity of former limit resonance current according to sinusoidal rule decline and exciting curent rises, the two numerical value is equal constantly at t1, and the converter secondary voltage is reduced to zero simultaneously.At this time do not have unnecessary electric current can be sent to by transformer secondary, former, secondary disengaging, the transmitting energy stage finishes.At this moment, secondary commutation diode DR1 turn-offs naturally because flowing through current resonance zero passage wherein, does not therefore almost have the oppositely process of recovery, and at this moment, the reverse voltage on the diode DR1 is output voltage.Because this moment, transformer secondary output no longer was output voltage clamp, the magnetizing inductance of transformer becomes free inductance so, resonance occurs in Lm, Lr, Cr together, because general transformer excitation inductance is very large, so this harmonic period is more much bigger than previous harmonic period, therefore in this mode, the DC converter primary current can be similar to and be seen as constant current source.
3) mode 3[t2, t3]
T2 is on-off switching tube S1 constantly, but still conducting of switching tube S2.The electric current that flows through magnetizing inductance Lm, resonant inductance Lr, resonant capacitance Cr flows through diode D1 afterflow.Simultaneously, the voltage on the switching tube S1 is clamped at Vin/2, and this mode is generally very short in the design.
4) mode 4[t3, t4]
T3 constantly switching tube S2 turn-offs, and the simple electric current of transformer is forced to transfer to switching tube S3 and S4 simultaneously, to the parasitic capacitance discharge at its two ends to zero potential.The then parasitic diode conducting of switching tube S3, S4.At this moment, the voltage sum on switching tube S1 and the S2 is input voltage vin.Because the voltage stress on the switching tube S1 is half of input voltage in mode 3, the voltage stress on the switching tube S2 also is half of input voltage so, that is Vin/2.When this mode finished, the voltage on switching tube S3, the S4 reduced to zero, for the no-voltage of switching tube S3, S4 is opened the condition prepared.
Lower half switch periods and the operation principle in first cycle are similar, herein no longer narration.
Can find out that from top analysis switching tube is Zero-voltage soft switch all, be operated in ZVS (zero voltage switch) state, and voltage stress be input voltage half; Secondary commutation diode DR1, DR2 work ZCS (Zero Current Switch) state does not almost have reversely restoring process, and due to voltage spikes is zero, and the voltage stress on it is 2 times output voltage.
Change in theory frequency and just can change output voltage gain, but frequency can not unrestrictedly increase, the one, frequency increases, and the switching device loss also increases; Frequency increases in addition, and gain occurs non-linear easily.Therefore, in embodiments of the present invention, when low pressure is exported, adopt the PWM mode, control flow to the energy of output by the mode that reduces duty ratio.
And, in order to reduce the loss of clamping diode D1 or D2, in embodiments of the present invention, switching tube S2 and switching tube S1 are carried out adjusted in concert, switching tube S2 is only turn-offed than switching tube S1 dead band Td1 time that lags.Equally, switching tube S4 and switching tube S3 are carried out adjusted in concert, switching tube S4 is only lagged one than switching tube S3 open the dead band Td1 time and turn-off, as shown in Figure 5.Like this, both controlled the output energy, the current time that flows through simultaneously clamping diode is also lacked (only conducting within the time of Td1), diode losses is less, and efficient is high, thereby in actual applications, can adopt the clamping diode of less through-current capability, save cost.
Equally, the three-level LLC DC converter of the embodiment of the invention also can be full-bridge three-level LLC DC converter, as shown in Figure 6, its principle and the course of work and half-bridge three-level LLC DC converter shown in Figure 2 are similar, the ripple mode of sending out of switching tube S8 is identical with the ripple mode of switching tube S1, the ripple mode of sending out of switching tube S7 is identical with the ripple mode of switching tube S2, the ripple mode of sending out of switching tube S6 is identical with the ripple mode of switching tube S3, and the ripple mode of sending out of switching tube S5 is identical with the ripple mode of switching tube S4.
Equally, this full-bridge three-level LLC DC converter no matter still transfer wide by frequency modulation, three-level LLC DC converter with respect to prior art, can greatly reduce the current time that flows through clamping diode, diode losses is less, thereby in actual applications, can adopt the clamping diode of less through-current capability, save cost.
Correspondingly, the embodiment of the invention also provides a kind of control method of three-level LLC DC converter, as shown in Figure 7, is the flow chart of the method, may further comprise the steps:
Step 701 adopts PFM and PWM mixed-control mode that described converter is controlled.
Such as, in embodiments of the present invention, adopt PFM to raise the efficiency during normal operation, in low pressure underloading situation, adopt PWM to realize pressure regulation.
Step 702 at the PWM state, is regulated the duty ratio of switching tube in the described converter, and second switch pipe and the first switching tube in four switching tubes of successively series connection carried out adjusted in concert, and the 3rd switching tube and the 4th switching tube are carried out adjusted in concert.
At the PFM state, to control the switching frequency of switching tube in the described converter and between the peak frequency of setting and minimum frequency, regulate, the duty ratio of described switching tube is fixed as 50%.
At the PWM state, the duty ratio of switching tube is regulated between 0 to 50%, and under this state, the switching frequency of switching tube is fixed value or changes between the peak frequency of setting and minimum frequency.
Above-mentioned second switch pipe and the first switching tube in four switching tubes of successively series connection are carried out adjusted in concert, the 3rd switching tube and the 4th switching tube are carried out adjusted in concert specifically can be:
Four switching tubes to successively series connection apply respectively driving signal PWM1, PWM2, PWM3 and PWM4, and make these four driving signals have following relation:
Driving signal PWM1, phase place or duty ratio that PWM2, PWM3 are identical with the PWM4 synchronous change, and PWM1 shifts to an earlier date setting-up time of PWM2 and turn-offs, PWM4 shifts to an earlier date setting-up time of PWM3 and turn-offs, described setting-up time can be the time that is lower than the ns level of 1us, such as being a Dead Time.
The control method of embodiment of the invention three-level LLC DC converter goes for half-bridge three-level LLC DC converter shown in Figure 2, also is applicable to full-bridge three-level LLC DC converter shown in Figure 6.Utilize the present invention program, can reduce the ON time of the clamping diode in the clamp circuit, the average current that clamping diode is born is very little, effectively reduces the loss of clamping diode.
Each embodiment in this specification all adopts the mode of going forward one by one to describe, and identical similar part is mutually referring to getting final product between each embodiment, and each embodiment stresses is difference with other embodiment.The explanation of relevant part cross-references appropriate section gets final product.
More than the embodiment of the invention is described in detail, used embodiment herein the present invention set forth, the explanation of above embodiment just is used for helping to understand method and apparatus of the present invention; Simultaneously, for one of ordinary skill in the art, according to thought of the present invention, all will change in specific embodiments and applications, in sum, this description should not be construed as limitation of the present invention.
Claims (12)
1. a three-level LLC DC converter is characterized in that, comprising: dividing potential drop electric capacity, converter, clamp circuit, resonant circuit, isolating transformer, rectification circuit, filter circuit; Wherein: described converter comprises at least one group of switch, is used for direct voltage is reverse into a square wave or staircase voltage; Every group of switch comprises four successively switching tubes (S1, S2, S3, S4) of series connection, wherein, and second switch pipe (S2) and the first switching tube (S1) adjusted in concert, the 3rd switching tube (S3) and the 4th switching tube (S4) adjusted in concert.
2. three-level LLC DC converter according to claim 1, it is characterized in that, described second switch pipe (S2) has the identical edge of opening with the first switching tube (S1), and the first switching tube (S1) is carried previous setting-up time than second switch pipe (S2) and turn-offed; The 3rd switching tube (S3) has the identical edge of opening with the 4th switching tube (S4), and the 4th switching tube (S4) is carried previous setting-up time than the 3rd switching tube (S3) and turn-offed.
3. three-level LLC DC converter according to claim 2 is characterized in that, described setting-up time is a Dead Time.
4. three-level LLC DC converter according to claim 3 is characterized in that, described Dead Time is less than or equal to 1 microsecond.
5. according to claim 1 to 4 each described three-level LLC DC converter, it is characterized in that described rectification circuit is zero formula rectification circuit or bridge rectifier.
6. according to claim 1 to 4 each described three-level LLC DC converter, it is characterized in that described filter circuit is an electric capacity, π type filter circuit or multi-stage filter circuit.
7. the control method of a three-level LLC DC converter is characterized in that, comprising:
Adopt PFM and PWM mixed-control mode that described converter is controlled;
At the PWM state, regulate the duty ratio of switching tube in the described converter, and second switch pipe and the first switching tube in four switching tubes of successively series connection carried out adjusted in concert, the 3rd switching tube and the 4th switching tube are carried out adjusted in concert.
8. method according to claim 7 is characterized in that, described duty ratio is between 0 to 50%.
9. method according to claim 7 is characterized in that, described second switch pipe and the first switching tube in four switching tubes of successively series connection is carried out adjusted in concert, the 3rd switching tube and the 4th switching tube is carried out adjusted in concert comprise:
Four switching tubes to successively series connection apply respectively driving signal PWM1, PWM2, PWM3 and PWM4, and make these four driving signals have following relation:
Drive signal PWM1, phase place or duty ratio that PWM2, PWM3 are identical with the PWM4 synchronous change, and PWM1 shifts to an earlier date setting-up time of PWM2 and turn-off, PWM4 shifts to an earlier date setting-up time of PWM3 and turn-offs.
10. method according to claim 9 is characterized in that, described setting-up time is a Dead Time.
11. method according to claim 10 is characterized in that, described Dead Time is less than or equal to 1 microsecond.
12. to 11 each described methods, it is characterized in that according to claim 7,
When the PWM state, the described successively switching frequency of four switching tubes of series connection is fixed value or changes between the peak frequency of setting and minimum frequency.
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Cited By (8)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN103414346A (en) * | 2013-07-11 | 2013-11-27 | 中国航天科工集团第三研究院第八三五七研究所 | Novel fixed frequency and variable frequency mixed control circuit of LLC resonant converter |
| CN106300984A (en) * | 2015-05-29 | 2017-01-04 | 三垦电气（上海）有限公司 | The control method of LLC circuit and electronic equipment |
| CN108258909A (en) * | 2017-12-22 | 2018-07-06 | 华为技术有限公司 | Resonant transform circuit and its control method |
| CN108270359A (en) * | 2016-12-30 | 2018-07-10 | 德州仪器公司 | For the adaptive turn-on time algorithm of LLC converter |
| CN110214411A (en) * | 2016-12-16 | 2019-09-06 | 株式会社村田制作所 | Simplification hybrid PWM/PFM control of SLLC converter |
| CN110649814A (en) * | 2019-09-10 | 2020-01-03 | 中国矿业大学 | Hybrid control method of full-bridge three-level LLC resonant converter |
| CN113517817A (en) * | 2021-06-07 | 2021-10-19 | 燕山大学 | Three-level bidirectional full-bridge LLCLC multi-resonant converter topology |
| WO2022077421A1 (en) * | 2020-10-16 | 2022-04-21 | 深圳欣锐科技股份有限公司 | Voltage conversion circuit and electronic device |
Citations (7)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US6344979B1 (en) * | 2001-02-09 | 2002-02-05 | Delta Electronics, Inc. | LLC series resonant DC-to-DC converter |
| CN1523746A (en) * | 2003-09-03 | 2004-08-25 | 浙江大学 | Three-level LLC series resonance DC/DC transformer |
| CN1992493A (en) * | 2005-12-30 | 2007-07-04 | 艾默生网络能源系统有限公司 | Resonant DC/DC converter and control method thereof |
| CN101047337A (en) * | 2007-04-12 | 2007-10-03 | 艾默生网络能源有限公司 | Three-level LLC resonance inverter |
| CN101098109A (en) * | 2007-05-17 | 2008-01-02 | 艾默生网络能源有限公司 | Three-level resonant transformer |
| CN101656480A (en) * | 2009-09-04 | 2010-02-24 | 艾默生网络能源有限公司 | PWM control method for three-level LLC converter |
| CN101707440A (en) * | 2009-11-12 | 2010-05-12 | 中兴通讯股份有限公司 | LLC resonant converter control method, synchronous rectification control method and device |
-
2011
- 2011-06-30 CN CN2011101813994A patent/CN102857103A/en active Pending
Patent Citations (7)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US6344979B1 (en) * | 2001-02-09 | 2002-02-05 | Delta Electronics, Inc. | LLC series resonant DC-to-DC converter |
| CN1523746A (en) * | 2003-09-03 | 2004-08-25 | 浙江大学 | Three-level LLC series resonance DC/DC transformer |
| CN1992493A (en) * | 2005-12-30 | 2007-07-04 | 艾默生网络能源系统有限公司 | Resonant DC/DC converter and control method thereof |
| CN101047337A (en) * | 2007-04-12 | 2007-10-03 | 艾默生网络能源有限公司 | Three-level LLC resonance inverter |
| CN101098109A (en) * | 2007-05-17 | 2008-01-02 | 艾默生网络能源有限公司 | Three-level resonant transformer |
| CN101656480A (en) * | 2009-09-04 | 2010-02-24 | 艾默生网络能源有限公司 | PWM control method for three-level LLC converter |
| CN101707440A (en) * | 2009-11-12 | 2010-05-12 | 中兴通讯股份有限公司 | LLC resonant converter control method, synchronous rectification control method and device |
Cited By (10)
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|---|---|---|---|---|
| CN103414346A (en) * | 2013-07-11 | 2013-11-27 | 中国航天科工集团第三研究院第八三五七研究所 | Novel fixed frequency and variable frequency mixed control circuit of LLC resonant converter |
| CN106300984A (en) * | 2015-05-29 | 2017-01-04 | 三垦电气（上海）有限公司 | The control method of LLC circuit and electronic equipment |
| CN110214411A (en) * | 2016-12-16 | 2019-09-06 | 株式会社村田制作所 | Simplification hybrid PWM/PFM control of SLLC converter |
| CN108270359A (en) * | 2016-12-30 | 2018-07-10 | 德州仪器公司 | For the adaptive turn-on time algorithm of LLC converter |
| CN108270359B (en) * | 2016-12-30 | 2021-07-30 | 德州仪器公司 | Adaptive on-time algorithm for LLC converter |
| CN108258909A (en) * | 2017-12-22 | 2018-07-06 | 华为技术有限公司 | Resonant transform circuit and its control method |
| US10978957B2 (en) | 2017-12-22 | 2021-04-13 | Huawei Technologies Co., Ltd. | Resonant converter circuit and resonant converter circuit control method |
| CN110649814A (en) * | 2019-09-10 | 2020-01-03 | 中国矿业大学 | Hybrid control method of full-bridge three-level LLC resonant converter |
| WO2022077421A1 (en) * | 2020-10-16 | 2022-04-21 | 深圳欣锐科技股份有限公司 | Voltage conversion circuit and electronic device |
| CN113517817A (en) * | 2021-06-07 | 2021-10-19 | 燕山大学 | Three-level bidirectional full-bridge LLCLC multi-resonant converter topology |
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