CN103296882A - DC-DC (direct-current to direct-current) resonant converter with automatic voltage equalizing function - Google Patents

DC-DC (direct-current to direct-current) resonant converter with automatic voltage equalizing function Download PDF

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CN103296882A
CN103296882A CN2013102065580A CN201310206558A CN103296882A CN 103296882 A CN103296882 A CN 103296882A CN 2013102065580 A CN2013102065580 A CN 2013102065580A CN 201310206558 A CN201310206558 A CN 201310206558A CN 103296882 A CN103296882 A CN 103296882A
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voltage
conduction device
circuit
capacitor
transformer
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CN103296882B (en
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李武华
罗清璟
罗皓泽
顾云杰
何湘宁
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Zhejiang University ZJU
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Zhejiang University ZJU
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Abstract

The invention discloses a DC-DC (direct-current to direct-current) resonant converter with an automatic voltage equalizing function. The DC-DC resonant converter comprises a switch capacitor circuit and an LLC (logic link control) series resonant circuit. The switch capacitor circuit is formed by concatenation of a plurality of half-bridge submodules. Middle nodes of two adjacent half-bridge submodules are connected through a switch capacitor module. According to the DC-DC converter, the half-bridge submodules are in series connection before being connected in parallel at two ends of a direct-current power supply. In the ideal case, the voltage of each bus capacitor is one n-th of the direct-current voltage; two switch tubes are in series connection inside one half-bridge submodule before being connected in parallel with one bus capacitor, and accordingly turn-off voltage stress of each switch tube is half of the voltage of one bus capacitor. Switch components with low voltage and high performances can be selected for the converter, efficiency of the converter is improved, and size of the converter is reduced.

Description

A kind of DC-DC controlled resonant converter with automatically equalizing voltage function
Technical field
The invention belongs to the power converter technical field, be specifically related to a kind of DC-DC controlled resonant converter with automatically equalizing voltage function.
Background technology
In recent years, various power-supply devices have been widely used in industries such as communication, illumination, military project.For the electricity quality of using of standard power-supply device, some global academic tissues and country begin to formulate and implemented the standard of a series of power-supply devices.The restriction power-supply device is one of important criterion to the harmonic pollution of AC network, as IEC555-2, IEEE519 etc.In order to satisfy harmonic standard, use multi-stage cascade type high-frequency converter in the industry usually, and in first order rectifying installation, use the Active PFC technology (Power Factor Correction, PFC).
When using multi-stage cascade type high-frequency converter in three-phase electrical power system, the output busbar voltage of first order three-phase PFC rectifier converter is generally 600-800V, even some occasion can be up to 1000V.The voltage stress of switching device increases greatly in this feasible back level converter.
Switched-capacitor circuit has its special advantages in the high input voltage occasion, as shown in Figure 1; By utilizing the switching capacity module between the half-bridge of two series connection, to realize the energy transmission, up and down the voltage of two input capacitances by clamped at 1/2nd input voltage, thereby the voltage stress of the power switch pipe of each half-bridge by clamped at 1/2nd of input voltage, be conducive to the application of low voltage power devices, thereby the reduction conduction loss promotes conversion efficiency.But the transformation ratio of switched-capacitor circuit is the transformation ratio of integral multiple often, causes its application very narrow; When input voltage changes, can't obtain stable voltage output by the method for control, this is very disadvantageous in commercial Application.In addition, switched-capacitor circuit itself can't be realized the soft switch of switching tube, thereby causes bigger switching loss, is unfavorable for the lifting of circuit efficiency.
In the prior art, traditional semibridge system LLC series resonance structure can realize high efficiency voltage transitions, as shown in Figure 2.It has the characteristic of soft switch in the full operating range, has greatly reduced the switching loss of circuit, thereby obtains high conversion rate.In addition, in certain voltage range, the LLC resonant circuit can be realized the function of voltage-regulation voltage-stabilization by the adjustment of frequency.But the former limit switching tube stress of traditional semibridge system LLC series resonance structure is input voltage; And because the high tension apparatus switching frequency is low, conducting resistance is big, causing converter can't satisfy the demand of high-efficient high performance, the high tension apparatus cost is than higher simultaneously; In addition, along with the increase to high step-down applications demand, volume of transformer will increase, thereby causes higher losses and lower power density.
Summary of the invention
At the above-mentioned technical problem of existing in prior technology, the invention provides a kind of DC-DC controlled resonant converter with automatically equalizing voltage function, can realize electric voltage equalization automatically, and switching device stress is low, stability of a system height.
A kind of DC-DC controlled resonant converter with automatically equalizing voltage function comprises:
Switched-capacitor circuit is used for input voltage is carried out the integral multiple step-down, obtains intermediate voltage;
The LLC series resonant circuit is used for described intermediate voltage is carried out frequency conversion voltage adjusting, obtains output voltage.
Described switched-capacitor circuit is formed by the cascade of a plurality of half-bridge submodule, and the intermediate node of adjacent two half-bridge submodules connects by the switching capacity module.
Described half-bridge submodule is by capacitor C and two switching tube S 1～S 2Form; Wherein, switching tube S 1An end link to each other with an end of capacitor C and be an end of half-bridge submodule, switching tube S 1The other end and switching tube S 2An end link to each other and be the intermediate node of half-bridge submodule, switching tube S 2The other end link to each other with the other end of capacitor C and be the other end of half-bridge submodule, two switching tube S 1～S 2The control utmost point receive the switching signal of a pair of phase place complementation that external equipment provides, switching tube S respectively 2Two ends constitute the outlet side of half-bridge submodule.
The duty ratio of described switching signal is 50%.
Described switching capacity module is by capacitor C sForm or by capacitor C sAnd inductance L sBe composed in series; The preferred capacitor C that adopts sAnd inductance L sCascaded structure is conducive to reduce the switching capacity branch road to the impulse current that bus capacitor discharges and recharges, and reduces two pressure reduction between the bus capacitor, makes the electric voltage equalization of two bus capacitors, can promote the performance of circuit.
Preferably, described two switching tube S 1～S 2Adopt the anti-also power switch pipe of diode of band, the two ends of this power switch pipe are parallel with electric capacity; Voltage build-up rate that can power-limiting switching tube blocking interval has reduced the turn-off power loss of power switch pipe; Utilize leakage inductance during power switch pipe is opened, to extract energy on the shunt capacitance simultaneously, can realize that the no-voltage of all power switch pipes is open-minded, effectively reduced the conduction loss of switching tube.
Described LLC series resonant circuit comprises resonant inductance L r, resonant capacitance C r, magnetizing inductance L m, transformer T and a secondary circuit; Wherein, resonant inductance L rAn end and resonance capacitor C rAn end constitute the voltage input side of LLC series resonant circuit, resonant inductance L rThe other end and magnetizing inductance L mAn end link to each other magnetizing inductance L mThe other end and resonant capacitance C rThe other end link to each other the former limit winding of transformer T and magnetizing inductance L mParallel connection, the secondary winding of transformer T and the corresponding connection of the input side of secondary circuit, described secondary circuit adopts full-wave rectifying circuit, half-wave rectifying circuit or full bridge rectifier.
Described full-wave rectifying circuit is by output capacitance C oWith two conduction device D 1～D 2Form; Wherein, conduction device D 1Input link to each other the other end and the conduction device D of transformer T secondary winding with an end of transformer T secondary winding 2Input link to each other conduction device D 1Output and conduction device D 2Output and output capacitance C oAn end link to each other output capacitance C oThe other end link to each other with the centre tap end of transformer T secondary winding.
Described half-wave rectifying circuit is by output capacitance C oForm with conduction device D; Wherein, the input of conduction device D links to each other with an end of transformer T secondary winding, the output of conduction device D and output capacitance C oAn end link to each other output capacitance C oThe other end link to each other with the other end of transformer T secondary winding.
Described full bridge rectifier is by output capacitance C oWith four conduction device D 1～D 4Form; Wherein, conduction device D 1Input and conduction device D 2Output and an end of transformer T secondary winding link to each other conduction device D 1Output and conduction device D 3Output and output capacitance C oAn end link to each other conduction device D 3Input and conduction device D 4Output and the other end of transformer T secondary winding link to each other conduction device D 2Input and conduction device D 4Input and output capacitance C oThe other end link to each other.
Described conduction device adopts diode or switching tube.
The voltage input side of described LLC series resonant circuit and the corresponding connection of the outlet side of arbitrary half-bridge submodule in the switched-capacitor circuit.
In the DC-DC converter of the present invention, be parallel to the DC power supply two ends after a plurality of half-bridge submodule series connection; In the ideal case, the voltage of each bus capacitor is n/one (n is half-bridge submodule number) of DC power supply voltage.Two switching tube series connection backs are in parallel with bus capacitor in the half-bridge submodule, so the shutoff voltage stress of each switching tube is again 1/2nd of single bus capacitor voltage.Therefore converter of the present invention can be selected low pressure, high performance switching device for use, be conducive to promote converter efficient, reduce the volume of converter.
DC-DC converter of the present invention utilizes the switching capacity branch road to connect the intermediate node of adjacent two half-bridge submodules, and such connected mode can realize the automatically equalizing voltage of DC side bus capacitor.The concrete course of work of switching capacity structure is: when the first, the 3rd power switch pipe conducting, first, second capacitance branch road series connection back is in parallel with first bus capacitor; When the second, the 4th power switch pipe conducting, first, second capacitance branch road series connection back is in parallel with second bus capacitor.In this parallel connection process, first, second capacitance branch road discharges to high-tension bus capacitor, to the bus capacitor charging of low-voltage, finally can make the voltage of two bus capacitors reach balanced.
Compare with the existing traditional semibridge system structure DC-DC controlled resonant converter of high voltage bus occasion that is applicable to, DC-DC controlled resonant converter of the present invention is reduced to half of input voltage with the voltage of each device for power switching, so can select the low-voltage power switch device for use.Because low voltage power devices has the advantage that performance is good, cost is low, switching frequency is high, so the present invention can realize the DC-DC conversion of high-efficient high performance under the high input voltage occasion.
Description of drawings
Fig. 1 is the electrical block diagram of traditional switch capacitance decompression converter.
Fig. 2 is the electrical block diagram of traditional semibridge system DC-DC controlled resonant converter.
Fig. 3 is the electrical block diagram of DC-DC controlled resonant converter of the present invention.
Fig. 4 is the working waveform figure of DC-DC controlled resonant converter of the present invention.
Fig. 5 is the circuit theory schematic diagram of DC-DC controlled resonant converter of the present invention.
Fig. 6 is the structural representation after DC-DC controlled resonant converter N level of the present invention is expanded.
Embodiment
In order more specifically to describe the present invention, below in conjunction with the drawings and the specific embodiments technical scheme of the present invention and related work principle thereof are elaborated.
As shown in Figure 3, a kind of DC-DC controlled resonant converter with automatically equalizing voltage function comprises switched-capacitor circuit and coupled LLC series resonant circuit; Wherein:
Switched-capacitor circuit is used for input voltage V In(E provides by DC power supply) carries out the integral multiple step-down, obtains intermediate voltage V; In the present embodiment, switched-capacitor circuit is formed by two half-bridge submodule H1～H2 cascades, and the intermediate node of two half-bridge submodules connects by the switching capacity module.
Half-bridge submodule H1 is by capacitor C 1With two metal-oxide-semiconductor S 1～S 2Form; Wherein, metal-oxide-semiconductor S 1Drain electrode link to each other with an end of capacitor C and be the end of half-bridge submodule H1, metal-oxide-semiconductor S 1Source electrode and metal-oxide-semiconductor S 2Drain electrode link to each other and be the intermediate node of half-bridge submodule H1, metal-oxide-semiconductor S 2Source electrode and capacitor C 1The other end link to each other and be the other end of half-bridge submodule H1, two metal-oxide-semiconductor S 1～S 2Grid receive the switching signal of a pair of phase place complementation that external equipment provides, metal-oxide-semiconductor S respectively 2The source leak the outlet side that two ends constitute half-bridge submodule H1.
Half-bridge submodule H2 is by capacitor C 2With two metal-oxide-semiconductor S 3～S 4Form; Wherein, metal-oxide-semiconductor S 3Drain electrode and capacitor C 2An end link to each other and be the end of half-bridge submodule H2, metal-oxide-semiconductor S 3Source electrode and metal-oxide-semiconductor S 4Drain electrode link to each other and be the intermediate node of half-bridge submodule H2, metal-oxide-semiconductor S 4Source electrode and capacitor C 2The other end link to each other and be the other end of half-bridge submodule H2, two metal-oxide-semiconductor S 3～S 4Grid receive the switching signal of a pair of phase place complementation that external equipment provides, metal-oxide-semiconductor S respectively 4The source leak the outlet side that two ends constitute half-bridge submodule H2.
The switching capacity module is by capacitor C sAnd inductance L sBe composed in series.
Four metal-oxide-semiconductor S 1～S 4The duty ratio of the switching signal that receives is 50%, wherein, and metal-oxide-semiconductor S 1With metal-oxide-semiconductor S 3The switching signal that receives is identical, metal-oxide-semiconductor S 1With metal-oxide-semiconductor S 2The switching signal complementation that receives, metal-oxide-semiconductor S 3With metal-oxide-semiconductor S 4The switching signal complementation that receives.
Four metal-oxide-semiconductor S 1～S 4All parasitism has anti-and diode, and the source of each metal-oxide-semiconductor is leaked two ends and all is parallel with electric capacity (parasitic capacitance).
The LLC series resonant circuit is used for middle voltage V is carried out frequency conversion voltage adjusting, obtains output voltage V OutIn the present embodiment, the LLC series resonant circuit comprises resonant inductance L r, resonant capacitance C r, magnetizing inductance L m, transformer T and a secondary circuit; Wherein, resonant inductance L rAn end and resonance capacitor C rAn end constitute the voltage input side of LLC series resonant circuit, resonant inductance L rThe other end and magnetizing inductance L mAn end link to each other magnetizing inductance L mThe other end and resonant capacitance C rThe other end link to each other the former limit winding of transformer T and magnetizing inductance L mParallel connection, the secondary winding of transformer T and the corresponding connection of the input side of secondary circuit, the secondary winding centre tap of transformer T, secondary circuit adopts full-wave rectifying circuit.
Full-wave rectifying circuit is by output capacitance C oWith two diode D 1～D 2Form; Wherein, diode D 1Anode link to each other the other end and the diode D of transformer T secondary winding with an end of transformer T secondary winding 2Anode link to each other diode D 1Negative electrode and diode D 2Negative electrode and output capacitance C oAn end link to each other output capacitance C oThe other end link to each other with the centre tap end of transformer T secondary winding; Output capacitance C oTwo ends shunt load R oThereby generation output voltage V Out
The corresponding connection of outlet side of half-bridge submodule H1 in the voltage input side of LLC series resonant circuit and the switched-capacitor circuit.
The power of the DC-DC controlled resonant converter of present embodiment is 1kW, and the input voltage at DC power supply E two ends is 600V, load R oThe output voltage at two ends requires to be 48V.
Fig. 4 is drive waveforms and the work wave of the DC-DC controlled resonant converter of present embodiment.Waveform V wherein Gs1～V Gs4Be respectively metal-oxide-semiconductor S 1～S 4Switching signal, V Gs1With V Gs3Identical; V Gs2With V Gs1Complementary; V Gs4With V Gs3Complementary; While V Gs1With V Gs2Between, V Gs3With V Gs4Between respectively exist one section common to be low level Dead Time.Waveform v Ds1～v Ds4Be respectively metal-oxide-semiconductor S 1～S 4Drain-source voltage; i LrFor flowing through resonant inductance L rElectric current, i LmFor flowing through magnetizing inductance L mElectric current, i CsFor flowing through switching capacity C sElectric current, i S1～i S4For flowing through metal-oxide-semiconductor S 1～S 4Electric current; i D1And i D2Be respectively and flow through diode D 1And D 2Electric current.
For the LLC resonant slots, resonant inductance L rInfluence can not ignore.Therefore, controlled resonant converter has two resonance links.A resonance link is by L r, C rConstitute, its resonance frequency is f rAnother is by L m, L r, C rConstitute, its resonance frequency is f mTwo calculating resonance frequency formula are as follows:
f r = 1 2 π L k · C b
f m = 1 2 π ( L k + L m ) · C b
According to the difference of operating frequency, circuit can be divided into f m＜f＜f r, f=f r, f＞f rThree operating frequency ranges.Wherein:
In these three frequency ranges, can realize that all the no-voltage of power switch pipe is open-minded, thereby reduce the turn-on consumption of switching tube.Simultaneously at f m＜f＜f rIn the service area, the electric current natural zero-crossing on the secondary diode can be realized zero-current switching, does not have reverse-recovery problems.So f m＜f＜f rBe the groundwork interval of present embodiment, as shown in Figure 4 and Figure 5, the concrete course of work of the DC-DC controlled resonant converter of present embodiment is as follows:
In the switch periods, have 6 working stages, wherein: working stage 1～working stage 2 is metal-oxide-semiconductor S 1And S 3Stabilization process during conducting; Working stage 3 is metal-oxide-semiconductor S 1And S 3Commutation states during conducting; Working stage 4～working stage 5 is metal-oxide-semiconductor S 2And S 4Stabilization process during conducting; Working stage 6 is metal-oxide-semiconductor S 2And S 4Commutation states during shutoff.
Working stage 1(t 0～t 1): S 1With S 3The beginning conducting, exciting current i LmLinear rising, the leakage inductance current i LrRise with sinusoidal form, and i LrGreater than i Lm, both differences flow through the former limit of transformer, make secondary diode D 1Conducting, the original edge voltage of transformer is output voltage V OutClamp.Therefore, the LLC resonant slots has only leakage inductance L rWith capacitor C rResonance takes place.
This stage switch capacitor C sWith input capacitance C 1Parallel connection, C sTo C 1Charging.
Working stage 2(t 1～t 2): at t 1Constantly, exciting current i LmEqual the leakage inductance current i LrSecondary current drops to zero naturally, rectifier diode D 1Realize zero-current switching.The while output voltage V OutNo longer clamped to transformer, magnetizing inductance L mBecome resonant inductance freely, so L m, L rWith C rResonance takes place.Because the cycle of this resonance is far longer than switch periods, thus in this stage i LrCan regard steady state value as.
Because C sWith L sBe in the second order resonance condition, and do not have additional power source, so switching capacity branch current i CsKeep original resonance trend to descend, also be and flow through S 3Current i S3In order to keep i LrConstant, i S1Equivalent increases thus, and output power of power supply increases.
Working stage 3(t 2～t 3): at t 3Constantly, S 1And S 3Begin to turn-off, enter Dead Time.Because leakage inductance current i LrKeep constant, at this moment switching tube junction capacitance C S1, C S3Begin charging, C S2, C S4Begin discharge.Work as C S2, C S4Voltage be down to zero respectively after, S 2, S 4Bypass diode conducting afterflow, be S 2And S 4No-voltage open and create conditions.
Working stage 4(t 3～t 4): at t 3Constantly, S 2And S 4Open-minded.i LrGreater than i Lm, both differences flow through the former limit of transformer, D 2Conducting, the original edge voltage of transformer is by V OutClamp, the LLC resonant slots has only L rWith C rResonance takes place.
This stage switch capacitor C sWith input capacitance C 2Parallel connection, C 2To C sCharging.
Working stage 5(t 4～t 5): at t 4Constantly, i LmEqual i LrSecondary current drops to zero naturally, rectifier diode D 2Realize zero-current switching.While V OutNo longer clamped to transformer, L mBecome resonant inductance freely, so L m, L rWith C rResonance takes place.Because the cycle of this resonance is far longer than switch periods, thus in this stage i LrCan regard steady state value as.
Because C sWith L sBe in the second order resonance condition, and do not have additional power source, so switching capacity branch current i CsKeep original resonance trend to descend, also be and flow through S 3Current i S4In order to keep i LrConstant, i S2Equivalent increases thus, and output power of power supply increases.
Working stage 6(t 5～t 6) at t 4Constantly, S 2And S 4Begin to turn-off, enter Dead Time.Because i LrKeep constant and for negative, this moment switching tube junction capacitance C S1, C S3Begin discharge, C S2, C S4Begin charging.Work as C S1, C S3Voltage be down to zero respectively after, S 1, S 3Bypass diode conducting afterflow, be S 1And S 3No-voltage open and create conditions.
The DC-DC controlled resonant converter of present embodiment can be realized DC side bus capacitor voltage automatic equalization, can improve the reliability of system applies when high voltage DC-DC occasion.The specific implementation of its voltage automatic equalization ability is as follows: power switch tube S 1And S 3When opening, switching capacity C sAnd L sWith bus capacitor C 1In parallel; Power switch tube S 2And S 4When opening, switching capacity C sAnd L sWith bus capacitor C 2In parallel; In process in parallel, C sAnd L sTo high-tension bus capacitor discharge, to the bus capacitor charging of low-voltage, finally reach the effect of automatically equalizing voltage.
As shown in Figure 6, the switched-capacitor circuit of the DC-DC controlled resonant converter of all pressing is equal die mould multiple-pole switch condenser network certainly, can expand switching capacity progression.N level circuit after the expansion is: N(N〉1) the high-pressure side electric capacity (C of individual series connection 1, C 2..., C N), the series connection back is in parallel with the high-pressure side power supply.Uppermost electric capacity (C 1) be called high-pressure side electric capacity 1, by that analogy, N electric capacity (C N) be called high-pressure side electric capacity N; N brachium pontis, n brachium pontis and high-pressure side electric capacity n(C n) parallel connection.Each brachium pontis is by last switching tube (S N1) and following switching tube (S N2) be in series; (for example, the brachium pontis in the top and high-pressure side electric capacity 1(C 1) parallel connection.This brachium pontis is by last switching tube (S 11) and following switching tube (S 12) be in series; N-1 switching capacity branch road, n switching capacity props up route switching capacity (C Sn) and resonant inductance (L Sn) be in series, this branch road one terminates between two switching tubes of n+1 brachium pontis, and the other end is connected between two switching tubes of n brachium pontis; (for example, the 1st switching capacity props up route switching capacity (C S1) and resonant inductance (L S1) be in series, this branch road one terminates between two switching tubes of the 2nd brachium pontis, and the other end is connected between two switching tubes of the 1st brachium pontis; ) LLC resonant network input port can be in parallel with any one switching tube.
Described current transformer uses symmetrical duty ratio control, each brachium pontis two pipe (S N1, S N2) control signal is the symmetrical complement signal, and certain Dead Time is arranged.Each switching tube (S 11, S 21..., S N1) duty ratio identical, be 50%.By frequency adjustment control output voltage.
Be similar to foregoing two-stage switching capacity DC-DC controlled resonant converter operation principle, multi-level pmultistage circuit has still kept advantages such as former limit switching tube Zero-voltage soft switch that the traditional LLC resonant circuit has and secondary diode zero-current soft switch.In addition, by utilizing switching capacity C Sn-1And series resonance inductance L Sn-1Every half period respectively with input capacitance C n, C N-1The in parallel switching, current transformer has been realized input capacitance C n, C N-1Between automatically equalizing voltage, thereby realized equal pressure between N the input capacitance.Therefore, the voltage stress of each brachium pontis switching tube is clamped at input voltage V In1/N, thereby reduced requirement to the switch tube device, be conducive to the occasion that current transformer is operated in the high voltage input.In addition, multilevel hierarchy also is conducive to current transformer is operated in requirements at the higher level to gain occasion.

Claims (10)

1. the DC-DC controlled resonant converter with automatically equalizing voltage function is characterized in that, comprising:
Switched-capacitor circuit is used for input voltage is carried out the integral multiple step-down, obtains intermediate voltage;
The LLC series resonant circuit is used for described intermediate voltage is carried out frequency conversion voltage adjusting, obtains output voltage.
2. DC-DC controlled resonant converter according to claim 1, it is characterized in that: described switched-capacitor circuit is formed by the cascade of a plurality of half-bridge submodule, and the intermediate node of adjacent two half-bridge submodules connects by the switching capacity module.
3. DC-DC controlled resonant converter according to claim 2, it is characterized in that: described half-bridge submodule is by capacitor C and two switching tube S 1～S 2Form; Wherein, switching tube S 1An end link to each other with an end of capacitor C and be an end of half-bridge submodule, switching tube S 1The other end and switching tube S 2An end link to each other and be the intermediate node of half-bridge submodule, switching tube S 2The other end link to each other with the other end of capacitor C and be the other end of half-bridge submodule, two switching tube S 1～S 2The control utmost point receive the switching signal of a pair of phase place complementation that external equipment provides, switching tube S respectively 2Two ends constitute the outlet side of half-bridge submodule.
4. DC-DC controlled resonant converter according to claim 2, it is characterized in that: described switching capacity module is by capacitor C sAnd inductance L sBe composed in series.
5. DC-DC controlled resonant converter according to claim 3 is characterized in that: described two switching tube S 1～S 2Adopt the anti-also power switch pipe of diode of band, the two ends of this power switch pipe are parallel with electric capacity.
6. DC-DC controlled resonant converter according to claim 1, it is characterized in that: described LLC series resonant circuit comprises resonant inductance L r, resonant capacitance C r, magnetizing inductance L m, transformer T and a secondary circuit; Wherein, resonant inductance L rAn end and resonance capacitor C rAn end constitute the voltage input side of LLC series resonant circuit, resonant inductance L rThe other end and magnetizing inductance L mAn end link to each other magnetizing inductance L mThe other end and resonant capacitance C rThe other end link to each other the former limit winding of transformer T and magnetizing inductance L mParallel connection, the secondary winding of transformer T and the corresponding connection of the input side of secondary circuit, described secondary circuit adopts full-wave rectifying circuit, half-wave rectifying circuit or full bridge rectifier.
7. DC-DC controlled resonant converter according to claim 6, it is characterized in that: described full-wave rectifying circuit is by output capacitance C oWith two conduction device D 1～D 2Form; Wherein, conduction device D 1Input link to each other the other end and the conduction device D of transformer T secondary winding with an end of transformer T secondary winding 2Input link to each other conduction device D 1Output and conduction device D 2Output and output capacitance C oAn end link to each other output capacitance C oThe other end link to each other with the centre tap end of transformer T secondary winding.
8. DC-DC controlled resonant converter according to claim 6, it is characterized in that: described half-wave rectifying circuit is by output capacitance C oForm with conduction device D; Wherein, the input of conduction device D links to each other with an end of transformer T secondary winding, the output of conduction device D and output capacitance C oAn end link to each other output capacitance C oThe other end link to each other with the other end of transformer T secondary winding.
9. DC-DC controlled resonant converter according to claim 6, it is characterized in that: described full bridge rectifier is by output capacitance C oWith four conduction device D 1～D 4Form; Wherein, conduction device D 1Input and conduction device D 2Output and an end of transformer T secondary winding link to each other conduction device D 1Output and conduction device D 3Output and output capacitance C oAn end link to each other conduction device D 3Input and conduction device D 4Output and the other end of transformer T secondary winding link to each other conduction device D 2Input and conduction device D 4Input and output capacitance C oThe other end link to each other.
10. DC-DC controlled resonant converter according to claim 6 is characterized in that: the voltage input side of described LLC series resonant circuit and the corresponding connection of the outlet side of arbitrary half-bridge submodule in the switched-capacitor circuit.
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