CN103296882B - A kind of DC-DC controlled resonant converter with automatically equalizing voltage function - Google Patents

A kind of DC-DC controlled resonant converter with automatically equalizing voltage function Download PDF

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CN103296882B
CN103296882B CN201310206558.0A CN201310206558A CN103296882B CN 103296882 B CN103296882 B CN 103296882B CN 201310206558 A CN201310206558 A CN 201310206558A CN 103296882 B CN103296882 B CN 103296882B
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CN103296882A (en
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李武华
罗清璟
罗皓泽
顾云杰
何湘宁
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Zhejiang University ZJU
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Zhejiang University ZJU
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Abstract

The invention discloses a kind of DC-DC controlled resonant converter with automatically equalizing voltage function, comprise switched-capacitor circuit and LLC series resonant circuit; Switched-capacitor circuit is formed by multiple half-bridge sub module cascade, and the intermediate node of adjacent two half-bridge submodules is by switching capacity model calling.In DC-DC converter of the present invention, after multiple half-bridge submodule series connection, be parallel to DC power supply two ends; In the ideal case, the voltage of each bus capacitor is n/mono-of direct current power source voltage; In parallel with bus capacitor after two switching tube series connection in half-bridge submodule, so the shutoff voltage stress of each switching tube is again 1/2nd of single bus capacitor voltage.Therefore converter of the present invention can select low pressure, high performance switching device, is conducive to the efficiency of Lifting Transform device, reduces the volume of converter.

Description

A kind of DC-DC controlled resonant converter with automatically equalizing voltage function
Technical field
The invention belongs to power converter technical field, be specifically related to a kind of DC-DC controlled resonant converter with automatically equalizing voltage function.
Background technology
In recent years, various power-supply device has been widely used in the industries such as communication, illumination, military project.In order to the power quality of specification power-supply device, some global academic organisations and country start to formulate and implement the standard of a series of power-supply device.The restriction harmonic pollution of power-supply device to AC network is one of important standard, as IEC555-2, IEEE519 etc.In order to meet harmonic standard, usually using multi-stage cascade type high-frequency converter in industry, and in first order rectifying installation, using power factor corrective circuit (Power FactorCorrection, PFC).
When using multi-stage cascade type high-frequency converter in three-phase electrical power system, the output busbar voltage of first order three-phase PFC rectifier converter is generally 600-800V, and even some occasion can up to 1000V.This makes the voltage stress of rear class converter breaker in middle device greatly increase.
Switched-capacitor circuit has the advantage of its uniqueness in high input voltage occasion, as shown in Figure 1; Between the half-bridge of two series connection, energy transferring is realized by utilizing switching capacity module, the voltage of upper and lower two input capacitances by clamped 1/2nd input voltage, thus the voltage stress of the power switch pipe of each half-bridge by clamped at 1/2nd of input voltage, be conducive to the application of low voltage power devices, thus reduction conduction loss, Lifting Transform efficiency.But the transformation ratio of switched-capacitor circuit is often the transformation ratio of integral multiple, cause its application very narrow; When input voltage changes time, cannot be obtained stable voltage by the method controlled and export, this is very disadvantageous in commercial Application.In addition, switched-capacitor circuit itself cannot realize the Sofe Switch of switching tube, thus causes larger switching loss, is unfavorable for the lifting of circuit efficiency.
In the prior art, traditional semibridge system LLC series resonant structure can realize high efficiency voltage transitions, as shown in Figure 2.It has the characteristic of Sofe Switch in full operating range, significantly reduces the switching loss of circuit, thus obtains higher conversion efficiency.In addition, in certain voltage range, LLC resonant circuit can realize the function of voltage-regulation voltage-stabilization by the adjustment of frequency.But the former limit switching tube stress of traditional semibridge system LLC series resonant structure is input voltage; And because high tension apparatus switching frequency is low, conducting resistance large, causing converter cannot meet the demand of high-efficient high performance, high tension apparatus cost compare is high simultaneously; In addition, along with the increase to high step-down applications demand, volume of transformer will increase, thus causes higher losses and lower power density.
Summary of the invention
For the above-mentioned technical problem existing for prior art, the invention provides a kind of DC-DC controlled resonant converter with automatically equalizing voltage function, automatically can realize electric voltage equalization, and switching device stress is low, the stability of a system is high.
There is a DC-DC controlled resonant converter for automatically equalizing voltage function, comprising:
Switched-capacitor circuit, for carrying out integral multiple step-down to input voltage, obtains intermediate voltage;
LLC series resonant circuit, for carrying out frequency conversion voltage adjusting to described intermediate voltage, obtains output voltage.
Described switched-capacitor circuit is formed by multiple half-bridge sub module cascade, and the intermediate node of adjacent two half-bridge submodules is by switching capacity model calling.
Described half-bridge submodule is by electric capacity C and two switching tube S 1~ S 2composition; Wherein, switching tube S 1one end be connected with one end of electric capacity C and be one end of half-bridge submodule, switching tube S 1the other end and switching tube S 2one end be connected and be the intermediate node of half-bridge submodule, switching tube S 2the other end be connected with the other end of electric capacity C and be the other end of half-bridge submodule, two switching tube S 1~ S 2control pole receive the switching signal of a pair phase complements that external equipment provides, switching tube S respectively 2two ends form the outlet side of half-bridge submodule.
The duty ratio of described switching signal is 50%.
Described switching capacity module is by electric capacity C scomposition or by electric capacity C sand inductance L sbe composed in series; Preferred employing electric capacity C sand inductance L scascaded structure, is conducive to reducing switching capacity branch road to the impulse current of bus capacitor discharge and recharge, reduces the pressure reduction between two bus capacitors, make the electric voltage equalization of two bus capacitors, can promote the performance of circuit.
Preferably, two described switching tube S 1~ S 2adopt band anti-and the power switch pipe of diode, the two ends of this power switch pipe are parallel with electric capacity; Can the voltage build-up rate of power-limiting switching tube blocking interval, reduce the turn-off power loss of power switch pipe; Utilize leakage inductance to open the energy on period extraction shunt capacitance at power switch pipe, the no-voltage that can realize all power switch pipes is open-minded, effectively reduces the conduction loss of switching tube simultaneously.
Described LLC series resonant circuit comprises resonant inductance L r, resonant capacitance C r, magnetizing inductance L m, transformer T and a secondary circuit; Wherein, resonant inductance L rone end and resonant capacitance C rone end form the voltage input side of LLC series resonant circuit, resonant inductance L rthe other end and magnetizing inductance L mone end be connected, magnetizing inductance L mthe other end and resonant capacitance C rthe other end be connected, the former limit winding of transformer T and magnetizing inductance L mparallel connection, the vice-side winding of transformer T is corresponding with the input side of secondary circuit to be connected, and described secondary circuit adopts full-wave rectifying circuit, half-wave rectifying circuit or full bridge rectifier.
Described full-wave rectifying circuit is by output capacitance C owith two conduction device D 1~ D 2composition; Wherein, conduction device D 1input be connected with one end of transformer T vice-side winding, the other end of transformer T vice-side winding and conduction device D 2input be connected, conduction device D 1output and conduction device D 2output and output capacitance C oone end be connected, output capacitance C othe other end be connected with the centre tap end of transformer T vice-side winding.
Described half-wave rectifying circuit is by output capacitance C oform with conduction device D; Wherein, the input of conduction device D is connected with one end of transformer T vice-side winding, the output of conduction device D and output capacitance C oone end be connected, output capacitance C othe other end be connected with the other end of transformer T vice-side winding.
Described full bridge rectifier is by output capacitance C owith four conduction device D 1~ D 4composition; Wherein, conduction device D 1input and conduction device D 2output be connected with one end of transformer T vice-side winding, conduction device D 1output and conduction device D 3output and output capacitance C oone end be connected, conduction device D 3input and conduction device D 4output be connected with the other end of transformer T vice-side winding, conduction device D 2input and conduction device D 4input and output capacitance C othe other end be connected.
Described conduction device adopts diode or switching tube.
The voltage input side of described LLC series resonant circuit is corresponding with the outlet side of half-bridge submodule arbitrary in switched-capacitor circuit to be connected.
In DC-DC converter of the present invention, after multiple half-bridge submodule series connection, be parallel to DC power supply two ends; In the ideal case, the voltage of each bus capacitor is n/mono-(n is half-bridge submodule number) of direct current power source voltage.In parallel with bus capacitor after two switching tube series connection in half-bridge submodule, so the shutoff voltage stress of each switching tube is again 1/2nd of single bus capacitor voltage.Therefore converter of the present invention can select low pressure, high performance switching device, is conducive to the efficiency of Lifting Transform device, reduces the volume of converter.
DC-DC converter of the present invention utilizes switching capacity branch road to connect the intermediate node of adjacent two half-bridge submodules, and such connected mode can realize the automatically equalizing voltage of DC side bus capacitor.The specific works process of Switch capacitor structure is: when first, the 3rd power switch pipe conducting time, in parallel with the first bus capacitor after the series connection of first, second capacitance branch road; When second, the 4th power switch pipe conducting time, in parallel with the second bus capacitor after the series connection of first, second capacitance branch road.In this parallel process, first, second capacitance branch road discharges to high-tension bus capacitor, charges to the bus capacitor of low-voltage, and the voltage of two bus capacitors finally can be made to reach balanced.
Compared with the existing conventional half-bridge formula structure DC-DC controlled resonant converter being applicable to high voltage bus occasion, the voltage of each device for power switching is reduced to the half of input voltage by DC-DC controlled resonant converter of the present invention, therefore can select low-voltage power switch device.Because low voltage power devices has the advantage that performance is good, cost is low, switching frequency is high, therefore the present invention can realize the DC-DC conversion of high-efficient high performance under high input voltage occasion.
Accompanying drawing explanation
Fig. 1 is the electrical block diagram of traditional switch capacitance decompression converter.
Fig. 2 is the electrical block diagram of conventional half-bridge formula DC-DC controlled resonant converter.
Fig. 3 is the electrical block diagram of DC-DC controlled resonant converter of the present invention.
Fig. 4 is the working waveform figure of DC-DC controlled resonant converter of the present invention.
Fig. 5 is the circuit theory schematic diagram of DC-DC controlled resonant converter of the present invention.
Fig. 6 is the structural representation after DC-DC controlled resonant converter N level of the present invention is expanded.
Embodiment
In order to more specifically describe the present invention, below in conjunction with the drawings and the specific embodiments, technical scheme of the present invention and related work principle thereof are described in detail.
As shown in Figure 3, a kind of DC-DC controlled resonant converter with automatically equalizing voltage function, comprises switched-capacitor circuit and coupled LLC series resonant circuit; Wherein:
Switched-capacitor circuit is used for input voltage V in(being provided by DC power supply E) carries out integral multiple step-down, obtains intermediate voltage V; In present embodiment, switched-capacitor circuit is formed by two half-bridge submodule H1 ~ H2 cascade, and the intermediate node of two half-bridge submodules is by switching capacity model calling.
Half-bridge submodule H1 is by electric capacity C 1with two metal-oxide-semiconductor S 1~ S 2composition; Wherein, metal-oxide-semiconductor S 1drain electrode be connected with one end of electric capacity C and be one end of half-bridge submodule H1, metal-oxide-semiconductor S 1source electrode and metal-oxide-semiconductor S 2drain electrode be connected and be the intermediate node of half-bridge submodule H1, metal-oxide-semiconductor S 2source electrode and electric capacity C 1the other end be connected and be the other end of half-bridge submodule H1, two metal-oxide-semiconductor S 1~ S 2grid receive the switching signal of a pair phase complements that external equipment provides, metal-oxide-semiconductor S respectively 2source and drain two ends form the outlet side of half-bridge submodule H1.
Half-bridge submodule H2 is by electric capacity C 2with two metal-oxide-semiconductor S 3~ S 4composition; Wherein, metal-oxide-semiconductor S 3drain electrode and electric capacity C 2one end be connected and be one end of half-bridge submodule H2, metal-oxide-semiconductor S 3source electrode and metal-oxide-semiconductor S 4drain electrode be connected and be the intermediate node of half-bridge submodule H2, metal-oxide-semiconductor S 4source electrode and electric capacity C 2the other end be connected and be the other end of half-bridge submodule H2, two metal-oxide-semiconductor S 3~ S 4grid receive the switching signal of a pair phase complements that external equipment provides, metal-oxide-semiconductor S respectively 4source and drain two ends form the outlet side of half-bridge submodule H2.
Switching capacity module is by electric capacity C sand inductance L sbe composed in series.
Four metal-oxide-semiconductor S 1~ S 4the duty ratio of the switching signal received is 50%, wherein, and metal-oxide-semiconductor S 1with metal-oxide-semiconductor S 3the switching signal received is identical, metal-oxide-semiconductor S 1with metal-oxide-semiconductor S 2the switching signal received is complementary, metal-oxide-semiconductor S 3with metal-oxide-semiconductor S 4the switching signal received is complementary.
Four metal-oxide-semiconductor S 1~ S 4equal parasitism is with anti-also diode, and the source and drain two ends of each metal-oxide-semiconductor are all parallel with electric capacity (parasitic capacitance).
LLC series resonant circuit is used for carrying out frequency conversion voltage adjusting to intermediate voltage V, obtains output voltage V out; In present embodiment, LLC series resonant circuit comprises resonant inductance L r, resonant capacitance C r, magnetizing inductance L m, transformer T and a secondary circuit; Wherein, resonant inductance L rone end and resonant capacitance C rone end form the voltage input side of LLC series resonant circuit, resonant inductance L rthe other end and magnetizing inductance L mone end be connected, magnetizing inductance L mthe other end and resonant capacitance C rthe other end be connected, the former limit winding of transformer T and magnetizing inductance L mparallel connection, the vice-side winding of transformer T is corresponding with the input side of secondary circuit to be connected, the vice-side winding centre tap of transformer T, and secondary circuit adopts full-wave rectifying circuit.
Full-wave rectifying circuit is by output capacitance C owith two diode D 1~ D 2composition; Wherein, diode D 1anode be connected with one end of transformer T vice-side winding, the other end of transformer T vice-side winding and diode D 2anode be connected, diode D 1negative electrode and diode D 2negative electrode and output capacitance C oone end be connected, output capacitance C othe other end be connected with the centre tap end of transformer T vice-side winding; Output capacitance C otwo ends shunt load R othus produce output voltage V out.
The voltage input side of LLC series resonant circuit connects with in switched-capacitor circuit, the outlet side of half-bridge submodule H1 is corresponding.
The power of the DC-DC controlled resonant converter of present embodiment is the input voltage at 1kW, DC power supply E two ends is 600V, load R othe output voltage at two ends requires as 48V.
Fig. 4 is drive waveforms and the work wave of the DC-DC controlled resonant converter of present embodiment.Wherein waveform V gs1~ V gs4metal-oxide-semiconductor S respectively 1~ S 4switching signal, V gs1with V gs3identical; V gs2with V gs1complementary; V gs4with V gs3complementary; V simultaneously gs1with V gs2between, V gs3with V gs4between each to have one section be low level Dead Time jointly.Waveform v ds1~ v ds4metal-oxide-semiconductor S respectively 1~ S 4drain-source voltage; i lrfor flowing through resonant inductance L relectric current, i lmfor flowing through magnetizing inductance L melectric current, i csfor flowing through switching capacity C selectric current, i s1~ i s4for flowing through metal-oxide-semiconductor S 1~ S 4electric current; i d1and i d2be respectively and flow through diode D 1and D 2electric current.
For LLC resonant slots, resonant inductance L rimpact can not ignore.Therefore, controlled resonant converter has two resonance links.A resonance link is by L r, C rform, its resonance frequency is f r; Another is by L m, L r, C rform, its resonance frequency is f m.The computing formula of two resonance frequencys is as follows:
f r = 1 2 π L k · C b
f m = 1 2 π ( L k + L m ) · C b
According to the difference of operating frequency, circuit can be divided into f m< f < f r, f=f r, f > f rthree operating frequency ranges.Wherein:
In these three frequency ranges, the no-voltage that all can realize power switch pipe is open-minded, thus reduces the turn-on consumption of switching tube.Simultaneously at f m< f < f rin service area, the electric current natural zero-crossing in secondary side diode, can realize zero-current switching, there is not reverse-recovery problems.Therefore f m< f < f rthe groundwork being present embodiment is interval, and as shown in Figure 4 and Figure 5, the specific works process of the DC-DC controlled resonant converter of present embodiment is as follows:
In a switch periods, have 6 working stages, wherein: working stage 1 ~ working stage 2 is metal-oxide-semiconductor S 1and S 3stabilization process during conducting; Working stage 3 is metal-oxide-semiconductor S 1and S 3commutation states during conducting; Working stage 4 ~ working stage 5 is metal-oxide-semiconductor S 2and S 4stabilization process during conducting; Working stage 6 is metal-oxide-semiconductor S 2and S 4commutation states during shutoff.
Working stage 1(t 0~ t 1): S 1with S 3start conducting, exciting current i lmlinear rising, leakage inductance current i lrrise with sinusoidal form, and i lrbe greater than i lm, both differences flow through transformer primary side, make secondary side diode D 1conducting, the original edge voltage of transformer is output voltage V outclamp.Therefore, LLC resonant slots only has leakage inductance L rwith electric capacity C rthere is resonance.
This stage switch electric capacity C swith input capacitance C 1parallel connection, C sto C 1charging.
Working stage 2(t 1~ t 2): at t 1moment, exciting current i lmequal leakage inductance current i lr.Secondary current drops to zero naturally, rectifier diode D 1realize zero-current switching.Output voltage V simultaneously outno longer clamped to transformer, magnetizing inductance L mbecome resonant inductance freely, therefore L m, L rwith C rthere is resonance.Because the cycle of this resonance is far longer than switch periods, thus within this stage i lrsteady state value can be regarded as.
Due to C swith L sbe in second order resonance condition, and there is no additional power source, therefore switching capacity branch current i cskeep original resonance trend to decline, be also and flow through S 3current i s3.In order to maintain i lrconstant, i s1equivalent increases thus, and output power of power supply increases.
Working stage 3(t 2~ t 3): at t 3moment, S 1and S 3start to turn off, enter Dead Time.Due to leakage inductance current i lrkeep constant, now switching tube junction capacitance C s1, C s3start charging, C s2, C s4start electric discharge.Work as C s2, C s4voltage be down to zero respectively after, S 2, S 4bypass diode conducting afterflow, be S 2and S 4no-voltage open and create conditions.
Working stage 4(t 3~ t 4): at t 3moment, S 2and S 4open-minded.I lrbe greater than i lm, both differences flow through transformer primary side, D 2conducting, the original edge voltage of transformer is by V outclamp, LLC resonant slots only has L rwith C rthere is resonance.
This stage switch electric capacity C swith input capacitance C 2parallel connection, C 2to C scharging.
Working stage 5(t 4~ t 5): at t 4moment, i lmequal i lr.Secondary current drops to zero naturally, rectifier diode D 2realize zero-current switching.V simultaneously outno longer clamped to transformer, L mbecome resonant inductance freely, therefore L m, L rwith C rthere is resonance.Because the cycle of this resonance is far longer than switch periods, thus within this stage i lrsteady state value can be regarded as.
Due to C swith L sbe in second order resonance condition, and there is no additional power source, therefore switching capacity branch current i cskeep original resonance trend to decline, be also and flow through S 3current i s4.In order to maintain i lrconstant, i s2equivalent increases thus, and output power of power supply increases.
Working stage 6(t 5~ t 6) at t 4moment, S 2and S 4start to turn off, enter Dead Time.Due to i lrkeep constant and be negative, now switching tube junction capacitance C s1, C s3start electric discharge, C s2, C s4start charging.Work as C s1, C s3voltage be down to zero respectively after, S 1, S 3bypass diode conducting afterflow, be S 1and S 3no-voltage open and create conditions.
The DC-DC controlled resonant converter of present embodiment can realize DC side bus capacitor voltage automatic equalization, can improve reliability when system is applied to high voltage DC-DC occasion.The specific implementation of its voltage automatic equalization ability is as follows: power switch tube S 1and S 3when opening, switching capacity C sand L swith bus capacitor C 1in parallel; Power switch tube S 2and S 4when opening, switching capacity C sand L swith bus capacitor C 2in parallel; In parallel process, C sand L shigh-tension bus capacitor is discharged, the bus capacitor of low-voltage is charged, finally reaches the effect of automatically equalizing voltage.
As shown in Figure 6, be equal die mould multiple-pole switch condenser network from the switched-capacitor circuit of the DC-DC controlled resonant converter of all pressing, switching capacity progression can be expanded.N level circuit after expansion is: the N(N>1) high-pressure side electric capacity (C of individual series connection 1, C 2..., C n), in parallel with high side power after series connection.Uppermost electric capacity (C 1) be called high-pressure side electric capacity 1, by that analogy, N number of electric capacity (C n) be called high-pressure side electric capacity N; N number of brachium pontis, the n-th brachium pontis and high-pressure side electric capacity n(C n) in parallel.Each brachium pontis is by upper switching tube (S n1) and lower switching tube (S n2) be in series; (such as, the brachium pontis in the top and high-pressure side electric capacity 1(C 1) in parallel.This brachium pontis is by upper switching tube (S 11) and lower switching tube (S 12) be in series; N-1 switching capacity branch road, the n-th switching capacity props up route switching capacity (C sn) and resonant inductance (L sn) be in series, this branch road one end is connected between (n+1)th brachium pontis, two switching tubes, and the other end is connected between the n-th brachium pontis two switching tubes; (such as, the 1st switching capacity props up route switching capacity (C s1) and resonant inductance (L s1) be in series, this branch road one end is connected between the 2nd brachium pontis two switching tubes, and the other end is connected between the 1st brachium pontis two switching tubes; ) LLC resonant network input port can with any one paralleled power switches.
Described current transformer uses symmetric duty ratio to control, and each brachium pontis two manages (S n1, S n2) control signal is symmetrical complement signal, has certain Dead Time.Each switching tube (S 11, S 21..., S n1) duty ratio identical, be 50%.Output voltage is controlled by frequency adjustment.
Be similar to foregoing two-stage switching capacity DC-DC controlled resonant converter operation principle, multi-level pmultistage circuit still maintains the advantage such as former limit switch tube zero voltage soft-switching and secondary side diode zero-current soft switch that traditional LLC resonant circuit has.In addition, by utilizing switching capacity C sn-1and series resonance inductor L sn-1every half period respectively with input capacitance C n, C n-1switching in parallel, current transformer achieves input capacitance C n, C n-1between automatically equalizing voltage, thus achieve all pressures between N number of input capacitance.Therefore, the voltage stress of each brachium pontis switching tube is clamped at input voltage V in1/N, thus reduce the requirement of switch tube device, be conducive to the occasion that current transformer is operated in high voltage input.In addition, multilevel hierarchy is also conducive to current transformer and is operated in occasion gain being had to requirements at the higher level.

Claims (4)

1. there is a DC-DC controlled resonant converter for automatically equalizing voltage function, it is characterized in that, comprising:
Switched-capacitor circuit, for carrying out integral multiple step-down to input voltage, obtains intermediate voltage;
LLC series resonant circuit, for carrying out frequency conversion voltage adjusting to described intermediate voltage, obtains output voltage;
Described switched-capacitor circuit is formed by multiple half-bridge sub module cascade, and the intermediate node of adjacent two half-bridge submodules is by switching capacity model calling; Described switching capacity module is by electric capacity C sand inductance L sbe composed in series;
Described half-bridge submodule is by electric capacity C 1with two switching tube S 1~ S 2composition; Wherein, switching tube S 1one end and electric capacity C 1one end be connected and be one end of half-bridge submodule, switching tube S 1the other end and switching tube S 2one end be connected and be the intermediate node of half-bridge submodule, switching tube S 2the other end and electric capacity C 1the other end be connected and be the other end of half-bridge submodule, two switching tube S 1~ S 2control pole receive the switching signal of a pair phase complements that external equipment provides, switching tube S respectively 2two ends form the outlet side of half-bridge submodule;
Two described switching tube S 1~ S 2adopt the power switch pipe of band anti-parallel diodes, the two ends of this power switch pipe are parallel with electric capacity;
Described LLC series resonant circuit comprises resonant inductance L r, resonant capacitance C r, magnetizing inductance L m, transformer T and a secondary circuit; Wherein, resonant inductance L rone end and resonant capacitance C rone end form the voltage input side of LLC series resonant circuit, resonant inductance L rthe other end and magnetizing inductance L mone end be connected, magnetizing inductance L mthe other end and resonant capacitance C rthe other end be connected, the former limit winding of transformer T and magnetizing inductance L mparallel connection, the vice-side winding of transformer T is corresponding with the input side of secondary circuit to be connected, and described secondary circuit adopts full-wave rectifying circuit, half-wave rectifying circuit or full bridge rectifier;
The voltage input side of described LLC series resonant circuit is corresponding with the outlet side of half-bridge submodule arbitrary in switched-capacitor circuit to be connected.
2. DC-DC controlled resonant converter according to claim 1, is characterized in that: described full-wave rectifying circuit is by output capacitance C owith two conduction device D 1~ D 2composition; Wherein, conduction device D 1input be connected with one end of transformer T vice-side winding, the other end of transformer T vice-side winding and conduction device D 2input be connected, conduction device D 1output and conduction device D 2output and output capacitance C oone end be connected, output capacitance C othe other end be connected with the centre tap end of transformer T vice-side winding.
3. DC-DC controlled resonant converter according to claim 1, is characterized in that: described half-wave rectifying circuit is by output capacitance C oform with conduction device D; Wherein, the input of conduction device D is connected with one end of transformer T vice-side winding, the output of conduction device D and output capacitance C oone end be connected, output capacitance C othe other end be connected with the other end of transformer T vice-side winding.
4. DC-DC controlled resonant converter according to claim 1, is characterized in that: described full bridge rectifier is by output capacitance C owith four conduction device D 1~ D 4composition; Wherein, conduction device D 1input and conduction device D 2output be connected with one end of transformer T vice-side winding, conduction device D 1output and conduction device D 3output and output capacitance C oone end be connected, conduction device D 3input and conduction device D 4output be connected with the other end of transformer T vice-side winding, conduction device D 2input and conduction device D 4input and output capacitance C othe other end be connected.
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