CN102364858B - Constant-current switching power supply controller capable of controlling through primary side and method - Google Patents
Constant-current switching power supply controller capable of controlling through primary side and method Download PDFInfo
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Abstract
The invention discloses a constant-current switching power supply controller capable of controlling through a primary side and a method. The constant-current switching power supply controller comprises a sampling hold module, a secondary diode turn-on time detection circuit, a multiplying unit module, an average current ring, a sawtooth wave generating module, a comparison module, a clocked flip-flop, a driving pulse generating module and a driving module. For the controller disclosed by the invention, an optical coupler and a secondary feedback circuit are not required and the output constant-current control can be realized only by detecting a primary current peak value, so the controller has good real-time performance, a control loop is easy to stabilize and the circuit has good dynamic performance. The constant-current switching power supply controller is applied to a place with the requirement on a power factor. Due to the adoption of fixed-frequency constant turn-on time control, a multiplying unit is not required, the structure is simple, and the high power factor of an input current in the full input range can be realized. Moreover, the circuit works under a fixed frequency, so that the constant-current switching power supply controller is easier to label by electromagnetic compatibility. Furthermore, the controller can be integrated into a single chip.
Description
Technical field
The invention belongs to the switch power technology field, relate to a kind of constant current switch power-supply controller of electric and method of former limit control.
Background technology
At present a lot of isolated supplies such as charger for mobile phone and high-power LED driver are because application demand requires circuit that the function of output constant current is arranged usually; In addition; In order to alleviate the extent of injury of electric pollution; Satisfy harmonic standard IEEE555-2 and IEC1000-3-2 of International Electrotechnical Commission etc.; Above-mentioned isolated supplies also must possess power factor correction (PFC) function, and Fig. 1 is a single-level power factor correction scheme relatively more commonly used at present: through detecting the output current of transformer secondary side, after secondary carries out constant current control, deliver to former limit PFC control circuit through the optocoupler feedback.Prior art scheme shown in Figure 1 has increased the complexity of circuit owing to the existence of secondary current sample circuit and optocoupler, further, because there is problem of aging in optocoupler, the stability of circuit and useful life all is under some influence.
Solution to the problems referred to above is to adopt the controlling schemes that has constant current control of former limit and power factor emendation function concurrently; Promptly need not secondary current sampling and optic coupling element; Directly through obtain the information of output current on the former limit of isolating transformer; Control and realize the output constant current, and realize High Power Factor simultaneously, as shown in Figure 2.The control chip that has at present had some can realize above-mentioned output constant current and PFC function on the market is like the ICL8001G of infineon company, the MP4020 of MPS, the LinkSwitch-PH series of PI etc.Yet these chips all adopt VFC pattern (electric current critical discontinuous mode), so the channel frequency fluctuation range is bigger, and are difficult through the Electro Magnetic Compatibility standard;
Input current was when said chip was applied to circuit of reversed excitation in addition:
Wherein
Convert the former limit of transformer voltage afterwards for output voltage, k is the current/voltage coefficient of correspondence, and D is a duty ratio, is the ratio of ON time and switch periods; Normalized output current wave in half power frequency period is as shown in Figure 3, wherein s=V
o'/V
Ac, can see that along with s diminishes promptly the input voltage amplitude increases, the wave distortion of input current is more severe, and power factor is low more.
Summary of the invention
The objective of the invention is the defective that exists in the above-mentioned prior art in order to overcome; A kind of constant current switch power-supply controller of electric and method of former limit control have been proposed; Simple in structure; Only need to detect the constant current control that the primary current peak value can be realized output current, can also in the full voltage input range, realize higher power factor; Circuit work frequency is constant in addition, therefore more easily through the Electro Magnetic Compatibility standard; The present invention also can be used for the small-power power that the reactive factor of direct current input requires, and realizes output constant current function.
The constant current switch power-supply controller of electric of former limit control comprises:
Sampling keeps module; Described sampling keeps the input of module to receive the output signal CS from the primary current sampling network of Switching Power Supply main circuit; An input of its output termination multiplication module; Described sampling keeps module to be used in each switch periods maintenances of sampling of primary current sampled signal, the peak value of the sampled signal of extraction primary current;
Secondary diode current flow time detection circuit; Described secondary diode current flow time detection circuit is according to receiving the signal TD from main circuit; Detecting the secondary diode has the time interval of electric current, and will detect the secondary diode and have the time interval signal of electric current to send to multiplication module;
Multiplication module; Described multiplication module receives sampling and keeps after the signal of module and secondary diode current flow time detection circuit; Exporting an amplitude keeps the output signal of module proportional with sampling; Duty ratio and cycle all with the identical rectangular pulse signal of output signal of secondary diode current flow time detection circuit, this output signal averaging and secondary diode current signal averaging are proportional;
The average current ring; Described average current articulating is received the output signal from multiplication module; An input of the output termination comparison module of average current ring, described average current ring are used for the inner voltage reference of the output signal averaging of multiplication module and average current ring is compared and error between the two is amplified;
The sawtooth waveforms generation module; The output of the said driving pulse generation module of input termination of described sawtooth waveforms generation module; The sawtooth waveforms generation module is switching tube conduction period generation sawtooth waveforms on the former limit of Switching Power Supply main circuit; The switching tube blocking interval on former limit, sawtooth waveforms generation module output low level;
Comparison module; The input of described comparison module receives the output signal of sawtooth waveforms generation module and the output signal of average electric current loop respectively; This comparison module compares the output signal of sawtooth waveforms generation module and the output signal of average electric current loop; When the output signal of sawtooth waveforms generation module rises to when equating with the output signal of average current ring; For high level, when the output signal of sawtooth waveforms generation module dropped to the output signal that is lower than the average current ring, comparison module output signal was low level from the high level upset to comparison module output signal from the low level upset;
Clocked flip-flop, described clocked flip-flop is used to produce the clock signal of fixed-frequency, outputs to the driving pulse generation module;
Driving pulse generation module, described driving pulse generation module are used for producing pulse signal according to the clock signal of the signal of comparison module output and clocked flip-flop output;
When low level of comparison module generation arrived the upset of high level, the pulse signal of driving pulse generation module reset to low level by high level; When the clock signal of clocked flip-flop output was high level by the low level upset, the pulse signal of driving pulse generation module was set to high level by low level; Go round and begin again, produce pulse train;
Driver module, described driver module are used to strengthen the ability of the former limit of the driving switching tube of said driving pulse generation module.
The input signal of described secondary diode current flow time detection circuit is from the signal that can embody the secondary diode current flow time in the circuit, as:
It is that a winding Na (auxiliary winding) from the main circuit transformer receives that described secondary diode current flow time detection circuit receives signal TD from main circuit.
It is that drain electrode from the former limit switching tube of main circuit is through receiving at a distance from straight/bleeder circuit that described secondary diode current flow time detection circuit receives signal TD from main circuit.
Described secondary diode current flow time detection circuit receives the anode of terminating diode Dc of the same name that signal TD from main circuit is the secondary winding of the current transformer CT from the secondary winding Ns circuit of main circuit, and the termination of the negative electrode connecting resistance Rc of diode Dc is received.
Described multiplication module can be multiplier or the equivalent electric circuit that can realize identical function.
Described average current ring comprises input resistance, voltage reference, compensating network and operational amplifier.
Further, said average current loop voltag benchmark can be the direct voltage benchmark, and average current loop voltag benchmark also can be the fixing half-sinusoid benchmark of amplitude when the Switching Power Supply main circuit is input as alternating current source.
Wherein, described Switching Power Supply main circuit is operated in discontinuous current (DCM) or critical discontinuous mode (BCM).
Wherein, the operational amplifier of described average current ring can be voltage-type or current mode (transconductance type).
Further, the compensating network of said average current ring can be pure integral element, also can be proportional integral link, perhaps PID link.
Wherein, said driver module is the push-pull configuration (totem structure) that two bipolar transistors or metal oxide semiconductor field effect tube constitute.
Control method of the present invention is:
(1) main circuit design through Switching Power Supply makes the Switching Power Supply main circuit be operated in discontinuous current or critical discontinuous state;
(2) to the maintenance of sampling of the former limit switched-current sampled signal of the main circuit of Switching Power Supply, extract main circuit primary current sampled peak; Detect the secondary diode current flow time simultaneously, said main circuit primary current sampled peak and secondary diode current flow time are multiplied each other, simulate and export the proportional current waveform of secondary diode current;
(3) through average current ring control, making the mean value of the signal that step (2) simulates is steady state value, thereby realizes the output current constant current.
Produce sawtooth waveforms when (4) carrying out above-mentioned steps; When sawtooth waveforms rises to when equating with the output signal amplitude of the said average current ring of step (3), obtain the shutoff triggering signal of the former limit switching tube of main circuit
Utilize the operating frequency of the switching tube of the Switching Power Supply that clocked flip-flop obtains to fix when (5) carrying out above-mentioned steps, utilize clocked flip-flop to produce the triggering signal that makes the switching tube conducting of former limit.
Beneficial effect of the present invention is: the constant current switch power-supply controller of electric and the method for former limit control of the present invention; Only need to detect the primary current peak value, need not optocoupler and secondary feedback circuit, can realize exporting constant current control; Therefore real-time is better; Control loop is stable easily, and the circuit dynamic property is better, and structure is simpler; Further, owing to adopt fixed frequently permanent ON time control, can realize the High Power Factor of input current in the full input range, and more easily through the Electro Magnetic Compatibility standard, this outer controller can be integrated into single-chip.
Description of drawings
Fig. 1 is the circuit of reversed excitation block diagram of traditional secondary constant current;
Fig. 2 is the circuit of reversed excitation block diagram of former limit constant current control;
Fig. 3 calculates waveform for the input current of the circuit of reversed excitation of employing VFC (critical conduction mode);
Fig. 4 controller circuitry block diagram of the present invention;
Fig. 5 (a) is the first specific embodiment circuit diagram of the current sample module 100 among the present invention;
Fig. 5 (b) is the working waveform figure of the first specific embodiment circuit of the current sample module 100 among the present invention;
Fig. 6 (a) is second kind of specific embodiment circuit diagram of the current sample module 100 among the present invention;
Fig. 6 (b) is the working waveform figure of second kind of specific embodiment circuit of the current sample module 100 among the present invention;
Fig. 7 (a) is the first specific embodiment circuit diagram of the present invention;
Fig. 7 (b) is the working waveform figure of the first specific embodiment circuit of the present invention;
Fig. 8 (a) is the second specific embodiment circuit diagram of the present invention;
Fig. 8 (b) is the working waveform figure of the second specific embodiment circuit of the present invention;
Fig. 9 is the 3rd specific embodiment circuit diagram among the present invention;
Figure 10 is the embodiment circuit diagram of the plurality of modules among the present invention;
Figure 11 is applied to the circuit diagram of a specific embodiment of the DC-DC transfer circuit of reactive factor requirement for the present invention;
Figure 12 be Figure 11 embodiment working waveform figure;
Figure 13 is applied to the circuit diagram of a specific embodiment of the ac-dc conversion circuit that power factor requires for the present invention;
Figure 14 is the working waveform figure of Figure 13 embodiment;
Figure 15 is applied to the sketch map of buck (buck-boost) circuit of non-isolation for the present invention.
Embodiment
Be elaborated below in conjunction with block diagram of the present invention and specific embodiment sketch map content of the present invention.
As shown in Figure 4, the constant current switch power-supply controller of electric of former limit control comprises:
Sampling keeps module 100; Described sampling keeps the input of module 100 to receive the output signal CS from the primary current sampling network 005 of Switching Power Supply main circuit; An input of its output termination secondary current analog module 300, described sampling keeps module 100 to be used in each switch periods primary current i
PriThe sampled signal maintenance of sampling, extract primary current i
PriThe peak value of sampled signal;
Secondary diode current flow time detection circuit 200; Described secondary diode current flow time detection circuit 200 is according to receiving the signal TD from the Switching Power Supply main circuit; Detecting the secondary diode has the time interval of electric current, and will detect the secondary diode and have the time interval signal of electric current to send to multiplication module 300;
Average current ring 400; Described average current ring 400 comprises input resistance Rf, compensating network, voltage reference Vref; The negative terminal input that the output of multiplication module 300 is received the operational amplifier Uf in the average current ring 400 through resistance R _ f, the input of operational amplifier Uf anode meets voltage reference Vref; Because average current ring 400 self has switch periods average value filtering effect, thus the operational amplifier negative terminal input signal of average current ring 400 be multiplication module 300 the output target signal filter mean value after the switch periods ripple; This signal and voltage reference Vref compare, and error is amplified through compensating network and operational amplifier between the two, an input of the output termination comparison module 600 of average current ring 400;
Sawtooth waveforms generation module 500; The output of the said driving pulse generation module of input termination of described sawtooth waveforms generation module; Sawtooth waveforms generation module 500 is at the former limit switching tube conduction period generation sawtooth waveforms of Switching Power Supply main circuit; The switching tube blocking interval on former limit, sawtooth waveforms generation module 500 output low levels;
Clocked flip-flop 700, described clocked flip-flop 700 is used for clocking, outputs to driving pulse generation module 800;
Driving pulse generation module 800, described driving pulse generation module 800 are used for producing pulse signal according to the clock signal of the signal of comparison module 600 outputs and clocked flip-flop 700 outputs; When low level of comparison module 600 generations arrived the upset of high level, the pulse signal of driving pulse generation module 800 reset to low level by high level; When the clock signal of clocked flip-flop 700 outputs was high level by the low level upset, the pulse signal of driving pulse generation module 800 was set to high level by low level; Go round and begin again, produce pulse train;
VDD connects main circuit externally fed power supply for detecting the power supply end of control circuit 008.
GND is for detecting the earth terminal of control circuit 008, will detect internally connecting with the ground of main circuit of control circuit through this terminal.
Fig. 5 (a) is the first specific embodiment circuit diagram of the maintenance of the sampling among the present invention module 100, and this circuit sampling module 100 adopts Chinese patents (publication number: CN 101615432).Fig. 5 (b) is the working waveform figure of the first specific embodiment circuit of the current sample module 100 among the present invention, and wherein Va is the input signal of peak sampling hold circuit, and Vb is the output signal of peak sampling hold circuit; Sampling keeps module also can adopt the circuit shown in Fig. 6 (a); The termination input signal Va of sampling switch Sa wherein, the positive input terminal of another termination capacitor Ca one end and amplifier Ua, the control termination control signal Vg of Sa; Capacitor Ca other end ground connection; The negative input end of amplifier links to each other with output, and the output signal representes that with Vb amplifier constitutes the forward follower; The work wave of the sampling hold circuit shown in Fig. 6 (a) is shown in Fig. 6 (b).
Secondary diode current flow time detection circuit 200 mainly is used for detecting the time interval that has electric current to flow through in the secondary diode; Receive mode difference according to described secondary diode current flow time detection circuit 200, can take following three kinds of schemes from the signal TD of main circuit:
Scheme one: realize secondary diode current flow time detection circuit 200 through detecting the auxiliary winding positive voltage of main circuit transformer, it is that a winding Na (auxiliary winding) from the main circuit transformer receives that promptly described secondary diode current flow time detection circuit 200 receives signal TD from main circuit.Shown in Fig. 7 (a), main waveform is shown in Fig. 7 (b).Wherein transformer is assisted the former border district of winding termination of the same name, different name termination positive level testing circuit input, and positive level testing circuit output termination time delay process input, the output of time delay process is as the output of secondary diode current flow time detection circuit 200; When the secondary diode current flow flows through current i
SecThe time, auxiliary winding voltage Vaux is a high level, and is interval through the high level time that detects auxiliary winding, can indirect detection go out the time interval that the secondary diode has electric current to flow through; Consider i in the side circuit
SecThere are certain lead in zero crossing and auxiliary winding voltage Vaux zero crossing, and Fig. 7 (a) realizes that after the positive level testing circuit, having introduced a time delay process in the circuit compensates; Another kind method is to improve the reference level of positive level testing circuit to reduce secondary diode current flow time detecting error; The positive level testing circuit can or simply extract the auxiliary winding forward voltage of transformer with diode and realize with the comparator realization among Fig. 7 (a).
Scheme two: through detecting the source-drain electrode voltage waveform V of main circuit switch pipe 004
QdsRealize secondary diode current flow time detection circuit 200, that is, it is that drain electrode from the former limit switching tube of main circuit is through receiving at a distance from straight/bleeder circuit 010 that described secondary diode current flow time detection circuit 200 receives signal TD from main circuit.Shown in Fig. 8 (a), main waveform is shown in Fig. 8 (b).I wherein
SecBe the secondary diode current, V
In_dcIt is input supply voltage; Source-drain electrode voltage V with switching tube 004
QdsThrough carry out after the direct sum dividing potential drop, obtaining detection signal V at a distance from straight/bleeder circuit 010
TD,, carry out the flow through time interval of electric current of the promptly roughly corresponding secondary diode of high level that differential ratio obtains after through comparator Ub, consider i in the side circuit equally
SecThere is certain lead in the zero crossing of zero crossing and comparator Ub output high level, and Fig. 8 (a) realizes that after comparator Ub, having introduced a time delay process in the circuit compensates.
Scheme three: realize secondary diode current flow time detection circuit 200 through direct detection secondary diode current; Promptly; The signal TD that described secondary diode current flow time detection circuit receives from main circuit is the anode of the terminating diode Dc of the same name of the current transformer CT secondary winding from the inferior limit winding Ns circuit of main circuit, and the termination of the negative electrode connecting resistance Rc of diode Dc is received.As shown in Figure 9; The negative terminal of the termination output capacitance of the same name of the former limit of current transformer CT winding; The end of the same name of the different name termination transformer secondary winding of the former limit of current transformer CT winding; The anode of the terminating diode Dc of the same name of current transformer CT secondary winding, the end of the negative electrode connecting resistance Rc of diode Dc and the positive input terminal of comparator Ub, the different name end of current transformer CT secondary winding and the other end ground connection of resistance R c; The negative input end ground connection of comparator Ub, the output of comparator is as the output of secondary diode current flow time detection circuit 200.
Sawtooth waveforms generation module 500 comprises DC current source IDC, capacitor Cs and switch S c, and is shown in figure 10; Wherein DC current source IDC can obtain through known technology; The input termination direct voltage source VDD of DC current source IDC; The end of output termination capacitor Cs and the end of switch S c link to each other as the output of sawtooth waveforms generation module 500; Ground connection after the other end of the other end of capacitor Cs and switch S c links to each other; The reversed-phase output
of the control termination driving and generating module 800 of switch S c when the control end level be high level; Switch S c conducting remains zero with capacitor Cs voltage; When the control end level is a high level, switch S c turn-offs, and DC current source IDC gives capacitor Cs charging, produces sawtooth signal.The sawtooth signal that produces when sawtooth waveforms generation module 500 touches the output level of average current ring 400, and the output level of comparison module 600 is high level from the low level upset.The sawtooth signal slope that sawtooth waveforms generation module 500 produces is fixed, the width of sawtooth signal corresponding the ON time of former limit switching tube 004, therefore for the output level amplitude of specific average current ring 400, the ON time of former limit switching tube 004 is constant.When the application that has power factor to require, constant when the ON time of former limit switching tube 004, the input signal that the current waveform envelope of former limit switching tube 004 is followed circuit of reversed excitation is and the half-sinusoid signal, thereby realizes High Power Factor.
Clocked flip-flop 700 produces the burst pulse of fixed-frequency, and this pulse frequency has determined the operating frequency of circuit, and clocked flip-flop 700 concrete realization circuit belong to known technology.
Driving pulse generation module 800 can adopt rest-set flip-flop to realize; Shown in figure 10; Wherein the R pin connects the output of comparison module 600; The S pin connects the output of clocked flip-flop 700: when low level of comparison module 600 generations arrived the upset of high level, the output signal of driving pulse generation module 800 reset to low level by high level; When low level of clocked flip-flop 700 generations arrived the upset of high level, the output signal of driving pulse generation module 800 was set to high level by low level, so goes round and begins again, and produces output pulse sequence.
The output of driving pulse generation module 800 is delivered to the gate pole of the former limit of inverse-excitation type led driver switching tube Q1 through driver module 900, and the concrete realization circuit of driving pulse generation module 800 belongs to known technology.
Figure 11 is applied to the circuit diagram of a specific embodiment of DC-DC transfer circuit for the present invention; Wherein the input power supply of main circuit adopts DC power supply Vdc; Transformer adopting three winding constructions; Promptly increased an auxiliary winding Taux, sampling keeps module 100 to adopt circuit shown in Fig. 5 (a), and secondary diode current detection module 200 employing schemes are same as shown in Figure 7.
Figure 12 is the working waveform figure of Figure 11 embodiment, wherein, and v
400Be the output waveform of average current ring 400, v
600Be the output waveform of sawtooth waveforms generation module 600, v
700Be the output waveform of clocked flip-flop 700, i
PriIt is the former limit of circuit of reversed excitation switching tube current waveform.i
SecBe circuit of reversed excitation secondary diode stream waveform, V
GS_Q1And V
GS_saBe respectively the drive waveforms of circuit of reversed excitation switching tube 004 and the control end waveform of switch S a, v
100Be the output waveform that sampling keeps module 100, v
TauxBe the voltage waveform of the auxiliary winding of transformer, v
300It is the output waveform of multiplication module 300.
Figure 13 is applied to the circuit diagram of a specific embodiment of the ac-dc conversion circuit that power factor requires for the present invention; Wherein, Main circuit input power supply adopts AC power Vac (001); The output of Vac connects two inputs of rectifier bridge B1, and the positive output of rectifier bridge B1 connects the end of capacitor Cin and the end of the same name and an end that absorbs network 002 of transformer 003, and the other end of the negative output of rectifier bridge B1 and capacitor Cin all connects former border district; Cin is the polarity free capacitor of low capacity, and other part of main circuit and controller module realize that circuit is with embodiment illustrated in fig. 11 identical.
Figure 14 is the working waveform figure of Figure 13 embodiment, wherein, and v
200It is the output waveform of secondary diode current detection module 200.Suppose that the former limit of main circuit transformer umber of turn is Np, the secondary number of turn is Ns, and former limit circuit sampling coefficient is K
1, can know by Figure 12 and Figure 14:
Be the output v of multiplication module 300
300Mean value be proportional to output current mean value I
oCan know by equation (2), as long as will
Send into average current ring 300, compare, can indirect regulation export average current, thereby realize the output current constant current with the benchmark Vref that sets.Because the average current ring self has filter function, as long as with v
300Send into average current ring 400, can obtain v at the operational amplifier input of average current ring 400
300Mean value
Also can increase the one-level filter circuit with average electric current loop 300, but circuit function is not had influence basically in the output of multiplication module 300.
Be applied to the ac-dc conversion circuit that power factor requires for the present invention, suppose that input voltage is U
InTherefore sin (ω t) can obtain the mean value of input current:
Wherein, Lm is the transformer excitation inductance, and Ton is the switching tube ON time, and T is a switch periods., therefore exchange primary voltage and be directly proportional with input voltage waveform fully down because switching tube ON time Ton is constant, and switch periods T is constant for certain specific input voltage, thereby realize High Power Factor.
The present invention can be applied to isolated form output, also can be applied to non-isolation type output.Figure 15 is applied to the sketch map of buck (buck-boost) circuit of non-isolation for the present invention; Wherein, the concrete realization of each module can be with reference to the specific embodiment shown in figure 7～Figure 10.
Concrete module that the present invention includes such as current sample-and-hold circuit 100, secondary diode current flow time detecting module 200, multiplication module 300 etc.; Those skilled in the art can be under the prerequisite of its spirit; Numerous embodiments can be arranged; Or, form different specific embodiments through various compound mode, be not described in detail here.
No matter how detailed the preceding text explanation is, and many mode embodiment of the present invention can be arranged in addition, and described in the specification is a practical implementation example of the present invention.All equivalent transformations that spirit is done according to the present invention or modification all should be encompassed within protection scope of the present invention.
The above-mentioned detailed description of the embodiment of the invention be not exhaustive or be used to limit the present invention to above-mentioned clear and definite in form.Above-mentioned with schematic purpose specific embodiment of the present invention and instance are described in, those skilled in the art will recognize that and can carry out various equivalent modifications within the scope of the invention.
At above-mentioned declarative description specific embodiment of the present invention and having described in the anticipated optimal set pattern, no matter how detailed explanation appearred hereinbefore, also can be implemented in numerous ways the present invention.The details of foregoing circuit structure and control mode thereof is carried out in the details at it can carry out considerable variation, yet it still is included among the present invention disclosed herein.
Should be noted that as above-mentioned that employed specific term should not be used to be illustrated in when explanation some characteristic of the present invention or scheme defines this term here again with restriction of the present invention some certain features, characteristic or the scheme relevant with this term.In a word, should be with the terminological interpretation of in the claims of enclosing, using for the present invention not being limited to disclosed specific embodiment in the specification, only if above-mentioned detailed description part defines these terms clearly.Therefore, actual range of the present invention not only comprises the disclosed embodiments, also is included among claims.
Claims (15)
1. the constant current switch power-supply controller of electric of former limit control is characterized in that comprising:
Sampling keeps module; Described sampling keeps the input of module to receive the output signal CS from the primary current sampling network of Switching Power Supply main circuit; An input of its output termination multiplication module; Described sampling keeps module to be used in each switch periods maintenances of sampling of primary current sampled signal, the peak value of the sampled signal of extraction primary current;
Secondary diode current flow time detection circuit; Described secondary diode current flow time detection circuit is according to receiving the signal TD from main circuit; Detecting the secondary diode has the time interval of electric current, and will detect the secondary diode and have the time interval signal of electric current to send to multiplication module;
Multiplication module; Described multiplication module receives sampling and keeps after the signal of module and secondary diode current flow time detection circuit; Exporting an amplitude keeps the output signal of module proportional with sampling; Duty ratio and cycle all with the identical rectangular pulse signal of output signal of secondary diode current flow time detection circuit, the output signal averaging and the secondary diode current signal averaging of this multiplication module are proportional;
The average current ring; Described average current articulating is received the output signal from multiplication module; An input of the output termination comparison module of average current ring, described average current ring are used for the inner voltage reference of the output signal averaging of multiplication module and average current ring is compared and error between the two is amplified;
The sawtooth waveforms generation module; The output of the input termination driving pulse generation module of described sawtooth waveforms generation module; The sawtooth waveforms generation module is switching tube conduction period generation sawtooth waveforms on the former limit of Switching Power Supply main circuit, the switching tube blocking interval on former limit, sawtooth waveforms generation module output low level;
Comparison module; The input of described comparison module receives the output signal of sawtooth waveforms generation module and the output signal of average electric current loop respectively; This comparison module compares the output signal of sawtooth waveforms generation module and the output signal of average electric current loop; When the output signal of sawtooth waveforms generation module rises to when equating with the output signal of average current ring; For high level, when the output signal of sawtooth waveforms generation module dropped to the output signal that is lower than the average current ring, comparison module output signal was low level from the high level upset to comparison module output signal from the low level upset;
Clocked flip-flop, described clocked flip-flop is used to produce the clock signal of fixed-frequency, outputs to the driving pulse generation module;
The driving pulse generation module; Two inputs of described driving pulse generation module connect the output of comparison module and the output of clocked flip-flop respectively, and the driving pulse generation module produces pulse signal according to the signal of comparison module output and the clock signal of clocked flip-flop output; When low level of comparison module generation arrived the upset of high level, the pulse signal of driving pulse generation module reset to low level by high level; When the clock signal of clocked flip-flop output was high level by the low level upset, the pulse signal of driving pulse generation module was set to high level by low level; Go round and begin again, produce pulse train;
Driver module, the input of described driver module connects the output of driving pulse generation module, is used to strengthen the ability of the former limit of the driving switching tube of said driving pulse generation module.
2. controller according to claim 1 is characterized in that it is that auxiliary winding from the main circuit transformer receives that described secondary diode current flow time detection circuit receives signal TD from main circuit.
3. controller according to claim 1 is characterized in that it is that drain electrode from the former limit switching tube of main circuit is through receiving at a distance from straight/bleeder circuit that described secondary diode current flow time detection circuit receives signal TD from main circuit.
4. controller according to claim 1; It is characterized in that described average current ring comprises input resistance, voltage reference, compensating network and operational amplifier; The negative terminal input that the output of multiplication module is received the operational amplifier in the average current ring through resistance R _ f, the input of operational amplifier Uf anode meets voltage reference Vref.
5. like the said controller of claim 4, it is characterized in that said average current loop voltag benchmark can be the direct voltage benchmark, average current loop voltag benchmark also can be the fixing half-sinusoid benchmark of amplitude when the Switching Power Supply main circuit is input as alternating current source.
6. controller according to claim 1, the operational amplifier that it is characterized in that described average current ring can be voltage-type or current mode.
7. controller according to claim 1, the compensating network that it is characterized in that said average current ring is pure integral element, proportional integral link, perhaps a kind of in the PID link.
8. the constant current switch power supply of former limit control comprises main circuit and controller, and said main circuit is isolated form or non-isolation type topology, comprises the input rectifying bridge, and switching tube, primary current sampling network is characterized in that said controller comprises:
Sampling keeps module; Described sampling keeps the input of module to receive the output signal CS from the primary current sampling network of Switching Power Supply main circuit; An input of its output termination multiplication module; Described sampling keeps module to be used in each switch periods maintenances of sampling of primary current sampled signal, the peak value of the sampled signal of extraction primary current;
Secondary diode current flow time detection circuit; Described secondary diode current flow time detection circuit is according to receiving the signal TD from main circuit; Detecting the secondary diode has the time interval of electric current, and will detect the secondary diode and have the time interval signal of electric current to send to multiplication module;
Multiplication module; Described multiplication module receives sampling and keeps after the signal of module and secondary diode current flow time detection circuit; Exporting an amplitude keeps the output signal of module proportional with sampling; Duty ratio and cycle all with the identical rectangular pulse signal of output signal of secondary diode current flow time detection circuit, the output signal averaging and the secondary diode current signal averaging of this multiplication module are proportional;
The average current ring; Described average current articulating is received the output signal from multiplication module; An input of the output termination comparison module of average current ring, described average current ring are used for the inner voltage reference of the output signal averaging of multiplication module and average current ring is compared and error between the two is amplified;
The sawtooth waveforms generation module; The output of the said driving pulse generation module of input termination of described sawtooth waveforms generation module; The sawtooth waveforms generation module is switching tube conduction period generation sawtooth waveforms on the former limit of Switching Power Supply main circuit; The switching tube blocking interval on former limit, sawtooth waveforms generation module output low level;
Comparison module; The input of described comparison module receives the output signal of sawtooth waveforms generation module and the output signal of average electric current loop respectively; This comparison module compares the output signal of sawtooth waveforms generation module and the output signal of average electric current loop; When the output signal of sawtooth waveforms generation module rises to when equating with the output signal of average current ring; For high level, when the output signal of sawtooth waveforms generation module dropped to the output signal that is lower than the average current ring, comparison module output signal was low level from the high level upset to comparison module output signal from the low level upset;
Clocked flip-flop, described clocked flip-flop is used to produce the clock signal of fixed-frequency, outputs to the driving pulse generation module;
Driving pulse generation module, described driving pulse generation module are used for producing pulse signal according to the clock signal of the signal of comparison module output and clocked flip-flop output;
When low level of comparison module generation arrived the upset of high level, the pulse signal of driving pulse generation module reset to low level by high level; When the clock signal of clocked flip-flop output was high level by the low level upset, the pulse signal of driving pulse generation module was set to high level by low level; Go round and begin again, produce pulse train;
Driver module, described driver module are used to strengthen the ability of the former limit of the driving switching tube of said driving pulse generation module.
9. like the said Switching Power Supply of claim 8, it is characterized in that it is that auxiliary winding from the main circuit transformer receives that said secondary diode current flow time detection circuit receives signal TD from main circuit.
10. like the said Switching Power Supply of claim 8, it is characterized in that it is that drain electrode from the former limit switching tube of main circuit is through receiving at a distance from straight/bleeder circuit that described secondary diode current flow time detection circuit receives signal TD from main circuit.
11. like the said Switching Power Supply of claim 8; It is characterized in that described average current ring comprises input resistance, voltage reference, compensating network and operational amplifier; The negative terminal input that the output of multiplication module is received the operational amplifier in the average current ring through resistance R _ f, the input of operational amplifier Uf anode meets voltage reference Vref.
12. like the said Switching Power Supply of claim 8, it is characterized in that said average current loop voltag benchmark can be the direct voltage benchmark, average current loop voltag benchmark also can be the fixing half-sinusoid benchmark of amplitude when the Switching Power Supply main circuit is input as alternating current source.
13. like the said Switching Power Supply of claim 8, the operational amplifier that it is characterized in that described average current ring can be voltage-type or current mode.
14. like the said Switching Power Supply of claim 8, the compensating network that it is characterized in that said average current ring is pure integral element, proportional integral link, perhaps a kind of in the PID link.
15. be operated in discontinuous current or critical discontinuous mode like the said Switching Power Supply main circuit of claim 8.
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| CN201110034597A CN102364858B (en) | 2011-02-01 | 2011-02-01 | Constant-current switching power supply controller capable of controlling through primary side and method |
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| CN102983553B (en) * | 2012-11-19 | 2015-11-18 | Tcl王牌电器(惠州)有限公司 | Switching Power Supply overload protection method and device |
| CN103152951B (en) * | 2013-03-13 | 2015-07-08 | 绍兴光大芯业微电子有限公司 | LED (light emitting diode) driving control circuit and driving circuit structure of LED driving control circuit |
| WO2014170976A1 (en) * | 2013-04-17 | 2014-10-23 | 三菱電機株式会社 | Switching power supply circuit and control method therefor |
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| CN105846701B (en) * | 2016-04-29 | 2019-02-15 | 杭州士兰微电子股份有限公司 | Constant-current control circuit, constant-current drive circuit and constant current control method |
| CN108964464B (en) * | 2017-05-19 | 2022-11-29 | 上海芯熠微电子有限公司 | Circuit and method for nondestructive testing of load current at output side of switching power supply |
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| CN109039093B (en) * | 2018-09-29 | 2024-01-23 | 杰华特微电子股份有限公司 | Isolation type switching power supply and control method thereof |
| CN112397016B (en) * | 2019-08-16 | 2022-02-22 | 华润微集成电路(无锡)有限公司 | Line voltage compensation circuit and compensation method thereof |
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| US7876583B2 (en) * | 2008-12-22 | 2011-01-25 | Power Integrations, Inc. | Flyback power supply with forced primary regulation |
| CN101841250B (en) * | 2010-04-27 | 2012-08-15 | 上海新进半导体制造有限公司 | Switching power supply control circuit and primary winding-controlled flyback switching power supply |
| CN101873750B (en) * | 2010-06-25 | 2013-11-13 | 深圳市欣锐特科技有限公司 | LED (light emitting diode) lamp fault processing method, LED driver and LED lamp |
| CN101944856B (en) * | 2010-07-13 | 2013-01-23 | 上海新进半导体制造有限公司 | Control circuit of switching power supply for primary side control |
| CN101925236B (en) * | 2010-08-20 | 2013-06-05 | 杭州电子科技大学 | Isolated high-power factor flyback type primary-side constant-current control device of LED driver |
| CN101951716B (en) * | 2010-09-30 | 2013-04-03 | 杭州电子科技大学 | Constant-on-time primary side constant-current control device for LED driver with high power factor |
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