CN102364858B - Constant-current switching power supply controller capable of controlling through primary side and method - Google Patents
Constant-current switching power supply controller capable of controlling through primary side and method Download PDFInfo
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Abstract
本发明公开了一种原边控制的恒流开关电源控制器及方法。所述的恒流开关电源控制器包括:采样保持模块、副边二极管导通时间检测电路、乘法器模块、平均电流环、锯齿波产生模块、比较模块、定时触发器、驱动脉冲产生模块和驱动模块。本发明的控制器,无需光耦和副边反馈电路,只需检测原边电流峰值,即可实现输出恒流控制,因此实时性较好,控制环路容易稳定,电路动态性能较好,应用于有功率因数要求的场合,由于采用定频恒导通时间控制,无需乘法器,结构简单,可以实现全输入范围内输入电流的高功率因数,此外由于电路是定频工作,更加容易通过电磁兼容标注;进一步,所述控制器可以集成为单芯片。
The invention discloses a constant current switching power supply controller and method for primary side control. The constant current switching power supply controller includes: a sampling and holding module, a secondary diode conduction time detection circuit, a multiplier module, an average current loop, a sawtooth wave generation module, a comparison module, a timing trigger, a driving pulse generation module and a drive module. The controller of the present invention does not need an optocoupler and a secondary side feedback circuit, and only needs to detect the peak value of the primary side current to realize output constant current control, so the real-time performance is good, the control loop is easy to stabilize, and the circuit dynamic performance is good. For occasions with power factor requirements, due to the use of constant frequency constant on-time control, no multiplier is required, the structure is simple, and high power factor of the input current within the full input range can be achieved. In addition, because the circuit works at a fixed frequency, it is easier to pass through the electromagnetic Compatible marking; further, the controller can be integrated into a single chip.
Description
技术领域 technical field
本发明属于开关电源技术领域,涉及一种原边控制的恒流开关电源控制器及方法。The invention belongs to the technical field of switching power supplies, and relates to a primary side controlled constant current switching power supply controller and a method.
背景技术 Background technique
目前很多隔离型电源如手机充电器和大功率的LED驱动器由于应用需求通常要求电路有输出恒流的功能;此外,为了减轻电力污染的危害程度,满足国际电工委员会的谐波标准IEEE555-2和IEC1000-3-2等,上述隔离型电源还必须具备功率因数校正(PFC)功能,图1为目前比较常用的单级功率因数校正方案:通过检测变压器副边侧的输出电流,在副边进行恒流控制之后经光耦反馈送到原边PFC控制电路。图1所示现有技术方案由于副边电流采样电路和光耦的存在,增加了电路的复杂性,进一步,由于光耦存在老化问题,使电路的稳定性和使用寿命都受到一定影响。At present, many isolated power supplies such as mobile phone chargers and high-power LED drivers usually require the circuit to have the function of outputting constant current due to application requirements; IEC1000-3-2, etc., the above-mentioned isolated power supply must also have the power factor correction (PFC) function. Figure 1 shows a commonly used single-stage power factor correction scheme: by detecting the output current on the secondary side of the transformer, the power factor correction is performed on the secondary side. After constant current control, it is fed back to the primary side PFC control circuit through the optocoupler. The existing technical scheme shown in FIG. 1 increases the complexity of the circuit due to the existence of the secondary current sampling circuit and the optocoupler. Furthermore, due to the aging problem of the optocoupler, the stability and service life of the circuit are affected to a certain extent.
针对上述问题的解决方案是采用兼具原边恒流控制和功率因数校正功能的控制方案,即无需副边电流采样和光耦元件,直接通过在隔离变压器的原边获得输出电流的信息,加以控制实现输出恒流,并且同时实现高功率因数,如图2所示。目前市面上已经有一些能实现上述输出恒流和PFC功能的控制芯片,如infineon公司的ICL8001G、MPS的MP4020、PI的LinkSwitch-PH系列等。然而这些芯片都采用变频控制模式(电流临界断续模式),因此电路频率波动范围较大,比较难通过电磁兼容性标准;The solution to the above problems is to adopt a control scheme with both primary side constant current control and power factor correction functions, that is, without secondary side current sampling and optocoupler components, and directly obtain output current information on the primary side of the isolation transformer to control Realize output constant current, and realize high power factor at the same time, as shown in Figure 2. At present, there are already some control chips on the market that can realize the above output constant current and PFC functions, such as ICL8001G from Infineon, MP4020 from MPS, LinkSwitch-PH series from PI, etc. However, these chips all adopt frequency conversion control mode (current critical intermittent mode), so the circuit frequency fluctuation range is relatively large, and it is difficult to pass the electromagnetic compatibility standard;
另外上述芯片应用于反激电路时输入电流为:In addition, when the above chip is applied to the flyback circuit, the input current is:
其中为输出电压折算到变压器原边之后的电压,k为电流电压对应系数,D为占空比,为导通时间与开关周期的比值;半个工频周期内的归一化的输出电流波形如图3所示,其中s=Vo’/Vac,可以看到随着s变小,即输入电压幅值增大,输入电流的波形失真越厉害,功率因数越低。in It is the voltage after converting the output voltage to the primary side of the transformer, k is the corresponding coefficient of current and voltage, D is the duty cycle, and is the ratio of the conduction time to the switching period; the normalized output current waveform in half a power frequency cycle is as follows As shown in Figure 3, where s=V o '/V ac , it can be seen that as s becomes smaller, that is, the amplitude of the input voltage increases, the waveform distortion of the input current is more severe, and the power factor is lower.
发明内容 Contents of the invention
本发明的目的是为了克服上述现有技术中存在的缺陷,提出了一种原边控制的恒流开关电源控制器及方法,结构简单,只需检测原边电流峰值即可实现输出电流的恒流控制,还可以在全电压输入范围内实现较高的功率因数;此外电路工作频率恒定,因此更容易通过电磁兼容性标准;本发明还可用于直流输入的无功率因数要求的小功率电源,实现输出恒流功能。The purpose of the present invention is to overcome the defects in the above-mentioned prior art, and propose a constant current switching power supply controller and method for primary side control, which has a simple structure and can realize constant output current only by detecting the peak value of the primary side current. Current control can also achieve a higher power factor in the full voltage input range; in addition, the circuit operating frequency is constant, so it is easier to pass the electromagnetic compatibility standard; the invention can also be used for low-power power supplies with no power factor requirements for DC input, Realize output constant current function.
原边控制的恒流开关电源控制器包括:Primary-side controlled constant current switching power supply controllers include:
采样保持模块,所述的采样保持模块的输入端接收来自开关电源主电路的原边电流采样网络的输出信号CS,其输出端接乘法器模块的一个输入端,所述的采样保持模块用于在每个开关周期对原边电流采样信号进行采样保持,提取原边电流的采样信号的峰值;Sample and hold module, the input terminal of the sample and hold module receives the output signal CS from the primary side current sampling network of the switching power supply main circuit, and its output terminal is connected to an input terminal of the multiplier module, and the described sample and hold module is used for Sample and hold the primary current sampling signal in each switching cycle, and extract the peak value of the primary current sampling signal;
副边二极管导通时间检测电路,所述的副边二极管导通时间检测电路根据接收到来自主电路的信号TD,检测出副边二极管有电流的时间区间,并将检测出副边二极管有电流的时间区间信号发送给乘法器模块;The secondary diode conduction time detection circuit, the secondary diode conduction time detection circuit detects the time interval during which the secondary diode has current according to the signal TD received from the main circuit, and detects the time interval during which the secondary diode has current The time interval signal is sent to the multiplier module;
乘法器模块,所述的乘法器模块接收到采样保持模块及副边二极管导通时间检测电路的信号之后,输出一幅值与采样保持模块的输出信号成比例,占空比和周期都与副边二极管导通时间检测电路的输出信号相同的矩形脉冲信号,该输出信号平均值与副边二极管电流信号平均值成比例;A multiplier module, after the multiplier module receives the signals of the sample-and-hold module and the conduction time detection circuit of the secondary side diode, an output value is proportional to the output signal of the sample-and-hold module, and the duty cycle and period are all related to the secondary The output signal of the side diode conduction time detection circuit is the same as the rectangular pulse signal, and the average value of the output signal is proportional to the average value of the secondary side diode current signal;
平均电流环,所述的平均电流环接收来自乘法器模块的输出信号,平均电流环的输出端接比较模块的一个输入端,所述的平均电流环用于对乘法器模块的输出信号平均值与平均电流环内部的电压基准进行比较并对二者之间误差加以放大;The average current loop, the average current loop receives the output signal from the multiplier module, the output terminal of the average current loop is connected to an input terminal of the comparison module, and the average current loop is used to average the output signal of the multiplier module Compare with the voltage reference inside the average current loop and amplify the error between the two;
锯齿波产生模块,所述的锯齿波产生模块的输入端接所述驱动脉冲产生模块的输出端,锯齿波产生模块在开关电源主电路原边开关管导通期间产生锯齿波,在原边开关管关断期间,锯齿波产生模块输出低电平;A sawtooth wave generation module, the input terminal of the sawtooth wave generation module is connected to the output end of the drive pulse generation module, the sawtooth wave generation module generates a sawtooth wave during the conduction period of the primary switch tube of the main circuit of the switching power supply, and the primary side switch tube During shutdown, the sawtooth wave generating module outputs low level;
比较模块,所述的比较模块的输入分别接收锯齿波产生模块的输出信号和平均电流环的输出信号,该比较模块对锯齿波产生模块的输出信号和平均电流环的输出信号进行比较,当锯齿波产生模块的输出信号上升到与平均电流环的输出信号相等时,比较模块输出信号从低电平翻转为高电平,当锯齿波产生模块的输出信号下降到低于平均电流环的输出信号时,比较模块输出信号从高电平翻转为低电平;Comparison module, the input of the comparison module receives the output signal of the sawtooth wave generation module and the output signal of the average current loop respectively, the comparison module compares the output signal of the sawtooth wave generation module and the output signal of the average current loop, when the sawtooth When the output signal of the wave generation module rises to be equal to the output signal of the average current loop, the output signal of the comparison module flips from low level to high level, and when the output signal of the sawtooth wave generation module drops below the output signal of the average current loop When , the output signal of the comparison module flips from high level to low level;
定时触发器,所述的定时触发器用于产生频率固定的时钟信号,输出到驱动脉冲产生模块;A timing trigger, the timing trigger is used to generate a clock signal with a fixed frequency, which is output to the driving pulse generation module;
驱动脉冲产生模块,所述的驱动脉冲产生模块用于根据比较模块输出的信号和定时触发器输出的时钟信号来产生脉冲信号;A driving pulse generating module, the driving pulse generating module is used to generate a pulse signal according to the signal output by the comparison module and the clock signal output by the timing trigger;
当比较模块产生一个低电平到高电平的翻转时,驱动脉冲产生模块的脉冲信号由高电平复位到低电平;当定时触发器输出的时钟信号由低电平翻转为高电平时,驱动脉冲产生模块的脉冲信号由低电平置位到高电平;周而复始,产生脉冲序列;When the comparison module produces a low-level to high-level reversal, the pulse signal of the driving pulse generation module is reset from high level to low level; when the clock signal output by the timing trigger is reversed from low level to high level , the pulse signal of the driving pulse generating module is set from low level to high level; repeating and beginning to generate a pulse sequence;
驱动模块,所述的驱动模块用于增强所述驱动脉冲产生模块的驱动原边开关管的能力。A driving module, the driving module is used to enhance the ability of the driving pulse generating module to drive the primary switching tube.
所述的副边二极管导通时间检测电路的输入信号来自电路中能体现副边二极管导通时间的信号,如:The input signal of the secondary diode conduction time detection circuit comes from a signal that can reflect the secondary diode conduction time in the circuit, such as:
所述的副边二极管导通时间检测电路接收到来自主电路的信号TD是从主电路变压器的一个绕组Na(辅助绕组)接收的。The signal TD received by the secondary diode conduction time detection circuit from the main circuit is received from a winding Na (auxiliary winding) of the main circuit transformer.
所述的副边二极管导通时间检测电路接收到来自主电路的信号TD是从主电路的原边开关管的漏极经隔直/分压电路接收的。The signal TD received from the main circuit by the conduction time detection circuit of the secondary diode is received from the drain of the primary switch tube of the main circuit through the DC blocking/voltage dividing circuit.
所述的副边二极管导通时间检测电路接收到来自主电路的信号TD是从主电路的副边绕组Ns电路中的电流互感器CT的副边绕组的同名端接二极管Dc的阳极,二极管Dc的阴极接电阻Rc的一端接收的。The signal TD received by the secondary diode conduction time detection circuit from the main circuit is from the secondary winding of the current transformer CT in the secondary winding Ns circuit of the main circuit. The cathode is received by one end of the resistor Rc.
所述的乘法器模块可以是乘法器或者能实现相同功能的等效电路。The multiplier module may be a multiplier or an equivalent circuit capable of realizing the same function.
所述的平均电流环包括输入电阻、电压基准、补偿网络和运算放大器。The average current loop includes input resistance, voltage reference, compensation network and operational amplifier.
进一步,所述平均电流环电压基准可以是直流电压基准,当开关电源主电路输入为交流源时平均电流环电压基准也可以是幅值固定的正弦半波基准。Further, the average current loop voltage reference may be a DC voltage reference, and when the main circuit input of the switching power supply is an AC source, the average current loop voltage reference may also be a sine half-wave reference with a fixed amplitude.
其中,所述的开关电源主电路工作在电流断续(DCM)或临界断续模式(BCM)。Wherein, the switching power supply main circuit works in discontinuous current mode (DCM) or critical discontinuous mode (BCM).
其中,所述的平均电流环的运算放大器可以是电压型或电流型(跨导型)。Wherein, the operational amplifier of the average current loop can be a voltage type or a current type (transconductance type).
进一步,所述平均电流环的补偿网络可以为纯积分环节,也可以为比例积分环节,或者比例积分微分环节。Further, the compensation network of the average current loop may be a pure integral link, or a proportional integral link, or a proportional integral derivative link.
其中,所述驱动模块是两个双极晶体管或金属氧化物半导体场效应管构成的推挽结构(图腾柱结构)。Wherein, the driving module is a push-pull structure (totem pole structure) composed of two bipolar transistors or metal oxide semiconductor field effect transistors.
本发明的控制方法为:Control method of the present invention is:
(1)通过开关电源的主电路设计使开关电源主电路工作在电流断续或者临界断续状态;(1) Through the design of the main circuit of the switching power supply, the main circuit of the switching power supply works in an intermittent or critical intermittent state;
(2)对开关电源的主电路的原边开关电流采样信号进行采样保持,提取主电路原边电流采样峰值;同时检测出副边二极管导通时间,将所述主电路原边电流采样峰值与副边二极管导通时间相乘,模拟出与输出副边二极管电流成比例的电流波形;(2) sample and hold the primary switching current sampling signal of the main circuit of the switching power supply, extract the primary current sampling peak value of the main circuit; detect the conduction time of the secondary side diode simultaneously, and compare the primary current sampling peak value of the main circuit with The conduction time of the secondary diodes is multiplied to simulate a current waveform proportional to the output secondary diode current;
(3)通过平均电流环控制,使步骤(2)模拟出的信号的平均值为恒定值,从而实现输出电流恒流。(3) Through the average current loop control, the average value of the signal simulated in step (2) is kept constant, thereby realizing the constant output current.
(4)进行上述步骤的同时产生锯齿波;当锯齿波上升到与步骤(3)所述平均电流环的输出信号幅值相等时,获得主电路的原边开关管的关断触发信号(4) produce sawtooth wave while carrying out above-mentioned steps; When sawtooth wave rises to be equal to the output signal amplitude of average current loop described in step (3), obtain the turn-off trigger signal of the primary switch tube of main circuit
(5)进行上述步骤的同时利用定时触发器来获得固定的开关电源的开关管的工作频率,利用定时触发器产生使原边开关管导通的触发信号。(5) While carrying out the above steps, use a timing trigger to obtain a fixed working frequency of the switching tube of the switching power supply, and use the timing trigger to generate a trigger signal to turn on the primary side switching tube.
本发明的有益效果在于:本发明的原边控制的恒流开关电源控制器及方法,只需检测原边电流峰值,无需光耦和副边反馈电路,即可实现输出恒流控制,因此实时性较好,控制环路容易稳定,电路动态性能较好,结构更加简单;进一步,由于采用定频恒导通时间控制,可以实现全输入范围内输入电流的高功率因数,并且更容易通过电磁兼容性标准,此外控制器可以集成为单芯片。The beneficial effect of the present invention is that: the constant current switching power supply controller and method of the primary side control of the present invention can realize the output constant current control only by detecting the peak value of the primary side current without optocoupler and secondary side feedback circuit, so real-time The control loop is easy to be stable, the dynamic performance of the circuit is better, and the structure is simpler; furthermore, due to the use of constant frequency and constant on-time control, the high power factor of the input current in the full input range can be achieved, and it is easier to pass the electromagnetic Compatibility standard, in addition the controller can be integrated as a single chip.
附图说明 Description of drawings
图1为传统的副边恒流的反激电路框图;Fig. 1 is a block diagram of a conventional secondary side constant current flyback circuit;
图2为原边恒流控制的反激电路框图;Fig. 2 is a block diagram of the flyback circuit of primary side constant current control;
图3为采用变频控制(临界导通模式)的反激电路的输入电流计算波形;Fig. 3 is the input current calculation waveform of the flyback circuit adopting frequency conversion control (critical conduction mode);
图4本发明控制器电路框图;Fig. 4 block diagram of the controller circuit of the present invention;
图5(a)为本发明中的电流采样模块100的第一具体实施例电路示意图;FIG. 5(a) is a schematic circuit diagram of a first specific embodiment of the
图5(b)为本发明中的电流采样模块100的第一具体实施例电路的工作波形图;FIG. 5(b) is a working waveform diagram of the circuit of the first specific embodiment of the
图6(a)为本发明中的电流采样模块100的第二种具体实施例电路示意图;Fig. 6 (a) is the circuit schematic diagram of the second specific embodiment of the
图6(b)为本发明中的电流采样模块100的第二种具体实施例电路的工作波形图;Fig. 6 (b) is the working waveform diagram of the circuit of the second specific embodiment of the
图7(a)为本发明的第一具体实施例电路示意图;Fig. 7 (a) is the circuit diagram of the first specific embodiment of the present invention;
图7(b)为本发明的第一具体实施例电路的工作波形图;Fig. 7 (b) is the working waveform diagram of the circuit of the first specific embodiment of the present invention;
图8(a)为本发明的第二具体实施例电路示意图;Fig. 8 (a) is the circuit schematic diagram of the second specific embodiment of the present invention;
图8(b)为本发明的第二具体实施例电路的工作波形图;Fig. 8 (b) is the working waveform diagram of the circuit of the second specific embodiment of the present invention;
图9为本发明中的第三具体实施例电路示意图;9 is a schematic circuit diagram of a third embodiment of the present invention;
图10为本发明中的若干模块的实施例电路示意图;FIG. 10 is a schematic circuit diagram of an embodiment of several modules in the present invention;
图11为本发明应用于无功率因数要求的直流-直流变换电路的一个具体实施例的电路示意图;Fig. 11 is a schematic circuit diagram of a specific embodiment of the present invention applied to a DC-DC conversion circuit without power factor requirements;
图12为图11实施例的的工作波形图;Fig. 12 is a working waveform diagram of Fig. 11 embodiment;
图13为本发明应用于有功率因数要求的交流-直流变换电路的一个具体实施例的电路示意图;FIG. 13 is a schematic circuit diagram of a specific embodiment of the present invention applied to an AC-DC conversion circuit with power factor requirements;
图14为图13实施例的工作波形图;Fig. 14 is the working waveform diagram of Fig. 13 embodiment;
图15为本发明应用于非隔离的升降压(buck-boost)电路的示意图。FIG. 15 is a schematic diagram of the present invention applied to a non-isolated buck-boost circuit.
具体实施方式 Detailed ways
以下结合本发明框图以及具体实施例示意图本发明内容进行详细说明。The content of the present invention will be described in detail below in conjunction with the block diagram of the present invention and the schematic diagrams of specific embodiments.
如图4所示,原边控制的恒流开关电源控制器包括:As shown in Figure 4, the constant current switching power supply controller controlled by the primary side includes:
采样保持模块100,所述的采样保持模块100的输入端接收来自开关电源主电路的原边电流采样网络005的输出信号CS,其输出端接副边电流模拟模块300的一个输入端,所述的采样保持模块100用于在每个开关周期对原边电流ipri的采样信号进行采样保持,提取原边电流ipri的采样信号的峰值;Sample and
副边二极管导通时间检测电路200,所述的副边二极管导通时间检测电路200根据接收到来自开关电源主电路的信号TD,检测出副边二极管有电流的时间区间,并将检测出副边二极管有电流的时间区间信号发送给乘法器模块300;The secondary diode conduction
乘法器模块300,所述的乘法器模块300接收到采样保持模块100及副边二极管导通时间检测电路200的信号之后,输出一幅值与采样保持模块的输出信号成比例,占空比和周期都与副边二极管导通时间检测电路的输出信号相同的矩形脉冲信号,该输出信号平均值与副边二极管电流信号平均值成比例;The
平均电流环400,所述的平均电流环400包括输入电阻Rf、补偿网络、电压基准Vref,乘法器模块300的输出经电阻Rf接到平均电流环400中的运算放大器Uf的负端输入,运算放大器Uf正端输入接电压基准Vref;由于平均电流环400自身具有开关周期平均值滤波效果,因此平均电流环400的运算放大器负端输入信号为乘法器模块300的输出信号滤除了开关周期纹波之后的平均值;该信号与电压基准Vref进行比较,二者之间误差经补偿网络和运算放大器加以放大,平均电流环400的输出端接比较模块600的一个输入端;Average
锯齿波产生模块500,所述的锯齿波产生模块的输入端接所述驱动脉冲产生模块的输出端,锯齿波产生模块500在开关电源主电路的原边开关管导通期间产生锯齿波,在原边开关管关断期间,锯齿波产生模块500输出低电平;The sawtooth
比较模块600,比较模块600包括比较器Uc,比较器Uc的负端输入接平均电流环400的输出,比较器Uc的正端输入接锯齿波产生模块500的输出;比较模块600对锯齿波产生模块500的输出信号和平均电流环400的输出信号进行比较,当锯齿波产生模块500的输出信号上升到与平均电流环400的输出信号相等时,比较模块600输出从低电平翻转为高电平,当锯齿波产生模块的输出信号下降到低于平均电流环的输出信号时,比较模块输出信号从高电平翻转为低电平;
定时触发器700,所述的定时触发器700用于产生时钟信号,输出到驱动脉冲产生模块800;Timing flip-
驱动脉冲产生模块800,所述的驱动脉冲产生模块800用于根据比较模块600输出的信号和定时触发器700输出的时钟信号来产生脉冲信号;当比较模块600产生一个低电平到高电平的翻转时,驱动脉冲产生模块800的脉冲信号由高电平复位到低电平;当定时触发器700输出的时钟信号由低电平翻转为高电平时,驱动脉冲产生模块800的脉冲信号由低电平置位到高电平;周而复始,产生脉冲序列;The driving
驱动模块900,所述的驱动模块900用于增强所述驱动脉冲产生模块800的驱动原边开关管004的能力。The
VDD为检测控制电路008的供电电源端,接主电路外部供电电源。VDD is the power supply end of the detection control circuit 008, which is connected to the external power supply of the main circuit.
GND为检测控制电路008的接地端,通过该端子将检测控制电路的内部地与主电路的地连接一起。GND is the ground terminal of the detection control circuit 008, through which the internal ground of the detection control circuit is connected with the ground of the main circuit.
图5(a)为本发明中的采样保持模块100的第一具体实施例电路示意图,该电路采样模块100采用中国专利(公开号:CN 101615432)。图5(b)为本发明中的电流采样模块100的第一具体实施例电路的工作波形图,其中Va为峰值采样保持电路的输入信号,Vb是峰值采样保持电路的输出信号;采样保持模块也可采用如图6(a)所示的电路,其中采样开关Sa的一端接输入信号Va,另一端接电容器Ca一端和运放Ua的正输入端,Sa的控制端接控制信号Vg,电容器Ca另一端接地,运放的负输入端与输出端相连,输出信号用Vb表示,运放构成正向跟随器;图6(a)所示的采样保持电路的工作波形如图6(b)所示。Fig. 5(a) is a schematic circuit diagram of the first specific embodiment of the sampling and holding
副边二极管导通时间检测电路200主要用来检测副边二极管中有电流流过的时间区间,根据所述的副边二极管导通时间检测电路200接收到来自主电路的信号TD的方式不同,可以采取下述三种方案:The secondary diode conduction
方案一:通过检测主电路变压器辅助绕组正电压实现副边二极管导通时间检测电路200,即所述的副边二极管导通时间检测电路200接收到来自主电路的信号TD是从主电路变压器的一个绕组Na(辅助绕组)接收的。如图7(a)所示,主要波形如图7(b)所示。其中变压器辅助绕组同名端接原边地,异名端接正电平检测电路输入端,正电平检测电路输出端接延时环节输入端,延时环节的输出作为副边二极管导通时间检测电路200的输出;当副边二极管导通流过电流isec时,辅助绕组电压Vaux为高电平,通过检测辅助绕组的高电平时间区间,即可间接检测出副边二极管有电流流过的时间区间;考虑到实际电路中isec过零点与辅助绕组电压Vaux过零点存在一定的提前量,图7(a)实现电路中在正电平检测电路之后引入了一个延时环节进行补偿;另一种方法是提高正电平检测电路的参考电平以降低副边二极管导通时间检测误差;图7(a)中正电平检测电路可用比较器实现或简单用二极管来提取变压器辅助绕组正向电压实现。Option 1: Realize the secondary diode conduction
方案二:通过检测主电路开关管004的源漏极电压波形VQds来实现副边二极管导通时间检测电路200,即,所述的副边二极管导通时间检测电路200接收到来自主电路的信号TD是从主电路的原边开关管的漏极经隔直/分压电路010接收的。如图8(a)所示,主要波形如图8(b)所示。其中isec是副边二极管电流,Vin_dc是输入电源电压;将开关管004的源漏极电压VQds经隔直/分压电路010进行隔直和分压之后,获得检测信号VTD,,经比较器Ub进行差分比较后获得的高电平即大致对应副边二极管流经电流的时间区间,同样考虑实际电路中isec过零点与比较器Ub输出高电平的过零点存在一定的提前量,图8(a)实现电路中在比较器Ub之后引入了一个延时环节进行补偿。Solution 2: Realize the secondary diode conduction
方案三:通过直接检测副边二极管电流来实现副边二极管导通时间检测电路200,即,所述的副边二极管导通时间检测电路接收到来自主电路的信号TD是从主电路的次边绕组Ns电路中的电流互感器CT副边绕组的同名端接二极管Dc的阳极,二极管Dc的阴极接电阻Rc的一端接收的。如图9所示,电流互感器CT原边绕组的同名端接输出电容的负端,电流互感器CT原边绕组的异名端接变压器副边绕组的同名端,电流互感器CT副边绕组的同名端接二极管Dc的阳极,二极管Dc的阴极接电阻Rc的一端和比较器Ub的正输入端,电流互感器CT副边绕组的异名端和电阻Rc的另一端接地,比较器Ub的负输入端接地,比较器的输出端作为副边二极管导通时间检测电路200的输出。Solution 3: Realize the secondary diode conduction
锯齿波产生模块500包括直流电流源IDC、电容器Cs和开关Sc,如图10所示;其中直流电流源IDC可通过公知技术得到;直流电流源IDC的输入端接直流电压源VDD,输出端接电容器Cs的一端和开关Sc的一端相连作为锯齿波产生模块500的输出端,电容器Cs的另一端和开关Sc的另一端相连之后接地,开关Sc的控制端接驱动产生模块800的反相输出端当控制端电平为高电平,开关Sc导通,将电容器Cs两端电压保持为零;当控制端电平为高电平,开关Sc关断,直流电流源IDC给电容器Cs充电,产生锯齿波信号。当锯齿波产生模块500产生的锯齿波信号触及到平均电流环400的输出电平,比较模块600的输出电平从低电平翻转为高电平。锯齿波产生模块500产生的锯齿波信号斜率固定,锯齿波信号的宽度对应着原边开关管004的导通时间,因此对于特定的平均电流环400的输出电平幅值,原边开关管004的导通时间恒定。在有功率因数要求的应用时,当原边开关管004的导通时间恒定,原边开关管004的电流波形包络线跟随反激电路的输入信号为与正弦半波信号,从而实现高功率因数。The sawtooth
定时触发器700产生频率固定的窄脉冲,该脉冲频率决定了电路的工作频率,定时触发器700具体实现电路属于公知技术。The timing flip-
驱动脉冲产生模块800可采用RS触发器实现,如图10所示,其中R脚接比较模块600的输出,S脚接定时触发器700的输出:当比较模块600产生一个低电平到高电平的翻转时,驱动脉冲产生模块800的输出信号由高电平复位到低电平;当定时触发器700产生一个低电平到高电平的翻转时,驱动脉冲产生模块800的输出信号由低电平置位到高电平,如此周而复始,产生输出脉冲序列。The driving
驱动脉冲产生模块800的输出经驱动模块900送到反激式LED驱动器原边开关管Q1的门极,驱动脉冲产生模块800的具体实现电路属于公知技术。The output of the driving
图11为本发明应用于直流-直流变换电路的一个具体实施例的电路示意图,其中主电路的输入电源采用直流电源Vdc,变压器采用三绕组结构,即增加了一个辅助绕组Taux,采样保持模块100采用图5(a)所示电路,副边二极管电流检测模块200采用方案与图7所示相同。Fig. 11 is a circuit schematic diagram of a specific embodiment of the present invention applied to a DC-DC conversion circuit, wherein the input power of the main circuit adopts a DC power supply Vdc, the transformer adopts a three-winding structure, that is, an auxiliary winding Taux is added, and the sample and hold
图12为图11实施例的工作波形图,其中,v400是平均电流环400的输出波形,v600是锯齿波产生模块600的输出波形,v700是定时触发器700的输出波形,ipri是反激电路原边开关管电流波形。isec是反激电路副边二极管流波形,VGS_Q1和VGS_sa分别是反激电路开关管004的驱动波形和开关Sa的控制端波形,v100是采样保持模块100的输出波形,vTaux是变压器辅助绕组的电压波形,v300是乘法器模块300的输出波形。Fig. 12 is the working waveform diagram of Fig. 11 embodiment, wherein, v 400 is the output waveform of average
图13为本发明应用于有功率因数要求的交流-直流变换电路的一个具体实施例的电路示意图,其中,主电路输入电源采用交流电源Vac(001),Vac的输出接整流桥B1的两个输入,整流桥B1的正输出接电容器Cin的一端以及变压器003的同名端和吸收网络002的一端,整流桥B1的负输出与电容器Cin的另一端都接原边地,Cin为小容量的无极性电容,主电路其它部分以及控制器模块实现电路与图11所示实施例相同。Fig. 13 is the circuit schematic diagram of a specific embodiment of the present invention applied to the AC-DC conversion circuit with power factor requirements, wherein, the main circuit input power adopts the AC power supply Vac (001), and the output of Vac is connected to the two rectifier bridges B1 Input, the positive output of the rectifier bridge B1 is connected to one end of the capacitor Cin, the same-named end of the
图14为图13实施例的工作波形图,其中,v200是副边二极管电流检测模块200的输出波形。假设主电路变压器原边绕组匝数为Np,副边匝数为Ns,原边电路采样系数为K1,由图12和图14可知:FIG. 14 is a working waveform diagram of the embodiment in FIG. 13 , where v 200 is the output waveform of the secondary diode
即乘法器模块300的输出v300的平均值正比于输出电流平均值Io;由方程(2)可知,只要将送入平均电流环300,与设定的基准Vref进行比较,即可间接调节输出平均电流,从而实现输出电流恒流。由于平均电流环自身具有滤波功能,只要将v300送入平均电流环400,即可在平均电流环400的运算放大器输入端获得v300的平均值也可以在乘法器模块300的输出和平均电流环300增加一级滤波电路,但对电路功能基本没有影响。That is, the average value of the output v 300 of the
对于本发明应用于有功率因数要求的交流-直流变换电路,假设输入电压为Uinsin(ωt),因此可以得到输入电流的平均值:For the application of the present invention to an AC-DC converter circuit with power factor requirements, it is assumed that the input voltage is U in sin(ωt), so the average value of the input current can be obtained:
其中,Lm是变压器激磁电感,Ton为开关管导通时间,T为开关周期。对于某特定输入电压下由于开关管导通时间Ton恒定,开关周期T恒定,因此交流进线电压完全与输入电压波形成正比,从而实现高功率因数。Among them, Lm is the excitation inductance of the transformer, Ton is the conduction time of the switch tube, and T is the switching period. For a certain input voltage, due to the constant conduction time Ton of the switch tube and the constant switching period T, the AC incoming line voltage is completely proportional to the input voltage wave, thereby achieving a high power factor.
本发明可以应用到隔离型输出,也可以应用到非隔离型输出。图15为本发明应用于非隔离的升降压(buck-boost)电路的示意图;其中,各模块的具体实现可参考图7~图10中所示的具体实施例。The present invention can be applied to isolated output, and can also be applied to non-isolated output. FIG. 15 is a schematic diagram of the present invention applied to a non-isolated buck-boost circuit; wherein, the specific implementation of each module can refer to the specific embodiments shown in FIGS. 7 to 10 .
本发明包括的具体模块如电流采样保持电路100、副边二极管导通时间检测模块200、乘法器模块300等,本领域技术人员可以在不违背其精神的前提下,可以有多种实施方式,或通过各种不同的组合方式,形成不同的具体实施例,这里不再详细描述。The specific modules included in the present invention, such as the current sampling and holding
无论上文说明如何详细,还有可以有许多方式实施本发明,说明书中所述的只是本发明的一个具体实施例子。凡根据本发明精神实质所做的等效变换或修饰,都应涵盖在本发明的保护范围之内。No matter how detailed the above description is, there are still many ways to implement the present invention, and what is described in the specification is only a specific implementation example of the present invention. All equivalent changes or modifications made according to the spirit of the present invention shall fall within the protection scope of the present invention.
本发明实施例的上述详细说明并不是穷举的或者用于将本发明限制在上述明确的形式上。在上述以示意性目的说明本发明的特定实施例和实例的同时,本领域技术人员将认识到可以在本发明的范围内进行各种等同修改。The above detailed description of embodiments of the invention is not intended to be exhaustive or to limit the invention to the precise forms described above. While specific embodiments of, and examples for, the invention were described above for illustrative purposes, various equivalent modifications are possible within the scope of the invention, those skilled in the relevant art will recognize.
在上述说明描述了本发明的特定实施例并且描述了预期最佳模式的同时,无论在上文中出现了如何详细的说明,也可以许多方式实施本发明。上述电路结构及其控制方式的细节在其执行细节中可以进行相当多的变化,然而其仍然包含在这里所公开的本发明中。While the above description describes particular embodiments of the invention and describes the best mode contemplated, no matter how detailed the foregoing description appears, the invention can be practiced in many ways. The details of the above-described circuit structure and its control manner may vary considerably in its implementation details, yet it is still included in the invention disclosed herein.
如上述一样应当注意,在说明本发明的某些特征或者方案时所使用的特殊术语不应当用于表示在这里重新定义该术语以限制与该术语相关的本发明的某些特定特点、特征或者方案。总之,不应当将在随附的权利要求书中使用的术语解释为将本发明限定在说明书中公开的特定实施例,除非上述详细说明部分明确地限定了这些术语。因此,本发明的实际范围不仅包括所公开的实施例,还包括在权利要求书之中。As above, it should be noted that specific terms used in describing certain features or solutions of the present invention should not be used to indicate that the terms are redefined here to limit some specific features, features or aspects of the present invention to which the terms are related. plan. In conclusion, the terms used in the following claims should not be construed to limit the invention to the particular embodiments disclosed in the specification, unless the above detailed description expressly defines those terms. Accordingly, the true scope of the invention encompasses not only the disclosed embodiments but also the appended claims.
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CN102983553B (en) * | 2012-11-19 | 2015-11-18 | Tcl王牌电器(惠州)有限公司 | Switching Power Supply overload protection method and device |
CN103152951B (en) * | 2013-03-13 | 2015-07-08 | 绍兴光大芯业微电子有限公司 | LED (light emitting diode) driving control circuit and driving circuit structure of LED driving control circuit |
WO2014170976A1 (en) * | 2013-04-17 | 2014-10-23 | 三菱電機株式会社 | Switching power supply circuit and control method therefor |
CN105763059B (en) * | 2014-12-16 | 2018-08-28 | 康舒科技股份有限公司 | power supply with current correction function |
CN105846701B (en) * | 2016-04-29 | 2019-02-15 | 杭州士兰微电子股份有限公司 | Constant-current control circuit, constant-current drive circuit and constant current control method |
CN108964464B (en) * | 2017-05-19 | 2022-11-29 | 上海芯熠微电子有限公司 | Circuit and method for nondestructive testing of load current at output side of switching power supply |
CN108565941A (en) * | 2018-06-07 | 2018-09-21 | 深圳市菱奇半导体有限公司 | A kind of charge control system and control method |
CN109039093B (en) * | 2018-09-29 | 2024-01-23 | 杰华特微电子股份有限公司 | Isolation type switching power supply and control method thereof |
CN112397016B (en) * | 2019-08-16 | 2022-02-22 | 华润微集成电路(无锡)有限公司 | Line voltage compensation circuit and compensation method thereof |
CN112834810B (en) * | 2021-01-04 | 2024-08-09 | 基合半导体(宁波)有限公司 | Commercial power voltage detection circuit and detection method applied to flyback isolated power supply |
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US7876583B2 (en) * | 2008-12-22 | 2011-01-25 | Power Integrations, Inc. | Flyback power supply with forced primary regulation |
CN101841250B (en) * | 2010-04-27 | 2012-08-15 | 上海新进半导体制造有限公司 | Switching power supply control circuit and primary winding-controlled flyback switching power supply |
CN101873750B (en) * | 2010-06-25 | 2013-11-13 | 深圳市欣锐特科技有限公司 | LED (light emitting diode) lamp fault processing method, LED driver and LED lamp |
CN101944856B (en) * | 2010-07-13 | 2013-01-23 | 上海新进半导体制造有限公司 | Control circuit of switching power supply for primary side control |
CN101925236B (en) * | 2010-08-20 | 2013-06-05 | 杭州电子科技大学 | Isolated high-power factor flyback type primary-side constant-current control device of LED driver |
CN101951716B (en) * | 2010-09-30 | 2013-04-03 | 杭州电子科技大学 | Constant-on-time primary side constant-current control device for LED driver with high power factor |
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