CN102089966B - N路doherty分布式功率放大器 - Google Patents
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Abstract
公开了一种功率放大器,该功率放大器使用N-路Doherty结构,用于延伸在诸如宽带码分多址接入和正交频分复用之类的复用调制信号的高峰均功率比上的效率区域。在一个实施例中,本发明将双馈分布式结构使用到N-路Doherty放大器,用以改善在至少一个主放大器和至少一个峰化放大器之间的隔离,并且还用以同时改善高输出回退功率处的增益和效率性能。混合耦合器可以用在输入和输出中的任意一个处或者可以同时用在输入和输出处。在至少某些实现中,由于将放大、功率分路与合并都集成在一起,所以还节省了电路空间。
Description
技术领域
本发明一般涉及高功率通信系统。更为特别地,本发明涉及用于这种系统的高效高功率放大器。
背景技术
在现代数字无线通信系统(诸如IS-95、PCS、WCDMA、OFDM等等)中,功率放大器已经朝着具有宽带宽和大量载波的方向发展。近来,正交频分复用(OFDM)调制是用于在像WiBRO和WiMAX之类的有限带宽内高效传输信息的具有吸引力的技术。然而,因为OFDM信号包括许多独立调制的子载波,所以它产生更高的峰均功率比(PAR)信号。64子载波OFDM信号的典型的PAR大约是8-13dB。当子载波的数目增长到2048时,PAR也增加,通常从11dB到16dB。被设计成同这些高PAR一起工作的功率放大器通常具有极端恶化的效率。
Doherty放大器是一种公知的用于改善高输出回退(backoff)功率处的效率的技术。它的主要优点是当应用到高功率放大器时,它容易配置,这不同于诸如切换模式放大器、EER、LINC等等之类的其它效率增强放大器或技术。最近的结果已经报道它使用:对称Doherty结构、具有不均匀功率晶体管的非对称Doherty结构、以及使用多个并联晶体管的N路Doherty结构。在对称Doherty结构的情况下,最大效率点在6dB回退功率处获得。
非对称Doherty放大器通过针对主放大器和峰化放大器使用不同功率器件尺寸的组合,可以在各种回退功率处获得高效率。遗憾的是,因为在主放大器和峰化放大器之间不同的器件匹配电路和延迟失配的原因,很难优化非对称Doherty放大器的增益和输出功率。
常规N路Doherty放大器通过使用多个并联的相同器件的晶体管,相比常规2路Doherty结构具有效率增强。它的一个缺陷是由于N路输入功率分路器的损耗的缘故,总增益将被减小。在低增益的情况下,这将增加驱动放大器的功率浪费。
另外,尽管常规N路Doherty放大器可以在高输出回退功率处提供改善的效率,但是常规N路Doherty放大器在针对较高的峰均功率比(PAR)信号,在增益和效率两方面性能会恶化。
因此,在本技术领域中,需要一种同时应用电路级和系统级的技术来改善N路Doherty放大器在高功率通信系统中在高输出回退功率处的增益和效率性能的方法。
发明内容
因此,考虑到上述问题,做出本发明,并且本发明的一个目标是提供一种针对高功率通信系统应用的、改善Doherty放大结构在高输出回退功率处的增益和效率性能的方法。为了实现这个目标,根据本发明,该技术使用双馈分布式放大。常规N路Doherty放大器中的功率分路器和合并器被具有传输线的混合耦合器所替代。相比常规N路Doherty放大器,本发明能够获得在输入和输出处的良好隔离以及具有高效率的高增益性能。
附图说明
从结合附图的以下详细描述中,本发明的其它目标和优点可以被更充分地理解。
图1是示出根据本发明的使用双馈分布式(DFD)方法的N路Doherty放大器的实施例的示意图。
图2是示出N路Doherty双馈分布式放大器的在各个输出回退功率水平处的效率特征的图。
图3是示出根据本发明的3路Doherty分布式放大器的实施例的示意图。
图4是示出根据本发明的3路Doherty分布式放大器的实施例的增益和功率增加效率性能(PAE)的仿真结果的图。
图5是示出根据本发明的3路Doherty分布式放大器的实施例的增益和功率增加效率性能(PAE)的测量结果的图。
图6是示出使用根据本发明的3路Doherty分布式放大器的实施例,针对单音信号的、作为旁路电容器和峰化放大器的偏置电压的函数的增益和PAE性能变化的测量结果的图。
图7是示出使用根据本发明的3路Doherty分布式放大器的针对单个WCDMA载波的频谱测量结果的图。
图8示出根据本发明的混合模式功率放大器系统。
具体实施方式
通常,本发明涉及使用具有N路Doherty放大器结构的单端双馈分布式(SEDFD)放大方法,从而获得高输出回退功率处的高增益和高效率性能。在某些实施例中,还通过分别在半波长的栅极线和漏极线的末端处调节N路峰化放大器的栅极偏置和旁路电容器来使增益和效率性能最大化。由此,相比常规N路Doherty放大器,本发明针对复用调制信号获得了更高的功率增加效率(PAE)和更高的增益。由此,本发明所提供的方法和装置此后被称为N路Doherty分布式功率放大器(NWDPA)。
现在,将参考附图详细地描述根据本发明的NWDPA的各种实施例。
图1是示出使用本发明的SEDFD方法的N路Doherty放大器的示意图。通过功率分路器,RF输入(RFin)信号101被提供作为主SEDFD放大器108和峰化SEFDF放大器107的输入。每个SEDFD放大器包括两个传输线109、110、111、112和N组晶体管113、114。SEDFD主放大器107和峰化放大器108中的所有晶体管113、114通过具有中心频率处的半波长度的栅极线和漏极线109、110、111、112连接,并且相同地工作。SEDFD放大器107、108的输入信号沿着栅极线109、111分布,并且放大的输出信号沿着漏极线110、112合并。因为每个晶体管添加同相功率到该信号,所以SEDFD放大器107、108能够提供更高增益。λ/4微带线103位于SEDFD峰化放大器107之前,目的是同步SEDFD主放大器108和SEDFD峰化放大器107之间的相位。SEDFD主放大器108的输出信号传输经过微带λ/4阻抗变换器104,并且通过功率合并器105与SEDFD峰化放大器107的输出信号合并。
图2是示出NWDPA在各个输出回退功率处的效率特性的图。NWDPA在最大功率水平处的效率由下式给出:
并且在中等功率水平处的效率由下式给出:
其中,vo和vmax分别是输出电压和最大输出电压,M是主放大器的晶体管的数目,而P是峰化放大器的晶体管的数目。取决于实施方式,主放大器和峰化放大器可以是单个晶体管也可以是多个晶体管,或者是其它形式的放大器。另外,晶体管可以是分立的或集成的,这也取决于实施方式。
对于低功率水平,NWDPA的效率被表达为:
放大器在各种输出回退功率水平处的效率被计算为主放大器和峰化放大器的数目的函数。延伸的回退状态XBO和主放大器与峰化放大器的数目之间的关系由下式给出:
图3是示出根据本发明的3路DohertySEDFD放大器的实施例的示意图。为了在9.5dB的回退功率处提供高效率,放大器包括使用相同类型的晶体管的一个主放大器203和两个峰化放大器204、205。RF输入信号201被传输经过90°混合耦合器202,并被分给主放大器203和两个峰化放大器204、205。输入阻抗匹配电路206、207、208分别连接在耦合器与主放大器203和峰化放大器204、205之间。在至少某些实施例中,主放大器203被偏置为AB类放大器而峰化放大器204、205被偏置为C类放大器。如果主放大器一般被偏置在AB类模式中,则它将具有增益压缩特性。相反,如果峰化放大器一般被偏置在C类模式中,则它将具有增益扩大特性。在至少某些实施例中,本发明利用了这些赠送的特性,从而AB类主放大器的增益压缩将由C类峰化放大器的增益扩大来补偿,以产生更好线性的功率放大器。
为了获得最优功率,输出阻抗匹配电路209、210、211被连接到主放大器203和峰化放大器204、205的输出。旁路电容器CM212被连接到主放大器203的输出阻抗匹配电路209,从而基于线性度优化的Doherty放大器方法来优化NWDPA的线性度,所述方法在2006年11月所提交的美国临时申请NO.60/846905中给出,通过援引将其并入此处。为了获得在期望的输出回退功率处的峰值效率点,补偿线(offsetline)213被插入在输出阻抗匹配电路209、210、211和λ/4阻抗变换器214、215之间。峰化放大器204、205通过使用双馈分布式结构组合起来,该双馈分布式结构在某些实施例中在第一峰化放大器的每个栅极和漏极处具有半波微带线217、218,出于图示和清楚的缘故该第一峰化放大器被示出为FET。在图3中,峰化放大器1通过使用双馈分布式结构与峰化放大器2相组合。该双馈分布式结构包括半波长线和四分之一波长线,并且在第二峰化放大器的每个栅极和漏极处的短路的四分之一波长微带线219、220分别通过相关联的输入和输出阻抗匹配电路相连接。虽然出于简化的目的,在示出的实施例中第二峰化放大器被示出为单个晶体管,但是其可以是一个或多个晶体管。在某些实施例中,输出处的四分之一波长传输线可以由混合耦合器来替代。
在某些实施例中,半波长线217和218被设置在工作功率放大器带宽的中心频率处。在某些实施例中,旁路电容器CP221、222被连接到短路的四分之一波长微带线219、220的两端用于优化NWDPA的增益和效率特性二者。补偿线213可以被包括以阻止主放大器203和峰化放大器204、205之间的泄露功率。在某些实施例中,混合耦合器202将导致某种增益压缩,并且这可以通过峰化放大器的增益扩大来补偿。在某些实施例中,可以在输出处连接额外的混合耦合器。另外,本领域的普通技术人员将意识到,主分布式放大器和峰化分布式放大器可以或者被构建成独立的微型微波集成电路或者被构建在一个集成MMIC上。
在检查NWDPA的性能时,通过使用具有150W的p1dB的LDMOSFET,设计和实现42dBm的高功率放大器。
图4是图示使用如图3中所示出的那样的3路Doherty分布式放大器,对2140MHz频率的单音信号的增益和PAE的仿真结果的图。AB类偏置的主放大器的工作点是:IDQ=510mA,VGS=3.82V以及VDS=27V。C类偏置的峰化放大器的工作点是:1)峰化放大器1;IDQ=0mA,VGS=2.4V以及VDS=27V,2)峰化放大器2;IDQ=0mA,VGS=2.6V以及VDS=27V。使用双馈分布式结构的组合的峰化放大器的输出阻抗是4.65+j2.1Ω。近似0.25λ的补偿线被插入;这对应于521Ω的最优输出电阻。从仿真结果看,在大约200W的峰值包络功率(PEP)处,获得43%的PAE。因此,实现了离峰值效率点9.5dB的回退功率处的40%的PAE。相比在图4中也示出2路常规Doherty放大器的6dB峰值点的PAE,这是大约7%的效率改善。从2130到2150MHz,获得了近似10.5dB的增益。
图5是示出本发明的3路Doherty分布式放大器的增益和PAE的测量结果的图。主放大器的工作点是:IDQ=480mA,VGS=3.9V。峰化放大器的工作点是:1)峰化放大器1;IDQ=0mA,VGS=2.1V;2)峰化放大器2;IDQ=0mA,VGS=1.9V。分别使用15pF和0.5pF的旁路电容器CP和CM。分别实现了在131W的PEP处的42.7%的PAE和在9.5dB的回退处的39.5%的PAE。在9.5dB的回退处获得了近似11dB的增益。
图6是示出使用本发明的3路Doherty分布式放大器的、针对单音信号的、作为旁路电容器和峰化放大器的偏置电压的函数的增益和PAE性能变化的测量结果。CP和两个峰化放大器的偏置点的优化在9.5dB的回退处产生了近似8%和2dB的效率和增益改善,尽管PAE在PEP处减少了。
图7是示出使用根据本发明的3路Doherty分布式放大器的针对单个WCDMA载波的频谱测量结果的图。工作点分别是VGS=3.79V(主PA),VGS=3.1V(峰化PA1)以及VGS=2.5V(峰化PA2)。分别使用9.1pF和0.5pF的旁路电容器CP和CM。为了实现高线性度,应用无记忆的和基于记忆的数字预失真二者。在41dBm的输出功率和+2.5MHz偏移频率处,经过无记忆补偿后获得-51dBc的ACLR性能,以及经过记忆补偿后获得-54dBc的ACLR性能。
总之,相比于常规N路Doherty放大器,本发明的NWDPA更有效地改善了增益性能,因为NWDPA使用了与Doherty放大器相结合的SEDFD结构。图8中示出了根据本发明的混合模式功率放大器系统,其中调制RF输入信号800被提供给数字预失真控制器805,其又将其输出提供给根据本发明的功率放大器810。RF输出(RFout)815被监视,并且表示输出的信号作为反馈信号820被反馈回控制器805。
尽管已经参考优选的实施例描述了本发明,但是应当理解本发明不限于这里所描述的优选的实施例。基于此处的教导,上述描述中所公开的各种替换和修改,以及其它内容对于本领域的普通技术人员而言是显而易见的。由此,所有这些替换和修改旨在被包括在由所附权利要求书所限定的本发明的范围内。
Claims (17)
1.一种N路Doherty分布式放大器,包括:
RF输入,
至少一个主分布式放大器,
至少两个峰化分布式放大器,所述至少两个峰化分布式放大器通过双馈分布式结构组合,其中所述双馈分布式结构包括将输入分布到所述至少两个峰化分布式放大器以及将来自所述至少两个峰化分布式放大器的输出组合成单个输出;
混合耦合器,其响应于输入信号,所述混合耦合器用于分别提供输入给所述至少一个主分布式放大器和所述至少两个峰化分布式放大器,以及
相位同步器,其响应于所述RF输入,用于同步所述至少一个主分布式放大器与所述至少两个峰化分布式放大器之间的相位。
2.根据权利要求1所述的N路Doherty分布式放大器,其中所述RF输入是单端双馈的。
3.根据权利要求1所述的N路Doherty分布式放大器,其中所述至少一个主分布式放大器和所述至少两个峰化分布式放大器中的所有晶体管基本上相同地操作。
4.根据权利要求1所述的N路Doherty分布式放大器,其中所述至少一个主分布式放大器的增益压缩由所述至少两个峰化分布式放大器的增益扩大来补偿。
5.根据权利要求1所述的N路Doherty分布式放大器,还包括旁路电容器,其可操作地连接到所述至少一个主分布式放大器和所述至少两个峰化分布式放大器,并且其中所述至少一个主分布式放大器和所述至少两个峰化分布式放大器的相位受所述旁路电容器的电容控制。
6.根据权利要求1所述的N路Doherty分布式放大器,其中所述N路Doherty分布式放大器在各种输出回退功率处的效率被确定为所述至少一个主放大器和所述至少两个峰化分布式放大器的数目的函数,其由以下方程给出:
其中v0和vmax分别是输出电压和最大输出电压,M是所述至少一个主分布式放大器的晶体管的数目,而P是所述至少两个峰化分布式放大器的晶体管的数目。
7.根据权利要求1所述的N路Doherty分布式放大器,其中延伸的回退状态XBO由以下方程来描述:
其中M是所述至少一个主分布式放大器的晶体管的数目,而P是所述至少两个峰化分布式放大器的晶体管的数目。
8.根据权利要求1所述的N路Doherty分布式放大器,其中所述N路Doherty分布式放大器被配置为前馈线性化技术的主放大器。
9.根据权利要求1所述的N路Doherty分布式放大器,其中所述N路Doherty分布式放大器从数字预失真器接收输入。
10.根据权利要求1所述的N路Doherty分布式放大器,其中所述至少一个主分布式放大器和所述至少两个峰化分布式放大器是下述组中的一种,所述组包括:第一,多个单独的微型微波集成电路,以及第二,一个集成MMIC。
11.根据权利要求1所述的N路Doherty分布式放大器,其中所述相位同步器将所述至少两个峰化分布式放大器的相位延迟成比所述至少一个主分布式放大器的相位滞后近似90°。
12.根据权利要求1所述的N路Doherty分布式放大器,其中所述相位同步器包括在所述至少两个峰化分布式放大器之前的λ/4微带线,以同步所述至少一个主分布式放大器和所述至少两个峰化分布式放大器之间的相位。
13.根据权利要求1所述的N路Doherty分布式放大器,还包括分别连接到所述至少一个主分布式放大器和所述至少两个峰化分布式放大器的前端的输入阻抗匹配电路。
14.根据权利要求1所述的N路Doherty分布式放大器,还包括连接到所述至少一个主分布式放大器和所述至少两个峰化分布式放大器的栅极线和漏极线,所述栅极线和漏极线具有在所述N路Doherty分布式放大器的中心频率处的半波长度。
15.根据权利要求1所述的N路Doherty分布式放大器,还包括输出阻抗匹配电路,其连接到所述至少一个主分布式放大器和所述至少两个峰化分布式放大器的至少一个输出。
16.根据权利要求15所述的N路Doherty分布式放大器,还包括至少一个补偿线,其插入所述至少一个主分布式放大器和所述至少两个峰化分布式放大器的输出阻抗匹配电路的末端之间,以阻止功率从所述至少一个主分布式放大器泄露到所述至少两个峰化分布式放大器。
17.根据权利要求16所述的N路Doherty分布式放大器,还包括连接到所述补偿线的针对特征阻抗Z0的λ/4阻抗变换器。
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- 2008-04-23 EP EP08829011.9A patent/EP2145385B1/en active Active
- 2008-04-23 JP JP2010504909A patent/JP5474764B2/ja active Active
- 2008-04-23 CN CN200880021149.0A patent/CN102089966B/zh active Active
- 2008-04-23 US US12/108,507 patent/US7688135B2/en active Active
- 2008-04-23 WO PCT/IB2008/003079 patent/WO2009031042A2/en active Application Filing
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Also Published As
Publication number | Publication date |
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KR101484796B1 (ko) | 2015-01-20 |
JP5474764B2 (ja) | 2014-04-16 |
EP2145385A4 (en) | 2014-06-11 |
KR20100017214A (ko) | 2010-02-16 |
US20080284509A1 (en) | 2008-11-20 |
US7688135B2 (en) | 2010-03-30 |
EP2145385A2 (en) | 2010-01-20 |
JP2010530148A (ja) | 2010-09-02 |
CN102089966A (zh) | 2011-06-08 |
EP2145385B1 (en) | 2018-10-17 |
WO2009031042A2 (en) | 2009-03-12 |
WO2009031042A3 (en) | 2011-04-28 |
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