JPH10164837A - Power supply - Google Patents
Power supplyInfo
- Publication number
- JPH10164837A JPH10164837A JP8315049A JP31504996A JPH10164837A JP H10164837 A JPH10164837 A JP H10164837A JP 8315049 A JP8315049 A JP 8315049A JP 31504996 A JP31504996 A JP 31504996A JP H10164837 A JPH10164837 A JP H10164837A
- Authority
- JP
- Japan
- Prior art keywords
- mos
- voltage
- fet
- power supply
- coil
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Pending
Links
Classifications
-
- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
Abstract
Description
【０００１】[0001]
【発明の属する技術分野】本発明は、例えばＡＣ入力を
整流したＤＣで駆動されるパーソナルコンピュータの電
源等に使用して好適な電源装置に関するものである。BACKGROUND OF THE INVENTION 1. Field of the Invention The present invention relates to a power supply device suitable for use as, for example, a power supply of a personal computer driven by DC obtained by rectifying an AC input.
【０００２】[0002]
【従来の技術】例えばＡＣ入力を整流したＤＣで駆動さ
れるパーソナルコンピュータの電源においては、内部で
必要な駆動電圧を得るために、いわゆるＤＣ−ＤＣコン
バータ等の電源装置が用いられている。すなわち図９に
は、そのような電源装置の一例の構成を示す。2. Description of the Related Art For example, in a power supply of a personal computer driven by DC in which an AC input is rectified, a power supply device such as a so-called DC-DC converter is used in order to obtain a necessary driving voltage internally. That is, FIG. 9 shows a configuration of an example of such a power supply device.
【０００３】この図９において、ＤＣ７０の＋端が、直
列に接続された２石のスイッチングトランジスタ７１、
７２のコレクタ・エミッタ間を通じてＤＣ７０の−端に
接続される。これらのトランジスタ７１、７２の中点が
過飽和リアクタトランス７３のコイル３Ａ、共振コンデ
ンサ７４を通じて電圧変換トランス７５の１次側コイル
５Ａの一端に接続される。またこの１次側コイル５Ａの
他端がＤＣ７０の−端に接続される。さらにトランジス
タ７１、７２の中点がコンデンサ７６を通じてＤＣ７０
の−端に接続される。In FIG. 9, the positive terminal of a DC 70 has two switching transistors 71 connected in series,
It is connected to the negative terminal of the DC 70 through the collector-emitter 72. The midpoint between these transistors 71 and 72 is connected to one end of the primary coil 5A of the voltage conversion transformer 75 through the coil 3A of the saturable reactor transformer 73 and the resonance capacitor 74. The other end of the primary coil 5A is connected to the negative end of DC 70. Further, the midpoint between the transistors 71 and 72 is
Is connected to the negative end of
【０００４】また、トランジスタ７１のコレクタが抵抗
器７７を通じてトランジスタ７１のベースに接続され、
このトランジスタ７１のベースが順方向のツェナーダイ
オード７８と逆方向のダイオード７９の直列回路を通じ
てトランジスタ７１のエミッタに接続される。さらにト
ランジスタ７１のベースが抵抗器８０、コンデンサ８１
と、過飽和リアクタトランス７３のコイル３Ｂ及びコン
デンサ８２の並列回路との直列回路を通じてトランジス
タ７１のエミッタに接続される。Further, the collector of the transistor 71 is connected to the base of the transistor 71 through a resistor 77,
The base of the transistor 71 is connected to the emitter of the transistor 71 through a series circuit of a zener diode 78 in the forward direction and a diode 79 in the reverse direction. Further, the base of the transistor 71 is a resistor 80, a capacitor 81
Is connected to the emitter of the transistor 71 through a series circuit of a coil 3B of the saturable reactor transformer 73 and a parallel circuit of the capacitor 82.
【０００５】さらにトランジスタ７２のコレクタが抵抗
器８３を通じてトランジスタ７２のベースに接続され、
このトランジスタ７２のベースが順方向のツェナーダイ
オード８４と逆方向のダイオード８５の直列回路を通じ
てトランジスタ７２のエミッタに接続される。さらにト
ランジスタ７２のベースが抵抗器８６、コンデンサ８７
と、過飽和リアクタトランス７３のコイル３Ｃ及びコン
デンサ８８の並列回路との直列回路を通じてトランジス
タ７２のエミッタに接続される。Further, the collector of the transistor 72 is connected to the base of the transistor 72 through a resistor 83,
The base of the transistor 72 is connected to the emitter of the transistor 72 through a series circuit of a zener diode 84 in the forward direction and a diode 85 in the reverse direction. Further, the base of the transistor 72 includes a resistor 86 and a capacitor 87.
Is connected to the emitter of the transistor 72 through a series circuit of a parallel circuit of the coil 3C of the saturable reactor transformer 73 and the capacitor 88.
【０００６】また、上述の電圧変換トランス７５の２次
側コイル５Ｂの一端及び他端が、それぞれ整流用の順方
向のダイオード８９、９０を通じて互いに接続される。
さらにこの接続点と２次側コイル５Ｂの中間タップとの
間に平滑用のコンデンサ９１が接続される。そしてこの
コンデンサ９１の両端から出力端子９２の＋端及び−端
が導出される。さらにこの出力端子９２の＋端がエラー
アンプ９３を通じて過飽和リアクタトランス７３の制御
コイル３Ｄに接続される。[0006] One end and the other end of the secondary coil 5B of the voltage conversion transformer 75 are connected to each other through forward diodes 89 and 90 for rectification.
Further, a smoothing capacitor 91 is connected between the connection point and the intermediate tap of the secondary coil 5B. The positive terminal and the negative terminal of the output terminal 92 are led out from both ends of the capacitor 91. Further, the positive terminal of the output terminal 92 is connected to the control coil 3D of the saturable reactor transformer 73 through the error amplifier 93.
【０００７】そしてこの装置において、上述のスイッチ
ングトランジスタ７１、７２が自励発振によって交互に
オンオフされることによって、電圧変換トランス７５の
１次側コイル５Ａには略正弦波の電流が流され、２次側
コイル５Ｂには所望の電圧が取り出される。さらにこの
取り出された電圧がダイオード８９、９０を通じて両波
整流され、整流された電圧がコンデンサ９１で平滑され
て出力端子９２に取り出される。In this device, the switching transistors 71 and 72 are turned on and off alternately by self-excited oscillation, so that a substantially sine-wave current flows through the primary coil 5A of the voltage conversion transformer 75. A desired voltage is extracted from the secondary coil 5B. Further, the extracted voltage is subjected to double-wave rectification through diodes 89 and 90, and the rectified voltage is smoothed by a capacitor 91 and extracted to an output terminal 92.
【０００８】また、出力端子９２の＋端に取り出された
電圧の、所望の電圧からの変動分がエラーアンプ９３で
検出され、この変動分が過飽和リアクタトランス７３の
制御コイル３Ｄに供給される。これによってこの過飽和
リアクタトランス７３のコイル３Ａ〜３Ｃに取り出され
る信号の波形が変化され、トランジスタ７１、７２のス
イッチング周波数が変化されて、出力端子９２の＋端に
取り出される電圧が所望の電圧に等しくなるように制御
が行われる。[0008] Further, a variation from a desired voltage of the voltage taken out at the + terminal of the output terminal 92 is detected by the error amplifier 93, and the variation is supplied to the control coil 3 D of the saturable reactor transformer 73. As a result, the waveforms of the signals extracted to the coils 3A to 3C of the saturable reactor transformer 73 are changed, the switching frequencies of the transistors 71 and 72 are changed, and the voltage extracted to the positive terminal of the output terminal 92 is equal to the desired voltage. Control is performed so that
【０００９】このようにして、上述の装置において、安
定化された所望の電圧を出力端子９２に取り出すことが
できる。そしてこの取り出された電圧は、例えばＤＣで
駆動されるパーソナルコンピュータの電源として使用さ
れるものである。Thus, in the above-described device, a stabilized desired voltage can be taken out to the output terminal 92. The extracted voltage is used as, for example, a power source of a personal computer driven by DC.
【００１０】[0010]
【発明が解決しようとする課題】ところが上述の電源装
置において、電圧変換トランス７５の２次側整流用のダ
イオード８９、９０の順方向降下電圧Ｖf によって損失
が発生する。すなわちこのようなダイオードの順方向降
下電圧Ｖf は、一般的０．４５Ｖ程度であるが、この順
方向降下電圧Ｖf によって上述の装置では、 １．１１×Ｉo ×Ｖf 〔Ｗ〕 （但し、Ｉo は出
力電流〔Ａ〕） の損失が発生する。However, in the power supply device described above, a loss occurs due to the forward drop voltage Vf of the diodes 89 and 90 for rectification on the secondary side of the voltage conversion transformer 75. That is, the forward drop voltage Vf of such a diode is generally about 0.45 V, and the forward drop voltage Vf causes the above-described device to be 1.11 × Io × Vf [W] (where Io is Output current [A]) is lost.
【００１１】そしてこのような２次側整流用のダイオー
ド８９、９０による損失が、例えば出力電流Ｉo が１０
〔Ａ〕では５〔Ｗ〕、２０〔Ａ〕では１０〔Ｗ〕にもな
ってしまい、特にパーソナルコンピュータのように低電
圧、大電流が要求される電源では、出力に対する損失の
割合が大きくなってしまうものである。The loss due to the secondary side rectifying diodes 89 and 90 is, for example, when the output current Io is 10
In [A], it becomes 5 [W], and in 20 [A], it becomes as much as 10 [W]. In particular, in a power supply requiring a low voltage and a large current such as a personal computer, the ratio of loss to output becomes large. It will be.
【００１２】この出願はこのような点に鑑みて成された
ものであって、解決しようとする問題点は、従来の装置
では、特にパーソナルコンピュータのように低電圧、大
電流の電源が要求される場合に、２次側整流用ダイオー
ドの順方向降下電圧によって、出力に対する損失の割合
が大きくなってしまうというものである。The present invention has been made in view of the above points, and the problem to be solved is that a conventional apparatus requires a power supply of a low voltage and a large current, particularly like a personal computer. In this case, the ratio of the loss to the output increases due to the forward drop voltage of the secondary-side rectifier diode.
【００１３】[0013]
【課題を解決するための手段】このため本発明において
は、電圧変換用トランスの２次側整流としてＭＯＳ−Ｆ
ＥＴを用いて同期整流を行うようにしたものであって、
これによれば、特に低オン抵抗のＭＯＳ−ＦＥＴを用い
ることで、２次側整流での損失を大幅に減少させること
ができる。Therefore, in the present invention, a MOS-F is used as a secondary rectifier of a voltage conversion transformer.
ET is used to perform synchronous rectification,
According to this, the loss due to rectification on the secondary side can be greatly reduced by using a MOS-FET having a low on-resistance.
【００１４】[0014]
【発明の実施の形態】すなわち本発明においては、スイ
ッチング素子を２石用いたハーフブリッジ構成を有し、
２石のスイッチング素子の中点に共振コンデンサと電圧
変換用トランスが設けられると共に、電圧変換用トラン
スの２次側整流としてＭＯＳ−ＦＥＴを用いて同期整流
を行うものである。以下、図面を参照して本発明を説明
するに、図１は本発明を適用した電源装置の一例の構成
を示すブロック図である。DESCRIPTION OF THE PREFERRED EMBODIMENTS That is, the present invention has a half bridge configuration using two switching elements,
A resonance capacitor and a voltage conversion transformer are provided at the midpoint of the two switching elements, and synchronous rectification is performed using a MOS-FET as secondary rectification of the voltage conversion transformer. Hereinafter, the present invention will be described with reference to the drawings. FIG. 1 is a block diagram showing a configuration of an example of a power supply device to which the present invention is applied.
【００１５】この図１において、ＡＣ入力を整流したＤ
Ｃ１００の＋端が、直列に接続された２石のスイッチン
グトランジスタ１、２のコレクタ・エミッタ間を通じて
ＤＣ１００の−端に接続される。これらのトランジスタ
１、２の中点が過飽和リアクタトランス３のコイル３
Ａ、共振コンデンサ４を通じて電圧変換トランス５の１
次側コイル５Ａの一端に接続される。またこの１次側コ
イル５Ａの他端がＤＣ１００の−端に接続される。さら
にトランジスタ１、２の中点がコンデンサ６を通じてＤ
Ｃ１００の−端に接続される。In FIG. 1, D is obtained by rectifying the AC input.
The positive terminal of C100 is connected to the negative terminal of DC100 through the collector and emitter of two switching transistors 1, 2 connected in series. The middle point of these transistors 1 and 2 is the coil 3 of the supersaturated reactor transformer 3.
A, one of the voltage conversion transformers 5 through the resonance capacitor 4
It is connected to one end of the secondary coil 5A. The other end of the primary coil 5A is connected to the negative end of DC100. Further, the midpoint between the transistors 1 and 2 is
Connected to the minus end of C100.
【００１６】また、トランジスタ１のコレクタが抵抗器
７を通じてトランジスタ１のベースに接続され、このト
ランジスタ１のベースが順方向のツェナーダイオード８
と逆方向のダイオード９の直列回路を通じてトランジス
タ１のエミッタに接続される。さらにトランジスタ１の
ベースが抵抗器１０、コンデンサ１１と、過飽和リアク
タトランス３のコイル３Ｂ及びコンデンサ１２の並列回
路との直列回路を通じてトランジスタ１のエミッタに接
続される。The collector of the transistor 1 is connected to the base of the transistor 1 through a resistor 7, and the base of the transistor 1 is connected to a zener diode 8 in the forward direction.
Is connected to the emitter of the transistor 1 through a series circuit of a diode 9 in the opposite direction. Further, the base of the transistor 1 is connected to the emitter of the transistor 1 through a series circuit of a resistor 10, a capacitor 11, and a parallel circuit of a coil 3B of the saturable reactor transformer 3 and a capacitor 12.
【００１７】さらにトランジスタ２のコレクタが抵抗器
１３を通じてトランジスタ２のベースに接続され、この
トランジスタ２のベースが順方向のツェナーダイオード
１４と逆方向のダイオード１５の直列回路を通じてトラ
ンジスタ２のエミッタに接続される。さらにトランジス
タ２のベースが抵抗器１６、コンデンサ１７と、過飽和
リアクタトランス３のコイル３Ｃ及びコンデンサ１８の
並列回路との直列回路を通じてトランジスタ２のエミッ
タに接続される。Further, the collector of the transistor 2 is connected to the base of the transistor 2 through a resistor 13, and the base of the transistor 2 is connected to the emitter of the transistor 2 through a series circuit of a forward Zener diode 14 and a reverse diode 15. You. Further, the base of the transistor 2 is connected to the emitter of the transistor 2 through a series circuit of the resistor 16 and the capacitor 17 and the parallel circuit of the coil 3C of the saturable reactor transformer 3 and the capacitor 18.
【００１８】また、上述の電圧変換トランス５の２次側
コイル５Ｂの一端及び他端が、それぞれＮチャンネルの
ＭＯＳ−ＦＥＴ１９、２０のソース・ドレイン間を通じ
て互いに接続される。さらにこの接続点と２次側コイル
５Ｂの中間タップとの間に平滑用のコンデンサ２１が接
続される。そしてこのコンデンサ２１の両端から出力端
子２２の＋端及び−端が導出される。さらにこの出力端
子２２の＋端が制御回路２３を通じて過飽和リアクタト
ランス３の制御コイル３Ｄに接続される。One end and the other end of the secondary coil 5B of the voltage conversion transformer 5 are connected to each other through the source and drain of N-channel MOS-FETs 19 and 20, respectively. Further, a smoothing capacitor 21 is connected between the connection point and an intermediate tap of the secondary coil 5B. The positive terminal and the negative terminal of the output terminal 22 are led out from both ends of the capacitor 21. Further, the positive terminal of the output terminal 22 is connected to the control coil 3D of the saturable reactor transformer 3 through the control circuit 23.
【００１９】そしてこの装置において、上述のスイッチ
ングトランジスタ１、２が自励発振によって交互にオン
オフされることによって、電圧変換トランス５の１次側
コイル５Ａには略正弦波の電流が流され、２次側コイル
５Ｂには所望の電圧が取り出される。さらにこの取り出
された電圧が、ＭＯＳ−ＦＥＴ１９、２０を通じて互い
に接続される。In this device, the switching transistors 1 and 2 are alternately turned on and off by self-excited oscillation, so that a substantially sine-wave current flows through the primary coil 5A of the voltage conversion transformer 5, and A desired voltage is extracted from the secondary coil 5B. Further, the extracted voltages are connected to each other through MOS-FETs 19 and 20.
【００２０】ここでこれらのＭＯＳ−ＦＥＴ１９、２０
はそれぞれ駆動回路２４、２５によってオンオフが制御
され、例えば図示の例ではコンデンサ２１側からコイル
５Ｂに向かって電流が流れている期間にのみオンされる
ように同期制御される。これによって２次側コイル５Ｂ
に取り出された電圧が両波整流され、整流された電圧が
コンデンサ２１で平滑されて出力端子２２に取り出され
る。Here, these MOS-FETs 19, 20
Are turned on and off by drive circuits 24 and 25, respectively. For example, in the example shown in the drawing, synchronous control is performed such that the transistor is turned on only during a period in which a current flows from the capacitor 21 toward the coil 5B. Thereby, the secondary coil 5B
Is rectified in both directions, and the rectified voltage is smoothed by the capacitor 21 and output to the output terminal 22.
【００２１】また、出力端子２２の＋端に取り出された
電圧の、所望の電圧からの変動分が制御回路２３で検出
され、この変動分が過飽和リアクタトランス３の制御コ
イル３Ｄに供給される。これによってこの過飽和リアク
タトランス３のコイル３Ａ〜３Ｃに取り出される信号の
波形が変化され、トランジスタ１、２のスイッチング周
波数が変化されて、出力端子２２の＋端に取り出される
電圧が所望の電圧に等しくなるように制御が行われる。The control circuit 23 detects a variation of the voltage taken out at the positive terminal of the output terminal 22 from the desired voltage, and supplies the variation to the control coil 3D of the supersaturated reactor transformer 3. As a result, the waveforms of the signals taken out to the coils 3A to 3C of the saturable reactor transformer 3 are changed, the switching frequency of the transistors 1 and 2 is changed, and the voltage taken out at the positive terminal of the output terminal 22 is equal to the desired voltage. Control is performed so that
【００２２】このようにして、上述の装置において、安
定化された所望の電圧を出力端子２２に取り出すことが
できる。さらにこの取り出された電圧は、例えばＤＣで
駆動されるパーソナルコンピュータの電源として使用さ
れるものである。In this manner, in the above-described device, a desired stabilized voltage can be taken out to the output terminal 22. Further, the extracted voltage is used as a power source of a personal computer driven by, for example, DC.
【００２３】そして上述の装置において、電圧変換トラ
ンス５の２次側の整流が、ＭＯＳ−ＦＥＴ１９、２０の
それぞれ同期制御による同期整流によって行われてい
る。従ってこの場合には、２次側整流用のＭＯＳ−ＦＥ
Ｔ１９、２０のオン抵抗Ｒonによって損失が発生する。In the above-described apparatus, rectification on the secondary side of the voltage conversion transformer 5 is performed by synchronous rectification by synchronous control of the MOS-FETs 19 and 20, respectively. Therefore, in this case, the MOS-FE for secondary side rectification is used.
Loss occurs due to the on-resistance Ron of T19 and T20.
【００２４】すなわちこのようなオン抵抗Ｒonは、例え
ば低オン抵抗のＭＯＳ−ＦＥＴでは７ｍΩ程度である。
そしてこのオン抵抗Ｒonによって上述の装置では、 １．１１×Ｉo ×１．１１×Ｉo ×Ｒon〔Ｗ〕 の損失が発生する。That is, such an on-resistance Ron is about 7 mΩ for a low on-resistance MOS-FET, for example.
In the device described above, a loss of 1.11 × Io × 1.11 × Io × Ron [W] occurs due to the on-resistance Ron.
【００２５】そしてこのような２次側整流用のＭＯＳ−
ＦＥＴ１９、２０による損失は、例えば出力電流Ｉo が
１０〔Ａ〕では約０．８６〔Ｗ〕、２０〔Ａ〕では約
３．４５〔Ｗ〕に留めることができ、特にパーソナルコ
ンピュータのように低電圧、大電流が要求される電源
で、出力に対する損失の割合を大幅に削減することがで
きるものである。The secondary side rectifying MOS-
The loss caused by the FETs 19 and 20 can be kept at about 0.86 [W] when the output current Io is 10 [A] and about 3.45 [W] when the output current Io is 20 [A], and particularly low as in a personal computer. It is a power supply that requires a large voltage and a large current, and can greatly reduce the ratio of loss to output.
【００２６】すなわち図２において、直線Ａは、従来の
２次側整流用の素子に例えば順方向降下電圧Ｖf ＝０．
４５Ｖのダイオードを用いた場合の、電流〔Ａ〕に対す
る損失〔Ｗ〕の発生の状況を示す。また、曲線Ｂは、２
次側整流用の素子に例えばオン抵抗Ｒon＝７ｍΩのＭＯ
Ｓ−ＦＥＴを用いた場合の、電流〔Ａ〕に対する損失
〔Ｗ〕の発生の状況を示している。That is, in FIG. 2, a straight line A represents, for example, a forward drop voltage Vf = 0.
The situation in which a loss [W] with respect to a current [A] occurs when a 45 V diode is used is shown. Curve B is 2
For the element for rectification on the secondary side, for example, an MO having an on-resistance Ron = 7 mΩ
This shows a situation in which a loss [W] with respect to a current [A] occurs when an S-FET is used.
【００２７】従ってこの装置において、電圧変換用トラ
ンスの２次側整流としてＭＯＳ−ＦＥＴを用いて同期整
流を行うことによって、特に低オン抵抗のＭＯＳ−ＦＥ
Ｔを用いることで、２次側整流での損失を大幅に減少さ
せることができる。Therefore, in this device, synchronous rectification is performed by using a MOS-FET as a secondary rectifier of the voltage conversion transformer, so that a MOS-FE having a low on-resistance can be obtained.
By using T, the loss in the secondary side rectification can be greatly reduced.
【００２８】これによって、従来の装置では、２次側整
流用ダイオードの順方向降下電圧によって、出力に対す
る損失の割合が大きくなっていたものを、本発明によれ
ば、特にパーソナルコンピュータのように低電圧、大電
流の電源が要求される場合に、２次側整流での損失を大
幅に減少させ、効率の良いスイッチング電源を実現する
ことができるものである。Thus, in the conventional device, the ratio of the loss to the output is increased due to the forward drop voltage of the secondary-side rectifier diode. When a power supply of a voltage and a large current is required, the loss in the secondary side rectification can be greatly reduced, and an efficient switching power supply can be realized.
【００２９】ところで上述の装置において、２次側整流
素子は、本来は電圧変換用トランス５の２次側コイル５
Ｂから平滑用コンデンサ２１を充電する方向のみに電流
を流さなければならない。ところが上述の装置におい
て、ＭＯＳ−ＦＥＴは、ゲートにオン電圧が印加される
とドレイン・ソース間は抵抗体と同等になるため、電流
は双方向に流れることができる。In the above-described apparatus, the secondary-side rectifying element is originally a secondary-side coil 5 of the transformer 5 for voltage conversion.
A current must flow only in the direction from B to charge the smoothing capacitor 21. However, in the above-described device, when an ON-voltage is applied to the gate of the MOS-FET, the current between the drain and the source becomes equivalent to that of a resistor, so that current can flow in both directions.
【００３０】従って上述の装置において、ＭＯＳ−ＦＥ
Ｔのゲートにオン電圧を印加するタイミングを悪くする
と、コンデンサ２１から２次側コイル５Ｂへ放電電流が
流れ、負荷側にエネルギーを有効に伝達できないばかり
か、逆電流によるＭＯＳ−ＦＥＴの発熱やノイズの発
生、１次側スイッチング損失の増大にもつながる恐れが
ある。Therefore, in the above device, the MOS-FE
If the timing of applying the on-voltage to the gate of T is deteriorated, a discharge current flows from the capacitor 21 to the secondary coil 5B, so that not only energy cannot be effectively transmitted to the load side, but also heat generation and noise of the MOS-FET due to the reverse current. This may lead to an increase in primary-side switching loss.
【００３１】そこで、このようなＭＯＳ−ＦＥＴのゲー
トにオン電圧を印加するタイミングを正確に制御するた
めに、例えば図３に示すような回路が用いられる。なお
以下の説明では、２次側整流用のＭＯＳ−ＦＥＴ１９、
２０の下側の片方の回路についてのみ示すが、上下両方
のＭＯＳ−ＦＥＴについての回路構成、及びその作用動
作は同じである。In order to accurately control the timing of applying the ON voltage to the gate of such a MOS-FET, for example, a circuit as shown in FIG. 3 is used. In the following description, the MOS-FET 19 for secondary rectification,
Although only one of the lower circuits 20 is shown, the circuit configuration and the operation of the upper and lower MOS-FETs are the same.
【００３２】この図３において、ＭＯＳ−ＦＥＴ２０に
直列に電流検出用トランス３１の１次側コイル３１Ａが
設けられる。そしてこの電流検出用トランス３１の２次
側コイル３１Ｂの両端間に検出用の抵抗器３２が接続さ
れ、この抵抗器３２の電圧がコンパレータ３３で検出さ
れる。In FIG. 3, a primary coil 31A of a current detecting transformer 31 is provided in series with the MOS-FET 20. A resistor 32 for detection is connected between both ends of the secondary coil 31B of the transformer 31 for current detection, and the voltage of the resistor 32 is detected by the comparator 33.
【００３３】すなわち上述の抵抗器３２の一端が電圧源
３４に接続され、この電圧源３４の電圧と抵抗器３２の
他端の電圧がコンパレータ３３で比較されて、他端の電
圧が所定値以上になったときに検出が行われる。そして
この検出信号がバッファ回路３５を通じてＭＯＳ−ＦＥ
Ｔ２０のゲートに供給される。That is, one end of the resistor 32 is connected to a voltage source 34. The voltage of the voltage source 34 and the voltage of the other end of the resistor 32 are compared by a comparator 33, and the voltage of the other end is equal to or more than a predetermined value. Detection is performed when This detection signal is supplied to the MOS-FE through the buffer circuit 35.
It is supplied to the gate of T20.
【００３４】従ってこの回路において、例えば上述の１
次側のトランジスタ１のコレクタ電流ＩC が、図４のＡ
に示すようであった場合には、電圧変換用トランス５の
２次側コイル５Ｂには図４のＢの電圧が誘起される。そ
してこの電圧がコンデンサ２１の充電電圧より大きくな
ると、ＭＯＳ−ＦＥＴ２０の寄生ダイオード２０Ａを通
じてコンデンサ２１に充電電流が流される。Therefore, in this circuit, for example,
The collector current I C of the transistor 1 on the next side is A
4, the voltage B in FIG. 4 is induced in the secondary coil 5B of the voltage conversion transformer 5. When this voltage becomes higher than the charging voltage of the capacitor 21, a charging current flows to the capacitor 21 through the parasitic diode 20A of the MOS-FET 20.
【００３５】さらにこの充電電流が電流検出用トランス
３１の１次側コイル３１Ａを流れることによって、２次
側コイル３１Ｂには電圧が誘起される。そしてこの出力
電圧がコンパレータ３３で検出され、この出力電圧が所
定値以上になると、即座にバッファ回路３５を通じて例
えば図４のＣに示すようなゲート電圧ＶgsがＭＯＳ−Ｆ
ＥＴ２０に印加される。Further, when the charging current flows through the primary coil 31A of the current detecting transformer 31, a voltage is induced in the secondary coil 31B. The output voltage is detected by the comparator 33, and when the output voltage becomes equal to or higher than a predetermined value, the gate voltage Vgs as shown in FIG.
Applied to ET20.
【００３６】また、上述の充電電流が減少すると、コン
パレータ３３の出力が反転され、バッファ回路３５を通
じてＭＯＳ−ＦＥＴ２０のゲート容量が放電されて、Ｍ
ＯＳ−ＦＥＴ２０がオフされる。なおこの時点でコンデ
ンサ２１の充電電流はゼロにはなっていないが、この電
流はＭＯＳ−ＦＥＴ２０の寄生ダイオード２０Ａを通じ
て流される。When the charge current decreases, the output of the comparator 33 is inverted, the gate capacitance of the MOS-FET 20 is discharged through the buffer circuit 35, and M
OS-FET 20 is turned off. At this point, the charging current of the capacitor 21 has not become zero, but this current flows through the parasitic diode 20A of the MOS-FET 20.
【００３７】これによって、ＭＯＳ−ＦＥＴ２０には、
例えば図４のＤに示すようなドレイン電流ＩD が流され
る。すなわちこのＭＯＳ−ＦＥＴ２０は、コンデンサ２
１への充電電流が流れ始めた後でオンされ、充電電流が
ゼロになる前にオフされる。そしてこのＭＯＳ−ＦＥＴ
２０がオンされている期間に、低オン抵抗を介して損失
の少ない充電が行われるものである。Thus, the MOS-FET 20 has
For example the drain current I D as shown in D of FIG. 4 is flowed. That is, this MOS-FET 20 is
It is turned on after the charging current to 1 starts flowing, and turned off before the charging current becomes zero. And this MOS-FET
During the period when the switch 20 is turned on, charging with low loss is performed via the low on-resistance.
【００３８】なお、上述のＭＯＳ−ＦＥＴ１９において
も作用動作は全く同じに行われる。すなわち例えば図５
のＡ、Ｂに示すＭＯＳ−ＦＥＴ２０の動作に反転した形
で、図５のＣ、Ｄに示すようにＭＯＳ−ＦＥＴ１９の動
作が行われる。そしてこの場合も、ＭＯＳ−ＦＥＴ１９
は、コンデンサ２１への充電電流が流れ始めた後でオン
され、充電電流がゼロになる前にオフされるものであ
る。The operation of the MOS-FET 19 is exactly the same. That is, for example, FIG.
The operation of the MOS-FET 19 is performed as shown in FIGS. 5C and D in a form inverted from the operation of the MOS-FET 20 shown in FIGS. Also in this case, the MOS-FET 19
Is turned on after the charging current to the capacitor 21 starts flowing, and turned off before the charging current becomes zero.
【００３９】従ってこの回路において、ＭＯＳ−ＦＥＴ
は充電電流がゼロになる前にオフされるので、例えばタ
ーンオフのタイミングが遅れて逆電流が流されるような
ことがない。これにより、いかなる動作条件でもＭＯＳ
−ＦＥＴのオン期間が充電電流の方向のみの電流だけ流
せるようにでき、逆電流の発生による不具合を解消する
ことができる。Therefore, in this circuit, the MOS-FET
Is turned off before the charging current becomes zero, so that, for example, the turn-off timing is delayed and a reverse current does not flow. This allows the MOS to operate under any operating conditions.
-The ON period of the FET can flow only the current in the direction of the charging current, and the problem caused by the generation of the reverse current can be solved.
【００４０】さらに図６、図７は、ＭＯＳ−ＦＥＴのゲ
ートにオン電圧を印加するタイミングを正確に制御する
ための回路の他の例を示す。すなわち図６は充電電流の
検出方法として検出抵抗４１を用いる場合であって、こ
の検出抵抗４１で検出された電圧をコンパレータ４２で
電圧源４３の電圧と比較し、この比較出力をバッファ回
路４４を通じてＭＯＳ−ＦＥＴ２０のゲートに印加して
いる。FIGS. 6 and 7 show another example of a circuit for accurately controlling the timing of applying the ON voltage to the gate of the MOS-FET. That is, FIG. 6 shows a case where the detection resistor 41 is used as a method of detecting the charging current. The voltage detected by the detection resistor 41 is compared with the voltage of the voltage source 43 by the comparator 42, and the comparison output is supplied through the buffer circuit 44. The voltage is applied to the gate of the MOS-FET 20.
【００４１】また、図７は検出抵抗としてＭＯＳ−ＦＥ
Ｔ２０のオン抵抗を用いるものである。すなわちこの例
では、ＭＯＳ−ＦＥＴ２０のオン抵抗で検出された電圧
をコンパレータ５１で電圧源５２の電圧と比較し、この
比較出力をバッファ回路５３を通じてＭＯＳ−ＦＥＴ２
０のゲートに印加している。なおこの図７の回路は、も
っとも損失が少なくなる構成である。FIG. 7 shows a MOS-FE as a detection resistor.
The on-resistance of T20 is used. That is, in this example, the voltage detected by the on-resistance of the MOS-FET 20 is compared with the voltage of the voltage source 52 by the comparator 51, and this comparison output is output through the buffer circuit 53 to the MOS-FET 2.
0 is applied to the gate. The circuit shown in FIG. 7 has a configuration in which the loss is minimized.
【００４２】こうして上述の電源装置によれば、スイッ
チング素子を２石用いたハーフブリッジ構成を有し、２
石のスイッチング素子の中点に共振コンデンサと電圧変
換用トランスが設けられると共に、電圧変換用トランス
の２次側整流としてＭＯＳ−ＦＥＴを用いて同期整流を
行うことにより、２次側整流での損失を大幅に減少さ
せ、効率の良いスイッチング電源を実現することができ
るものである。Thus, according to the power supply device described above, the power supply device has a half-bridge configuration using two switching elements,
A resonance capacitor and a voltage conversion transformer are provided at the middle point of the stone switching element, and synchronous rectification is performed by using a MOS-FET as the secondary rectification of the voltage conversion transformer, so that the loss in the secondary rectification is reduced. Can be greatly reduced, and an efficient switching power supply can be realized.
【００４３】なお、上述の説明では、いずれも２次側整
流用のＭＯＳ−ＦＥＴ１９、２０を電圧変換トランス５
の２次側コイル５Ｂの−側に設ける場合について行った
が、例えば従来の装置で述べたダイオードのように＋側
に設けても同様の作用効果を得ることができる。ただ
し、−側に設けた方がＭＯＳ−ＦＥＴの駆動には適正で
ある。In the above description, each of the secondary-side rectifying MOS-FETs 19 and 20 is connected to the voltage conversion transformer 5.
However, the same effect can be obtained by providing the diode on the + side as in the diode described in the conventional device. However, the provision on the negative side is more appropriate for driving the MOS-FET.
【００４４】また、例えば図８に示すように１次側のス
イッチング素子が他励発振によってオンオフ駆動される
場合においても本発明を適用することができる。すなわ
ち図８においては、コントロール回路６０からの制御信
号がドライブ回路６１、６２を通じてそれぞれスイッチ
ング素子６３、６４に供給され、これらのスイッチング
素子６３、６４がオンオフ駆動されて、上述の電圧変換
トランス５の１次側コイル５Ａに略正弦波の電流が流さ
れる。The present invention can also be applied to a case where the primary-side switching element is driven to be turned on and off by separately excited oscillation as shown in FIG. That is, in FIG. 8, the control signal from the control circuit 60 is supplied to the switching elements 63 and 64 through the drive circuits 61 and 62, respectively, and these switching elements 63 and 64 are driven on and off to drive the voltage conversion transformer 5 described above. A substantially sinusoidal current flows through the primary coil 5A.
【００４５】さらにこの装置において、出力端子２２の
＋端に取り出された電圧の、所望の電圧からの変動分が
フィードバック回路６５を通じてコントロール回路６０
に供給され、これによってスイッチング素子６３、６４
のスイッチング周波数が変化されて、出力端子２２の＋
端に取り出される電圧が所望の電圧に等しくなるように
制御が行われる。Further, in this device, the variation of the voltage taken out at the + terminal of the output terminal 22 from the desired voltage is supplied to the control circuit 60 through the feedback circuit 65.
And the switching elements 63, 64
Of the output terminal 22 is changed.
Control is performed so that the voltage taken out at the end is equal to the desired voltage.
【００４６】そしてさらにこの装置においても、電圧変
換用トランスの２次側整流としてＭＯＳ−ＦＥＴを用い
て同期整流を行うことによって、特に低オン抵抗のＭＯ
Ｓ−ＦＥＴを用いることで、２次側整流での損失を大幅
に減少させることができ、効率の良いスイッチング電源
を実現することができるものである。Further, in this apparatus, synchronous rectification is performed by using a MOS-FET as secondary rectification of the voltage conversion transformer, so that a particularly low on-resistance MO is realized.
By using the S-FET, the loss in the secondary side rectification can be greatly reduced, and an efficient switching power supply can be realized.
【００４７】[0047]
【発明の効果】この発明によれば、電圧変換用トランス
の２次側整流としてＭＯＳ−ＦＥＴを用いて同期整流を
行うことによって、特に低オン抵抗のＭＯＳ−ＦＥＴを
用いることで、２次側整流での損失を大幅に減少させる
ことができるようになった。According to the present invention, synchronous rectification is performed by using a MOS-FET as a secondary rectifier of a voltage conversion transformer, and in particular, by using a low on-resistance MOS-FET, a secondary rectifier is used. The rectification loss can be greatly reduced.
【００４８】これによって、従来の装置では、２次側整
流用ダイオードの順方向降下電圧によって、出力に対す
る損失の割合が大きくなっていたものを、本発明によれ
ば、特にパーソナルコンピュータのように低電圧、大電
流の電源が要求される場合に、２次側整流での損失を大
幅に減少させ、効率の良いスイッチング電源を実現する
ことができるものである。Thus, according to the present invention, the ratio of the loss to the output is increased due to the forward drop voltage of the diode for secondary rectification. When a power supply of a voltage and a large current is required, the loss in the secondary side rectification can be greatly reduced, and an efficient switching power supply can be realized.
【図１】本発明の適用される電源装置の一例の構成図で
ある。FIG. 1 is a configuration diagram of an example of a power supply device to which the present invention is applied.
【図２】その説明のための図である。FIG. 2 is a diagram for explaining this.
【図３】本発明の適用される電源装置の要部の一例の構
成図である。FIG. 3 is a configuration diagram of an example of a main part of a power supply device to which the present invention is applied.
【図４】その動作の説明のための図である。FIG. 4 is a diagram for explaining the operation.
【図５】その動作の説明のための図である。FIG. 5 is a diagram for explaining the operation.
【図６】本発明の適用される電源装置の要部の他の例の
構成図である。FIG. 6 is a configuration diagram of another example of a main part of a power supply device to which the present invention is applied.
【図７】本発明の適用される電源装置の要部の他の例の
構成図である。FIG. 7 is a configuration diagram of another example of a main part of a power supply device to which the present invention is applied.
【図８】本発明の適用される電源装置の他の例の構成図
である。FIG. 8 is a configuration diagram of another example of a power supply device to which the present invention is applied.
【図９】従来の電源装置の構成図である。FIG. 9 is a configuration diagram of a conventional power supply device.
１００ ＡＣ入力を整流したＤＣ、１，２ スイッチン
グトランジスタ、３過飽和リアクタトランス、４ 共振
コンデンサ、５ 電圧変換トランス、６ コンデンサ、
７ 抵抗器、８ ツェナーダイオード、９ ダイオー
ド、１０ 抵抗器、１１，１２ コンデンサ、１３ 抵
抗器、１４ ツェナーダイオード、１５ダイオード、１
６ 抵抗器、１７，１８ コンデンサ、１９，２０ Ｍ
ＯＳ−ＦＥＴ、２１ コンデンサ、２２ 出力端子、２
３ 制御回路、２４，２５ 駆動回路100 DC rectified AC input, 1, 2 switching transistor, 3 supersaturated reactor transformer, 4 resonance capacitor, 5 voltage conversion transformer, 6 capacitor,
7 resistor, 8 Zener diode, 9 diode, 10 resistor, 11, 12 capacitor, 13 resistor, 14 Zener diode, 15 diode, 1
6 resistors, 17 and 18 capacitors, 19 and 20 M
OS-FET, 21 capacitor, 22 output terminal, 2
3 control circuit, 24, 25 drive circuit
Claims (5)
リッジ構成を有し、 上記２石のスイッチング素子の中点に共振コンデンサと
電圧変換用トランスが設けられると共に、 上記電圧変換用トランスの２次側整流としてＭＯＳ−Ｆ
ＥＴを用いて同期整流を行うことを特徴とする電源装
置。1. A half-bridge configuration using two switching elements, wherein a resonance capacitor and a voltage conversion transformer are provided at a midpoint of the two switching elements, and a secondary side of the voltage conversion transformer. MOS-F as rectification
A power supply device that performs synchronous rectification using ET.
記ＭＯＳ−ＦＥＴを流れる電流を検出した信号を用いる
ことを特徴とする電源装置。2. The power supply device according to claim 1, wherein a signal obtained by detecting a current flowing through the MOS-FET is used as a drive signal of the secondary-side rectification MOS-FET.
て上記ＭＯＳ−ＦＥＴを流れる電流を検出することを特
徴とする電源装置。3. The power supply device according to claim 2, wherein a current detection transformer is connected in series with said MOS-FET to detect a current flowing through said MOS-FET.
の電圧降下により上記ＭＯＳ−ＦＥＴを流れる電流を検
出することを特徴とする電源装置。4. The power supply device according to claim 2, wherein a current detection resistor is connected in series to said MOS-FET, and a current flowing through said MOS-FET is detected by a voltage drop.
記ＭＯＳ−ＦＥＴを流れる電流を検出することを特徴と
する電源装置。5. The power supply device according to claim 2, wherein a current flowing through the MOS-FET is detected by a voltage drop due to an on-resistance of the MOS-FET.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP8315049A JPH10164837A (en) | 1996-11-26 | 1996-11-26 | Power supply |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP8315049A JPH10164837A (en) | 1996-11-26 | 1996-11-26 | Power supply |
Publications (1)
| Publication Number | Publication Date |
|---|---|
| JPH10164837A true JPH10164837A (en) | 1998-06-19 |
Family
ID=18060824
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| JP8315049A Pending JPH10164837A (en) | 1996-11-26 | 1996-11-26 | Power supply |
Country Status (1)
| Country | Link |
|---|---|
| JP (1) | JPH10164837A (en) |
Cited By (80)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JP2001309580A (en) * | 2000-04-25 | 2001-11-02 | Matsushita Electric Works Ltd | Non-contact power transfer apparatus |
| EP1415386A2 (en) * | 2001-07-05 | 2004-05-06 | DI/DT, Inc. | Simple and efficient switching regulator for fast transient loads |
| JP2008301680A (en) * | 2007-06-04 | 2008-12-11 | Fuji Electric Systems Co Ltd | Dc-dc converter |
| JP2010187478A (en) * | 2009-02-12 | 2010-08-26 | Shindengen Electric Mfg Co Ltd | Means for controlling series resonant converter |
| WO2012049911A1 (en) * | 2010-10-15 | 2012-04-19 | 三洋電機株式会社 | Charge/discharge circuit |
| WO2012153799A1 (en) * | 2011-05-12 | 2012-11-15 | 株式会社村田製作所 | Switching power supply device |
| JP2012244786A (en) * | 2011-05-20 | 2012-12-10 | Omron Corp | Full-wave rectifier circuit |
| WO2013020138A3 (en) * | 2011-08-04 | 2013-04-04 | Witricity Corporation | Tunable wireless power architectures |
| US8692412B2 (en) | 2008-09-27 | 2014-04-08 | Witricity Corporation | Temperature compensation in a wireless transfer system |
| US8847548B2 (en) | 2008-09-27 | 2014-09-30 | Witricity Corporation | Wireless energy transfer for implantable devices |
| US8875086B2 (en) | 2011-11-04 | 2014-10-28 | Witricity Corporation | Wireless energy transfer modeling tool |
| US8901778B2 (en) | 2008-09-27 | 2014-12-02 | Witricity Corporation | Wireless energy transfer with variable size resonators for implanted medical devices |
| US8901779B2 (en) | 2008-09-27 | 2014-12-02 | Witricity Corporation | Wireless energy transfer with resonator arrays for medical applications |
| US8907531B2 (en) | 2008-09-27 | 2014-12-09 | Witricity Corporation | Wireless energy transfer with variable size resonators for medical applications |
| US8912687B2 (en) | 2008-09-27 | 2014-12-16 | Witricity Corporation | Secure wireless energy transfer for vehicle applications |
| US8922066B2 (en) | 2008-09-27 | 2014-12-30 | Witricity Corporation | Wireless energy transfer with multi resonator arrays for vehicle applications |
| US8928276B2 (en) | 2008-09-27 | 2015-01-06 | Witricity Corporation | Integrated repeaters for cell phone applications |
| US8933594B2 (en) | 2008-09-27 | 2015-01-13 | Witricity Corporation | Wireless energy transfer for vehicles |
| US8937408B2 (en) | 2008-09-27 | 2015-01-20 | Witricity Corporation | Wireless energy transfer for medical applications |
| US8947186B2 (en) | 2008-09-27 | 2015-02-03 | Witricity Corporation | Wireless energy transfer resonator thermal management |
| US8946938B2 (en) | 2008-09-27 | 2015-02-03 | Witricity Corporation | Safety systems for wireless energy transfer in vehicle applications |
| US8957549B2 (en) | 2008-09-27 | 2015-02-17 | Witricity Corporation | Tunable wireless energy transfer for in-vehicle applications |
| US8963488B2 (en) | 2008-09-27 | 2015-02-24 | Witricity Corporation | Position insensitive wireless charging |
| US9035499B2 (en) | 2008-09-27 | 2015-05-19 | Witricity Corporation | Wireless energy transfer for photovoltaic panels |
| US9065423B2 (en) | 2008-09-27 | 2015-06-23 | Witricity Corporation | Wireless energy distribution system |
| US9065286B2 (en) | 2005-07-12 | 2015-06-23 | Massachusetts Institute Of Technology | Wireless non-radiative energy transfer |
| US9093853B2 (en) | 2008-09-27 | 2015-07-28 | Witricity Corporation | Flexible resonator attachment |
| US9095729B2 (en) | 2007-06-01 | 2015-08-04 | Witricity Corporation | Wireless power harvesting and transmission with heterogeneous signals |
| US9105959B2 (en) | 2008-09-27 | 2015-08-11 | Witricity Corporation | Resonator enclosure |
| US9106203B2 (en) | 2008-09-27 | 2015-08-11 | Witricity Corporation | Secure wireless energy transfer in medical applications |
| US9160203B2 (en) | 2008-09-27 | 2015-10-13 | Witricity Corporation | Wireless powered television |
| US9184595B2 (en) | 2008-09-27 | 2015-11-10 | Witricity Corporation | Wireless energy transfer in lossy environments |
| US9246336B2 (en) | 2008-09-27 | 2016-01-26 | Witricity Corporation | Resonator optimizations for wireless energy transfer |
| US9287607B2 (en) | 2012-07-31 | 2016-03-15 | Witricity Corporation | Resonator fine tuning |
| US9306635B2 (en) | 2012-01-26 | 2016-04-05 | Witricity Corporation | Wireless energy transfer with reduced fields |
| US9318257B2 (en) | 2011-10-18 | 2016-04-19 | Witricity Corporation | Wireless energy transfer for packaging |
| US9318922B2 (en) | 2008-09-27 | 2016-04-19 | Witricity Corporation | Mechanically removable wireless power vehicle seat assembly |
| US9343922B2 (en) | 2012-06-27 | 2016-05-17 | Witricity Corporation | Wireless energy transfer for rechargeable batteries |
| US9369182B2 (en) | 2008-09-27 | 2016-06-14 | Witricity Corporation | Wireless energy transfer using variable size resonators and system monitoring |
| US9396867B2 (en) | 2008-09-27 | 2016-07-19 | Witricity Corporation | Integrated resonator-shield structures |
| US9404954B2 (en) | 2012-10-19 | 2016-08-02 | Witricity Corporation | Foreign object detection in wireless energy transfer systems |
| US9421388B2 (en) | 2007-06-01 | 2016-08-23 | Witricity Corporation | Power generation for implantable devices |
| US9444520B2 (en) | 2008-09-27 | 2016-09-13 | Witricity Corporation | Wireless energy transfer converters |
| US9442172B2 (en) | 2011-09-09 | 2016-09-13 | Witricity Corporation | Foreign object detection in wireless energy transfer systems |
| US9444265B2 (en) | 2005-07-12 | 2016-09-13 | Massachusetts Institute Of Technology | Wireless energy transfer |
| US9449757B2 (en) | 2012-11-16 | 2016-09-20 | Witricity Corporation | Systems and methods for wireless power system with improved performance and/or ease of use |
| US9515494B2 (en) | 2008-09-27 | 2016-12-06 | Witricity Corporation | Wireless power system including impedance matching network |
| US9544683B2 (en) | 2008-09-27 | 2017-01-10 | Witricity Corporation | Wirelessly powered audio devices |
| US9595378B2 (en) | 2012-09-19 | 2017-03-14 | Witricity Corporation | Resonator enclosure |
| US9601270B2 (en) | 2008-09-27 | 2017-03-21 | Witricity Corporation | Low AC resistance conductor designs |
| US9602168B2 (en) | 2010-08-31 | 2017-03-21 | Witricity Corporation | Communication in wireless energy transfer systems |
| US9601266B2 (en) | 2008-09-27 | 2017-03-21 | Witricity Corporation | Multiple connected resonators with a single electronic circuit |
| JP2017508437A (en) * | 2014-03-14 | 2017-03-23 | アヴォジー，インコーポレイテッド | Adaptive synchronous switching in resonant converters. |
| US9744858B2 (en) | 2008-09-27 | 2017-08-29 | Witricity Corporation | System for wireless energy distribution in a vehicle |
| US9754718B2 (en) | 2008-09-27 | 2017-09-05 | Witricity Corporation | Resonator arrays for wireless energy transfer |
| US9780573B2 (en) | 2014-02-03 | 2017-10-03 | Witricity Corporation | Wirelessly charged battery system |
| US9831682B2 (en) | 2008-10-01 | 2017-11-28 | Massachusetts Institute Of Technology | Efficient near-field wireless energy transfer using adiabatic system variations |
| US9837860B2 (en) | 2014-05-05 | 2017-12-05 | Witricity Corporation | Wireless power transmission systems for elevators |
| US9842688B2 (en) | 2014-07-08 | 2017-12-12 | Witricity Corporation | Resonator balancing in wireless power transfer systems |
| US9843217B2 (en) | 2015-01-05 | 2017-12-12 | Witricity Corporation | Wireless energy transfer for wearables |
| US9842687B2 (en) | 2014-04-17 | 2017-12-12 | Witricity Corporation | Wireless power transfer systems with shaped magnetic components |
| US9857821B2 (en) | 2013-08-14 | 2018-01-02 | Witricity Corporation | Wireless power transfer frequency adjustment |
| US9892849B2 (en) | 2014-04-17 | 2018-02-13 | Witricity Corporation | Wireless power transfer systems with shield openings |
| US9929721B2 (en) | 2015-10-14 | 2018-03-27 | Witricity Corporation | Phase and amplitude detection in wireless energy transfer systems |
| US9948145B2 (en) | 2011-07-08 | 2018-04-17 | Witricity Corporation | Wireless power transfer for a seat-vest-helmet system |
| US9952266B2 (en) | 2014-02-14 | 2018-04-24 | Witricity Corporation | Object detection for wireless energy transfer systems |
| US9954375B2 (en) | 2014-06-20 | 2018-04-24 | Witricity Corporation | Wireless power transfer systems for surfaces |
| US10018744B2 (en) | 2014-05-07 | 2018-07-10 | Witricity Corporation | Foreign object detection in wireless energy transfer systems |
| US10063110B2 (en) | 2015-10-19 | 2018-08-28 | Witricity Corporation | Foreign object detection in wireless energy transfer systems |
| US10063104B2 (en) | 2016-02-08 | 2018-08-28 | Witricity Corporation | PWM capacitor control |
| US10075019B2 (en) | 2015-11-20 | 2018-09-11 | Witricity Corporation | Voltage source isolation in wireless power transfer systems |
| US10141788B2 (en) | 2015-10-22 | 2018-11-27 | Witricity Corporation | Dynamic tuning in wireless energy transfer systems |
| US10218224B2 (en) | 2008-09-27 | 2019-02-26 | Witricity Corporation | Tunable wireless energy transfer systems |
| US10248899B2 (en) | 2015-10-06 | 2019-04-02 | Witricity Corporation | RFID tag and transponder detection in wireless energy transfer systems |
| US10256741B2 (en) | 2014-03-14 | 2019-04-09 | Nexgen Power Systems, Inc. | Adaptive synchronous switching in a resonant converter |
| US10263473B2 (en) | 2016-02-02 | 2019-04-16 | Witricity Corporation | Controlling wireless power transfer systems |
| US10410789B2 (en) | 2008-09-27 | 2019-09-10 | Witricity Corporation | Integrated resonator-shield structures |
| US10424976B2 (en) | 2011-09-12 | 2019-09-24 | Witricity Corporation | Reconfigurable control architectures and algorithms for electric vehicle wireless energy transfer systems |
| US10574091B2 (en) | 2014-07-08 | 2020-02-25 | Witricity Corporation | Enclosures for high power wireless power transfer systems |
| US11031818B2 (en) | 2017-06-29 | 2021-06-08 | Witricity Corporation | Protection and control of wireless power systems |
-
1996
- 1996-11-26 JP JP8315049A patent/JPH10164837A/en active Pending
Cited By (152)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JP2001309580A (en) * | 2000-04-25 | 2001-11-02 | Matsushita Electric Works Ltd | Non-contact power transfer apparatus |
| EP1415386A2 (en) * | 2001-07-05 | 2004-05-06 | DI/DT, Inc. | Simple and efficient switching regulator for fast transient loads |
| EP1415386A4 (en) * | 2001-07-05 | 2007-03-14 | Power One Inc | Simple and efficient switching regulator for fast transient loads |
| US9450421B2 (en) | 2005-07-12 | 2016-09-20 | Massachusetts Institute Of Technology | Wireless non-radiative energy transfer |
| US11685270B2 (en) | 2005-07-12 | 2023-06-27 | Mit | Wireless energy transfer |
| US10097044B2 (en) | 2005-07-12 | 2018-10-09 | Massachusetts Institute Of Technology | Wireless energy transfer |
| US10141790B2 (en) | 2005-07-12 | 2018-11-27 | Massachusetts Institute Of Technology | Wireless non-radiative energy transfer |
| US11685271B2 (en) | 2005-07-12 | 2023-06-27 | Massachusetts Institute Of Technology | Wireless non-radiative energy transfer |
| US9831722B2 (en) | 2005-07-12 | 2017-11-28 | Massachusetts Institute Of Technology | Wireless non-radiative energy transfer |
| US10666091B2 (en) | 2005-07-12 | 2020-05-26 | Massachusetts Institute Of Technology | Wireless non-radiative energy transfer |
| US9444265B2 (en) | 2005-07-12 | 2016-09-13 | Massachusetts Institute Of Technology | Wireless energy transfer |
| US9065286B2 (en) | 2005-07-12 | 2015-06-23 | Massachusetts Institute Of Technology | Wireless non-radiative energy transfer |
| US9450422B2 (en) | 2005-07-12 | 2016-09-20 | Massachusetts Institute Of Technology | Wireless energy transfer |
| US9509147B2 (en) | 2005-07-12 | 2016-11-29 | Massachusetts Institute Of Technology | Wireless energy transfer |
| US9943697B2 (en) | 2007-06-01 | 2018-04-17 | Witricity Corporation | Power generation for implantable devices |
| US10420951B2 (en) | 2007-06-01 | 2019-09-24 | Witricity Corporation | Power generation for implantable devices |
| US10348136B2 (en) | 2007-06-01 | 2019-07-09 | Witricity Corporation | Wireless power harvesting and transmission with heterogeneous signals |
| US9421388B2 (en) | 2007-06-01 | 2016-08-23 | Witricity Corporation | Power generation for implantable devices |
| US9318898B2 (en) | 2007-06-01 | 2016-04-19 | Witricity Corporation | Wireless power harvesting and transmission with heterogeneous signals |
| US9843230B2 (en) | 2007-06-01 | 2017-12-12 | Witricity Corporation | Wireless power harvesting and transmission with heterogeneous signals |
| US9101777B2 (en) | 2007-06-01 | 2015-08-11 | Witricity Corporation | Wireless power harvesting and transmission with heterogeneous signals |
| US9095729B2 (en) | 2007-06-01 | 2015-08-04 | Witricity Corporation | Wireless power harvesting and transmission with heterogeneous signals |
| JP2008301680A (en) * | 2007-06-04 | 2008-12-11 | Fuji Electric Systems Co Ltd | Dc-dc converter |
| US8957549B2 (en) | 2008-09-27 | 2015-02-17 | Witricity Corporation | Tunable wireless energy transfer for in-vehicle applications |
| US9515494B2 (en) | 2008-09-27 | 2016-12-06 | Witricity Corporation | Wireless power system including impedance matching network |
| US10097011B2 (en) | 2008-09-27 | 2018-10-09 | Witricity Corporation | Wireless energy transfer for photovoltaic panels |
| US9035499B2 (en) | 2008-09-27 | 2015-05-19 | Witricity Corporation | Wireless energy transfer for photovoltaic panels |
| US9065423B2 (en) | 2008-09-27 | 2015-06-23 | Witricity Corporation | Wireless energy distribution system |
| US10084348B2 (en) | 2008-09-27 | 2018-09-25 | Witricity Corporation | Wireless energy transfer for implantable devices |
| US9093853B2 (en) | 2008-09-27 | 2015-07-28 | Witricity Corporation | Flexible resonator attachment |
| US8946938B2 (en) | 2008-09-27 | 2015-02-03 | Witricity Corporation | Safety systems for wireless energy transfer in vehicle applications |
| US9105959B2 (en) | 2008-09-27 | 2015-08-11 | Witricity Corporation | Resonator enclosure |
| US8947186B2 (en) | 2008-09-27 | 2015-02-03 | Witricity Corporation | Wireless energy transfer resonator thermal management |
| US9106203B2 (en) | 2008-09-27 | 2015-08-11 | Witricity Corporation | Secure wireless energy transfer in medical applications |
| US9160203B2 (en) | 2008-09-27 | 2015-10-13 | Witricity Corporation | Wireless powered television |
| US9184595B2 (en) | 2008-09-27 | 2015-11-10 | Witricity Corporation | Wireless energy transfer in lossy environments |
| US9246336B2 (en) | 2008-09-27 | 2016-01-26 | Witricity Corporation | Resonator optimizations for wireless energy transfer |
| US8937408B2 (en) | 2008-09-27 | 2015-01-20 | Witricity Corporation | Wireless energy transfer for medical applications |
| US11479132B2 (en) | 2008-09-27 | 2022-10-25 | Witricity Corporation | Wireless power transmission system enabling bidirectional energy flow |
| US8933594B2 (en) | 2008-09-27 | 2015-01-13 | Witricity Corporation | Wireless energy transfer for vehicles |
| US11114897B2 (en) | 2008-09-27 | 2021-09-07 | Witricity Corporation | Wireless power transmission system enabling bidirectional energy flow |
| US9318922B2 (en) | 2008-09-27 | 2016-04-19 | Witricity Corporation | Mechanically removable wireless power vehicle seat assembly |
| US11114896B2 (en) | 2008-09-27 | 2021-09-07 | Witricity Corporation | Wireless power system modules |
| US9369182B2 (en) | 2008-09-27 | 2016-06-14 | Witricity Corporation | Wireless energy transfer using variable size resonators and system monitoring |
| US10673282B2 (en) | 2008-09-27 | 2020-06-02 | Witricity Corporation | Tunable wireless energy transfer systems |
| US9396867B2 (en) | 2008-09-27 | 2016-07-19 | Witricity Corporation | Integrated resonator-shield structures |
| US8928276B2 (en) | 2008-09-27 | 2015-01-06 | Witricity Corporation | Integrated repeaters for cell phone applications |
| US8922066B2 (en) | 2008-09-27 | 2014-12-30 | Witricity Corporation | Wireless energy transfer with multi resonator arrays for vehicle applications |
| US9444520B2 (en) | 2008-09-27 | 2016-09-13 | Witricity Corporation | Wireless energy transfer converters |
| US10559980B2 (en) | 2008-09-27 | 2020-02-11 | Witricity Corporation | Signaling in wireless power systems |
| US8912687B2 (en) | 2008-09-27 | 2014-12-16 | Witricity Corporation | Secure wireless energy transfer for vehicle applications |
| US8907531B2 (en) | 2008-09-27 | 2014-12-09 | Witricity Corporation | Wireless energy transfer with variable size resonators for medical applications |
| US10536034B2 (en) | 2008-09-27 | 2020-01-14 | Witricity Corporation | Wireless energy transfer resonator thermal management |
| US8901779B2 (en) | 2008-09-27 | 2014-12-02 | Witricity Corporation | Wireless energy transfer with resonator arrays for medical applications |
| US10446317B2 (en) | 2008-09-27 | 2019-10-15 | Witricity Corporation | Object and motion detection in wireless power transfer systems |
| US9496719B2 (en) | 2008-09-27 | 2016-11-15 | Witricity Corporation | Wireless energy transfer for implantable devices |
| US8901778B2 (en) | 2008-09-27 | 2014-12-02 | Witricity Corporation | Wireless energy transfer with variable size resonators for implanted medical devices |
| US9515495B2 (en) | 2008-09-27 | 2016-12-06 | Witricity Corporation | Wireless energy transfer in lossy environments |
| US8963488B2 (en) | 2008-09-27 | 2015-02-24 | Witricity Corporation | Position insensitive wireless charging |
| US9544683B2 (en) | 2008-09-27 | 2017-01-10 | Witricity Corporation | Wirelessly powered audio devices |
| US9577436B2 (en) | 2008-09-27 | 2017-02-21 | Witricity Corporation | Wireless energy transfer for implantable devices |
| US9584189B2 (en) | 2008-09-27 | 2017-02-28 | Witricity Corporation | Wireless energy transfer using variable size resonators and system monitoring |
| US8847548B2 (en) | 2008-09-27 | 2014-09-30 | Witricity Corporation | Wireless energy transfer for implantable devices |
| US9596005B2 (en) | 2008-09-27 | 2017-03-14 | Witricity Corporation | Wireless energy transfer using variable size resonators and systems monitoring |
| US9601270B2 (en) | 2008-09-27 | 2017-03-21 | Witricity Corporation | Low AC resistance conductor designs |
| US9843228B2 (en) | 2008-09-27 | 2017-12-12 | Witricity Corporation | Impedance matching in wireless power systems |
| US9601266B2 (en) | 2008-09-27 | 2017-03-21 | Witricity Corporation | Multiple connected resonators with a single electronic circuit |
| US10410789B2 (en) | 2008-09-27 | 2019-09-10 | Witricity Corporation | Integrated resonator-shield structures |
| US9662161B2 (en) | 2008-09-27 | 2017-05-30 | Witricity Corporation | Wireless energy transfer for medical applications |
| US9698607B2 (en) | 2008-09-27 | 2017-07-04 | Witricity Corporation | Secure wireless energy transfer |
| US9711991B2 (en) | 2008-09-27 | 2017-07-18 | Witricity Corporation | Wireless energy transfer converters |
| US9742204B2 (en) | 2008-09-27 | 2017-08-22 | Witricity Corporation | Wireless energy transfer in lossy environments |
| US9748039B2 (en) | 2008-09-27 | 2017-08-29 | Witricity Corporation | Wireless energy transfer resonator thermal management |
| US9744858B2 (en) | 2008-09-27 | 2017-08-29 | Witricity Corporation | System for wireless energy distribution in a vehicle |
| US9754718B2 (en) | 2008-09-27 | 2017-09-05 | Witricity Corporation | Resonator arrays for wireless energy transfer |
| US9780605B2 (en) | 2008-09-27 | 2017-10-03 | Witricity Corporation | Wireless power system with associated impedance matching network |
| US10218224B2 (en) | 2008-09-27 | 2019-02-26 | Witricity Corporation | Tunable wireless energy transfer systems |
| US8692412B2 (en) | 2008-09-27 | 2014-04-08 | Witricity Corporation | Temperature compensation in a wireless transfer system |
| US9806541B2 (en) | 2008-09-27 | 2017-10-31 | Witricity Corporation | Flexible resonator attachment |
| US10230243B2 (en) | 2008-09-27 | 2019-03-12 | Witricity Corporation | Flexible resonator attachment |
| US11958370B2 (en) | 2008-09-27 | 2024-04-16 | Witricity Corporation | Wireless power system modules |
| US10340745B2 (en) | 2008-09-27 | 2019-07-02 | Witricity Corporation | Wireless power sources and devices |
| US10300800B2 (en) | 2008-09-27 | 2019-05-28 | Witricity Corporation | Shielding in vehicle wireless power systems |
| US10264352B2 (en) | 2008-09-27 | 2019-04-16 | Witricity Corporation | Wirelessly powered audio devices |
| US9831682B2 (en) | 2008-10-01 | 2017-11-28 | Massachusetts Institute Of Technology | Efficient near-field wireless energy transfer using adiabatic system variations |
| JP2010187478A (en) * | 2009-02-12 | 2010-08-26 | Shindengen Electric Mfg Co Ltd | Means for controlling series resonant converter |
| US9602168B2 (en) | 2010-08-31 | 2017-03-21 | Witricity Corporation | Communication in wireless energy transfer systems |
| WO2012049911A1 (en) * | 2010-10-15 | 2012-04-19 | 三洋電機株式会社 | Charge/discharge circuit |
| JPWO2012153799A1 (en) * | 2011-05-12 | 2014-07-31 | 株式会社村田製作所 | Switching power supply |
| WO2012153799A1 (en) * | 2011-05-12 | 2012-11-15 | 株式会社村田製作所 | Switching power supply device |
| US8988901B2 (en) | 2011-05-12 | 2015-03-24 | Murata Manufacturing Co., Ltd. | Switching power supply device |
| JP2012244786A (en) * | 2011-05-20 | 2012-12-10 | Omron Corp | Full-wave rectifier circuit |
| US9948145B2 (en) | 2011-07-08 | 2018-04-17 | Witricity Corporation | Wireless power transfer for a seat-vest-helmet system |
| US9787141B2 (en) | 2011-08-04 | 2017-10-10 | Witricity Corporation | Tunable wireless power architectures |
| US9384885B2 (en) | 2011-08-04 | 2016-07-05 | Witricity Corporation | Tunable wireless power architectures |
| WO2013020138A3 (en) * | 2011-08-04 | 2013-04-04 | Witricity Corporation | Tunable wireless power architectures |
| US10734842B2 (en) | 2011-08-04 | 2020-08-04 | Witricity Corporation | Tunable wireless power architectures |
| US11621585B2 (en) | 2011-08-04 | 2023-04-04 | Witricity Corporation | Tunable wireless power architectures |
| US10027184B2 (en) | 2011-09-09 | 2018-07-17 | Witricity Corporation | Foreign object detection in wireless energy transfer systems |
| US10778047B2 (en) | 2011-09-09 | 2020-09-15 | Witricity Corporation | Foreign object detection in wireless energy transfer systems |
| US9442172B2 (en) | 2011-09-09 | 2016-09-13 | Witricity Corporation | Foreign object detection in wireless energy transfer systems |
| US10424976B2 (en) | 2011-09-12 | 2019-09-24 | Witricity Corporation | Reconfigurable control architectures and algorithms for electric vehicle wireless energy transfer systems |
| US11097618B2 (en) | 2011-09-12 | 2021-08-24 | Witricity Corporation | Reconfigurable control architectures and algorithms for electric vehicle wireless energy transfer systems |
| US9318257B2 (en) | 2011-10-18 | 2016-04-19 | Witricity Corporation | Wireless energy transfer for packaging |
| US8875086B2 (en) | 2011-11-04 | 2014-10-28 | Witricity Corporation | Wireless energy transfer modeling tool |
| US9306635B2 (en) | 2012-01-26 | 2016-04-05 | Witricity Corporation | Wireless energy transfer with reduced fields |
| US9343922B2 (en) | 2012-06-27 | 2016-05-17 | Witricity Corporation | Wireless energy transfer for rechargeable batteries |
| US10158251B2 (en) | 2012-06-27 | 2018-12-18 | Witricity Corporation | Wireless energy transfer for rechargeable batteries |
| US9287607B2 (en) | 2012-07-31 | 2016-03-15 | Witricity Corporation | Resonator fine tuning |
| US9595378B2 (en) | 2012-09-19 | 2017-03-14 | Witricity Corporation | Resonator enclosure |
| US10686337B2 (en) | 2012-10-19 | 2020-06-16 | Witricity Corporation | Foreign object detection in wireless energy transfer systems |
| US10211681B2 (en) | 2012-10-19 | 2019-02-19 | Witricity Corporation | Foreign object detection in wireless energy transfer systems |
| US9404954B2 (en) | 2012-10-19 | 2016-08-02 | Witricity Corporation | Foreign object detection in wireless energy transfer systems |
| US9465064B2 (en) | 2012-10-19 | 2016-10-11 | Witricity Corporation | Foreign object detection in wireless energy transfer systems |
| US10186372B2 (en) | 2012-11-16 | 2019-01-22 | Witricity Corporation | Systems and methods for wireless power system with improved performance and/or ease of use |
| US9842684B2 (en) | 2012-11-16 | 2017-12-12 | Witricity Corporation | Systems and methods for wireless power system with improved performance and/or ease of use |
| US9449757B2 (en) | 2012-11-16 | 2016-09-20 | Witricity Corporation | Systems and methods for wireless power system with improved performance and/or ease of use |
| US11720133B2 (en) | 2013-08-14 | 2023-08-08 | Witricity Corporation | Impedance adjustment in wireless power transmission systems and methods |
| US9857821B2 (en) | 2013-08-14 | 2018-01-02 | Witricity Corporation | Wireless power transfer frequency adjustment |
| US11112814B2 (en) | 2013-08-14 | 2021-09-07 | Witricity Corporation | Impedance adjustment in wireless power transmission systems and methods |
| US9780573B2 (en) | 2014-02-03 | 2017-10-03 | Witricity Corporation | Wirelessly charged battery system |
| US9952266B2 (en) | 2014-02-14 | 2018-04-24 | Witricity Corporation | Object detection for wireless energy transfer systems |
| JP2017508437A (en) * | 2014-03-14 | 2017-03-23 | アヴォジー，インコーポレイテッド | Adaptive synchronous switching in resonant converters. |
| US10256741B2 (en) | 2014-03-14 | 2019-04-09 | Nexgen Power Systems, Inc. | Adaptive synchronous switching in a resonant converter |
| US9892849B2 (en) | 2014-04-17 | 2018-02-13 | Witricity Corporation | Wireless power transfer systems with shield openings |
| US10186373B2 (en) | 2014-04-17 | 2019-01-22 | Witricity Corporation | Wireless power transfer systems with shield openings |
| US9842687B2 (en) | 2014-04-17 | 2017-12-12 | Witricity Corporation | Wireless power transfer systems with shaped magnetic components |
| US9837860B2 (en) | 2014-05-05 | 2017-12-05 | Witricity Corporation | Wireless power transmission systems for elevators |
| US10018744B2 (en) | 2014-05-07 | 2018-07-10 | Witricity Corporation | Foreign object detection in wireless energy transfer systems |
| US10371848B2 (en) | 2014-05-07 | 2019-08-06 | Witricity Corporation | Foreign object detection in wireless energy transfer systems |
| US11637458B2 (en) | 2014-06-20 | 2023-04-25 | Witricity Corporation | Wireless power transfer systems for surfaces |
| US9954375B2 (en) | 2014-06-20 | 2018-04-24 | Witricity Corporation | Wireless power transfer systems for surfaces |
| US10923921B2 (en) | 2014-06-20 | 2021-02-16 | Witricity Corporation | Wireless power transfer systems for surfaces |
| US10574091B2 (en) | 2014-07-08 | 2020-02-25 | Witricity Corporation | Enclosures for high power wireless power transfer systems |
| US9842688B2 (en) | 2014-07-08 | 2017-12-12 | Witricity Corporation | Resonator balancing in wireless power transfer systems |
| US9843217B2 (en) | 2015-01-05 | 2017-12-12 | Witricity Corporation | Wireless energy transfer for wearables |
| US10248899B2 (en) | 2015-10-06 | 2019-04-02 | Witricity Corporation | RFID tag and transponder detection in wireless energy transfer systems |
| US9929721B2 (en) | 2015-10-14 | 2018-03-27 | Witricity Corporation | Phase and amplitude detection in wireless energy transfer systems |
| US10063110B2 (en) | 2015-10-19 | 2018-08-28 | Witricity Corporation | Foreign object detection in wireless energy transfer systems |
| US10141788B2 (en) | 2015-10-22 | 2018-11-27 | Witricity Corporation | Dynamic tuning in wireless energy transfer systems |
| US10651689B2 (en) | 2015-10-22 | 2020-05-12 | Witricity Corporation | Dynamic tuning in wireless energy transfer systems |
| US10651688B2 (en) | 2015-10-22 | 2020-05-12 | Witricity Corporation | Dynamic tuning in wireless energy transfer systems |
| US10075019B2 (en) | 2015-11-20 | 2018-09-11 | Witricity Corporation | Voltage source isolation in wireless power transfer systems |
| US10263473B2 (en) | 2016-02-02 | 2019-04-16 | Witricity Corporation | Controlling wireless power transfer systems |
| US10637292B2 (en) | 2016-02-02 | 2020-04-28 | Witricity Corporation | Controlling wireless power transfer systems |
| US10913368B2 (en) | 2016-02-08 | 2021-02-09 | Witricity Corporation | PWM capacitor control |
| US11807115B2 (en) | 2016-02-08 | 2023-11-07 | Witricity Corporation | PWM capacitor control |
| US10063104B2 (en) | 2016-02-08 | 2018-08-28 | Witricity Corporation | PWM capacitor control |
| US11588351B2 (en) | 2017-06-29 | 2023-02-21 | Witricity Corporation | Protection and control of wireless power systems |
| US11637452B2 (en) | 2017-06-29 | 2023-04-25 | Witricity Corporation | Protection and control of wireless power systems |
| US11043848B2 (en) | 2017-06-29 | 2021-06-22 | Witricity Corporation | Protection and control of wireless power systems |
| US11031818B2 (en) | 2017-06-29 | 2021-06-08 | Witricity Corporation | Protection and control of wireless power systems |
Similar Documents
| Publication | Publication Date | Title |
|---|---|---|
| JPH10164837A (en) | Power supply | |
| US6198638B1 (en) | Synchronous rectifier flyback circuit for zero voltage switching | |
| US7499299B2 (en) | Method and apparatus for reducing body diode conduction of synchronous rectifiers | |
| KR100734715B1 (en) | Externally-driven synchronous rectifier circuit and method of rectifying the same | |
| US20080291702A1 (en) | Switching power supply apparatus | |
| EP0957568B1 (en) | Current resonance type switching power source | |
| US20080037290A1 (en) | Ac-dc converter and method for driving for ac-dc converter | |
| JP5040268B2 (en) | Switching power supply | |
| US7400061B2 (en) | Soft switched secondary side post regulator for DC to DC converter | |
| US11539300B1 (en) | DC to DC power converter device capable of either bidirectional step-up conversion or bidirectional step-down conversion, and control method thereof | |
| JP3626072B2 (en) | Switching power supply | |
| US20050041438A1 (en) | Pulse width modulation soft-switching control | |
| WO2001052395A1 (en) | Method and apparatus for driving switching elements of current-controlled power conversion device | |
| JPH10243647A (en) | Power unit | |
| US7400519B2 (en) | Switching power supply | |
| JP4683364B2 (en) | Composite resonant switching power supply | |
| KR100774145B1 (en) | Power converter having a self driven synchronous rectifier | |
| JP2001292571A (en) | Synchronous rectifying circuit | |
| JPH0636392U (en) | Flyback converter | |
| US20050265056A1 (en) | Control method and circuit for synchronous rectifiers used in ZVS DC/DC converter | |
| JP3226470B2 (en) | Synchronous rectification circuit and switching power supply circuit | |
| JP4419341B2 (en) | Switching power supply | |
| JP2882472B2 (en) | Power supply circuit using power insulated gate type FET | |
| JP2716221B2 (en) | DC-DC converter | |
| JPH06303769A (en) | Step-down chopper type switching power supply |