WO2024051767A1 - 天线结构件、天线和基站 - Google Patents

天线结构件、天线和基站 Download PDF

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Publication number
WO2024051767A1
WO2024051767A1 PCT/CN2023/117404 CN2023117404W WO2024051767A1 WO 2024051767 A1 WO2024051767 A1 WO 2024051767A1 CN 2023117404 W CN2023117404 W CN 2023117404W WO 2024051767 A1 WO2024051767 A1 WO 2024051767A1
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WO
WIPO (PCT)
Prior art keywords
antenna
capacitor
gap
capacitance value
structural
Prior art date
Application number
PCT/CN2023/117404
Other languages
English (en)
French (fr)
Inventor
张玉禄
白雪
谢国庆
肖伟宏
李磊
Original Assignee
华为技术有限公司
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by 华为技术有限公司 filed Critical 华为技术有限公司
Publication of WO2024051767A1 publication Critical patent/WO2024051767A1/zh

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Classifications

    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/12—Supports; Mounting means
    • H01Q1/22—Supports; Mounting means by structural association with other equipment or articles
    • H01Q1/24—Supports; Mounting means by structural association with other equipment or articles with receiving set
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/52—Means for reducing coupling between antennas; Means for reducing coupling between an antenna and another structure
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q15/00—Devices for reflection, refraction, diffraction or polarisation of waves radiated from an antenna, e.g. quasi-optical devices
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q15/00—Devices for reflection, refraction, diffraction or polarisation of waves radiated from an antenna, e.g. quasi-optical devices
    • H01Q15/02—Refracting or diffracting devices, e.g. lens, prism
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q19/00—Combinations of primary active antenna elements and units with secondary devices, e.g. with quasi-optical devices, for giving the antenna a desired directional characteristic
    • H01Q19/06—Combinations of primary active antenna elements and units with secondary devices, e.g. with quasi-optical devices, for giving the antenna a desired directional characteristic using refracting or diffracting devices, e.g. lens
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04W—WIRELESS COMMUNICATION NETWORKS
    • H04W88/00—Devices specially adapted for wireless communication networks, e.g. terminals, base stations or access point devices
    • H04W88/08—Access point devices

Definitions

  • the present application relates to the field of antenna technology, and in particular to an antenna structural member, an antenna and a base station.
  • the radiating unit may be blocked by surrounding metal parts.
  • the electromagnetic wave When the electromagnetic wave propagates to these metal parts, it will scatter on the surface of the metal part and cannot completely propagate to the rear of the metal part, causing the generation of electromagnetic waves behind the metal part.
  • Electromagnetic shadow For the signal receiving process of the antenna, the electromagnetic shadow will cause the received signal quality of the antenna device located behind the metal component to deteriorate; for the signal radiation process of the antenna, the electromagnetic shadow will affect the communication quality of the terminal located behind the metal component.
  • the present application provides an antenna structure, an antenna and a base station, which can improve the electromagnetic shadow problem caused by the shielding of metal parts.
  • the solution of the present application provides an antenna structural member for use in a base station antenna system.
  • the antenna structural member includes a conductive base and at least two structural units; each of the at least two structural units surrounds the conductive base, and each structural unit is spaced apart from the conductive base.
  • the at least two structural units include adjacent The first structural unit and the second structural unit, and the first structural unit and the second structural unit are arranged at intervals and form a first capacitor, and different parts of the first capacitor have different capacitance values.
  • the antenna structure is a component that physically blocks the radiating unit.
  • the conductive base in the antenna structure has conductive properties, and the conductive base at least includes a conductive part.
  • the entire area of the conductive base is a conductor, or the conductive base includes a conductor part and an insulating part.
  • the conductive substrate includes but is not limited to poles, pole brackets, feed networks, transmission mechanisms, support structures and other metal parts. Conductive substrates will block electromagnetic waves.
  • the structural unit is a conductive structure located outside the conductive base and surrounding the conductive base.
  • the structural unit may be a thin layer.
  • the structural unit and the conductive matrix may be separated, and the two may not be directly connected, so that the two may be electrically isolated.
  • the first structural unit is adjacent to the second structural unit, and a gap may be formed between the first structural unit and the second structural unit, and the gap may surround the conductive base.
  • the first structural unit, the slit and the second structural unit can essentially form a first capacitor, and both the first structural unit and the second structural unit can serve as plates of the first capacitor.
  • Different parts of the first capacitor (corresponding to different areas of the gap) have different capacitance values, that is, some parts have a larger capacitance and other parts have a smaller capacitance value.
  • at least one first capacitor may be formed.
  • the antenna structure can be located near the wave source.
  • the electromagnetic wave emitted by the wave source propagates to the antenna structure, it will be restrained in the first capacitor, propagate along the gap, and be emitted from a certain position in the gap.
  • This allows electromagnetic waves to propagate around the antenna structure. Therefore, even if the antenna structure blocks the wave source, the electromagnetic waves can bypass the antenna structure and propagate to the rear of the antenna structure due to the presence of the first capacitance. Therefore, in this solution, by arranging at least two structural units on the outer periphery of the conductive base and forming a first capacitor, the conductive base has electromagnetic stealth performance relative to electromagnetic waves, thereby reducing or avoiding electromagnetic shadows caused by the conductive base blocking electromagnetic waves.
  • the capacitance values of different regions of the first capacitor are different, electromagnetic wave signals of different frequency bands can resonate in the gap with their respective electrical lengths, so that electromagnetic waves of different frequency bands can pass through the gap. Therefore, by making the capacitance values of different areas of the first capacitor different, the gap can allow electromagnetic waves of multiple frequency bands to pass through, thereby expanding the stealth bandwidth.
  • the first capacitor includes a first part, a second part, a third part and a fourth part, and the first part, the second part, the third part and the fourth part are connected end to end in order, and the first part
  • the capacitance value of the second part is equal to the capacitance value of the third part
  • the capacitance value of the second part is equal to the capacitance value of the fourth part
  • the capacitance value of the first part is different from the capacitance value of the second part.
  • the above four regions can be divided from the first capacitor. These four regions are connected end to end to form a circle, and the capacitance value of the entire first capacitor forms a distribution of large capacitance - small capacitance - large capacitance - small capacitance. style.
  • the area with a larger capacitance value can be equivalent to a patch antenna, and the area with a smaller capacitance value can be equivalent to a slot transmission line (slotline).
  • the wave source can be close to an area with a large capacitance value, and the electromagnetic wave emitted by the wave source can enter the gap from one of the areas with a large capacitance value, and be divided into two paths: one of them is constrained to be transmitted in one of the areas with a small capacitance value, and It emits from another area with a larger capacitance value; the other path is constrained to transmit in another area with a smaller capacitance value, and emits from the other area with a larger capacitance value like the previous electromagnetic wave.
  • this solution can make electromagnetic waves diffract according to the design requirements. It can not only achieve electromagnetic stealth, but also make the propagation characteristics of electromagnetic waves meet the needs of the antenna.
  • the first part and the third part are centrally symmetrically distributed, and the second part and the fourth part are centrally symmetrically distributed.
  • central symmetry means that the structures of the two are consistent, and one of them coincides with the other after rotating 180 degrees around the center of symmetry.
  • the propagation characteristics such as propagation direction, polarization characteristics, frequency band, etc.
  • the width of the gap is different in different parts of the first capacitor.
  • This solution sets different gap widths for different parts of the first capacitor, which ultimately results in different capacitance values of different parts of the first capacitor, thereby achieving the purpose of expanding the stealth bandwidth. It can be understood that this solution at least sets the gap width.
  • the gap width d can also be set at the same time, and at least one of the dielectric constant ⁇ and the plate area S is set, so that different parts of the first capacitor have different capacitance values. the goal of. This solution is simple in design and has good mass productionability.
  • the first capacitor includes a first part and a second part connected; the slit of the first part and the slit of the second part both have the same width, and the width of the slit of the first part is smaller than that of the second part
  • the width of the gap, the capacitance value of the first part is greater than the capacitance value of the second part; or, the gap of the first part and one of the gaps of the second part have the same width, and the other has a variable width, and the maximum value of the gap of the first part
  • the width is less than or equal to the minimum width of the gap in the second part, and the capacitance value of the first part is greater than the capacitance value of the second part.
  • the same width may mean that the gap is a gap of uniform width, the two sides of the gap are basically parallel, and the width of the gap can be consistent everywhere.
  • Variable width can mean that the gap is a gap of non-uniform width, the two sides of the gap are not parallel, and the gap width is inconsistent everywhere in the gap.
  • the gap width of the first part can be smaller than the gap width of the second part, and the capacitance value of the first part can be larger than the capacitance value of the second part, thereby facilitating the purpose of expanding the stealth bandwidth.
  • the maximum width is the width at any position of the gap; when the first part of the gap has a variable width, the maximum width is the width at the widest point of the gap) is less than or equal to the minimum width of the second part of the gap (when the second part of the gap has the same width, the minimum width is the width at any position of the gap; when the gap in the second part has a variable width, the maximum width is the width at the narrowest point of the gap), which can make the gap in the first part overall larger than the gap in the second part narrow.
  • the capacitance value of the first part is made larger than the capacitance value of the second part, thereby facilitating the purpose of expanding the stealth bandwidth.
  • This solution can achieve good electromagnetic stealth and expand the stealth bandwidth by performing the above design on the gap of the first capacitor. Moreover, the design of this solution is relatively simple and has good mass productionability.
  • the first capacitor includes a connected first part and a second part, and the gap in the first part is sequentially bent by at least two sub-slits. Connected, the capacitance value of the first part is greater than the capacitance value of the second part.
  • the first part of the gap is formed by bending and connecting at least two sub-slits in sequence, that is, several sub-slits are connected in sequence, and each two adjacent sub-slits form a bending angle.
  • the bending angle between the sub-slits can be designed as needed, for example, it can be 90°, and the resulting gap can form a shape similar to a square wave.
  • the bending angle of adjacent sub-slits may not be limited to 90°, so that the gaps can form other shapes, such as curved shapes (such as sinusoids, parabolas, etc.).
  • the slits of the second part have the same width; each sub-slit of the first part has the same width, the width of all sub-slits is the same, and the width of the sub-slit is less than or equal to the width of the second part.
  • the width of the gap is less than or equal to the width of the second part.
  • the width of the sub-slit is the width of the first part of the gap.
  • the first capacitor includes a first part and a second part connected, the first part is filled with a first insulating medium, the second part is filled with a second insulating medium, and the first part is filled with a second insulating medium.
  • the dielectric constant is greater than the dielectric constant of the second insulating medium, and the capacitance value of the first part is greater than the capacitance value of the second part.
  • the first insulating medium can fill the gaps in the first part
  • the second insulating medium can fill the gaps in the second part.
  • the first capacitor includes a connected first part and a second part;
  • the antenna structural member includes a second capacitor, the second capacitor is provided in the first part, and the capacitance value of the first part is greater than that of the second part. capacitance value.
  • the second capacitor is an independent capacitor device (may have pins).
  • the second capacitor may be located in the gap of the first part.
  • the total capacitance value of the first part is the capacitance value of the first part calculated according to the capacitance formula plus the capacitance value of the second capacitor.
  • the antenna structural member includes a third capacitor, the third capacitor is provided in the second part, and the capacitance value of the third capacitor is smaller than the capacitance value of the second capacitor.
  • the third capacitor is also an independent capacitor device (may have pins), and the third capacitor may be located in the gap of the second part.
  • the total capacitance value of the second part is the capacitance value of the second part calculated according to the capacitance formula plus the capacitance value of the third capacitor.
  • This solution superimposes a second capacitor in the first part and a third capacitor in the second part, so that the capacitance value of the first part is greater than the capacitance value of the second part, thereby expanding the stealth bandwidth.
  • This solution is simple in design and has good mass productionability.
  • the capacitance value of the second capacitor and/or the third capacitor is adjustable.
  • the capacitance value is adjustable means that the capacitance device can change the capacitance value under signal control.
  • a capacitance device can be a varactor, for example.
  • At least one structural unit is provided with a coupling gap, and parts of the structural unit located on both sides of the coupling gap are disconnected by the coupling gap and coupled through the coupling gap.
  • the structural unit may not be an integrated structure, but may have a coupling gap, which completely separates the structural unit into different regions. There may be at least one coupling gap. The parts of the structural unit located on both sides of the coupling gap are coupled through the coupling gap. When the electromagnetic wave propagates to the structural unit, the electromagnetic wave can "cross" the coupling gap.
  • the number of structural units with a coupling gap is at least one. For example, the above-mentioned first structural unit and the second structural unit have a coupling gap.
  • a coupling gap is formed in the structural unit to facilitate the assembly of different parts of the structural unit onto the conductive substrate in sequence, and finally to form a complete structural unit.
  • This can achieve reliable assembly of the structural unit in some scenarios.
  • the split assembly method can simplify the assembly process and improve the assembly yield.
  • the coupling gap can allow electromagnetic waves in certain frequency bands to pass through, so that the antenna structure has a certain effect in expanding the stealth bandwidth.
  • the antenna structural member includes an inductive element, and a structural unit of at least two structural units is connected to the conductive base through the inductive element.
  • the inductive element can be a conductive mechanical component, such as a metal pillar.
  • the inductive component may be an inductor (which may have leads) belonging to an electronic component.
  • the inductance element connects the structural unit and the conductive substrate.
  • Each structural unit may be connected to the conductive base through at least one inductive element, or only a part of the structural units may be connected to the conductive base through the inductive element.
  • a capacitance (for example, called a plate capacitor) can be formed between the structural unit and the conductive base, and the plate capacitance can affect the frequency band of electromagnetic waves that bypass the antenna structural member.
  • a capacitance for example, called a plate capacitor
  • reducing the spacing may lead to an increase in the frequency band of electromagnetic waves that bypass the antenna structure, changing the propagation characteristics of electromagnetic waves.
  • this solution provides an inductor element, which can form a parallel resonant circuit with the above-mentioned plate capacitor. This parallel resonant circuit can reduce the frequency band of electromagnetic waves that bypass the antenna structure.
  • the effects on the frequency band of arranging the inductive element and reducing the distance between the structural unit and the conductive substrate can cancel each other out, so that the frequency band of the electromagnetic wave that bypasses the antenna structural member remains unchanged, thereby maintaining the propagation characteristics of the electromagnetic wave.
  • At least one structural unit is hollowed out.
  • hollowing out refers to hollowing out local areas of structural units to form holes.
  • At least one structural unit can have such a hollow design.
  • the hollow design can reduce weight and help reduce the weight of the antenna structure. Especially when the structural unit is a heavier metal piece, opening a hollow area can greatly reduce weight.
  • At least two structural units have the same structure, and there is a gap between any two adjacent structural units and the shape is the same, and a third structural unit is formed between any two adjacent structural units.
  • a capacitor
  • the structures of all structural units are consistent. There are gaps between any two structural units, and the shapes of each gaps are the same. As a result, a first capacitance is formed between any two adjacent structural units.
  • This solution allows a plurality of first capacitors to be formed on the antenna structural member, so that electromagnetic waves can be diffracted in various areas of the antenna structural member, making the entire antenna structural member invisible to electromagnetic waves and avoiding electromagnetic shadows.
  • all structural units can form a periodic stealth structural layer, which is easy to manufacture and has good mass production.
  • the structures of at least two structural units are not entirely the same, and/or there is a gap between at least two structural units and the shapes are not entirely the same; there are gaps between any two adjacent structural units. forming the first capacitor.
  • the quasi-periodic stealth structure layer can adapt to the shape and structure of the conductive matrix. For example, if there is a protrusion somewhere on the outer surface of the conductive substrate, the stealth structure layer can avoid the protrusion there to form a quasi-periodic structure.
  • each structural unit includes a conductor layer and an insulating layer, and the insulating layer is located between the conductor layer and the conductive base; or, each structural unit is a conductor.
  • the conductor layer and the insulating layer in the structural unit are stacked, the insulating layer is close to the conductive matrix, and the conductor layer is away from the conductive matrix.
  • the conductor layer is made of conductive material, and the insulating layer is made of insulating material.
  • the conductor layer can be thin and the structural strength is weak.
  • the conductor layer is attached to the insulating layer, and the insulating layer can support and strengthen the conductor layer.
  • the structural unit of this structure can meet product needs and has good mass production.
  • the base station antenna system includes a pole, a pole bracket, and a feed network
  • the conductive base includes at least one of a pole, a pole bracket, and a feed network
  • the antenna structural component can be applied to the base station antenna system (or base station).
  • the base station antenna system includes a radiating unit and a feed network installed in the radome.
  • the radome is fixed on the pole through a pole bracket.
  • the technical solution of the present application provides an antenna, including a radiation unit and any of the above antenna structural members.
  • the radiating unit is close to the antenna structure.
  • the electromagnetic waves sent and received by the radiation unit can propagate around the antenna structural member, thereby improving the electromagnetic shadow problem.
  • the technical solution of this application provides a base station, which includes a pole and a first antenna.
  • the first antenna is fixed on the pole, and the first antenna is the antenna mentioned above.
  • the electromagnetic waves sent and received by the radiating unit of the first antenna can propagate around the antenna structural member, thereby improving the electromagnetic shadow problem.
  • the base station includes a second antenna and a frequency selection surface.
  • the frequency selection surface is located between the radiating unit of the first antenna and the radiating unit of the second antenna.
  • the frequency selection surface is used to reflect the first antenna.
  • the radiation signal is transmitted through the radiation signal of the second antenna.
  • the working frequency band of the second antenna may be different from the working frequency band of the first antenna.
  • the radiating unit of the second antenna and the radiating unit of the first antenna may be in different radomes, and the two radomes may be fixed on the same pole. This allows the two antennas to be deployed separately, enabling decoupling design and flexible deployment of antennas in different frequency bands.
  • the radiating unit of the second antenna and the radiating unit of the first antenna may be in the same radome.
  • the frequency selective surface is a two-dimensional structure including several units. All units can be identical and arranged in a certain way, or all units are not identical and arranged in a certain way.
  • the frequency selective surface can be a single-layer structure or a multi-layer structure.
  • the frequency selective surface has a specific frequency selective effect. It can be transmissive to the incident wave of one frequency band under resonance and can be reflective to the incident wave of another frequency band under resonance, thus effectively controlling the incident wave. Transmission and reflection of electromagnetic waves.
  • the frequency selective surface can be, for example, a spatial filter, which interacts with electromagnetic waves to exhibit obvious bandpass or bandstop filtering characteristics. Multiple layers of frequency selective surfaces can be used as multi-order spatial filters to expand bandwidth and increase frequency selectivity.
  • the frequency selective surface can reflect most of the electromagnetic waves of the radiating unit of the first antenna, so the frequency selective surface can serve as a reflecting plate of the radiating unit of the first antenna.
  • the frequency selective surface can also transmit the electromagnetic waves of the radiating unit of the second antenna. Therefore, the frequency selective surface will not block the electromagnetic waves of the radiating unit of the second antenna.
  • the frequency selective surface will not block the electromagnetic waves of the radiating unit of the second antenna. It is equivalent to being electromagnetically transparent.
  • the radiating unit of the first antenna and the radiating unit of the second antenna are respectively located on both sides of the frequency selection surface, so that the first antenna and the second antenna are arranged in a stacked manner.
  • the stacked arrangement can deploy antennas with more frequency bands and channels within a limited antenna aperture to meet communication requirements.
  • the electromagnetic waves radiated by the second antenna will bypass the antenna structural member and continue to propagate, or the electromagnetic wave will bypass the antenna structural member and be received by the second antenna, thereby Improved electromagnetic shadow issue.
  • Figure 1 shows the application scenario of wireless communication between the base station and the terminal
  • Figure 2 shows the assembly structure of an antenna system according to an embodiment of the present application
  • Figure 3 shows part of the internal frame structure of the antenna system in Figure 2;
  • Figure 4 shows part of the internal frame structure of an antenna system according to an embodiment of the present application
  • Figure 5 is a schematic three-dimensional structural diagram of an antenna structural member in an embodiment
  • Figure 6 is a schematic side cross-sectional structural view of the antenna structure shown in Figure 5;
  • Figure 7 is a schematic three-dimensional structural diagram of an antenna structural member in an embodiment
  • Figure 8(a) is a schematic three-dimensional structural diagram of an antenna structural member in an embodiment
  • Figure 8(b) is a partial enlarged structural diagram of position A in Figure 8(a);
  • Figure 9 is a schematic three-dimensional structural diagram of an antenna structural member in an embodiment
  • Figure 10 shows the application principle of the antenna structural component shown in Figure 9 in an antenna system
  • Figure 11 is a schematic three-dimensional structural diagram of an antenna structural member in an embodiment
  • Figure 12 is a schematic three-dimensional structural diagram of an antenna structural member in an embodiment
  • Figure 13 is a schematic three-dimensional structural diagram of an antenna structural member in an embodiment
  • Figure 14 is a schematic three-dimensional structural diagram of an antenna structural member in an embodiment
  • Figure 15 is a schematic side view of the antenna structure shown in Figure 14;
  • Figure 16 is a schematic three-dimensional structural diagram of an antenna structural member in an embodiment
  • Figure 17 is a schematic three-dimensional structural diagram of an antenna structural member in an embodiment.
  • 1-antenna system 11-pole; 12-pole bracket; 13-radome; 14-antenna device; 15-RF processing unit; 16-cable; 17-baseband processing unit; 18-feed network; 181 -Phase shifter; 182-power divider; 183-filter;
  • 2-antenna system 21-first radome; 22-first antenna device; 221-first radiating unit; 222-second radiating unit; 23-frequency selective surface; 24-antenna structural member; 241-stealth structural layer ; 242-phase shifter 242; 25-second antenna cover; 26-second antenna device;
  • 3-antenna structural member 3a-spacing; 31-conductive matrix; 32-structural unit; 32a-first capacitor; 32b-first part; 32c-second part; 32d-third part; 32e-fourth part; E -Electric field direction; H-Magnetic field direction; K-Electromagnetic wave propagation direction;
  • 5-antenna structural member 51-conductive matrix; 52-structural unit; 52b-first part; 52d-sub-slit; 52c-second part;
  • 6-antenna structural member 61-conductive matrix; 62-structural unit; 62b-first part; 62c-second part; 62d-third part; 62e-fourth part;
  • 7-antenna structural member 71-conductive matrix; 72-structural unit; 721-first part; 722-second part; 723-third part; 724-fourth part; 72b-first part; 72c-second part; 72f-coupling gap; 72g-coupling gap; 72h-coupling gap; 72i-coupling gap;
  • 8-antenna structural member 81-conductive matrix; 82-structural unit; 821-first part; 822-second part; 82b-first part; 82c-second part; 82f-coupling gap; 82g-coupling gap;
  • 9-antenna structural member 91-conductive matrix; 92-structural unit; 92b-first part; 92c-second part; 92f-hollow area; 92g-hollow area;
  • 10-antenna structural member 101-conductive matrix; 102-structural unit; 102a-first capacitor; 103a-first insulating medium; 103b-second insulating medium;
  • 20-antenna structural member 201-conductive matrix; 202-structural unit; 202a-first capacitor; 203-second capacitor device; 204-first capacitor device;
  • 30-antenna structural member 301-conductive substrate; 302-structural unit; 302a-first capacitor; 303-inductor element.
  • the embodiment of the present application provides an antenna system, which can be applied to any device or system capable of radiating and receiving antenna signals.
  • the antenna system can be used in radar systems on ships.
  • the antenna system may be a base station, and the antenna system may include, for example, a base station antenna feed system of the base station. The following will first introduce the base station, and then take the antenna system including the base station antenna feeder system as an example.
  • FIG. 1 illustrates the application scenario of wireless communication between a base station and a terminal.
  • the base station is used to provide cell coverage for wireless signals to achieve communication between terminal equipment and the wireless network.
  • the base station can be a base transceiver station (BTS) in the global system for mobile communication (GSM) or code division multiple access (code division multiple access, CDMA) system, or it can be A NodeB (NB) in a wideband code division multiple access (WCDMA) system, or an evolutionary NodeB (eNB) in a long term evolution (LTE) system , or it can be a wireless controller in a cloud radio access network (CRAN) scenario.
  • GSM global system for mobile communication
  • CDMA code division multiple access
  • NB wideband code division multiple access
  • eNB evolutionary NodeB
  • LTE long term evolution
  • CRAN cloud radio access network
  • the base station can also be a relay station, an access point, a vehicle-mounted device, a wearable device, a g node (gNodeB or gNB) in a new radio (NR) system or a base station in a future evolved network, etc., in the embodiments of this application Not limited.
  • gNodeB or gNB g node
  • NR new radio
  • FIG. 2 shows a schematic diagram of an application scenario of the antenna equipped with the base station shown in Figure 1 (or base station antenna system, that is, antenna system 1 in Figure 2).
  • the antenna system 1 may include a pole 11 , a pole bracket 12 , a radome 13 , an antenna array 14 , a radio frequency processing unit 15 , a cable 16 and a baseband processing unit 17 .
  • the pole support 12, the radome 13, and the antenna array 14 can be collectively referred to as an antenna, and the antenna can also include a feed network and a reflector, which will be described below.
  • the pole 11 can be fixed to the ground.
  • the pole bracket 12 connects the pole 11 and the radome 13 , and the radome 13 is fixed to the pole 11 through the pole bracket 12 .
  • Antenna array 14 may be mounted within radome 13 .
  • a feed network can also be installed inside the radome 13 .
  • the radome 11 has good electromagnetic wave penetration characteristics and environmental weather resistance, and can protect components installed inside it.
  • Antenna array 14 is used to radiate and receive antenna signals.
  • the antenna array 14 may include several radiating units arranged in a certain regular array, and each radiating unit can radiate and receive electromagnetic waves.
  • the radiating unit may also include an antenna element.
  • the working frequency bands of different radiating units may be the same or different.
  • the antenna may also include a reflective plate.
  • the reflective plate may also be called a bottom plate, an antenna panel, a reflective surface, etc.
  • the reflective plate may be made of a metal material, for example.
  • the radiating unit can be mounted on the surface on one side of the reflector. When the radiating unit receives the antenna signal, the reflective plate can reflect the antenna signal and focus it on the receiving point to achieve directional reception; when the radiating unit transmits the antenna signal, the reflective plate can achieve directional transmission of the antenna signal.
  • the reflective plate can enhance the reception or emission capability of the antenna signal of the radiating unit, and can also block and shield the interference effect of other signals on the antenna signal from the back of the reflective plate (the back refers to the side of the reflective plate facing away from the radiating unit). , improve the gain of the antenna.
  • the radio frequency processing unit 15 (also called a radio frequency remote unit (RRU)) can be connected to the feed network through a jumper, and is electrically connected to the antenna array 14 through the feed network.
  • the feed network (will be described below) ) can be used as a signal transmission path between the radio frequency processing unit 15 and the antenna array 14 .
  • the radio frequency processing unit 15 may be electrically connected to the baseband processing unit 17 (which may also be called a baseband unit (BBU)) through a cable 16 (such as an optical cable).
  • BBU baseband unit
  • the radio frequency processing unit 15 and the baseband processing unit 17 may both be located outside the radome 13 , and the radio frequency processing unit 15 may be located at the proximal end of the antenna.
  • the radio frequency processing unit 15 can perform frequency selection, amplification and frequency down-conversion processing on the antenna signals received by the antenna array 14 , and convert them into intermediate frequency signals or baseband signals and send them to the baseband processing unit 17 .
  • the radio frequency processing unit 15 can also convert the baseband processing unit 17 or the intermediate frequency signal through up-conversion and amplification processing into electromagnetic waves through the antenna array 14 and send them out.
  • FIG. 3 may represent part of the internal frame structure of the antenna system 1 in FIG. 2 .
  • the antenna array 14 of the antenna system 1 is connected to the feed network 18 .
  • the feed network 18 can achieve different radiation beam directions through a transmission mechanism, or be connected to a calibration network to obtain the calibration signals required by the antenna system 1 .
  • the feeding network 18 can feed signals to the antenna array 14 according to a certain amplitude and phase, or send received signals to the baseband processing unit 17 according to a certain amplitude and phase.
  • the feed network 18 may include a phase shifter 181, which is used to change the maximum direction of antenna signal radiation.
  • the feed network 18 may also include modules for extending performance, such as a power splitter 182 .
  • the power splitter 182 is used to combine multiple signals into one signal and transmit it through the antenna array 14; or, the power splitter 182 divides one signal into multiple signals, for example, the signal received by the antenna array 14 is Different frequencies are multiplexed and transmitted to the baseband processing unit 17 for processing.
  • the feed network 18 may also include a filter 183 for filtering out interference signals.
  • the structure of the antenna system 1 shown in Figures 2 and 3 is only an example. In fact, the structure of the antenna system in the embodiment of the present application can be flexibly designed according to product requirements and is not limited to the above.
  • the antenna system may not have the pole 11 , and the radome 13 may be fixed to the tower through the pole bracket 12 .
  • the antenna device may be surrounded by a conductive component (the conductive component at least includes a conductive part, for example, the entire area of the conductive component is a conductor, or the conductive component includes a conductive part and an insulating part.
  • the conductive component will be referred to as When electromagnetic waves propagate to these conductive components, they will be scattered on the surface of the conductive components and cannot completely propagate to the rear of the conductive components, causing electromagnetic shadows to be generated behind the conductive components.
  • the electromagnetic shadow will cause the received signal quality of the antenna device located behind the conductive component to deteriorate; for the signal radiation process of the antenna device, the electromagnetic shadow will affect the communication quality of the terminal located behind the conductive component.
  • the antenna system of the embodiment of the present application has an "electromagnetic stealth" design for the conductor component around the antenna device, so that electromagnetic waves can continue to propagate around the conductor component, reducing or eliminating electromagnetic shadows. This will be explained in detail below.
  • Figure 4 illustrates a partial internal frame structure of the antenna system 2 in an embodiment.
  • the antenna system 2 has the above-mentioned electromagnetic stealth design.
  • the antenna system 2 may include a first antenna and a second antenna.
  • the first antenna may include a first radome 21 , a first radiating unit 22 , a frequency selection surface 23 , and an antenna structure 24 .
  • the second antenna may include a second antenna cover 25 and a second radiating unit 26 .
  • the first radome 21 and the second radome 25 are two independent radomes, and they can be fixed on the same pole or tower.
  • the first radiating unit 22 , the frequency selective surface (FSS) 23 and the antenna structure 24 may be located in the first radome 21
  • the second radiating unit 26 may be located in the second radome 25 .
  • the first radiation unit 22 may include a third radiation unit 221 and a fourth radiation unit 222.
  • Each of the third radiation unit 221 and the fourth radiation unit 222 may be several.
  • the third radiation unit 221 and the fourth radiating unit 222 may have different working frequency bands.
  • the working frequency band of the third radiating unit 221 may be 690MHz-960MHz
  • the working frequency band of the fourth radiating unit 222 may be 1427MHz-2690MHz.
  • Both the third radiating unit 221 and the fourth radiating unit 222 may be connected to respective feed networks.
  • the working frequency band of the second radiating unit 26 may be 3.3GHz-3.8GHz. It can be understood that other components may also be provided in the second antenna cover 25 , such as a feed network connected to the second radiating unit 26 .
  • the first radiating unit 22 and the second radiating unit 26 are respectively provided in different radomes, so that the two antennas can be deployed separately, realizing decoupling design and flexible deployment of antennas in different frequency bands. It is understood that this scheme is only an example. In other embodiments, the first radiating unit 22 and the second radiating unit 26 may also be in the same radome.
  • both the frequency selection surface 23 and the first radiating unit 22 may be located within the first radome 21 , and the frequency selecting surface 23 may be located between the first radiating unit 22 and the second radiating unit 26 . Therefore, the first radiating unit 22 and the second radiating unit 26 can be said to be arranged in a stacked manner.
  • the stacked arrangement can deploy antennas with more frequency bands and channels within a limited antenna aperture to meet communication requirements.
  • the frequency selective surface 23 is a two-dimensional structure including several units. All units may be identical and arranged in a certain manner (this frequency selective surface 23 may be called a periodic array structure), or all units may not be identical. (Any two units are different; or there are at least two identical units, but not all units are the same) and arranged in a certain manner (this frequency selective surface 23 can be called a quasi-periodic array structure).
  • the frequency selective surface 23 may have a single-layer structure or a multi-layer structure.
  • the frequency selection surface 23 in FIG. 3 may be a two-layer structure. When it is a multi-layer structure, the layers of the frequency selective surface 23 can be separated by insulating materials or air.
  • the frequency selection surface 23 has a specific frequency selection function, which can be transmissive to the incident wave of one frequency band under resonance and can be reflective to the incident wave of another frequency band under resonance, so that it can effectively control Transmission and reflection of incident electromagnetic waves.
  • the frequency selection surface 23 may be, for example, a spatial filter, which interacts with electromagnetic waves to exhibit obvious band-pass or band-rejection filtering characteristics.
  • the multi-layered frequency selective surface 23 can be used as a multi-order spatial filter, which can expand the bandwidth and increase the frequency selectivity.
  • the frequency selective surface 23 can reflect most of the electromagnetic waves radiated by the third radiating unit 221 and the fourth radiating unit 222 , so the frequency selective surface 23 can serve as a reflecting plate for the third radiating unit 221 and the fourth radiating unit 222 .
  • the frequency selective surface 23 can also transmit the electromagnetic waves radiated by the second radiating unit 26. Therefore, the frequency selective surface 23 does not block the second radiating unit 26.
  • the frequency selective surface 23 does not block the electromagnetic waves radiated by the second radiating unit 26. It is equivalent to being electromagnetically transparent.
  • the antenna structure 24 may be located between the first radiating unit 22 and the second radiating unit 26 .
  • the antenna structure 24 may be a feed network with an electromagnetic stealth design, such as a phase shifter with an electromagnetic stealth design.
  • the antenna structure 24 may include a phase shifter 242 and a stealth structure layer 241 covering the outer surface of the phase shifter 242 .
  • the phase shifter 242 may be connected to the third radiating unit 221 and the fourth radiating unit 222 .
  • Phase shifter 242 has a metal housing, Phase shifter 242 may be referred to as a conductive matrix.
  • the phase shifter 242 located between the first radiating unit 22 and the second radiating unit 26 may block the signal of the second radiating unit 26 .
  • the stealth structure layer 241 may cover part of the outer surface of the phase shifter 242 or the entire outer surface of the phase shifter 242 .
  • the stealth structure layer 241 can allow electromagnetic waves to bypass the phase shifter 242 and continue to propagate, reducing or eliminating electromagnetic shadows, thereby ensuring the transceiver performance of the second radiation unit 26.
  • the specific structure and working principle of the stealth structure layer 241 will be described in detail below.
  • the antenna structure 24 in the above embodiment is a feed network with an electromagnetic stealth design, which is only an example.
  • the stealth structural layer can be provided on the outer surface of any conductive base in the antenna system 2 that may block the signal of the second radiation unit 26 to form an antenna structure.
  • the pole 11 may block the signal of the antenna array 14 in the radome 13.
  • the outer surface of the pole 11 can be covered with a stealth structure layer.
  • the specific distribution of the stealth structure layer can be determined as needed.
  • the stealth structure layer can be covered in a corresponding local area of the outer surface of the pole 11 according to the scanning range of the antenna array 14; or, the stealth structure layer can cover the entire outer surface of the pole 11.
  • the pole 11 serves as a conductive base, and the pole 11 and the stealth structural layer can form an antenna structure.
  • the pole support 12 can be used as a conductive base, and the pole support 12 and the stealth structure layer thereon can constitute another antenna structure.
  • antenna system 1 can also be used as conductive substrates, and these metal parts and the stealth structural layer on them can constitute another antenna structure.
  • the antenna structure described below can be applied to any antenna system, such as the antenna system 1 shown in FIG. 2 and the antenna system 2 shown in FIG. 4 .
  • FIG. 5 illustrates the schematic three-dimensional structure of the antenna structural member 3 in an embodiment
  • FIG. 6 schematically illustrates the schematic side view structure of the antenna structural member 3 of FIG. 5
  • the antenna structural member 3 may include a conductive base 31 and at least two structural units 32 .
  • the conductive base 31 may be substantially cylindrical, and its axial length is, for example, at least 1* ⁇ ( ⁇ is the wavelength corresponding to the lowest frequency band of the antenna device blocked by the conductive base 31). It can be understood that the substantially cylindrical conductive base 31 is only an example, and the embodiments of the present application do not limit the actual shape and structure of the conductive base.
  • the cross-sectional shape of the conductive substrate includes, but is not limited to, quadrangular, circular, elliptical, hexagonal, etc.
  • Figure 5 schematically depicts five structural units 32.
  • the structure of the structural unit 32 can be designed as needed, for example, it can be sheet-shaped, ring-shaped, etc. All structural units 32 may be collectively referred to as the stealth structural layer.
  • all structural units 32 are located outside the conductive base 31 .
  • these structural units 32 may only surround the outside of the outer peripheral surface of the conductive base 31 (the outer peripheral surface is the surface surrounding the axis of the conductive base 31 ), and are not provided on the end surface of the conductive base 31 (the outer peripheral surface is the surface surrounding the axis of the conductive base 31 ).
  • the end surface is the outer surface (surface) perpendicular to the axis of the conductive base 31 .
  • the structural units 32 may be distributed both outside the outer peripheral surface and outside the end surface. The following description will continue with the implementation shown in FIG. 5 as an example.
  • the structural unit 32 can be made of conductive material.
  • Such structural unit 32 can be, for example, a metal piece formed from sheet metal, which has a relatively large weight and structural strength.
  • the structural unit 32 may include a conductor layer and an insulating layer, which are stacked, with the insulating layer close to the conductive base 31 and the conductor layer facing away from the conductive base 31 .
  • the conductor layer is made of conductive material, and the insulating layer is made of insulating material.
  • the conductor layer can be thin and the structural strength is weak.
  • the conductor layer is attached to the insulating layer, and the insulating layer can support and strengthen the conductor layer.
  • each structural unit 32 is separated from the conductive base 31 , and they are not directly connected.
  • the radial size of the gap 3a (that is, the size of the gap 3a in the radial direction of the conductive base 31, this size can also be called the electrical thickness) can be, for example, 0.5* ⁇ ( ⁇ is the lowest frequency band corresponding to the antenna device blocked by the conductive base 31 wavelength).
  • the gap 3a between the structural unit 32 and the conductive base 31 can be filled with an insulating medium (used in Figure 6 Diagonal shading indicates insulating media).
  • the insulating medium can be continuously distributed and cover the entire outer circumferential surface of the conductive base 31 , that is, the insulating medium is distributed both in the intervals 3 a and in the gaps between adjacent structural units 32 (the gaps will be in (Explanation continues below).
  • the insulating medium is distributed discretely on the entire outer circumferential surface of the conductive base 31 .
  • the insulating medium is only distributed in the intervals 3 a but not in the gaps between adjacent structural units 32 .
  • the insulating medium in each interval 3a can be distributed discretely, the insulating medium everywhere forms a structure similar to several connecting pillars, gaps are formed between the insulating medium everywhere, and air exists in the gap; or, each The insulating medium within interval 3a is continuously distributed.
  • the insulating medium can not only connect the structural unit 32 and the conductive base 31 , but also electrically isolate the structural unit 32 and the conductive base 31 .
  • the insulating medium everywhere on the outer circumferential surface of the conductive base 31 is of the same material, that is, all the insulating media on the outer peripheral surface of the conductive base 31 are made of the same material.
  • the insulating media at the locations have the same dielectric constant.
  • the insulating medium at various places on the outer circumferential surface of the conductive base may be different materials with different dielectric constants, which will be further described below.
  • the insulating layer in the structural unit 32 can replace the insulating medium in the gap 3a, so the gap 3a does not need to be filled with the insulating medium. It can be understood that, according to product requirements, the structural unit 32 with an insulating layer can also be filled with an insulating medium.
  • the above-mentioned insulating medium may also be called an insulating bracket.
  • the insulating bracket serves to connect and isolate the structural unit 32 and the conductive base 31 .
  • the structural unit 32 includes an insulating layer and a conductive layer, the insulating layer may also be called an insulating bracket.
  • the structural unit 32 is connected to the conductive base 31 through the insulating bracket and is isolated from the conductive base 31 .
  • all structural units 32 can be distributed sequentially along the axial direction of the conductive base 31 , and every two adjacent structural units 32 (one structural unit 32 can be called the first structural unit, and the other structural unit 32 can be called the first structural unit).
  • a gap may be formed between the units 32 (called second structural units), and the gap surrounds the conductive base 31 .
  • the above-mentioned insulating medium may be distributed in the gap, or may not be distributed in the gap.
  • Each structural unit 32 has conductive properties, so that the gap can actually form a capacitor, which can be called the first capacitor 32a.
  • the structural units 32 on both sides of the first capacitor 32a can serve as the plates of the first capacitor 32a.
  • the insulating medium in the gap can also be a component of the first capacitor 32a.
  • the first capacitor 32a may include a first part 32b, a second part 32c, a third part 32d and a fourth part 32e, and these four areas are connected end to end in sequence.
  • the first part 32b and the third part 32d may be centrally symmetrical, and the center of symmetry of the two parts may be the axis of the conductive base 31 .
  • the first part 32b and the third part 32d are centrally symmetrically distributed, which means that the structures of the two are consistent (the consistent structure includes the distribution of the insulating medium in the two areas). One of them coincides with the other after rotating 180 degrees around the center of symmetry. .
  • the second part 32c and the fourth part 32e may be centrally symmetrical, and the center of symmetry of the two parts may be the axis of the conductive base 31 .
  • the second part 32c and the fourth part 32e are centrally symmetrically distributed, which means that the structures of the two are consistent (the consistent structure includes the distribution of the insulating medium in the two areas). One of them is rotated 180 degrees around the center of symmetry and is connected to the other. coincide.
  • the electrode plates are the structural units 32 on both sides of the first capacitor 32a, and the medium between the electrode plates is the insulating medium (for the case where the insulating medium is distributed in the gap between the structural units 32) or air (for the situation between the structural units 32). There is no insulating medium in the gap between them), S is the facing area of the adjacent structural unit 32, and d is the width of the gap.
  • the capacitance values of the first part 32b and the third part 32d are equal.
  • the second part 32c and the fourth part 32e are centrally symmetrically distributed, the capacitance values of the second part 32c and the fourth part 32e are equal. The following will take the first part 32b and the second part 32c as the description object, and continue to explain the characteristics of the first capacitor 32a.
  • the corresponding gap in the first part 32b can have a uniform width, that is, the two sides of the gap in the first part 32b are basically parallel, and the width of the gap everywhere in the first part 32b can be the same, or it can be said that the gap in the first part 32b has the same width.
  • the gap corresponding to the second part 32c may have a non-uniform width, that is, the two sides of the gap in the second part 32c are not parallel, and the width of the gap everywhere in the second part 32c is inconsistent, or it is said that the gap in the second part 32c has a variable width.
  • the two sides of the gap in the second part 32c can be curves (for example, arcs), the width of the gap at both ends of the second part 32c can be smaller, and the width of the gap in the middle between the two ends can be larger. , the gap width from both ends to the middle may be gradual, thereby making the gap widths everywhere in the second part 32c inconsistent.
  • the maximum width of the gap in the first part 32b may be less than or equal to the minimum width of the gap in the second part 32c (for example, the second part 32c is adjacent to the first part 32b (the gap width at ), that is to say, overall, the gap width of the first part 32b is smaller than the gap width of the second part 32c. Therefore, according to the above capacitance formula, it can be known that the capacitance value of the first part 32b is greater than the capacitance value of the second part 32c.
  • all structural units 32 have the same shape and are evenly spaced, so that all the gaps have the same shape and are evenly spaced.
  • the stealth structure layer thus formed can be said to have a periodic structure. .
  • the shapes of all structural units 32 may not be exactly the same (meaning that any two structural units 32 have different shapes; or, at least two structural units 32 may have the same shape, but not all structural units 32 may have the same shape). same), and/or, all structural units 32 may not be evenly spaced (meaning that for all gaps between structural units 32, the shapes of any two gaps are different; or at least two gaps have the same shape, but not All gaps have the same shape). This results in all gaps having inconsistent shapes and/or non-uniform shapes. Evenly spaced distribution, the resulting stealth structure layer can be called a quasi-periodic structure.
  • a quasi-periodic structure may be a structure obtained by deleting several structural units from a periodic structure.
  • the stealth structure layer with a quasi-periodic structure can adapt to the shape and structure of the conductive base 31 . For example, if there is a protrusion somewhere on the outer surface of the conductive base 31, the stealth structure layer can avoid the protrusion there to form a quasi-periodic structure.
  • Figures 5 and 6 also show the relationship between the wave source and the antenna structural member 3, where the wave source refers to the source of the electromagnetic wave.
  • the wave source is the antenna device; for the receiving process of the antenna device, the wave source can be understood as aerial environment.
  • K represents the propagation direction of electromagnetic waves
  • E represents the direction of the electric field
  • H represents the direction of the magnetic field.
  • the origin of the coordinate system can refer to the position of the wave source.
  • the narrower first part 32b can be closest to the wave source, and the narrower third part 32d can be farthest from the wave source.
  • the electromagnetic wave will change the direction of propagation and be constrained to propagate in the gap along the extension direction of the gap.
  • the electromagnetic wave can propagate in two ways. One electromagnetic wave propagates along the paths of the first part 32b, the second part 32c and the third part 32d, and the other electromagnetic wave propagates along the paths of the first part 32b, the fourth part 32e and the third part 32d. Three parts of 32d path propagation. When the two electromagnetic waves propagate to the third part 32d, they will be emitted from the third part 32d in the propagation direction K.
  • the first part 32b can receive electromagnetic waves from the wave source, and the third part 32d can emit electromagnetic waves.
  • the first part 32b and the third part 32d are equivalent to patch antennas.
  • the second part 32c and the fourth part 32e can confine electromagnetic waves therein for transmission, and they can be equivalent to slot lines.
  • the function of the first capacitor 32a is to change the propagation direction of the electromagnetic wave emitted by the wave source and constrain the electromagnetic wave to propagate within it, so that the electromagnetic wave can propagate around the antenna structure 3 and keep the electromagnetic wave from the first capacitor.
  • the propagation direction remains unchanged when 32a is ejected. Therefore, even if the antenna structural member 3 blocks the wave source, the electromagnetic wave can bypass the antenna structural member 3 and propagate to the rear of the antenna structural member 3 due to the presence of the first capacitor 32a, thereby reducing or eliminating electromagnetic shadows.
  • the propagation direction of the electromagnetic wave does not need to be changed, the propagation characteristics of the electromagnetic wave can be ensured to remain unchanged.
  • the antenna structural member 3 of this embodiment disposes at least two structural units 32 on the outer periphery of the conductive base 31 and forms the first capacitor 32a, so that the conductive base 31 has electromagnetic stealth performance relative to electromagnetic waves, thereby avoiding or reducing the need for 31 Blocking of electromagnetic waves.
  • the electromagnetic wave signals of different frequency bands can resonate in the gap with their respective electrical lengths, so that the electromagnetic waves of different frequency bands can pass through the gap. That is, by making the capacitance values of different areas of the first capacitor 32a different, the gap can allow electromagnetic waves of multiple frequency bands to pass through, thereby expanding the stealth bandwidth.
  • first capacitor 32a in the antenna structural member 3 the shielding of electromagnetic waves by the conductive base 31 can be improved and the stealth bandwidth can be expanded.
  • the number of first capacitors 32a may be multiple according to actual needs.
  • the design with a larger capacitance value in the first part 32b close to the wave source can meet the propagation needs of electromagnetic waves in some frequency bands, but this is not a limitation on the embodiment of the present application.
  • the corresponding relationship between the capacitance value of each area of the first capacitor 32a and the distance from the wave source can be designed as needed, and is not limited to the above. For example, for electromagnetic waves in some frequency bands, a region in the first capacitor 32a that is closer to the wave source can be made to have a smaller capacitance value.
  • the gap in the first part 32b close to the wave source has a uniform width
  • the gap in the second part 32c slightly farther away from the wave source has a non-uniform width.
  • the gap of the first part 32b close to the wave source have a non-uniform width
  • the minimum gap width that is, the gap width anywhere in the second part 32c
  • the first capacitor 32a is divided into four parts by changing the width of the gap.
  • the width of the gap can also be designed to change from the first capacitor to the first capacitor.
  • Other quantities are divided into 32a.
  • the gap in the embodiment of the present application only needs to be a non-constant width gap, so that the purpose of expanding the stealth bandwidth can be achieved.
  • the first part 32b is centrally symmetrical to the third part 32d
  • the second part 32c is centrally symmetrical to the fourth part 32e.
  • This design can ensure that the electromagnetic wave maintains its previous propagation direction and propagation characteristics after being emitted through the first capacitor 32a. (such as polarization characteristics, frequency band, etc.).
  • this design is only an example and does not limit the embodiments of the present application.
  • the shapes of the first part 32b and the third part 32d can only be consistent, but the positions are not required to be centrally symmetrical.
  • the electromagnetic waves emitted from the first capacitor 32a are refracted to other directions to expand the signal scanning range of the antenna device (for example, a multiple-input multiple-output MIMO antenna can apply this solution).
  • the shapes of the first portion 32b and the third portion 32d can be different, and the positions do not require central symmetry.
  • the antenna structure 24 in the antenna system 2 may include a phase shifter 242 and a stealth structure layer 241 covering the outer surface of the phase shifter 242 .
  • the phase shifter 242 is a specific form of the above-mentioned conductive base 31, and the stealth structure layer 241 corresponds to the above-mentioned stealth structure layer.
  • the antenna structural member 24 has a certain shielding effect on the second radiating unit 26.
  • the stealth structure layer 241 the electromagnetic waves radiated by the second radiating unit 26 will continue to propagate around the antenna structural member 24, or the electromagnetic waves will bypass the antenna structure.
  • the element 24 is received by the second radiation unit 26, thereby reducing or eliminating the electromagnetic shadow. Therefore, the second radiation unit 26 can have a large-angle scanning capability, and its aperture (for example, the horizontal aperture in FIG. 4 ) can be expanded without being blocked or restricted by the front phase shifter 242 .
  • the conductive base 41 of the antenna structure member 4 may be substantially a rectangular columnar structure.
  • the structural unit 42 may be roughly a square cylindrical structure surrounded by four flat plates.
  • the first capacitance between adjacent structural units 42 may include a first part 42b and a second part 42c.
  • the first part 42b may be located on the periphery of one side of the conductive base 41
  • the second part 42c may be located on the outer periphery of the other side of the conductive base 41.
  • the adjacent position of the first part 42b and the second part 42c may correspond to the edge of the conductive base 41.
  • both the first part 42b and the second part 42c may be rectangular areas, and the gaps between the first part 42b and the second part 42c have uniform widths.
  • the gap width of the first portion 42b may be smaller than the gap width of the second portion 42c.
  • the first capacitor of the structural unit 42 may also include a third part and a fourth part (not shown due to the perspective of FIG. 7).
  • the third part and the first part 42b may be centrally symmetrical, and the fourth part and the fourth part may be centrally symmetrical.
  • the two portions 42c may be centrally symmetrical.
  • the capacitance value of the first part 42b is greater than the capacitance value of the second part 42c. That is, the gap widths in different areas of the first capacitor are different, resulting in different capacitance values in different areas of the first capacitor.
  • the propagation direction K of the electromagnetic wave can be perpendicular to the side surface where the first part 42 b of the antenna structure 4 is located.
  • the solution of this embodiment is not limited to this.
  • the side surface where the first part 42 b is located can also be Not perpendicular to the propagation direction K.
  • the solution of this embodiment enables the conductive substrate 41 to have electromagnetic stealth performance relative to electromagnetic waves, avoids or reduces the shielding of electromagnetic waves by the conductive substrate 41, and can also expand the stealth bandwidth.
  • the structure of the gap on the antenna structural member 4 is simple, has good mass production, and can meet specific product requirements.
  • a capacitor may include a first part 52b and a second part 52c, wherein the gap in the first part 52b may be formed by bending and connecting at least two sub-slits 52d in sequence, that is, several sub-slits 52d are connected in sequence, and each two adjacent sub-slits 52d Form a bent corner.
  • the bending angle between the sub-slits 52d can be designed as needed, for example, it can be 90°, and the gap in the first part 52b can form a shape similar to a square wave.
  • the bending angle of adjacent sub-slots 52d may not be limited to 90°, so that the slots of the first part 52b form other shapes, such as curved shapes (such as sinusoids, parabolas, etc.).
  • each sub-slot 52d may have a uniform width, and all sub-slits 52d have the same width, so the width of the sub-slit 52d is also the slot width d1 of the first part 52b.
  • the slit of the second part 52c has a uniform width, and the slit width d2 of the second part 52c may be greater than the slit width of the first part 52b.
  • the total gap length formed by connecting all the sub-slits 52d in the first part 52b may be greater than the gap length of the second part 52c.
  • ⁇ the dielectric constant of the medium between the plates
  • S the area of the plates
  • d the distance between the plates
  • the gap length and gap width of different regions of the first capacitor can be configured so that the capacitance values of different regions of the first capacitor are different.
  • the solution of this embodiment enables the conductive substrate 51 to have electromagnetic stealth performance relative to electromagnetic waves, avoids or reduces the shielding of electromagnetic waves by the conductive substrate 41, and can also expand the stealth bandwidth.
  • the solution of this embodiment can be applied in the following scenarios: when due to limitations of the manufacturing process, it is impossible to manufacture the first part of a regular shape (such as a rectangular shape) with a gap width smaller than a threshold, you can consider designing the first part as shown in Figure 8
  • the first part 52b shown in (a) (the first part 52b can be considered as an irregular shape) increases the gap length to compensate for the process limitation that the gap width cannot be made small, ultimately making the first part have a larger capacitance value. Therefore, the design of this embodiment can match the existing manufacturing process and has good mass production.
  • the first part can be formed by bending and connecting at least two sub-slits in sequence, and the slits of the first part The length is greater than the gap length of the second part, each sub-slit has a uniform width, the width of all sub-slits is consistent, the gap of the second part has a uniform width, and the gap width of the second part is equal to the gap width of the first part.
  • the first part can be formed by bending and connecting at least two sub-slits in sequence, and the slit length of the first part is greater than the slit length of the second part, but the width of the sub-slits is not limited (for example The sub-slits may have non-uniform slits, the widths of all sub-slits are not all the same, etc.), and the gap width of the second part is not limited (for example, the second slit may have non-uniform widths, and the gap width of the second slit is not limited to the width of the sub-slits). the width of the gap).
  • the first part can be formed by at least two sections of sub-slits being bent and connected in sequence
  • the second part can also be formed by at least two sections of sub-slits being bent and connected in sequence. There is no limit to this. .
  • the first capacitance between adjacent structural units 62 of the antenna structural member 6 may include a first part 62 b and a second Section 62c.
  • the second part 62c can span one edge of the conductive base 61 and can be distributed on the periphery of two adjacent sides of the conductive base 61, that is, a part of the second part 62c is located on one side, and the other part of the second part 62c is located on one side. One part is located on the other side, and the two parts of the second part 62c are bent and connected.
  • the first part 62b may span another edge of the conductive base 61 and may be distributed on the periphery of the other two adjacent sides of the conductive base 61 (due to the perspective of FIG. 9, the complete first part 62b is not shown).
  • the propagation direction K of electromagnetic waves is not perpendicular to any side surface of the antenna structure 6 .
  • the solution of this embodiment enables the conductive substrate 61 to have electromagnetic stealth performance relative to electromagnetic waves, avoids or reduces the shielding of electromagnetic waves by the conductive substrate 61, and can also expand the stealth bandwidth.
  • the structure of the slot on the antenna structural member 6 is simple, has good mass production, and can meet specific product requirements. A specific application of the solution shown in Figure 9 will be described below.
  • FIG. 10 shows the specific application of the electromagnetic stealth design shown in FIG. 9 in the antenna system 2 shown in FIG. 4 .
  • FIG. 10 shows a part of the antenna system 2 .
  • the antenna structural member 6 in the antenna system 2 may be the antenna structural member 24
  • the conductive base 61 may be the phase shifter 242 of the antenna structural member 24
  • the stealth structural layer 241 is provided on the phase shifter.
  • the stealth structure layer 241 includes a first capacitor
  • the first capacitor includes a first part 62b, a second part 62c, a third part 62d and a fourth part 62e.
  • the first part 62b is centrally symmetrical to the third part 62d
  • the second part 62c is centrally symmetrical to the fourth part 62e.
  • the second radiating unit 26 is closest to the first part 62b.
  • the electromagnetic waves radiated by the second radiating unit 26 will generally propagate in the "oblique direction" to two adjacent sides of the antenna structure 24, so that the first part 62b is distributed on these two sides, so that the first part 62b can receive the electromagnetic waves and transmit the electromagnetic waves.
  • the confinement propagates within the first capacitor, eventually causing the electromagnetic wave to emit from the third portion 62d. Since the first portion 62b is distributed "across the edge of the phase shifter 242", the second portion 62c, the third portion 62d and the fourth portion 62e are also distributed "across the edge of the phase shifter 242". It can be seen from this that the regions with different capacitance values of the first capacitor are distributed on two adjacent sides of the phase shifter 242, which can match the position of the wave source, thereby achieving a better electromagnetic stealth effect.
  • the antenna structural member 7 includes a conductive base 71 and at least two structural units 72 , and a structure formed between adjacent structural units 72
  • the first capacitor may include a first part 72b and a second part 72c.
  • the structural unit 72 of this embodiment is not an integrated structure, but has a coupling gap inside, and the parts of the structural unit 72 located on both sides of the coupling gap are completely disconnected. Without connection, the parts on both sides of the coupling gap can be coupled through the coupling gap.
  • the structural unit 72 may include a first part 721, a second part 722, a third part 723 and a fourth part 724, and these four parts may be respectively located on different sides of the conductive base 71.
  • coupling gap 72f between the first part 721 and the second part 722
  • a coupling gap 72g between the second part 722 and the third part 723
  • a coupling gap 72h between the third part 723 and the fourth part 724
  • the fourth part There is a coupling gap 72i between 724 and the first part 721.
  • the above-mentioned four coupling gaps can separate the structural unit 72 into four independent parts. When the electromagnetic wave propagates to the structural unit 72, the electromagnetic wave can "cross" these coupling gaps, so the parts of the structural unit 72 located on both sides of the coupling gap are coupled through the coupling gap.
  • each coupling gap extends along the edge of the conductive base 71 .
  • the structural unit 72 has four coupling slits, which separate the structural unit 72 into four independent parts.
  • the above are only examples and are not limitations of this embodiment. According to product needs, the position and extension direction of the coupling gap can be flexibly designed, and the number of coupling gaps can be at least one. In addition, all structural units 72 may have coupling gaps, or only some structural units 72 may have coupling gaps.
  • a coupling gap is formed in the structural unit 72 to facilitate the assembly of different parts of the structural unit 72 onto the conductive base 71 in sequence, and finally to form a complete structural unit 72.
  • This can realize the coupling of the structural unit 72 in some scenarios. Reliable assembly.
  • the separate assembly method can simplify the assembly process and improve the assembly yield.
  • the coupling gap can allow electromagnetic waves in certain frequency bands to pass through, so that the antenna structural member 7 has a certain effect in expanding the stealth bandwidth.
  • the antenna structure 8 includes a conductive base 81 to And at least two structural units 82, a first capacitor is formed between adjacent structural units 82, and the first capacitor may include a first part 82b and a second part 82c.
  • the structural unit 82 is not an integral structure, but has a coupling gap inside. The parts of the structural unit 82 on both sides of the coupling gap are completely disconnected and the parts on both sides of the coupling gap can be coupled through the coupling gap.
  • the structural unit 82 of this embodiment may have a coupling gap 82f and a coupling gap 82g.
  • the coupling gap 82f and the coupling gap 82g may be located at opposite sides of the structural unit 82 respectively. side.
  • both the coupling gap 82f and the coupling gap 82g can be approximately in the middle of the side of the structural unit 82, rather than at the edge of the structural unit 82.
  • the coupling gap 82f and the coupling gap 82g can separate the structural unit 82 into a first part 821 and a second part 822, and both the first part 821 and the second part 822 can have an approximately C-shaped structure.
  • the stealth structure layer of this embodiment may have a periodic structure, so the coupling gaps on the same side of all structural units 82 may be collinear.
  • a coupling gap is formed in the structural unit 82 to facilitate the assembly of different parts of the structural unit 82 onto the conductive base 81 in sequence, and finally to form a complete structural unit 82.
  • This can realize the coupling of the structural unit 82 in some scenarios. Reliable assembly.
  • the separate assembly method can simplify the assembly process and improve the assembly yield. Since the number of components of the structural unit 82 is small, the assembly process can be simplified to a certain extent.
  • the coupling gap can allow electromagnetic waves in certain frequency bands to pass through, so that the antenna structural member 8 has a certain effect in expanding the stealth bandwidth.
  • the antenna structural member 9 includes a conductive base 91 and at least two structural units 92 , and a structure formed between adjacent structural units 92
  • the first capacitor may include a first part 92b and a second part 92c.
  • each structural unit 92 can be hollowed out to form a hollow area.
  • hollows can be formed on two opposite sides of each structural unit 92 to form hollow regions 92f and 92g respectively.
  • the position and number of the hollow areas can be designed according to product requirements, and are not limited to those shown in FIG. 13 . For example, as long as at least one structural unit 92 forms a hollow area.
  • forming a hollow area on the structural unit 92 can reduce the weight, which is beneficial to reducing the weight of the antenna structural member 9 .
  • the structural unit 92 is a heavier metal piece, providing a hollow area can greatly reduce the weight.
  • the electromagnetic field is mainly distributed at the first capacitor, and the electromagnetic field in the remaining areas is very weak. Therefore, opening the hollow area will basically not affect the propagation characteristics of the electromagnetic wave.
  • the antenna structural member 10 may include a conductive base 101 and at least two structural units 102 , and a first capacitor 102 a is formed between adjacent structural units 102 .
  • the first capacitor 102a in FIG. 14 may have a uniform gap width, that is, the width of each position of the gap of the first capacitor 102a may be consistent.
  • an insulating medium may be filled between the structural unit 102 and the conductive base 101, and the insulating medium may, for example, cover the entire outer peripheral surface of the conductive base 101.
  • the insulating medium may include a first insulating medium 103a and a second insulating medium 103b, and the dielectric constant of the first insulating medium 103a may be greater than the dielectric constant of the second insulating medium 103b.
  • first insulating medium 103a and the second insulating medium 103b may extend from one end to the other end of the conductive base 101 along the length direction of the conductive base 101, and they may be alternately arranged in the circumferential direction of the conductive base 101, so as to The arrangement shown in Figure 15 is formed: first insulating medium 103a - second insulating medium 103b - first insulating medium 103a - second insulating medium 103b.
  • the first insulating medium 103a can be distributed on two adjacent sides of the conductive base 101, and the second insulating medium 103b can also be distributed on two adjacent sides of the conductive base 101. Both the first insulating medium 103a and the second insulating medium 103b can be across the edges of the conductive substrate 101 .
  • a first part, a second part, a third part and a fourth part can be defined in the first capacitor 102a.
  • the first part is closest to the wave source, the first part is filled with the first insulating medium 103a, and the second part is close to the wave source.
  • the first part is adjacent, the second part is filled with the second insulating medium 103b, the third part is opposite to the first part (for example, it can be centrally symmetrical), the third part is filled with the first insulating medium 103a, the fourth part is with the second part Oppositely (for example, it can be centrally symmetrical), the fourth part is filled with the second insulating medium 103b.
  • this embodiment can make the first capacitor 102a have a uniform gap width and make the first capacitor 102a have different The regions are filled with insulating media with different dielectric constants, so that the capacitance values of different regions of the first capacitor 102a are different.
  • the solution of this embodiment enables the conductive substrate 101 to have electromagnetic stealth performance relative to electromagnetic waves, avoids or reduces the shielding of electromagnetic waves by the conductive substrate 101, and can also expand the stealth bandwidth.
  • the propagation direction K of the electromagnetic wave may not be perpendicular to any side of the antenna structure 10.
  • This design enables the antenna structure 10 to be applied to the antenna system 2 shown in Figure 10, by making the first capacitor
  • the different capacitance value areas of 102a are distributed on two adjacent sides of the phase shifter 242, which can match the position of the wave source, thereby achieving a better electromagnetic stealth effect.
  • the detailed principles have been described above and will not be repeated here.
  • this embodiment realizes the design of different capacitance values in different areas by filling insulating media with different dielectric constants, and can be applied to any other embodiment of the present application as needed.
  • the gap size of the first capacitor including the width dimension and length dimension, etc.
  • the gap pattern referring to whether the gap is a whole gap, or it is composed of several segments of gaps that are connected by bending in sequence as shown in Figure 8(a) (formed)
  • gap distribution referring to whether the gap is only distributed on one side of the conductive substrate or on two adjacent sides
  • insulating media with different dielectric constants are filled in different areas of the first capacitor.
  • the antenna structural member 20 may include a conductive base 201 and at least two structural units 202, and a first structural unit 202 is formed between adjacent structural units 202. Capacitor 202a.
  • the first capacitor 202a does not need to be filled with an insulating medium, or can be filled with an insulating medium of the same dielectric constant.
  • capacitor devices with different capacitance values can be installed in different areas of the first capacitor 202a.
  • the first capacitor device 204 can be installed in the areas closest and farthest from the wave source (due to the limitation of the viewing angle in Figure 16, the area farthest from the wave source is not shown.
  • the second capacitive device 203 can be installed in the area adjacent to the first capacitive device 204.
  • the area where the first capacitor device 204 is installed can be called a first part and a third part, and the area where the second capacitor device 203 is installed can be called a second part and a fourth part.
  • the capacitance value of the first capacitive device 204 is greater than the capacitance value of the second capacitive device 203 .
  • the first capacitive device 204 may be a capacitive device with a fixed capacitance value, or may be a capacitive device (such as a varactor) that can change the capacitance value under signal control.
  • the second capacitive device 203 may be a capacitive device with a fixed capacitance value, or may be a capacitive device (such as a varactor) that can change the capacitance value under signal control.
  • the first capacitive device 204 may also be called a second capacitor, and the second capacitive device 203 may also be called a third capacitor.
  • the first capacitor device 204 and the second capacitor device 203 may be fixed in the gap by welding or other methods.
  • the number of the first capacitive device 204 and the second capacitive device 203 can be determined as needed, and is not limited in this embodiment.
  • the capacitance value is added to the capacitance value of the capacitive device in the area.
  • the capacitance value of the first part is larger; since the second capacitor device 203 with a smaller capacitance value is disposed in the second part, the capacitance value of the second part is The value is smaller.
  • the capacitance value of the third part may be equal to the capacitance value of the first part, and the capacitance value of the fourth part may be equal to the capacitance value of the second part.
  • this embodiment can make the capacitance values of different areas of the first capacitor 202a different by making the first capacitor 202a have a uniform gap width and installing capacitor devices with different capacitance values in different areas of the first capacitor 202a.
  • the solution of this embodiment enables the conductive substrate 201 to have electromagnetic stealth performance relative to electromagnetic waves, avoids or reduces the shielding of electromagnetic waves by the conductive substrate 201, and can also expand the stealth bandwidth.
  • the capacitive device is a capacitive device with variable capacitance
  • the capacitance of the capacitive device in the corresponding area can be adaptively adjusted according to the change of the scanning angle of the wave source, and then the capacitance value of the area can be adjusted to ensure that the antenna structural member 20 Electromagnetic cloaking effect on wave sources.
  • the capacitive device (eg, the first part) may be provided only in a part of the first capacitor 202a, and no capacitive device may be provided in other regions.
  • the capacitance values of different regions of the first capacitor 202a may be different.
  • the design of influencing the capacitance value of the area by arranging the capacitive device in the area can be applied to any embodiment of the present application as needed.
  • the gap size, gap pattern, gap distribution, filling condition of the insulating medium, etc. of the first capacitor may not be limited, and the capacitor device may be installed in the first capacitor. The electrical constant and the capacitance value of the capacitive device ultimately make the capacitance value of the first part greater than the capacitance value of the second part.
  • a capacitance (for example, called a plate capacitor) may be formed between the structural unit and the conductive base, and the plate capacitance may affect the frequency band of electromagnetic waves that bypass the antenna structural member.
  • the plate capacitance may affect the frequency band of electromagnetic waves that bypass the antenna structural member.
  • it may be desirable to reduce the spacing between the structural units and the conductive substrate.
  • reducing the spacing may lead to an increase in the frequency band of electromagnetic waves that bypass the antenna structure, changing the propagation characteristics of electromagnetic waves.
  • the antenna structural member may also include an inductor element.
  • the inductor element may be disposed in the interval between the structural unit and the conductive base, and connect the structural unit and the conductive base, so that the structural unit and the conductive base are connected.
  • the conductive base is electrically connected.
  • the inductor element can form a parallel resonant circuit with the above-mentioned plate capacitor, and the parallel resonant circuit can reduce the frequency band of electromagnetic waves that bypass the antenna structure.
  • the inductance element may be a conductive structural component, such as a metal pillar.
  • This inductance component may be equivalent to an inductor.
  • This inductance component facilitates the mechanical processing of the antenna structure.
  • the inductive component can be directly an inductor.
  • the position of the inductor element can be designed as needed, for example, it is at a certain distance from the first capacitor to avoid being too close.
  • the number of inductance elements can be designed as needed.
  • each structural unit can be connected to the conductive base through at least one inductance element, or only some of the structural units can be connected to the conductive base through inductance elements.
  • FIG. 17 illustrates an antenna structure 30 designed using the inductive element of this embodiment.
  • the antenna structural member 30 may include a conductive base 301 and at least two structural units 302 , and a first capacitor 302 a is formed between adjacent structural units 302 .
  • Each side of the structural unit 302 is connected to the conductive base 301 through an inductor element 303, and several inductor elements 303 are provided between each structural unit 302 and the conductive base 301.
  • the antenna structure 30 shown in FIG. 17 is only an example and does not limit the application environment of the inductive element 303.

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Abstract

本申请提供了一种天线结构件，包括导电基体和至少两个结构单元；至少两个结构单元中的每个结构单元均环绕导电基体一周，每个结构单元均与导电基体间隔设置，至少两个结构单元包括相邻的第一结构单元与第二结构单元，第一结构单元与第二结构单元间隔排布并形成第一电容，第一电容的不同部分的电容值不同。本申请还提供了一种包括该天线结构件的天线，以及包括该天线的基站。本申请的方案能够改善由于金属部件遮挡导致的电磁阴影问题。

Description

天线结构件、天线和基站
本申请要求于2022年09月08日提交中国专利局、申请号为202211097500.2、申请名称为“天线结构件、天线和基站”的中国专利申请的优先权，其全部内容通过引用结合在本申请中。
技术领域
本申请涉及天线技术领域，特别涉及一种天线结构件、天线和基站。
背景技术
在天线系统中，辐射单元可能会被周围的金属部件遮挡，电磁波传播至这些金属部件时会在该金属部件的表面产生散射，无法完全传播至该金属部件的后方，使得该金属部件的后方产生电磁阴影。对于天线的信号接收过程，电磁阴影会导致位于该金属部件后方的天线装置的接收信号质量劣化；对于天线的信号辐射过程，电磁阴影会影响位于金属部件后方的终端的通信质量。
发明内容
本申请提供一种天线结构件、天线和基站，能够改善由于金属部件遮挡导致的电磁阴影问题。
第一方面，本申请的方案提供了一种天线结构件，用于基站天线系统中。天线结构件包括导电基体和至少两个结构单元；至少两个结构单元中的每个结构单元均环绕导电基体一周，每个结构单元均与导电基体间隔设置，至少两个结构单元包括相邻的第一结构单元与第二结构单元，第一结构单元与第二结构单元间隔排布并形成第一电容，第一电容的不同部分的电容值不同。
本方案中，天线结构件是会对辐射单元造成物理遮挡的部件。天线结构件中的导电基体具有导电性能，导电基体至少包含导电部分，例如导电基体的全部区域均是导体，或者导电基体包括导体部分与绝缘部分。导电基体包括但不限于抱杆、抱杆支架、馈电网络、传动机构、支撑结构等金属件。导电基体会对电磁波产生遮挡。结构单元是设于导电基体外侧并环绕导电基体一周的导电结构，结构单元可以是薄层。结构单元与导电基体之间可以是隔开的，二者可以不直接相连，这样使得二者之间可以是电隔绝的。第一结构单元与第二结构单元相邻，第一结构单元与第二结构单元之间可以形成缝隙，缝隙可以环绕导电基体一周。第一结构单元、缝隙和第二结构单元实质上可以形成第一电容，第一结构单元与第二结构单元均可作为第一电容的极板。第一电容的不同部分(对应着缝隙的不同区域)的电容值不同，也即某些部分的电容较大，另一部分的电容值较小。在所有结构单元中，可以形成至少一个第一电容。
本方案中，天线结构件可以设在波源附近。波源发出的电磁波传播至天线结构件时，将会被约束在第一电容内沿缝隙传播，并从缝隙中的一定位置射出。这样使得电磁波能够绕着天线结构件进行传播，因此即使天线结构件对波源存在遮挡，但是由于存在第一电容，使得电磁波能够绕过天线结构件传播至天线结构件的后方。所以，本方案通过在导电基体的外周设置至少两个结构单元，并形成第一电容，使得导电基体相对电磁波具有电磁隐身性能，从而减少或者避免了导电基体对电磁波的遮挡导致的电磁阴影。并且，由于第一电容的不同区域的电容值不同，使得不同频段的电磁波信号均能够以各自的电长度在缝隙内发生谐振，从而使得不同频段的电磁波均能通过缝隙。因此，通过使第一电容的不同区域的电容值不同，使缝隙能够允许多种频段的电磁波通过，从而拓展了隐身带宽。
在第一方面的一种实现方式中，第一电容包括第一部分、第二部分、第三部分与第四部分，第一部分、第二部分、第三部分与第四部分依次首尾相连，第一部分的电容值与第三部分的电容值相等，第二部分的电容值与第四部分的电容值相等，且第一部分的电容值与第二部分的电容值不同。
本方案中，可以从第一电容中划分出上述四个区域，这四个区域首尾相连围成一周，并使整个第一电容的电容值形成大电容-小电容-大电容-小电容的分布样式。其中，电容值较大的区域可以相当于贴片天线，电容值较小的区域可以相当于缝隙传输线(slotline)。波源可以靠近电容值较大的区域，波源发出的电磁波可以从其中一个电容值较大的区域进入缝隙，并分为两路：其中一路被约束在其中一个电容值较小的区域内传输，并从另一个电容值较大的区域射出；另外一路被约束在另一个电容值较小的区域内传输，并与前一路电磁波一样从该另一个电容值较大的区域射出。本方案通过上述设计，能够使电磁波按照设计需求绕射，不仅能实现电磁隐身，而且能使电磁波的传播特性满足天线需求。
在第一方面的一种实现方式中，第一部分与第三部分呈中心对称分布，第二部分与第四部分呈中心对称分布。
本方案中，中心对称指二者的结构一致，且其中一个绕对称中心旋转180度后与另一个重合。通过中心对称设计，使得电磁波在出入缝隙时的传播特性(例如传播方向、极化特性、频段等)保持一致，从而满足天线需求。
在第一方面的一种实现方式中，第一结构单元和第二结构单元之间存在缝隙，第一电容的不同部分的缝隙的宽度不同。
本方案中，第一电容的电容值C满足电容公式：C＝εS/d，ε为极板间介质的介电常数，S为极板面积(即第一结构单元与第二结构单元的正对面积)，d为极板间的距离(也即缝隙宽度)。本方案通过对第一电容的不同部分设置不同的缝隙宽度，最终使得第一电容的不同部分的电容值不同，从而实现拓展隐身带宽的目的。可以理解的是，本方案至少设置了缝隙宽度，当然还可以同时设置缝隙宽度d，以及设置介电常数ε与极板面积S中的至少一个，从而实现第一电容的不同部分的电容值不同的目的。本方案设计简单，量产性较好。
在第一方面的一种实现方式中，第一电容包括相连的第一部分与第二部分；第一部分的缝隙与第二部分的缝隙均具有同一宽度，且第一部分的缝隙的宽度小于第二部分的缝隙的宽度，第一部分的电容值大于第二部分的电容值；或者，第一部分的缝隙与第二部分的缝隙中的一个具有同一宽度，另一个具有可变宽度，第一部分的缝隙的最大宽度小于或者等于第二部分的缝隙的最小宽度，第一部分的电容值大于第二部分的电容值。
本方案的一种实现方式中，同一宽度可以指缝隙是均匀宽度的缝隙，缝隙的两边基本平行，缝隙各处的缝隙宽度可以一致。可变宽度可以指缝隙是非均匀宽度的缝隙，缝隙的两边不平行，缝隙各处的缝隙宽度不一致。
对于本方案的第一种实现方式，可以通过使第一部分的缝隙宽度小于第二部分的缝隙宽度，且使第一部分的电容值大于第二部分的电容值，从而便于实现拓展隐身带宽的目的。
对于本方案的第二种实现方式，不论第一部分的缝隙(或者第二部分的缝隙)具有同一宽度还是可变宽度，使得第一部分的缝隙的最大宽度(当第一部分的缝隙具有同一宽度时，最大宽度就是缝隙任意位置的宽度；当第一部分的缝隙具有可变宽度时，最大宽度为缝隙最宽处的宽度)小于或者等于第二部分的缝隙的最小宽度(当第二部分的缝隙具有同一宽度时，最小宽度就是缝隙任意位置的宽度；当第二部分的缝隙具有可变宽度时，最大宽度为缝隙最窄处的宽度)，就能使第一部分的缝隙整体上比第二部分的缝隙窄。同时，使第一部分的电容值大于第二部分的电容值，从而便于实现拓展隐身带宽的目的。
本方案通过对第一电容的缝隙进行上述设计，能够实现良好的电磁隐身以及拓展隐身带宽的效果。并且，本方案的设计较为简单，量产性较好。
在第一方面的一种实现方式中，第一结构单元和第二结构单元之间存在缝隙；第一电容包括相连的第一部分与第二部分，第一部分的缝隙由至少两段子缝隙依次弯折连接而成，第一部分的电容值大于第二部分的电容值。
本方案中，第一部分的缝隙由至少两段子缝隙依次弯折连接而成，也即若干段子缝隙依次连接，且每相邻的两段子缝隙形成弯折角。子缝隙之间的弯折角度可以根据需要设计，例如可以为90°，由此形成的缝隙可以形成类似方波的形状。或者相邻子缝隙的弯折角可以不限于90°，以使缝隙形成其他形状，例如曲线形状(如正弦曲线、抛物线等)。
本方案中，通过将第一部分的缝隙设计成上述形状，便于增加缝隙的总长度。根据电容公式C＝εS/d，缝隙的总长度增加，则S增大，可以使得电容值C增大，从而实现使第一部分的电容值较大的目的。本方案可以应用在如下的场景中：当出于制造工艺的限制，无法制造出缝隙宽度小于阈值的第一部分时，可以考虑将第一部分设计成上述的形状，通过增加缝隙长度来弥补缝隙宽度无法做小的工艺限制，最终使得第一部分具有较大的电容值。所以，本方案能够与已有制造工艺匹配，量产性较好。
在第一方面的一种实现方式中，第二部分的缝隙具有同一宽度；第一部分的每段子缝隙均具有同一宽度，所有子缝隙的宽度一致，且子缝隙的宽度小于或等于第二部分的缝隙的宽度。
本方案中，子缝隙的宽度即第一部分的缝隙的宽度。通过使第一部分的缝隙宽度d1小于或等于第二部分的缝隙宽度d2，且第一部分的极板面积S1大于第二部分的极板面积S2，从而使S1/d1＞S2/d2。根据电容公式C＝εS/d可知，第一部分的电容值C1＞第二部分的电容值C2。因此，本方案通过综合配置第一电容的不同区域的缝隙长度与缝隙宽度，使得第一部分的电容值大于第二部分的电容值，以便实现拓展隐 身带宽的目的。
在第一方面的一种实现方式中，第一电容包括相连的第一部分与第二部分，第一部分内填充有第一绝缘介质，第二部分内填充有第二绝缘介质，第一绝缘介质的介电常数大于第二绝缘介质的介电常数，第一部分的电容值大于第二部分的电容值。
本方案中，第一绝缘介质可以充满第一部分的缝隙，第二绝缘介质可以充满第二部分的缝隙。通过使第一绝缘介质的介电常数大于第二绝缘介质的介电常数，便于调整电容公式C＝εS/d中的ε参量，以便实现第一部分的电容值大于第二部分的电容值的目的，进而拓展隐身带宽。同时，所填充的绝缘介质不会影响电磁波的传输，保证电磁波能够绕射天线结构件，从而保证电磁隐身效果。
在第一方面的一种实现方式中，第一电容包括相连的第一部分与第二部分；天线结构件包括第二电容，第二电容设于第一部分，第一部分的电容值大于第二部分的电容值。
本方案中，与第一电容不同(第一电容等同于平板电容)，第二电容是独立的电容器件(可以具有引脚)。第二电容可以设在第一部分的缝隙内。第一部分的总电容值为按照电容公式计算出的第一部分的电容值加上第二电容的电容值。本方案通过在第一部分内叠加第二电容，使得第一部分的电容值较大，从而拓展隐身带宽。本方案设计简单，量产性较好。
在第一方面的一种实现方式中，天线结构件包括第三电容，第三电容设于第二部分，第三电容的电容值小于第二电容的电容值。
本方案中，第三电容也是独立的电容器件(可以具有引脚)，第三电容可以设在第二部分的缝隙内。第二部分的总电容值为按照电容公式计算出的第二部分的电容值加上第三电容的电容值。本方案通过在第一部分内叠加第二电容，且在第二部分内叠加第三电容，使得第一部分的电容值大于第二部分的电容值，从而拓展隐身带宽。本方案设计简单，量产性较好。
在第一方面的一种实现方式中，第二电容和/或第三电容的电容值可调。
本方案中，电容值可调指的是电容器件能在信号控制下改变电容值，这样的电容器件例如可以是变容管。通过此种电容值可调的设计，可以根据波源的扫描角度变化，适应性地调整缝隙内相应区域的电容器件的电容，进而调整该区域的电容值大小，确保天线结构件对波源的电磁隐身效果。
在第一方面的一种实现方式中，至少一个结构单元设有耦合缝隙，结构单元分别位于耦合缝隙两侧的部分被耦合缝隙断开，并通过耦合缝隙耦合。
本方案中，结构单元可以不是一体式结构，而是开设有耦合缝隙，耦合缝隙将结构单元完全断开为不同的区域。耦合缝隙可以有至少一条。结构单元中位于耦合缝隙两侧的部分通过耦合缝隙耦合，当电磁波传播至结构单元时，电磁波可以“跨过”耦合缝隙。具有耦合缝隙结构单元的数量为至少一个，例如上述的第一结构单元与第二结构单元具有耦合缝隙。
本方案中，在结构单元中形成耦合缝隙，便于将结构单元的不同部分依次装配到导电基体上，最后拼成完整的结构单元，这样能够在一些场景下实现结构单元的可靠组装。尤其是在导电基体的尺寸较大、结构单元的数量较多时，分体组装的方式能够简化组装工艺，提高组装良率。另外，耦合缝隙能够允许某些频段的电磁波通过，使得天线结构件具有一定的拓展隐身带宽作用。
在第一方面的一种实现方式中，天线结构件包括电感元件，至少两个结构单元中的结构单元通过电感元件与导电基体连接。
本方案中，电感元件可以是导电的机械部件，例如金属柱。或者，电感元件可以是属于电子元件的电感(可以带引脚)。电感元件连接结构单元与导电基体。可以是每个结构单元均通过至少一个电感元件与导电基体连接，也可以是只有其中一部分结构单元通过电感元件与导电基体连接。
本方案中，结构单元与导电基体之间可以形成电容(例如称为平板电容)，该平板电容可以影响绕过天线结构件的电磁波的频段。出于产品需要(例如减小体积的需要)，可能希望减小结构单元与导电基体的间隔。但是间隔减小可能导致绕过天线结构件的电磁波的频段提高，改变电磁波的传播特性。有鉴于此，本方案通过设置电感元件，电感元件可与上述的平板电容构成并联谐振电路，该并联谐振电路能使绕过天线结构件的电磁波的频段降低。因此，设置电感元件与减小结构单元与导电基体的间隔对频段的影响可以相互抵消，使得绕过天线结构件的电磁波的频段保持不变，从而保持电磁波的传播特性。
在第一方面的一种实现方式中，至少一个结构单元镂空。
本方案中，镂空指将结构单元的局部区域挖空以形成孔洞。至少一个结构单元可做此种镂空设计。镂空设计能够减轻重量，有利于减小天线结构件的重量。特别是当结构单元为较重的金属件时，开设镂空区能极大减重。
在第一方面的一种实现方式中，至少两个结构单元的结构相同，且任意相邻的两个结构单元之间存在缝隙且形状相同，任意两个相邻的结构单元之间均形成第一电容。
本方案中，所有结构单元的结构均一致。任意两个结构单元之间存在缝隙，且各个缝隙的形状相同。由此，任意两个相邻的结构单元之间均形成第一电容。本方案使得天线结构件上形成多个第一电容，使得电磁波能在天线结构件的各个区域进行绕射，使得整个天线结构件能相对电磁波隐身，避免了电磁阴影。本方案中，所有结构单元可以构成周期性隐身结构层，该周期性隐身结构层容易制造，量产性好。
在第一方面的一种实现方式中，至少两个结构单元的结构不全相同，和/或，至少两个结构单元之间存在缝隙且形状不全相同；任意两个相邻的结构单元之间均形成第一电容。
本方案中，不全相同指任意两个都不同；或者，至少有两个相同，但不是所有都相同。本方案中，相较上述的周期性隐身结构层，所有结构单元可以构成准周期性隐身结构层。准周期性隐身结构层能够与导电基体的外形结构适配。例如，若导电基体的外表面某处具有凸起，则隐身结构层在该处可以避让该凸起，以形成准周期性结构。
在第一方面的一种实现方式中，每个结构单元包括导体层与绝缘层，绝缘层位于导体层与导电基体之间；或者，每个结构单元为导体。
本方案中，结构单元中的导体层与绝缘层层叠设置，绝缘层靠近导电基体，导体层背离导电基体。导体层由导体材料制造，绝缘层由绝缘材料制造。导体层可以较薄，结构强度较弱，导体层依附在绝缘层上，绝缘层能对导体层进行支撑和加强。此种结构的结构单元能满足产品需要，量产性好。
在第一方面的一种实现方式中，基站天线系统包括抱杆、抱杆支架与馈电网络，导电基体包括抱杆、抱杆支架及馈电网络中的至少一个。
本方案中，天线结构件可以应用于基站天线系统(或称基站)。基站天线系统包括安装在天线罩内的辐射单元与馈电网络，天线罩通过抱杆支架固定在抱杆上。通过在抱杆、抱杆支架及馈电网络中的至少一个上设置隐身结构层，也即使得抱杆、抱杆支架及馈电网络中的至少一个及其上的结构单元构成天线结构件，能够减小或避免抱杆、抱杆支架及馈电网络对电磁波的遮挡，并拓展隐身带宽。
第二方面，本申请的技术方案提供了一种天线，包括辐射单元和上述任一项的天线结构件。
本方案中，辐射单元靠近天线结构件。通过设置天线结构件，使得辐射单元所收发的电磁波能够绕过天线结构件传播，从而改善了电磁阴影问题。
第三方面，本申请的技术方案提供了一种基站，包括抱杆和第一天线，第一天线固定于抱杆，第一天线为上文的天线。
本方案中，通过在第一天线中设置天线结构件，使得第一天线的辐射单元所收发的电磁波能够绕过天线结构件传播，从而改善了电磁阴影问题。
在第三方面的一种实现方式中，基站包括第二天线与频率选择表面，频率选择表面位于第一天线的辐射单元与第二天线的辐射单元之间，频率选择表面用于反射第一天线的辐射信号，并透过第二天线的辐射信号。
本方案中，第二天线的工作频段可与第一天线的工作频段不同。第二天线的辐射单元与第一天线的辐射单元可以分别在不同的天线罩内，两个天线罩可固定在同一个抱杆上。这样使得两个天线可以单独部署，实现了不同频段天线的解耦设计与灵活部署。或者，第二天线的辐射单元与第一天线的辐射单元也可以同一个天线罩内。
本方案中，频率选择表面是一种包括若干个单元的二维结构，所有单元可以相同并按照一定方式排列而成，或者所有单元不全相同并按照一定方式排列而成。频率选择表面可以是单层结构，也可以多层结构。频率选择表面具有特定的频率选择作用，其可以对谐振情况下的一种频段的入射波呈现出透射性，对谐振情况下的另一种频段的入射波呈现出反射性，从而可以有效控制入射电磁波的透射和反射。频率选择表面例如可以是空间滤波器，与电磁波相互作用表现出明显的带通或带阻的滤波特性。多层的频率选择表面可以用做多阶空间滤波器，能够拓展带宽，并增加频率选择性。本方案中，频率选择表面能够反射第一天线的辐射单元的大部分电磁波，因而频率选择表面可以作为第一天线的辐射单元的反射板。频率选择表面还能够使第二天线的辐射单元的电磁波透过，因此频率选择表面对于第二天线的辐射单元而言并不会造成遮挡，频率选择表面对第二天线的辐射单元的电磁波而言相当于是电磁透明的。
本方案中，第一天线的辐射单元与第二天线的辐射单元分别位于频率选择表面的两侧，使得第一天线与第二天线为层叠布置。层叠布置能够在有限的天线口面口径下部署更多频段和通道的天线，满足通信要求。
本方案中，通过在第一天线中设置天线结构件，使得第二天线辐射的电磁波将会绕过天线结构件继续传播，或者电磁波将会绕过天线结构件而被第二天线接收到，从而改善了电磁阴影问题。
附图说明
图1表示基站与终端进行无线通信的应用场景；
图2表示本申请实施例的一种天线系统的组装结构；
图3表示图2中的天线系统的部分内部框架结构；
图4表示本申请实施例的一种天线系统的部分内部框架结构；
图5是一种实施例中的天线结构件的立体结构示意图；
图6是图5所示的天线结构件的侧剖结构示意图；
图7是一种实施例中的天线结构件的立体结构示意图；
图8(a)是一种实施例中的天线结构件的立体结构示意图；
图8(b)是图8(a)中A处的局部放大结构示意图；
图9是一种实施例中的天线结构件的立体结构示意图；
图10表示图9所示的天线结构件在一种天线系统中的应用原理；
图11是一种实施例中的天线结构件的立体结构示意图；
图12是一种实施例中的天线结构件的立体结构示意图；
图13是一种实施例中的天线结构件的立体结构示意图；
图14是一种实施例中的天线结构件的立体结构示意图；
图15是图14所示的天线结构件的侧视结构示意图；
图16是一种实施例中的天线结构件的立体结构示意图；
图17是一种实施例中的天线结构件的立体结构示意图。
附图标记：
1-天线系统；11-抱杆；12-抱杆支架；13-天线罩；14-天线装置；15-射频处理单元；16-线缆；17-基带处理单元；18-馈电网络；181-移相器；182-功分器；183-滤波器；
2-天线系统；21-第一天线罩；22-第一天线装置；221-第一辐射单元；222-第二辐射单元；23-频率选择表面；24-天线结构件；241-隐身结构层；242-移相器242；25-第二天线罩；26-第二天线装置；
3-天线结构件；3a-间隔；31-导电基体；32-结构单元；32a-第一电容；32b-第一部分；32c-第二部分；32d-第三部分；32e-第四部分；E-电场方向；H-磁场方向；K-电磁波的传播方向；
4-天线结构件；41-导电基体；42-结构单元；42b-第一部分；42c-第二部分；
5-天线结构件；51-导电基体；52-结构单元；52b-第一部分；52d-子缝隙；52c-第二部分；
6-天线结构件；61-导电基体；62-结构单元；62b-第一部分；62c-第二部分；62d-第三部分；62e-第四部分；
7-天线结构件；71-导电基体；72-结构单元；721-第一部分；722-第二部分；723-第三部分；724-第四部分；72b-第一部分；72c-第二部分；72f-耦合缝隙；72g-耦合缝隙；72h-耦合缝隙；72i-耦合缝隙；
8-天线结构件；81-导电基体；82-结构单元；821-第一部分；822-第二部分；82b-第一部分；82c-第二部分；82f-耦合缝隙；82g-耦合缝隙；
9-天线结构件；91-导电基体；92-结构单元；92b-第一部分；92c-第二部分；92f-镂空区；92g-镂空区；
10-天线结构件；101-导电基体；102-结构单元；102a-第一电容；103a-第一绝缘介质；103b-第二绝缘介质；
20-天线结构件；201-导电基体；202-结构单元；202a-第一电容；203-第二电容器件；204-第一电容器件；
30-天线结构件；301-导电基体；302-结构单元；302a-第一电容；303-电感元件。
具体实施方式
下面将结合本申请实施例中的附图，对本申请实施例中的技术方案进行描述，显然，所描述的实施例仅仅是本申请一部分实施例，而不是全部的实施例。
本申请实施例中，术语“第一”、“第二”等仅用于描述目的，而不能理解为指示或暗示相对重要性或 者隐含指明所指示的技术特征的数量。由此，限定有“第一”、“第二”的特征可以明示或者隐含地包括一个或者更多个该特征。在本申请实施例的描述中，除非另有说明，“多个”的含义是两个或两个以上。
本申请实施例中，“上”、“下”等方位术语是相对于附图中的结构示意置放的方位来定义的，应当理解到，这些方向性术语是相对的概念，它们用于相对于的描述和澄清，其可以根据结构所放置的方位的变化而相应地发生变化。
本申请实施例中，除非另有说明，“和/或”仅仅是一种描述关联对象的关联关系，表示可以存在三种关系。例如A和/或B，可以表示：单独存在A，同时存在A和B，单独存在B这三种情况。
本申请实施例提供了一种天线系统，该天线系统可以应用于任意能够辐射与接收天线信号的设备或系统。例如，该天线系统可以应用于舰船上的雷达系统中。或者，该天线系统可以是基站，该天线系统例如可以包括基站的基站天馈系统。下文先介绍基站，再以天线系统包括基站天馈系统为例进行说明。
图1示意出了基站与终端进行无线通信的应用场景。如图1所示，基站用于进行无线信号的小区覆盖以实现终端设备与无线网络之间的通信。具体来说，基站可以是全球移动通信系统(global system for mobile comunication，GSM)或码分多址(code division multiple access,CDMA)系统中的基站收发台(base transceiver station，BTS)，也可以是宽带码分多址(wideband code division multiple access，WCDMA)系统中的节点B(NodeB，NB)，还可以是长期演进(long term evolution,LTE)系统中的演进型节点B(evolutional NodeB，eNB)，还可以是云无线接入网络(cloud radio access network，CRAN)场景下的无线控制器。或者基站也可以为中继站、接入点、车载设备、可穿戴设备以及新无线(new radio,NR)系统中的g节点(gNodeB或者gNB)或者未来演进的网络中的基站等，本申请实施例并不限定。
基站配备有天线来实现信号在空间中的传输。图2展示了如图1所示的基站(或称基站天线系统，也即图2中的天线系统1)所配备的天线的一种应用场景示意图。如图2所示，天线系统1可以包括抱杆11、抱杆支架12、天线罩13、天线阵列14、射频处理单元15、线缆16和基带处理单元17。其中，抱杆支架12、天线罩13、天线阵列14可以合称天线，该天线还可以包括下文将要描述的馈电网络与反射板等。
其中，抱杆11可以固定至地面。抱杆支架12连接抱杆11与天线罩13，天线罩13通过抱杆支架12固定至抱杆11。天线阵列14可以安装在天线罩13内。天线罩13内还可以安装馈电网络。天线罩11具有良好的电磁波穿透特性和环境耐候性，能够对安装于其内的部件进行防护。
天线阵列14用于辐射和接收天线信号。天线阵列14可以包括若干个按照一定规律阵列排布的辐射单元，每个辐射单元均能辐射与接收电磁波。该辐射单元也可以包括天线振子。在天线阵列14中，不同辐射单元的工作频段可以相同或者不同。
在一些实施例中，天线还可以包括反射板，反射板也可以称为底板、天线面板或者反射面等，反射板例如可以采用金属材料制造。辐射单元可以安装在反射板一侧的表面上。辐射单元接收天线信号时，反射板可以把天线信号反射聚集在接收点上，从而实现定向接收；辐射单元发射天线信号时，反射板可以实现天线信号的定向发射。反射板可以增强辐射单元的天线信号的接收或发射能力，还能够阻挡、屏蔽来自反射板背面(该背面是指反射板上的背向辐射单元的一侧)的其它信号对天线信号的干扰作用，提升天线的增益。
射频处理单元15(又可称为射频拉远单元(remote radio unit，RRU))可通过跳线连接馈电网络，并通过馈电网络与天线阵列14电连接，馈电网络(下文将继续说明)可以作为射频处理单元15与天线阵列14之间的信号传输通路。射频处理单元15可以通过线缆16(例如光缆)与基带处理单元17(也可以称为基带单元(baseband unit，BBU))电连接。如图2所示，射频处理单元15和基带处理单元17可以均位于天线罩13外，射频处理单元15可以位于天线的近端。
射频处理单元15可对天线阵列14接收到的天线信号进行选频、放大以及下变频处理，并将其转换成中频信号或基带信号发送给基带处理单元17。射频处理单元15还可以将基带处理单元17或中频信号经过上变频以及放大处理通过天线阵列14转换成电磁波发送出去。
图3可以表示图2中的天线系统1的部分内部框架结构。如图3所示，天线系统1的天线阵列14与馈电网络18相连。馈电网络18可以通过传动机构实现不同辐射波束指向，或者与校准网络连接以获取天线系统1所需的校准信号。馈电网络18可将信号按照一定的幅度、相位馈送到天线阵列14，或者将接收到的信号按照一定的幅度、相位发送到基带处理单元17。
示意性的，馈电网络18可以包括移相器181，移相器181用于改变天线信号辐射的最大方向。馈电网络18还可以包括用于扩展性能的模块，例如功分器182。功分器182用于将多路信号合路为一路信号，通过天线阵列14发射；或者，功分器182将一路信号分为多路信号，例如将天线阵列14接收到的信号根据 不同的频率分成多路传输到基带处理单元17进行处理。馈电网络18还可以包括滤波器183，用于滤除干扰信号。
图2-图3所示的天线系统1的结构仅仅是一种举例，实际上本申请实施例中的天线系统的结构可以根据产品需求灵活地设计，并不限于上文所述。例如，天线系统也可以没有抱杆11，天线罩13可以通过抱杆支架12固定至铁塔。
在天线系统中，天线装置可能会被周围的导体部件(该导体部件至少包含导电部分，例如该导体部件的全部区域均是导体，或者该导体部件包括导体部分与绝缘部分。下文将该导体部件称之为导电基体)遮挡，电磁波传播至这些导体部件时会在该导体部件的表面产生散射，无法完全传播至该导体部件的后方，使得该导体部件的后方产生电磁阴影。对于天线装置的信号接收过程，电磁阴影会导致位于该导体部件后方的天线装置的接收信号质量劣化；对于天线装置的信号辐射过程，电磁阴影会影响位于导体部件后方的终端的通信质量。
为了解决上述问题，本申请实施例的天线系统对天线装置周围的导体部件做了“电磁隐身”设计，使得电磁波能够绕过该导体部件继续传播，减少或者消除了电磁阴影。下面将详细说明。
图4示意出了一种实施例中的天线系统2的局部内部框架结构，天线系统2具有上述的电磁隐身设计。
如图4所示，天线系统2可以包括第一天线与第二天线。第一天线可以包括第一天线罩21、第一辐射单元22、频率选择表面23、天线结构件24。第二天线可以包括第二天线罩25以及第二辐射单元26。
其中，第一天线罩21与第二天线罩25分别是两个独立的天线罩，二者可以固定于同一个抱杆或者铁塔。第一辐射单元22、频率选择表面(frequency selective surface，FSS)23及天线结构件24均可以位于第一天线罩21内，第二辐射单元26可以位于第二天线罩25内。
如图4所示，示意性的，第一辐射单元22可以包括第三辐射单元221与第四辐射单元222，第三辐射单元221与第四辐射单元222均可以为若干个，第三辐射单元221与第四辐射单元222的工作频段可以不同，例如第三辐射单元221的工作频段可以为690MHz-960MHz，第四辐射单元222的工作频段可以为1427MHz-2690MHz。第三辐射单元221与第四辐射单元222均可以与各自馈电网络连接。示意性的，第二辐射单元26的工作频段可以为3.3GHz-3.8GHz。可以理解的是，第二天线罩25内还可以设置其他部件，例如与第二辐射单元26连接的馈电网络等。
本实施例中，第一辐射单元22与第二辐射单元26分别设在不同的天线罩内，这样使得两个天线可以分别单独部署，实现了不同频段天线的解耦设计与灵活部署。可以理解的是，此种方案仅仅是一种示例。在其他实施例中，第一辐射单元22与第二辐射单元26也可以同一个天线罩内。
如图4所示，频率选择表面23与第一辐射单元22均可以位于第一天线罩21内，频率选择表面23可以位于第一辐射单元22与第二辐射单元26之间。由此，第一辐射单元22与第二辐射单元26可以称为是层叠布置的。层叠布置能够在有限的天线口面口径下部署更多频段和通道的天线，满足通信要求。
频率选择表面23是一种包括若干个单元的二维结构，所有单元可以相同并按照一定方式排列而成(此种频率选择表面23可以称为是一种周期阵列结构)，或者所有单元不全相同(任意两个单元均不同；或者存在至少两个相同的单元，但不是所有单元都一样)并按照一定方式排列而成(此种频率选择表面23可以称为是一种准周期阵列结构)。频率选择表面23可以是单层结构，也可以多层结构。示意性的，图3中的频率选择表面23可以是两层结构。当为多层结构时，频率选择表面23的各层之间可通过绝缘材料或者空气隔开。
频率选择表面23具有特定的频率选择作用，其可以对谐振情况下的一种频段的入射波呈现出透射性，对谐振情况下的另一种频段的入射波呈现出反射性，从而可以有效控制入射电磁波的透射和反射。频率选择表面23例如可以是空间滤波器，与电磁波相互作用表现出明显的带通或带阻的滤波特性。多层的频率选择表面23可以用做多阶空间滤波器，能够拓展带宽，并增加频率选择性。
本实施例中，频率选择表面23能够反射第三辐射单元221与第四辐射单元222辐射的大部分电磁波，因而频率选择表面23可以作为第三辐射单元221与第四辐射单元222的反射板。频率选择表面23还能够使第二辐射单元26辐射的电磁波透过，因此频率选择表面23对于第二辐射单元26而言并不会造成遮挡，频率选择表面23对第二辐射单元26辐射的电磁波而言相当于是电磁透明的。
如图4所示，天线结构件24可以位于第一辐射单元22与第二辐射单元26之间。天线结构件24可以是具有电磁隐身设计的馈电网络，例如为具有电磁隐身设计的移相器。
如图4所示，示意性的，天线结构件24可以包括移相器242以及覆盖移相器242的外表面的隐身结构层241。其中，移相器242可与第三辐射单元221及第四辐射单元222连接。移相器242具有金属外壳， 可将移相器242称为导电基体。位于第一辐射单元22与第二辐射单元26之间的移相器242可能对第二辐射单元26的信号产生遮挡。隐身结构层241可以覆盖移相器242的局部外表面或者全部外表面。隐身结构层241能够使得电磁波绕过移相器242继续传播，减少或者消除电磁阴影，从而保证第二辐射单元26的收发性能。隐身结构层241的具体结构及工作原理将在下文详细说明。
上述实施例中的天线结构件24是具有电磁隐身设计的馈电网络，这仅仅是一种举例。实际上，天线系统2中任意可能遮挡第二辐射单元26的信号的导电基体的外表面均可以设置该隐身结构层，以形成天线结构件。
下面将借助图2，继续列举几种天线系统中的天线结构件。
参考图2所示，抱杆11可能会对天线罩13内的天线阵列14的信号产生遮挡，可以在抱杆11的外表面覆盖隐身结构层，该隐身结构层的具体分布可以根据需要确定。例如，可以根据天线阵列14的扫描范围，将该隐身结构层覆盖在抱杆11的外表面的相应局部区域；或者，该隐身结构层可以覆盖抱杆11的全部外表面。本方案中，抱杆11作为导电基体，抱杆11与该隐身结构层可以构成一种天线结构件。
同理，可以将抱杆支架12作为导电基体，抱杆支架12与其上的隐身结构层可以构成另一种天线结构件。
或者，天线系统1中的其他金属件(如传动机构、支撑结构等)也可以作为导电基体，这些金属件与其上的隐身结构层可以构成另一种天线结构件。
下文将详细说明本申请实施例的天线结构件的电磁隐身设计。可以理解的是，下文所述的天线结构件可以应用于任意的天线系统中，例如图2所示的天线系统1与图4所示的天线系统2。
图5示意出了一种实施例中的天线结构件3的原理性立体结构，图6示意出了图5的天线结构件3的原理性侧视结构。如图5与图6所示，天线结构件3可以包括导电基体31与至少两个结构单元32。
示意性的，导电基体31可以大致呈圆柱状，其轴向长度例如至少为1*λ(λ为导电基体31所遮挡的天线装置的最低频段对应的波长)。可以理解的是，大致呈圆柱状的导电基体31仅仅是一种举例，本申请实施例并不限定导电基体的实际形状与构造。例如，导电基体的横截面外形包括不限于四边形、圆形、椭圆、六边形等。
图5示意性的画出了五个结构单元32。结构单元32的结构可以根据需要设计，例如可以为片状、环状等。所有结构单元32可以合称隐身结构层。
如图5所示，所有结构单元32均位于导电基体31的外侧。图5所示的实施方式中，这些结构单元32可以仅环绕导电基体31的外周面(该外周面是环绕导电基体31的轴线的表面)的外侧，并未设在导电基体31的端面(该端面是垂直于导电基体31的轴线的表面)的外侧。在另一种实施方式中，结构单元32可以同时分布在该外周面的外侧以及该端面的外侧。下文将以图5所示的实施方式为例继续说明。
本实施例的一种实施方式中，结构单元32可以由导体材料制造，此种结构单元32例如可以是钣金成型的金属件，其重量与结构强度较大。在本实施例的另一种实施方式中，结构单元32可以包括导体层与绝缘层，二者层叠设置，且绝缘层靠近导电基体31，导体层背离导电基体31。导体层由导体材料制造，绝缘层由绝缘材料制造。导体层可以较薄，结构强度较弱，导体层依附在绝缘层上，绝缘层能对导体层进行支撑和加强。
如图5与图6所示，每个结构单元32与导电基体31之间均具有间隔3a，也即每个结构单元32与导电基体31是隔开的，二者并未直接相连。间隔3a的径向尺寸(即间隔3a在导电基体31的径向上的尺寸，该尺寸也可以称为电厚度)例如可以为0.5*λ(λ为导电基体31所遮挡的天线装置的最低频段对应的波长)。
如图5和图6所示，本实施例中，对于仅由导体材料制造的结构单元32而言，该结构单元32与导电基体31之间的间隔3a内可以填充绝缘介质(图6中用斜线阴影表示绝缘介质)。一种实施方式中，绝缘介质可以连续分布并覆盖导电基体31的整个外周面，也即绝缘介质既分布在间隔3a内，也分布在相邻结构单元32之间的缝隙内(该缝隙将在下文继续说明)。另一种实施方式中，绝缘介质在导电基体31的整个外周面上呈离散分布，例如绝缘介质仅分布在间隔3a内，但并未分布在相邻结构单元32之间的缝隙内。其中，每个间隔3a内的绝缘介质可以是离散分布的，各处的绝缘介质形成类似若干个连接柱的结构，各处的绝缘介质之间形成间隙，该间隙内存在空气；或者，每个间隔3a内的绝缘介质是连续分布的。
本实施例中，该绝缘介质既可以起到连接结构单元32与导电基体31的作用，又能将结构单元32与导电基体31电隔绝。
本实施例中，导电基体31的外周面上各处的绝缘介质是同一种材料，也即导电基体31的外周面上各 处的绝缘介质具有相同的介电常数。在其他实施例中，导电基体的外周面上各处的绝缘介质可以是具有不同介电常数的不同材料，该方案将在下文继续说明。
本实施例中，对于包括导体层与绝缘层的结构单元32而言，该结构单元32中的绝缘层可以替代间隔3a内的绝缘介质，因而间隔3a内可以无需再填充绝缘介质。可以理解的是，根据产品需要，针对具有绝缘层的结构单元32也可以填充绝缘介质。
本实施例中，上述的绝缘介质(例如离散分布的绝缘介质)也可以称为绝缘支架，该绝缘支架起到连接并隔绝结构单元32与导电基体31的作用。当没有绝缘介质且结构单元32包括绝缘层与导电层时，该绝缘层也可以称为绝缘支架，结构单元32通过该绝缘支架与导电基体31连接，并与导电基体31隔绝。
如图5所示，所有结构单元32可以沿导电基体31的轴向依次间隔分布，每相邻的两个结构单元32(可以将其中一个结构单元32称为第一结构单元，将另一个结构单元32称为第二结构单元)之间均可以形成缝隙，该缝隙环绕导电基体31一周。上述的绝缘介质可以分布在该缝隙内，也可以不在该缝隙内。每个结构单元32均具有导电性能，使得该缝隙实质上可形成电容，可以称其为第一电容32a，其中，第一电容32a两侧的结构单元32可作为第一电容32a的极板。当绝缘介质分布在该缝隙内时，该缝隙内的绝缘介质也可以作为第一电容32a的组成部分。
如图5和图6所示，第一电容32a可以包括第一部分32b、第二部分32c、第三部分32d和第四部分32e，这四个区域依次首尾相连。第一部分32b与第三部分32d可以是中心对称的，二者的对称中心可以是导电基体31的轴心。第一部分32b与第三部分32d呈中心对称分布，意味着二者的结构一致(结构一致包括两个区域内绝缘介质的分布情况也一致)，其中一个绕对称中心旋转180度后与另一个重合。第二部分32c与第四部分32e可以是中心对称的，二者的对称中心可以是导电基体31的轴心。第二部分32c与第四部分32e呈中心对称分布，意味着二者的结构一致(结构一致包括两个区域内绝缘介质的分布情况也一致)，其中一个绕对称中心旋转180度后与另一个重合。
本实施例中，第一电容32a的电容值C满足电容公式：C＝εS/d，ε为极板间介质的介电常数，S为极板面积，d为极板间的距离。其中，极板即第一电容32a两侧的结构单元32，极板间介质即该绝缘介质(对于该绝缘介质分布在结构单元32之间的缝隙内的情况)或者空气(对于结构单元32之间的缝隙内没有该绝缘介质的情况)，S为相邻的结构单元32的正对面积，d为缝隙宽度。
本实施例中，由于第一部分32b与第三部分32d呈中心对称分布，根据上述电容公式可知：第一部分32b与第三部分32d的电容值相等。同理，由于第二部分32c与第四部分32e呈中心对称分布，因此第二部分32c与第四部分32e的电容值相等。下面将以第一部分32b和第二部分32c为描述对象，继续说明第一电容32a的特征。
如图5所示，第一部分32b对应的缝隙可以具有均匀宽度，即第一部分32b的缝隙的两边基本平行，第一部分32b的各处的缝隙宽度可以一致，或称第一部分32b的缝隙具有同一宽度。第二部分32c对应的缝隙可以具有非均匀宽度，即第二部分32c的缝隙的两边不平行，第二部分32c的各处的缝隙宽度不一致，或称第二部分32c的缝隙具有可变宽度。示意性的，第二部分32c的缝隙的两条边可以是曲线(例如为弧线)，第二部分32c的两端的缝隙宽度可以较小，位于两端之间的中部的缝隙宽度可以较大，从两端到中部的缝隙宽度可以是渐变的，由此使得第二部分32c的各处的缝隙宽度不一致。
如图5所示，第一部分32b的缝隙的最大宽度(也第一部分32b的任意处的缝隙宽度)可以小于或等于第二部分32c的缝隙的最小宽度(例如第二部分32c与第一部分32b邻接处的缝隙宽度)，也即从整体来上看，第一部分32b的缝隙宽度是小于第二部分32c的缝隙宽度的。因此根据上述电容公式可知：第一部分32b的电容值大于第二部分32c的电容值。
综上所述，在第一电容32a中，第一部分32b的缝隙宽度＝第三部分32d的缝隙宽度＜第二部分32c的缝隙宽度＝第四部分32e的缝隙宽度，第一部分32b的电容值＝第三部分32d的电容值＞第二部分32c的电容值＝第四部分32e的电容值。也即，第一电容32a的不同区域的缝隙宽度不同，导致第一电容32a的不同区域的电容值不同。
如图5所示，在天线结构件3中，所有结构单元32的形状一致且均匀间隔分布，使得所有缝隙的形状也一致并均匀间隔分布，这样形成的隐身结构层可以称为具有周期性结构。
在其他实施方式中，所有结构单元32的形状可以不全相同(指任意两个结构单元32的形状都不同；或者，至少有两个结构单元32的形状相同，但不是所有结构单元32的形状都相同)，和/或，所有结构单元32可以不是均匀间隔分布(指对于结构单元32之间的所有缝隙而言，任意两个缝隙的形状不同；或者至少有两个缝隙的形状相同，但不是所有缝隙的形状都相同)。这样使得所有缝隙的形状不全一致和/或非 均匀间隔分布，由此形成的隐身结构层可以称为准周期性结构。例如，准周期性结构可以是在周期性结构中删除若干个结构单元得到的结构。具有准周期性结构的隐身结构层，能够与导电基体31的外形结构适配。例如若导电基体31的外表面某处具有凸起，则隐身结构层在该处可以避让该凸起，以形成准周期性结构。
下面将说明天线结构件3的电磁隐身原理。
图5与图6中还示出了波源与天线结构件3的关系，其中波源指电磁波的源头，对于天线装置的辐射过程，波源即为天线装置；对于天线装置的接收过程，波源可以理解为空中环境。如图5与图6所示，在KEH三坐标系中，K表示电磁波的传播方向，E表示电场方向，H表示磁场方向，坐标系的原点可以指代波源位置。
结合图5与图6所示，示意性的，较窄的第一部分32b可以距离波源最近，较窄的第三部分32d可以距离波源最远。当电磁波沿K向传播至第一部分32b内时，电磁波将改变传播方向，并被约束在缝隙内沿缝隙的延伸方向传播。从第一部分32b起，电磁波可以分为两路传播，一路电磁波沿着第一部分32b、第二部分32c与第三部分32d的路径传播，另一路电磁波沿着第一部分32b、第四部分32e与第三部分32d的路径传播。两路电磁波传播至第三部分32d时，将会以传播方向K从第三部分32d射出。
本实施例中，如图6所示，第一部分32b可以接收波源的电磁波，第三部分32d可出射电磁波，第一部分32b与第三部分32d相当于贴片天线。第二部分32c与第四部分32e可将电磁波束缚在其内传输，二者可相当于缝隙传输线(slotline)。
由此可见，第一电容32a的作用是改变波源发出的电磁波的传播方向，并将电磁波约束在其内进行传播，使得电磁波能够绕着天线结构件3进行传播，并可以保持电磁波从第一电容32a内射出时的传播方向不变。因此，即使天线结构件3对波源存在遮挡，但是由于存在第一电容32a，使得电磁波能够绕过天线结构件3传播至天线结构件3的后方，从而减少或者消除了电磁阴影。并且，由于可以不改变电磁波的传播方向，因而能够保证电磁波的传播特性不变。
所以，本实施例的天线结构件3，通过在导电基体31的外周设置至少两个结构单元32，并形成第一电容32a，使得导电基体31相对电磁波具有电磁隐身性能，避免或减少了导电基体31对电磁波的遮挡。
本实施例中，由于第一电容32a的不同区域的电容值不同，使得不同频段的电磁波信号均能够以各自的电长度在缝隙内发生谐振，从而使得不同频段的电磁波均能通过缝隙。也即，通过使第一电容32a的不同区域的电容值不同，使缝隙能够允许多种频段的电磁波通过，从而拓展了隐身带宽。
根据上述的原理说明容易理解，天线结构件3中只要存在一个第一电容32a，即能改善导电基体31对电磁波的遮挡，拓展隐身带宽。当然根据实际需要，第一电容32a的数量可以是多个。
本实施例中，靠近波源的第一部分32b的电容值较大的设计，能够满足一些频段的电磁波的传播需要，但这并非是对本申请实施例的限定。在其他实施例中，第一电容32a的各个区域的电容值大小，与距离波源的远近的对应关系可以根据需要设计，不限于上文所述。例如，针对一些频段的电磁波，可以使得第一电容32a中的距离波源较近的区域具有较小的电容值。
本实施例中，使得靠近波源的第一部分32b的缝隙具有均匀宽度，距离波源稍远的第二部分32c的缝隙具有非均匀宽度，这仅仅是一种举例，并非是对本申请实施例的限定。例如，也可以使得靠近波源的第一部分32b的缝隙具有非均匀宽度，使得距离波源稍远的第二部分32c的缝隙具有均匀宽度，且使得第一部分32b的最大缝隙宽度小于或等于第二部分32c的最小缝隙宽度(也即第二部分32c的任意处的缝隙宽度)，进而使得第一部分32b电容值大于所述第二部分32c的电容值。
本实施例中，以缝隙的宽度变化将第一电容32a分为四个部分，这仅仅是一种举例，并非是对本申请实施例的限定，还可以设计缝隙的宽度变化，以从第一电容32a中划分出其他数量的部分。实际上根据产品需要，本申请实施例中的缝隙只要不是恒定宽度缝隙即可，这样就能够实现拓展隐身带宽的目的。
本实施例中，第一部分32b与第三部分32d中心对称，第二部分32c与第四部分32e中心对称，该设计能够能保证电磁波经第一电容32a射出后，保持之前的传播方向与传播特性(例如极化特性、频段等)。但是该设计仅仅是一种举例，并非是对本申请实施例的限定。例如，可以仅使第一部分32b与第三部分32d的形状一致，但位置上并不要求中心对称，这样虽然改变了电磁波的传播方向与传播特性，但是可以满足天线信号的互易性，还可以使得从第一电容32a射出的电磁波折射到其他方向进而扩大天线装置的信号扫描范围(例如一种多输入多输出MIMO天线可应用该方案)。或者，可以使得第一部分32b与第三部分32d的形状不同，且位置上不要求中心对称。
上文详细说明了本实施例的电磁隐身的原理设计，下面将结合图4说明本实施例的电磁隐身设计在天 线系统2中的具体应用。
如图4所示，天线系统2中的天线结构件24可以包括移相器242，以及覆盖移相器242的外表面的隐身结构层241。其中，移相器242为上述的导电基体31的一种具体形式，隐身结构层241对应上述的隐身结构层。天线结构件24对第二辐射单元26具有一定遮挡，但是由于设置了隐身结构层241，第二辐射单元26辐射的电磁波将会绕过天线结构件24继续传播，或者电磁波将会绕过天线结构件24而被第二辐射单元26接收到，从而能减少或者消除电磁阴影。因此，第二辐射单元26可以具备大角度扫描能力，其口径(例如图4中的水平方向的口径)可以得到扩展，而不会受到前置移相器242的遮挡与限制。
与上述实施例不同的是，如图7所示，在另一种实施例中，天线结构件4的导电基体41可以大致为矩形柱状结构。结构单元42可以大致是由四个平板围成的方形筒状结构。相邻的结构单元42之间的第一电容可以包括第一部分42b与第二部分42c。第一部分42b可以位于导电基体41的一个侧面的外周，第二部分42c可以位于导电基体41的另一个侧面的外周，第一部分42b与第二部分42c的邻接位置可以对应导电基体41的棱边。
如图7所示，示意性的，第一部分42b与第二部分42c均可以为矩形区域，第一部分42b与第二部分42c的缝隙均具有均匀宽度。第一部分42b的缝隙宽度可以小于第二部分42c的缝隙宽度。可以理解的是，结构单元42的第一电容还可以包括第三部分与第四部分(由于图7视角原因未显示)，第三部分与第一部分42b可以是中心对称的，第四部分与第二部分42c可以是中心对称的。
本实施例中，由于第一部分42b的缝隙宽度小于第二部分42c的缝隙宽度，因此根据上述电容公式，第一部分42b的电容值大于第二部分42c的电容值。也即，第一电容的不同区域的缝隙宽度不同，导致第一电容的不同区域的电容值不同。
如图7所示，示意性的，电磁波的传播方向K可以垂直于天线结构件4中第一部分42b所在的侧面，但是本实施例的方案并不限于此，例如第一部分42b所在的侧面也可与传播方向K不垂直。
本实施例的方案使得导电基体41相对电磁波具有电磁隐身性能，避免或减少了导电基体41对电磁波的遮挡，还能拓展隐身带宽。另外，天线结构件4上的缝隙的结构简单，量产性好，并且能满足特定的产品需求。
与图7所示的实施例不同的是，如图8(a)和图8(b)所示，在另一种实施例中，天线结构件5的相邻的结构单元52之间的第一电容可以包括第一部分52b与第二部分52c，其中，第一部分52b的缝隙可由至少两段子缝隙52d依次弯折连接而成，即若干段子缝隙52d依次连接，且每相邻的两段子缝隙52d形成弯折角。子缝隙52d之间的弯折角度可以根据需要设计，例如可以为90°，第一部分52b的此种缝隙可以形成类似方波的形状。在其他实施方式中，相邻子缝隙52d的弯折角可以不限于90°，以使第一部分52b的缝隙形成其他形状，例如曲线形状(如正弦曲线、抛物线等)。
如图8(b)所示，每段子缝隙52d均可以具有均匀宽度，且所有子缝隙52d的宽度相同，因此子缝隙52d的宽度也即第一部分52b的缝隙宽度d1。第二部分52c的缝隙具有均匀宽度，且第二部分52c的缝隙宽度d2可以大于第一部分52b的缝隙宽度。
本实施例中，第一部分52b中的所有子缝隙52d连接而成的总缝隙长度，可以大于第二部分52c的缝隙长度。对于上述电容公式C＝εS/d(ε为极板间介质的介电常数，S为极板面积，d为极板间的距离)，由于第一部分52b的缝隙长度较大，因此第一部分52b的极板面积S1较大(第一部分52b与第二部分52c的缝隙深度一致)；第二部分52c的缝隙长度较小，因此第一部分52b的极板面积S2较小。
本实施例中，对于第一部分52b与第二部分52c而言，可以使(S1/d1)＞(S2/d2)，从而使第一部分52b的电容值C1＞第二部分52c的电容值C2。也即，本实施例可通过配置第一电容的不同区域的缝隙长度与缝隙宽度，使得第一电容的不同区域的电容值不同。
本实施例的方案使得导电基体51相对电磁波具有电磁隐身性能，避免或减少了导电基体41对电磁波的遮挡，还能拓展隐身带宽。
本实施例的方案可以应用在如下的场景中：当出于制造工艺的限制，无法制造出缝隙宽度小于阈值的规则形状(例如矩形形状)的第一部分时，可以考虑将第一部分设计成图8(a)所示的第一部分52b(第一部分52b可认为是一种不规则形状)，通过增加缝隙长度来弥补缝隙宽度无法做小的工艺限制，最终使得第一部分具有较大的电容值。所以，本实施例的设计能够与已有制造工艺匹配，量产性较好。
在其他实施例中，可以采用与图8(a)所示实施例不同的方案，只要保证(S1/d1)＞(S2/d2)从而使第一部分的电容值大于第二部分的电容值即可。
例如，在一种实施方式中，可以使得第一部分由至少两段子缝隙依次弯折连接而成，第一部分的缝隙 长度大于第二部分的缝隙长度，每段子缝隙具有均匀宽度，所有子缝隙的宽度一致，第二部分的缝隙具有均匀宽度，且第二部分的缝隙宽度等于第一部分的缝隙宽度。
或者，在另一种实施方式中，可以使得第一部分由至少两段子缝隙依次弯折连接而成，第一部分的缝隙长度大于第二部分的缝隙长度，但是对子缝隙的宽度不做限定(例如子缝隙可以具有非均匀缝隙，所有子缝隙的宽度不全相同等)，对第二部分的缝隙宽度也不做限定(例如第二缝隙可以具有非均匀宽度，不限定第二缝隙的缝隙宽度与子缝隙的宽度的大小关系)。
或者，在另一种实施方式中，可以使得第一部分由至少两段子缝隙依次弯折连接而成，第二部分也由至少两段子缝隙依次弯折连接而成，除此之外均不做限定。
与图7所示实施例不同的是，如图9所示，在另一种实施例中，天线结构件6的相邻的结构单元62之间的第一电容可以包括第一部分62b与第二部分62c。其中，第二部分62c可以跨越导电基体61的一条棱边，并可以分布于导电基体61的两个相邻侧面的外周，也即第二部分62c的一部分位于一个侧面，第二部分62c的另一部分位于另一个侧面，第二部分62c的这两部分弯折连接。第一部分62b可以跨越导电基体61的另一条棱边，并可以分布于导电基体61的另外两个相邻侧面的外周(由于图9视角原因，并未显示出完整的第一部分62b)。另外，电磁波的传播方向K并不垂直于天线结构件6的任一个侧面。
本实施例的方案使得导电基体61相对电磁波具有电磁隐身性能，避免或减少了导电基体61对电磁波的遮挡，还能拓展隐身带宽。另外，天线结构件6上的缝隙的结构简单，量产性好，并且能满足特定的产品需求。下面将说明图9所示方案的一种具体应用。
图10示出了图9所示的电磁隐身设计在图4所示的天线系统2中的具体应用。为了突出说明重点，图10显示了天线系统2的局部。如图9和图10所示，天线结构件6在天线系统2中具体可以是天线结构件24，导电基体61具体可以是天线结构件24的移相器242，隐身结构层241设在移相器242的外周。隐身结构层241包括第一电容，第一电容包括第一部分62b、第二部分62c、第三部分62d和第四部分62e。示意性的，第一部分62b与第三部分62d中心对称，第二部分62c与第四部分62e中心对称。
如图10所示，以第二辐射单元26作为波源为例，第二辐射单元26距离第一部分62b最近。第二辐射单元26辐射的电磁波大致会沿“斜向”传播至天线结构件24的两个相邻侧面，因此使得第一部分62b分布在这两个侧面，便于第一部分62b接收电磁波，并将电磁波约束在第一电容内进行传播，最终使电磁波从第三部分62d射出。由于第一部分62b采用“跨越移相器242的棱边”式分布，因此第二部分62c、第三部分62d和第四部分62e也是“跨越移相器242的棱边”式分布。由此可见，使得第一电容的不同电容值区域均分布在移相器242的两个相邻侧面，能够与波源的位置匹配，从而实现较好的电磁隐身效果。
与图7所示实施例相同的是，如图11所示，在另一种实施例中，天线结构件7包括导电基体71以及至少两个结构单元72，相邻的结构单元72之间形成第一电容，第一电容可以包括第一部分72b与第二部分72c。
与图7所示实施例不同的是，如图11所示，本实施例的结构单元72并非是一体式结构，而是内部具有耦合缝隙，结构单元72位于耦合缝隙两侧的部分完全断开不连接，耦合缝隙两侧的部分可通过该耦合缝隙耦合。示意性的，结构单元72可以包括第一部分721、第二部分722、第三部分723和第四部分724，这四个部分可以分别位于导电基体71的不同侧面。第一部分721与第二部分722之间具有耦合缝隙72f，第二部分722与第三部分723之间具有耦合缝隙72g，第三部分723与第四部分724之间具有耦合缝隙72h，第四部分724与第一部分721之间具有耦合缝隙72i。上述四个耦合缝隙可以将结构单元72分隔成四个独立的部分。当电磁波传播至结构单元72时，电磁波可以“跨过”这些耦合缝隙，因此结构单元72位于耦合缝隙两侧的部分通过耦合缝隙耦合。
如图11所示，示意性的，每个耦合缝隙均沿着导电基体71的棱边延伸。结构单元72具有四个耦合缝隙，四个耦合缝隙将结构单元72分隔成四个独立的部分。以上均仅仅是一种举例，并非是对本实施例的限定。根据产品需要，耦合缝隙的位置与延伸方向可以灵活设计，耦合缝隙的数量可以是至少一个。另外，可以是所有结构单元72均具有耦合缝隙，也可以仅有部分结构单元72具有耦合缝隙。
本实施例中，在结构单元72中形成耦合缝隙，便于将结构单元72的不同部分依次装配到导电基体71上，最后拼成完整的结构单元72，这样能够在一些场景下实现结构单元72的可靠组装。尤其是在导电基体71的尺寸较大、结构单元72的数量较多时，分体组装的方式能够简化组装工艺，提高组装良率。另外，耦合缝隙能够允许某些频段的电磁波通过，使得天线结构件7具有一定的拓展隐身带宽作用。
可以理解的是，本实施例的耦合缝隙设计可以根据需要，应用在本申请的其他任一实施例中。
与图11所示实施例相同的是，如图12所示，在另一种实施例中，天线结构件8包括导电基体81以 及至少两个结构单元82，相邻的结构单元82之间形成第一电容，第一电容可以包括第一部分82b与第二部分82c。结构单元82并非是一体式结构，而是内部具有耦合缝隙，结构单元82位于耦合缝隙两侧的部分完全断开不连接，耦合缝隙两侧的部分可通过该耦合缝隙耦合。
与图11所示实施例不同的是，如图12所示，本实施例的结构单元82可以具有耦合缝隙82f与耦合缝隙82g，耦合缝隙82f与耦合缝隙82g可以分别位于结构单元82的相对两侧。示意性的，耦合缝隙82f与耦合缝隙82g均可以大致在结构单元82的侧面的中部，并非是在结构单元82的棱边处。耦合缝隙82f与耦合缝隙82g可以将结构单元82分隔成第一部分821与第二部分822，第一部分821与第二部分822均可以近似呈C形结构。示意性的，本实施例的隐身结构层可以具有周期性结构，因此所有结构单元82的同侧的耦合缝隙可以共线。
本实施例中，在结构单元82中形成耦合缝隙，便于将结构单元82的不同部分依次装配到导电基体81上，最后拼成完整的结构单元82，这样能够在一些场景下实现结构单元82的可靠组装。尤其是在导电基体81的尺寸较大、结构单元82的数量较多时，分体组装的方式能够简化组装工艺，提高组装良率。由于结构单元82的部件数量较少，可以一定程度上简化组装工艺。另外，耦合缝隙能够允许某些频段的电磁波通过，使得天线结构件8具有一定的拓展隐身带宽作用。
可以理解的是，本实施例的耦合缝隙设计可以根据需要应用在本申请的其他任一实施例中，包括下文将要描述的实施例。
与图7所示实施例相同的是，如图13所示，在另一种实施例中，天线结构件9包括导电基体91以及至少两个结构单元92，相邻的结构单元92之间形成第一电容，第一电容可以包括第一部分92b与第二部分92c。
与图7所示实施例不同的是，如图13所示，每个结构单元92的局部区域可以镂空形成镂空区。示意性的，每个结构单元92的两个相对侧面均可以形成镂空，分别形成镂空区92f与镂空区92g。在其他实施方式中，可以根据产品需要设计镂空区的位置及数量，不限于图13所示。例如，只要至少一个结构单元92形成镂空区即可。
本实施例中，在结构单元92上形成镂空区，能够减轻重量，有利于减小天线结构件9的重量。特别是当结构单元92为较重的金属件时，开设镂空区能极大减重。另外，当电磁波传播至天线结构件9附近时，电磁场主要分布在第一电容处，其余区域的电磁场很弱，因此开设镂空区也基本不影响电磁波的传播特性。
可以理解的是，本实施例的镂空设计可以应用在本申请的其他任一实施例中，包括下文将要描述的实施例。
与上述实施例相同的是，如图14所示的实施例中，天线结构件10可以包括导电基体101以及至少两个结构单元102，相邻的结构单元102之间形成第一电容102a。
与上述实施例均不同的是，图14中的第一电容102a可以具有均匀的缝隙宽度，也即第一电容102a的缝隙的各个位置的宽度可以一致。并且，结构单元102与导电基体101之间可以填充绝缘介质，绝缘介质例如可以覆盖导电基体101的整个外周面。绝缘介质可以包括第一绝缘介质103a与第二绝缘介质103b，第一绝缘介质103a的介电常数可以大于第二绝缘介质103b的介电常数。第一绝缘介质103a与第二绝缘介质103b例如可以沿着导电基体101的长度方向从导电基体101的一端延伸到另一端，并且二者可以在导电基体101的周向方向上交替排布，以形成图15所示的排布方式：第一绝缘介质103a-第二绝缘介质103b-第一绝缘介质103a-第二绝缘介质103b。第一绝缘介质103a可以分布于导电基体101的两个相邻侧面，第二绝缘介质103b也可以分布于导电基体101的两个相邻侧面，第一绝缘介质103a与第二绝缘介质103b均可以跨越导电基体101的棱边。
本实施例中，可以在第一电容102a中定义出第一部分、第二部分、第三部分与第四部分，第一部分距离波源最近，第一部分内填充有第一绝缘介质103a，第二部分与第一部分相邻，第二部分内填充有第二绝缘介质103b，第三部分与第一部分相对(例如可以中心对称)，第三部分内填充有第一绝缘介质103a，第四部分与第二部分相对(例如可以中心对称)，第四部分内填充有第二绝缘介质103b。
根据上述的电容公式C＝εS/d(ε为极板间介质的介电常数，S为极板面积，d为极板间的距离)，对于第一电容102a的各个区域而言，在S与d均一致的情况下，由于第一部分内的第一绝缘介质103a的介电常数较大，因此第一部分的电容值较大；由于第二部分内的第二绝缘介质103b的介电常数较小，因此第一部分的电容值较小。第三部分的电容值可以等于第一部分的电容值，第四部分的电容值可以等于第二部分的电容值。因此，本实施例可通过使第一电容102a具有均匀缝隙宽度，且使得第一电容102a的不同 区域填充不同介电常数的绝缘介质，使得第一电容102a的不同区域的电容值不同。
本实施例的方案使得导电基体101相对电磁波具有电磁隐身性能，避免或减少了导电基体101对电磁波的遮挡，还能拓展隐身带宽。另外如图15所示，电磁波的传播方向K可以不垂直于天线结构件10的任一个侧面，该设计使得天线结构件10能够应用于图10所示的天线系统2中，通过使得第一电容102a的不同电容值区域均分布在移相器242的两个相邻侧面，能够与波源的位置匹配，从而实现较好的电磁隐身效果。详细原理上文已有描述，此处不再重复。
可以理解的是，本实施例通过填充不同介电常数的绝缘介质实现不同区域的电容值差异的设计，可以根据需要应用在本申请的其他任一实施例中。例如，可以不限定第一电容的缝隙尺寸(包括宽度尺寸与长度尺寸等)、缝隙样式(指缝隙为一整条缝隙，还是如图8(a)所示的由若干段子缝隙依次弯折连接而成)、缝隙分布(指缝隙仅分布在导电基体的一个侧面还是分布在两个相邻侧面)等，并在第一电容的不同区域填充不同介电常数的绝缘介质，通过综合配置缝隙的形状尺寸、位置尺寸和绝缘介质的介电常数，最终使第一部分的电容值大于第二部分的电容值。
与上图14所示实施例相同的是，如图16所示的实施例中，天线结构件20可以包括导电基体201以及至少两个结构单元202，相邻的结构单元202之间形成第一电容202a。
与上图14所示实施例不同的是，如图16所示，第一电容202a可以无需填充绝缘介质，或者可以填充同种介电常数的绝缘介质。并且，第一电容202a的不同区域可以分别安装电容值不同的电容器件，例如距离波源最近与最远的区域可以安装第一电容器件204(由于图16视角所限，未显示距离波源最远的、位于下方的第一电容器件204)，与第一电容器件204相邻的区域可以安装第二电容器件203。可以将安装第一电容器件204的区域称为第一部分与第三部分，将安装第二电容器件203的区域称为第二部分与第四部分。第一电容器件204的电容值大于第二电容器件203的电容值。第一电容器件204可以是固定电容值的电容器件，或者可以是能在信号控制下改变电容值的电容器件(例如变容管)。第二电容器件203可以是固定电容值的电容器件，或者可以是能在信号控制下改变电容值的电容器件(例如变容管)。第一电容器件204也可以称为第二电容，第二电容器件203也可以称为第三电容。
第一电容器件204与第二电容器件203例如可以通过焊接等方式固定在缝隙内。第一电容器件204与第二电容器件203的数量可以根据需要确定，本实施例不做限定。
第一电容202a的各个区域的电容值可以等于根据上述的电容公式C＝εS/d(ε为极板间介质的介电常数，S为极板面积，d为极板间的距离)计算得到的电容值加上该区域的电容器件的电容值。对于第一电容202a的各个区域而言，在ε、S、d均一致的情况下，根据电容公式C＝εS/d计算得到的电容值相等。由于第一部分内设有电容值较大的第一电容器件204，因此第一部分的电容值较大；由于第二部分内设有电容值较小的第二电容器件203，因此第二部分的电容值较小。第三部分的电容值可以等于第一部分的电容值，第四部分的电容值可以等于第二部分的电容值。
因此，本实施例可通过使第一电容202a具有均匀缝隙宽度，且使得第一电容202a的不同区域安装不同电容值的电容器件，使得第一电容202a的不同区域的电容值不同。
本实施例的方案使得导电基体201相对电磁波具有电磁隐身性能，避免或减少了导电基体201对电磁波的遮挡，还能拓展隐身带宽。示意性的，当电容器件为可变电容的电容器件时，可以根据波源的扫描角度变化，适应性地调整相应区域的电容器件的电容，进而调整该区域的电容值大小，确保天线结构件20对波源的电磁隐身效果。
基于本实施例的原理容易得出其他变形方案。例如，可以仅在第一电容202a的部分区域设电容器件(例如第一部分)，不在其他区域设电容器件，同样可以使得第一电容202a的不同区域的电容值不同。另外，通过在区域内设置电容器件影响区域的电容值的设计，可以根据需要应用在本申请的任一实施例中。例如，可以不限定第一电容的缝隙尺寸、缝隙样式、缝隙分布、绝缘介质的填充情况等，并在第一电容内安装电容器件，通过综合配置缝隙的形状尺寸、位置尺寸、绝缘介质的介电常数及电容器件的电容值，最终使第一部分的电容值大于第二部分的电容值。
在以上任一实施例中，结构单元与导电基体之间可以形成电容(例如称为平板电容)，该平板电容可以影响绕过天线结构件的电磁波的频段。出于产品需要(例如减小体积的需要)，可能希望减小结构单元与导电基体的间隔。但是间隔减小可能导致绕过天线结构件的电磁波的频段提高，改变电磁波的传播特性。
有鉴于此，在以上任一实施例的基础上，天线结构件还可以包括电感元件，电感元件可以设在结构单元与导电基体的间隔内，并连接结构单元与导电基体，以使结构单元与导电基体电连接。电感元件可与上述的平板电容构成并联谐振电路，该并联谐振电路能使绕过天线结构件的电磁波的频段降低。因此，设置 电感元件与减小结构单元与导电基体的间隔对频段的影响可以相互抵消，使得绕过天线结构件的电磁波的频段保持不变，从而保持电磁波的传播特性。
本实施例中，电感元件可以是导体结构件，例如金属柱，此种电感元件可以等效为电感，此种电感元件便于实现天线结构件的机械加工。或者，电感元件可以直接为电感。
本实施例中，电感元件的位置可以根据需要设计，例如与第一电容相距一定距离，避免过于靠近。电感元件的数量可以根据需要设计，例如每个结构单元均可通过至少一个电感元件与导电基体连接，或者仅有部分结构单元通过电感元件与导电基体连接。
图17示意了一种应用本实施例的电感元件设计的天线结构件30。如图17所示，天线结构件30可以包括导电基体301以及至少两个结构单元302，相邻的结构单元302之间形成第一电容302a。结构单元302的每个侧面均通过电感元件303与导电基体301连接，每个结构单元302与导电基体301之间均设有若干个电感元件303。可以理解的，图17所示的天线结构件30仅仅是一种举例，并非是在限定电感元件303的应用环境。
以上对本申请实施例的详细介绍。本文中应用了具体个例对本申请的原理及实施例进行了阐述，以上实施例的说明只是用于帮助理解本申请的方法及其核心思想；同时，对于本领域的一般技术人员，依据本申请的思想，在具体实施例及应用范围上均会有改变之处。综上所述，本说明书内容不应理解为对本申请的限制。

Claims (21)

  1. 一种天线结构件，用于基站天线系统中，其特征在于，
    所述天线结构件包括导电基体和至少两个结构单元；所述至少两个结构单元中的每个结构单元均环绕所述导电基体一周，每个结构单元均与所述导电基体间隔设置，所述至少两个结构单元包括相邻的第一结构单元与第二结构单元，所述第一结构单元与所述第二结构单元间隔排布并形成第一电容，所述第一电容的不同部分的电容值不同。
  2. 根据权利要求1所述的天线结构件，其特征在于，
    所述第一电容包括第一部分、第二部分、第三部分与第四部分，所述第一部分、所述第二部分、所述第三部分与所述第四部分依次首尾相连，所述第一部分的电容值与所述第三部分的电容值相等，所述第二部分的电容值与所述第四部分的电容值相等，且所述第一部分的电容值与所述第二部分的电容值不同。
  3. 根据权利要求2所述的天线结构件，其特征在于，
    所述第一部分与所述第三部分呈中心对称分布，所述第二部分与所述第四部分呈中心对称分布。
  4. 根据权利要求1-3任一项所述的天线结构件，其特征在于，
    所述第一结构单元和所述第二结构单元之间存在缝隙，所述第一电容的不同部分的缝隙的宽度不同。
  5. 根据权利要求4所述的天线结构件，其特征在于，
    所述第一电容包括相连的第一部分与第二部分；
    所述第一部分的缝隙与所述第二部分的缝隙均具有同一宽度，且所述第一部分的缝隙的宽度小于所述第二部分的缝隙的宽度，第一部分的电容值大于所述第二部分的电容值；
    或者，所述第一部分的缝隙与所述第二部分的缝隙中的一个具有同一宽度，另一个具有可变宽度，所述第一部分的缝隙的最大宽度小于或者等于所述第二部分的缝隙的最小宽度，第一部分的电容值大于所述第二部分的电容值。
  6. 根据权利要求1-5任一项所述的天线结构件，其特征在于，
    所述第一结构单元和所述第二结构单元之间存在缝隙；所述第一电容包括相连的第一部分与第二部分，所述第一部分的缝隙由至少两段子缝隙依次弯折连接而成，所述第一部分的电容值大于所述第二部分的电容值。
  7. 根据权利要求6所述的天线结构件，其特征在于，
    所述第二部分的缝隙具有同一宽度；所述第一部分的每段所述子缝隙均具有同一宽度，所有所述子缝隙的宽度一致，且所述子缝隙的宽度小于或等于所述第二部分的缝隙的宽度。
  8. 根据权利要求1-7任一项所述的天线结构件，其特征在于，
    所述第一电容包括相连的第一部分与第二部分，所述第一部分内填充有第一绝缘介质，所述第二部分内填充有第二绝缘介质，所述第一绝缘介质的介电常数大于所述第二绝缘介质的介电常数，所述第一部分的电容值大于所述第二部分的电容值。
  9. 根据权利要求1-8任一项所述的天线结构件，其特征在于，
    所述第一电容包括相连的第一部分与第二部分；
    所述天线结构件包括第二电容，所述第二电容设于所述第一部分，所述第一部分的电容值大于所述第二部分的电容值。
  10. 根据权利要求9所述的天线结构件，其特征在于，
    所述天线结构件包括第三电容，所述第三电容设于所述第二部分，所述第三电容的电容值小于所述第二电容的电容值。
  11. 根据权利要求10所述的天线结构件，其特征在于，
    所述第二电容和/或所述第三电容的电容值可调。
  12. 根据权利要求1-11任一项所述的天线结构件，其特征在于，
    至少一个所述结构单元设有耦合缝隙，所述结构单元分别位于所述耦合缝隙两侧的部分被所述耦合缝隙断开，并通过所述耦合缝隙耦合。
  13. 根据权利要求1-12任一项所述的天线结构件，其特征在于，
    所述天线结构件包括电感元件，所述至少两个结构单元中的结构单元通过所述电感元件与所述导电基体连接。
  14. 根据权利要求1-13任一项所述的天线结构件，其特征在于，
    至少一个所述结构单元镂空。
  15. 根据权利要求1-14任一项所述的天线结构件，其特征在于，
    所述至少两个结构单元的结构相同，且任意相邻的两个所述结构单元之间存在缝隙且形状相同，任意两个相邻的所述结构单元之间均形成所述第一电容。
  16. 根据权利要求1-14任一项所述的天线结构件，其特征在于，
    所述至少两个结构单元的结构不全相同，和/或，所述至少两个结构单元之间存在缝隙且形状不全相同；任意两个相邻的所述结构单元之间均形成所述第一电容。
  17. 根据权利要求1-16任一项所述的天线结构件，其特征在于，
    每个所述结构单元包括导体层与绝缘层，所述绝缘层位于所述导体层与所述导电基体之间；
    或者，每个所述结构单元为导体。
  18. 根据权利要求1-17任一项所述的天线结构件，其特征在于，
    所述基站天线系统包括抱杆、抱杆支架与馈电网络，所述导电基体包括所述抱杆、所述抱杆支架及所述馈电网络中的至少一个。
  19. 一种天线，其特征在于，
    包括辐射单元和权利要求1-18任一项所述的天线结构件。
  20. 一种基站，其特征在于，
    包括抱杆和第一天线，所述第一天线固定于所述抱杆，所述第一天线为权利要求19所述的天线。
  21. 根据权利要求20所述的基站，其特征在于，
    所述基站包括第二天线与频率选择表面，所述频率选择表面位于所述第一天线的辐射单元与所述第二天线的辐射单元之间，所述频率选择表面用于反射所述第一天线的辐射信号，并透过所述第二天线的辐射信号。
PCT/CN2023/117404 2022-09-08 2023-09-07 天线结构件、天线和基站 WO2024051767A1 (zh)

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Citations (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN107634290A (zh) * 2017-08-28 2018-01-26 广州司南天线设计研究所有限公司 一种新型耦合移相器
CN108140923A (zh) * 2015-09-15 2018-06-08 赛尔麦克斯科技公司 使用间接互连的天线装置
CN112886170A (zh) * 2019-11-29 2021-06-01 华为技术有限公司 一种射频器件
CN114094347A (zh) * 2020-08-24 2022-02-25 华为技术有限公司 多频段天线系统和基站
WO2022140999A1 (zh) * 2020-12-28 2022-07-07 华为技术有限公司 基站天线

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CN108140923A (zh) * 2015-09-15 2018-06-08 赛尔麦克斯科技公司 使用间接互连的天线装置
CN107634290A (zh) * 2017-08-28 2018-01-26 广州司南天线设计研究所有限公司 一种新型耦合移相器
CN112886170A (zh) * 2019-11-29 2021-06-01 华为技术有限公司 一种射频器件
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