WO2023286158A1 - Système de communication sans fil et procédé de communication - Google Patents

Système de communication sans fil et procédé de communication Download PDF

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Publication number
WO2023286158A1
WO2023286158A1 PCT/JP2021/026305 JP2021026305W WO2023286158A1 WO 2023286158 A1 WO2023286158 A1 WO 2023286158A1 JP 2021026305 W JP2021026305 W JP 2021026305W WO 2023286158 A1 WO2023286158 A1 WO 2023286158A1
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WIPO (PCT)
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signal
receiving device
transmitting device
communication system
jitter
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PCT/JP2021/026305
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English (en)
Japanese (ja)
Inventor
淳 増野
斗煥 李
貴之 山田
裕文 笹木
康徳 八木
知哉 景山
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日本電信電話株式会社
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Priority to JP2023534476A priority Critical patent/JPWO2023286158A1/ja
Priority to PCT/JP2021/026305 priority patent/WO2023286158A1/fr
Publication of WO2023286158A1 publication Critical patent/WO2023286158A1/fr

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    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B7/00—Radio transmission systems, i.e. using radiation field
    • H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
    • H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
    • H04B7/0413—MIMO systems
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/26—Systems using multi-frequency codes

Definitions

  • the present invention relates to technology for spatially multiplexing radio signals.
  • Non-Patent Document 2 In MIMO communication, spatial multiplexing transmission/reception is generally performed on the premise of time synchronization between antenna ports. That is, the sampling timings of the transmitting antenna ports #1 to #N are the same, and according to the rules of the radio frame, etc., the signals to be spatially multiplexed are superimposed on the same sample range at each antenna port, and MIMO detection processing is performed on the receiving side.
  • the alias component that appears when the baseband signal is oversampled in digital signal processing is extracted with an appropriate BPF (Band-pass filter), and the RF frequency band signal There are also radios that transmit as (and vice versa, receive).
  • BPF Band-pass filter
  • GSa/s class high-speed sampling DAC operation is a prerequisite, and when transmission (reception) is performed from multiple antenna ports as in a MIMO antenna configuration, sampling between antenna ports Level synchronization becomes difficult.
  • the specifications are such that a maximum deviation of ⁇ 1 sample occurs between the antenna ports.
  • the disclosed technology aims to improve sample-level synchronization performance between antenna ports and to separate spatially multiplexed signals appropriately.
  • a technology disclosed herein is a wireless communication system that performs MIMO communication and includes a transmitting device and a receiving device, wherein the transmitting device transmits a wireless communication signal to the receiving device, and the receiving device communicates with the transmitting device. obtaining information indicating a maximum jitter value indicating sample synchronization capability between antenna ports of the transmitting device, based on the maximum jitter value of the transmitting device and the maximum jitter value of the receiving device.
  • the sample-level synchronization performance between antenna ports can be improved, and spatially multiplexed signals can be separated appropriately.
  • FIG. 1 is a configuration diagram of a communication system according to an embodiment of the present invention
  • FIG. FIG. 4 is a diagram for explaining synchronization of sample levels between antenna ports
  • FIG. 4 is a first diagram for explaining how inter-symbol interference occurs
  • FIG. 10 is a second diagram for explaining how inter-symbol interference occurs.
  • FIG. 10 is a diagram for explaining a method of offsetting an FFT interval according to the first embodiment
  • FIG. 2 is a diagram illustrating a configuration example of a transmission device according to Example 1
  • FIG. 2 is a diagram illustrating a configuration example of a receiving device according to Example 1
  • FIG. FIG. 10 is a diagram illustrating a configuration example of a transmission device according to a second embodiment
  • FIG. 10 is a diagram illustrating a configuration example of a receiving device according to Example 2;
  • FIG. 11 is a diagram for explaining a method of offsetting an FFT interval according to the second embodiment;
  • FIG. 4 is a diagram for explaining a method of offsetting FFT intervals in uplink multi-user MIMO;
  • FIG. 11 is a diagram illustrating a configuration example of a wireless communication system according to a third embodiment;
  • FIG. 13 is a diagram illustrating a configuration example of a transmission device according to a fourth embodiment;
  • FIG. 11 is a diagram for explaining a method of offsetting an FFT interval according to the fourth embodiment;
  • FIG. 1 is a configuration diagram of a communication system according to an embodiment of the present invention. As shown in FIG. 1, the radio communication system according to this embodiment has transmitting apparatus 100 and receiving apparatus 200 .
  • FIG. 2 is a diagram for explaining synchronization of sample levels between antenna ports.
  • reception is performed based on the SYNC signal (synchronization signal) for time synchronization multiplexed on a specific antenna port (ch1 in the figure).
  • the FFT Fast Fourier Transform
  • the FFT interval is an interval used for signal demodulation or signal equalization.
  • CPrefix a cyclic prefix that duplicates the end of the signal waveform of the DATA part (data signal) ) is added before the DATA part, and after removing these on the receiving side, FFT is performed to obtain modulation symbols for each subcarrier.
  • CPrefix cyclic prefix
  • MIMO-OFDM if sample levels between antenna ports are not synchronized, sample positions of CPrefix shift for each MIMO channel, which causes inter-symbol interference.
  • FIG. 3 is a first diagram for explaining how inter-symbol interference occurs.
  • a SYNC signal is multiplexed to a specific antenna port (ch1 in the figure), and the receiver detects this to identify the start and end points of the following CPrefix and the start and end points of the DATA portion.
  • the receiver performs OFDM demodulation with the end point of CPrefix as the FFT start point, that is, the FFT section from the start point to the end point of the DATA section.
  • inter-symbol interference occurs when the received signal of the other antenna port is forward-shifted compared to the received signal of a specific reference antenna port.
  • FIG. 4 is a second diagram for explaining how inter-symbol interference occurs. As shown in FIG. 4, the case where the reference antenna port (ch1) is the rearmost is the case where the severest inter-symbol interference occurs.
  • FIG. 5 is a diagram for explaining a method of offsetting FFT intervals according to the first embodiment.
  • the transmitting apparatus 100 grasps in advance the maximum value of jitter that indicates sample synchronization capability between antenna ports.
  • the receiving device 200 acquires the information from the transmitting device 100 . At this time, let the jitter on the transmitting device 100 side be ⁇ Tx and the jitter on the receiving device 200 side be ⁇ Rx .
  • Receiving apparatus 200 determines the end point of CPrefix inserted by transmitting apparatus 100 as a countermeasure against delayed waves using a synchronization signal or the like for a specific antenna port, and a sample point of CPrefix that is at least 2 ( ⁇ Tx + ⁇ Rx ) samples ahead of that point. is the starting point of the FFT section, channel estimation, equalization and OFDM demodulation are performed. Since CPrefix is a cyclic shift signal in the DATA section, although phase rotation occurs, OFDM demodulation is possible without inter-symbol interference (ISI). The effect of phase rotation is compensated by channel estimation.
  • ISI inter-symbol interference
  • FIG. 6 is a diagram illustrating a configuration example of a transmission device according to the first embodiment;
  • the transmission device 100 includes a bit distribution circuit 110 and multiple transmission circuits 120 .
  • the number of transmission circuits 120 included in the transmission device 100 corresponds to the number of spatial multiplexing layers of the transmission signal.
  • Each transmission circuit 120 includes a transmission path estimation signal addition circuit 121, an m-QAM modulation circuit 122, a frequency multiplexing circuit 123, an IFFT circuit 124, a cyclic prefix addition circuit 125, a synchronization signal multiplexing circuit 126, and a transmission side.
  • a synchronization capability information transmission circuit 127 , a radio frame configuration circuit 128 , and a frequency conversion circuit 129 are provided.
  • the bit distribution circuit 110 distributes input bits to n MIMO channels for spatial multiplexing.
  • the m-QAM modulation circuit 122 of each MIMO channel performs symbol mapping for each subcarrier.
  • amplitude multilevel IQ quadrature modulation such as 16QAM and 64QAM is assumed, but other modulation schemes such as QPSK (4QAM) and BPSK may also be used.
  • a transmission path estimation signal output from a transmission path estimation signal addition circuit 121 is multiplexed on a specific subcarrier by a frequency multiplexing circuit 123, and then an IFFT circuit 124 for OFDM modulation is used. produces the time domain data signal.
  • the CyclicPrefix addition circuit 125 connects CPrefix, which is a copy of the latter half of the time domain data signal, to the head of the time domain data signal.
  • the length of CPrefix may generally be treated as a fixed parameter as a countermeasure against inter-symbol interference caused by delayed waves, but a separate control means may be provided.
  • the radio frame configuration circuit 128 embeds the control information sent by the transmission side synchronization capability information sending circuit 127 in the control information channel or the like.
  • the control information includes information indicating the maximum jitter value ( ⁇ Tx ) that indicates sample synchronization capability between antenna ports of transmitting apparatus 100 . Since the information indicating the maximum value of jitter ( ⁇ Tx ) is a value unique to the wireless device, transmitting apparatus 100 may report it only once in the initial connection stage before performing MIMO communication. good.
  • the synchronization signal (eg, modulated wave generated based on the M sequence) sent from the synchronization signal multiplexing circuit 126 is time-multiplexed at the beginning of the radio frame.
  • the radio frame configuration circuit 128 may multiplex the channel estimation signal at an appropriate location.
  • a signal of each MIMO channel is sent out from each antenna port through the frequency conversion circuit 129 .
  • the frequency conversion means an inexpensive configuration can be used in which an alias component that appears when the baseband signal is oversampled is extracted by an appropriate BPF and transmitted as a signal in the RF frequency band.
  • FIG. 7 is a diagram illustrating a configuration example of a receiving apparatus according to the first embodiment;
  • the receiving device 200 includes a bit mixing circuit 210 , multiple m-QAM demodulation circuits 220 , a MIMO equalization circuit 230 and multiple receiving circuits 240 .
  • the number of receiving circuits 240 included in the receiving apparatus 200 corresponds to the number of spatial multiplexing layers of the received signal.
  • Each receiving circuit 240 includes a transmission path estimation signal detection circuit 241, an FFT section determination circuit 242, a radio frame position detection circuit 243, a transmission side synchronization capability information detection circuit 244, a synchronization signal detection circuit 245, and an FFT circuit. 246, and a frequency demultiplexing circuit 247.
  • Synchronization signal detection circuit 245 detects a known synchronization signal (for example, a modulated wave generated based on the M-sequence) by sliding correlation or the like from the received signal of a specific MIMO channel (for example, ch1) in which the synchronization signal is multiplexed. do.
  • the radio frame position detection circuit 243 determines the position of the radio frame, that is, the start/end point of CPrefix and the start/end point of the DATA part of each OFDM symbol.
  • the transmission-side synchronization capability information detection circuit 244 acquires information indicating the maximum value ⁇ Tx of the jitter that indicates the sampling synchronization capability between the antenna ports of the transmission device 100 .
  • the radio frame position detection circuit 243 transmits this information to the reception circuits 240 of other MIMO channels for sharing within the reception device 200 .
  • the FFT interval determination circuit 242 determines the sample point of the CPrefix that is at least 2 ( ⁇ Tx + ⁇ Rx ) samples ahead of the end point of the identified CPrefix as the starting point of the FFT interval, and from there corresponds to the FFT size (2048 samples for 2048 FFT). is determined to be the FFT interval.
  • the FFT circuit 246 performs FFT and decomposes into subcarriers based on the determined FFT interval.
  • a frequency demultiplexing circuit 247 demultiplexes the transmission path estimation signal.
  • the transmission path estimation signal detection circuit 241 estimates information indicating the transmission path.
  • the information indicating the transmission path includes the amount of phase rotation due to the forward offset of the FFT starting point, in addition to the amplitude change and phase rotation in the spatial propagation.
  • the MIMO equalization circuit 230 performs MIMO interference cancellation/equalization on the data subcarriers of each MIMO channel separated by the frequency demultiplexing circuit 247 using transmission path information.
  • ZeroForcing in the frequency domain is well known as a method of interference cancellation/equalization, but other methods may be used.
  • the number of m-QAM demodulation circuits 220 provided in the receiving device 200 corresponds to the number of MIMO channels of the received signal after equalization by the MIMO equalization circuit 230 .
  • Each m-QAM demodulation circuit 220 converts the equalized signal of each MIMO channel into bits.
  • the bit mixing circuit 210 collects and outputs the bits distributed to each spatial multiplexing.
  • Transmitting apparatus 100 obtains the maximum value of jitter ⁇ Rx indicating sample synchronization capability between antenna ports of receiving apparatus 200 in the feedback link from receiving apparatus 200 to transmitting apparatus 100, and then obtains 2( ⁇ Tx CPrefix may be variably controlled so as to be + ⁇ Rx ) samples or more, and in that case, it is desirable to perform control in consideration of delayed wave tolerance. That is, if the longest delay of the expected delayed wave is Cp samples, transmitting apparatus 100 may set the length of CPrefix to Cp+2( ⁇ Tx + ⁇ Rx ) samples, for example.
  • communication assuming OFDM-MIMO is taken as an example, but it is also applicable to other MIMO transmission systems assuming block-type frequency domain signal processing.
  • DFT-s-OFDM DFT-spreading-OFDM
  • SC-FDE Single Carrier-Frequency Domain Equalization
  • a forward error correction code may be combined.
  • both the transmitting apparatus 100 and the receiving apparatus 200 assume n ⁇ n MIMO that implements n spatial multiplexing using n antennas, but the present invention is not particularly limited to this. It can be applied to a k ⁇ n MIMO antenna configuration with k transmission antennas and n reception antennas, or it can be applied to OAM radio multiplexing using UCA antennas, which is considered as one aspect of MIMO. .
  • the maximum values of jitter ⁇ Tx and ⁇ Rx indicate the sample synchronization capability between the antenna ports of transmitting apparatus 100 and receiving apparatus 200, they may be values that take into account the influence of other factors.
  • a raised-cosine filter with a low roll-off rate may be combined as a band-limiting filter in order to increase the frequency utilization efficiency. In such a case, the absolute value of jitter in the forward direction may be increased.
  • the maximum jitter value ⁇ Tx ( ⁇ Rx ) is notified as control information, it may be stored in advance in transmitting apparatus 100 and receiving apparatus 200 as known information.
  • Example 2 A second embodiment will be described below with reference to the drawings.
  • the second embodiment is different from the first embodiment in that a synchronization signal is multiplexed on each MIMO channel, and the receiving apparatus 200 directly detects the synchronization deviation amount of each antenna port with respect to a specific antenna port. Therefore, in the following description of the second embodiment, the differences from the first embodiment will be mainly described. Reference numerals are assigned and descriptions thereof are omitted.
  • FIG. 8 is a diagram illustrating a configuration example of a transmission device according to a second embodiment.
  • Each transmission circuit 120 of the transmission device 100 according to the present embodiment has a configuration obtained by removing the transmission side synchronization capability information transmission circuit 127 from the transmission circuit 120 according to the first embodiment.
  • the transmitting apparatus 100 multiplexes the synchronization signal sent from the synchronization signal multiplexing circuit 126 in each MIMO channel at the beginning of the radio frame. Transmitting apparatus 100 may reuse a single synchronization signal in each MIMO channel by time-division processing that changes the MIMO channel that multiplexes the synchronization signal for each radio frame.
  • a plurality of excellent synchronization signals (for example, modulated waves generated based on Zadoff-Chu sequences) may be spatially multiplexed to each MIMO channel.
  • FIG. 9 is a diagram illustrating a configuration example of a receiving apparatus according to the second embodiment.
  • the FFT interval determination circuit 242 sets the end point of the CPrefix of the MIMO channel received at the earliest timing as the starting point of the FFT interval of each MIMO channel, and sets a sample interval corresponding to the FFT size (2048 samples for 2048 FFT) as the FFT interval. decide.
  • the FFT circuit 246 performs FFT and decomposes into subcarriers based on the determined FFT interval.
  • FIG. 10 is a diagram for explaining the method of offsetting the FFT interval according to the second embodiment.
  • Transmitting apparatus 100 multiplexes synchronization signals with good cross-correlation characteristics onto each MIMO channel.
  • Receiving apparatus 200 detects the sample position of the radio frame of each MIMO channel from the synchronization signal. As a result, OFDM demodulation can be performed with the end point of the CPrefix of the earliest arriving MIMO channel as the start point of the FFT interval.
  • Example 3 A third embodiment will be described below with reference to the drawings.
  • the third embodiment differs from the first embodiment in that the transmitter 100 individually transmits the maximum value of jitter to the receiver 200 . Therefore, in the following description of the third embodiment, the differences from the first embodiment will be mainly described. Reference numerals are assigned and descriptions thereof are omitted.
  • the radio communication system it is possible to support uplink multi-user MIMO from a plurality of terminal stations (an example of the transmitting device 100) to a single base station (an example of the receiving device 200).
  • FIG. 11 is a diagram for explaining a method of offsetting FFT intervals in uplink multi-user MIMO.
  • synchronization signals are detected in the downlink, while transmission timing is controlled in consideration of transmission delay in order to achieve uplink synchronization, as described above. Synchronization of sample levels between antenna ports can be difficult.
  • the terminal design differs for each user, the inter-antenna port jitter ⁇ Tx may also have a different value ⁇ Tx_UEi for each user.
  • transmitting apparatus 100 and receiving apparatus 200 share information indicating ⁇ Tx_UEi using a control channel or the like during non-MIMO communication.
  • FIG. 12 is a diagram illustrating a configuration example of a wireless communication system according to the third embodiment.
  • each terminal station transmits a jitter value indicating the sample synchronization capability between the antenna ports of the transmitting apparatus 100 to the base station (receiving station) (an example of the receiving apparatus 200).
  • the transmitting apparatus 100 in the uplink need not include the synchronization signal multiplexing circuit 126 .
  • the jitter ⁇ Rx which indicates the sample synchronization capability between the antenna ports of the receiving apparatus 200 itself, is grasped in advance.
  • the FFT interval determination circuit 242 determines the starting point of the FFT interval of each MIMO channel by at least 2 ⁇ ( ⁇ MAX + ⁇ Rx ) samples ahead of the end point of CPrefix identified in a specific MIMO channel (for example, ch1), and performs FFT from there. A sample interval corresponding to the size (2048 samples for 2048 FFT) is determined as the FFT interval.
  • the FFT circuit 246 performs FFT and decomposes into subcarriers based on the determined FFT interval.
  • Example 4 A fourth embodiment will be described below with reference to the drawings.
  • the fourth embodiment differs from the first embodiment in that the transmitting apparatus 100 adds CyclicPostfix (CPostfix) in addition to CPrefix. Therefore, in the following description of the fourth embodiment, the differences from the first embodiment will be mainly described. Reference numerals are assigned and descriptions thereof are omitted.
  • FIG. 13 is a diagram illustrating a configuration example of a transmission device according to the fourth embodiment.
  • Each transmission circuit 120 of the transmission device 100 according to the present embodiment includes a CyclicPrefix/Postfix addition circuit 1251 instead of the CyclicPrefix addition circuit 125 of the configuration of each transmission circuit 120 according to the first embodiment.
  • the CyclicPrefix/Postfix addition circuit 1251 concatenates CPrefix to the head of the time domain data signal and concatenates a cyclic postfix (hereinafter referred to as CPostfix) to the end of the time domain data signal.
  • CyclicPrefix/Postfix addition circuit 1251 acquires information indicating the maximum value ⁇ Rx of jitter indicating sample synchronization capability between antenna ports of receiving apparatus 200 in the feedback link from receiving apparatus 200 to transmitting apparatus 100, Setting or variable control is performed so that CPostfix is 2 ( ⁇ Tx + ⁇ Rx ) samples or more.
  • FIG. 14 is a diagram for explaining the method of offsetting the FFT interval according to the fourth embodiment.
  • the FFT interval determining circuit 242 uses the end point of the CPrefix identified by the synchronization signal as the starting point of the FFT interval, and determines a sample interval corresponding to the FFT size (2048 samples for 2048 FFT) as the FFT interval.
  • the FFT circuit 2216 performs FFT and decomposes into subcarriers based on the determined FFT interval.
  • the CyclicPrefix/Postfix adding circuit 1251 adds CPostfix in addition to CPrefix.
  • the forward offset can be absorbed by CPrefix, while the backward offset can be absorbed by CPostfix.
  • the receiver 200 does not require the transmission-side synchronization capability information detection circuit 244 . That is, receiving apparatus 200 does not need to acquire information indicating maximum jitter value ⁇ Tx indicating sample synchronization capability between antenna ports of transmitting apparatus 100 . This is because inter-symbol interference can be avoided by adding a sufficiently long CPostfix to the data signal.
  • Embodiments 1 to 4 may be combined as appropriate.
  • the first embodiment and the fourth embodiment may be combined.
  • transmitting apparatus 100 adds CPostfix of at least 2 ⁇ Tx samples to avoid inter-symbol interference due to jitter ⁇ ⁇ Tx , which indicates sample synchronization capability between antenna ports of transmitting apparatus 100 .
  • receiving apparatus 200 detects the synchronization signal from the end point of the identified CPrefix in a specific MIMO channel. A sample point at least 2 ⁇ Rx samples ahead is taken as the starting point of the FFT interval and OFDM demodulated.
  • a wireless communication system comprising a transmitting device and a receiving device and performing MIMO communication, The transmitting device transmits a wireless communication signal to the receiving device, The receiving device obtains information indicating a maximum value of jitter indicating sample synchronization capability between antenna ports of the transmitting device, and obtains the maximum jitter value of the transmitting device and the maximum jitter value of the receiving device. Based on and, determining the FFT interval used for demodulation or signal equalization of the signal transmitted from the transmitting device, wireless communication system.
  • the transmitting device multiplexes a synchronization signal on a specific MIMO channel in a radio frame of the signal, adds a cyclic prefix to the data signal of each MIMO channel, At least 2 ( ⁇ Tx+ ⁇ Rx) samples from the end point of the cyclic prefix identified by the synchronization signal, based on the maximum jitter value ⁇ Tx of the transmitting device and the maximum jitter value ⁇ Rx of the receiving device.
  • the sample point of the cyclic prefix above is the starting point of the FFT interval
  • the transmitting device acquires information indicating a maximum jitter value ⁇ Rx of the receiving device from the receiving device, and sets the length of the cyclic prefix to at least 2 ( ⁇ Tx + ⁇ Rx) samples or more. 3.
  • the wireless communication system according to item 2. (Section 4) The transmitting device multiplexes a synchronization signal on each MIMO channel in a radio frame of the signal, adds a cyclic prefix to the data signal of each MIMO channel, The receiving device detects the sample position of the radio frame of each MIMO channel from the synchronization signal, and sets the end point of the cyclic prefix of the earliest arriving MIMO channel as the starting point of the FFT interval.
  • the wireless communication system comprises a plurality of transmitters, each of the plurality of transmitting devices adds a cyclic prefix to a data signal of each MIMO channel in a radio frame of the signal, and transmits information indicating the maximum value of the jitter to the receiving device;
  • the receiving device receives information indicating the maximum value of the jitter from each of the plurality of transmitting devices, derives the maximum value ⁇ MAX of the jitter of each received transmitting device, and determines the jitter of the receiving device.
  • the starting point of the FFT interval is at least 2 ⁇ ( ⁇ MAX + ⁇ Rx ) samples ahead from the end point of the cyclic prefix. 5.
  • the wireless communication system according to any one of items 1 to 4. (Section 6)
  • the transmitting device multiplexes a synchronization signal on a specific MIMO channel in a radio frame of the signal, adds a cyclic prefix and a cyclic postfix to the data signal of each MIMO channel,
  • the receiving device sets the end point of the cyclic prefix identified by the synchronization signal as the starting point of the FFT interval, 5.
  • the wireless communication system according to any one of items 1 to 4.
  • the transmitting device multiplexes a synchronization signal on a specific MIMO channel in a radio frame of the signal, adds a cyclic prefix to the data signal of each MIMO channel, and based on the maximum value ⁇ Tx of the jitter of the transmitting device , appending a cyclic postfix of length at least 2 ⁇ Tx samples, and The receiving device sets the starting point of the FFT interval to be at least 2 ⁇ Rx samples or more ahead from the end point of the cyclic prefix identified by the synchronization signal. 5.
  • the wireless communication system according to any one of items 1 to 4.
  • a communication method in a wireless communication system comprising a transmitting device and a receiving device, the transmitting device transmitting a wireless communication signal to the receiving device;
  • the receiving device acquires information indicating a maximum jitter value indicating sample synchronization capability between antenna ports of the transmitting device, and obtains the maximum jitter value of the transmitting device and the maximum jitter value of the receiving device. and determining an FFT interval to be used for demodulation or signal equalization of the signal transmitted from the transmitting device, based on Communication method.
  • transmission device 110 bit distribution circuit 120 transmission circuit 121 transmission path estimation signal adding circuit 122 m-QAM modulation circuit 123 frequency multiplexing circuit 124 IFFT circuit 125 Cyclic Prefix adding circuit 1251 Cyclic Prefix/Postfix adding circuit 126 synchronous signal multiplexing circuit 127 transmitting side synchronization capability information transmission circuit 128 radio frame configuration circuit 129 frequency conversion circuit 200 receiver 210 bit mixing circuit 220 m-QAM demodulation circuit 230 MIMO equalization circuit 240 reception circuit 241 transmission path estimation signal detection circuit 242 FFT section determination circuit 243 radio frame Position detection circuit 244 Transmission side synchronization capability information detection circuit 245 Synchronization signal detection circuit 246 FFT circuit 247 Frequency demultiplexing circuit

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Abstract

Le présent système de communication sans fil comprend un dispositif de transmission et un dispositif de réception, et réalise une communication MIMO. Le dispositif de transmission transmet un signal de communication sans fil au dispositif de réception. Le dispositif de réception acquiert des informations indiquant des valeurs maximales de gigue représentant des performances de synchronisation d'échantillon entre des ports d'antenne du dispositif de transmission, et détermine une section FFT à utiliser pour la démodulation ou l'égalisation du signal transmis depuis le dispositif de transmission, sur la base des valeurs maximales de gigue du dispositif de transmission et du dispositif de réception.
PCT/JP2021/026305 2021-07-13 2021-07-13 Système de communication sans fil et procédé de communication WO2023286158A1 (fr)

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Citations (2)

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Publication number Priority date Publication date Assignee Title
WO2018030243A1 (fr) * 2016-08-10 2018-02-15 株式会社Ｎｔｔドコモ Terminal utilisateur et procédé de communication sans fil
JP2020537455A (ja) * 2017-10-18 2020-12-17 フラウンホーファー−ゲゼルシャフト・ツール・フェルデルング・デル・アンゲヴァンテン・フォルシュング・アインゲトラーゲネル・フェライン 空間遅延プリコーディングを使用する受信機、送信機、システムおよび方法

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Publication number Priority date Publication date Assignee Title
WO2018030243A1 (fr) * 2016-08-10 2018-02-15 株式会社Ｎｔｔドコモ Terminal utilisateur et procédé de communication sans fil
JP2020537455A (ja) * 2017-10-18 2020-12-17 フラウンホーファー−ゲゼルシャフト・ツール・フェルデルング・デル・アンゲヴァンテン・フォルシュング・アインゲトラーゲネル・フェライン 空間遅延プリコーディングを使用する受信機、送信機、システムおよび方法

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