WO2023282015A1 - アンテナ装置 - Google Patents

アンテナ装置 Download PDF

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Publication number
WO2023282015A1
WO2023282015A1 PCT/JP2022/024160 JP2022024160W WO2023282015A1 WO 2023282015 A1 WO2023282015 A1 WO 2023282015A1 JP 2022024160 W JP2022024160 W JP 2022024160W WO 2023282015 A1 WO2023282015 A1 WO 2023282015A1
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WO
WIPO (PCT)
Prior art keywords
feed
feeding
line
antenna device
points
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Ceased
Application number
PCT/JP2022/024160
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English (en)
French (fr)
Japanese (ja)
Inventor
崇弥 根本
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Murata Manufacturing Co Ltd
Original Assignee
Murata Manufacturing Co Ltd
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Murata Manufacturing Co Ltd filed Critical Murata Manufacturing Co Ltd
Priority to CN202280047739.0A priority Critical patent/CN117642934A/zh
Priority to JP2023533496A priority patent/JP7597221B2/ja
Publication of WO2023282015A1 publication Critical patent/WO2023282015A1/ja
Priority to US18/404,905 priority patent/US20240154315A1/en
Anticipated expiration legal-status Critical
Ceased legal-status Critical Current

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    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q13/00—Waveguide horns or mouths; Slot antennas; Leaky-waveguide antennas; Equivalent structures causing radiation along the transmission path of a guided wave
    • H01Q13/08—Radiating ends of two-conductor microwave transmission lines, e.g. of coaxial lines, of microstrip lines
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/52—Means for reducing coupling between antennas; Means for reducing coupling between an antenna and another structure
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q21/00—Antenna arrays or systems
    • H01Q21/24—Combinations of antenna units polarised in different directions for transmitting or receiving circularly and elliptically polarised waves or waves linearly polarised in any direction
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q5/00—Arrangements for simultaneous operation of antennas on two or more different wavebands, e.g. dual-band or multi-band arrangements
    • H01Q5/40—Imbricated or interleaved structures; Combined or electromagnetically coupled arrangements, e.g. comprising two or more non-connected fed radiating elements
    • H01Q5/42—Imbricated or interleaved structures; Combined or electromagnetically coupled arrangements, e.g. comprising two or more non-connected fed radiating elements using two or more imbricated arrays
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q9/00—Electrically-short antennas having dimensions not more than twice the operating wavelength and consisting of conductive active radiating elements
    • H01Q9/04—Resonant antennas
    • H01Q9/0407—Substantially flat resonant element parallel to ground plane, e.g. patch antenna
    • H01Q9/0414—Substantially flat resonant element parallel to ground plane, e.g. patch antenna in a stacked or folded configuration
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q9/00—Electrically-short antennas having dimensions not more than twice the operating wavelength and consisting of conductive active radiating elements
    • H01Q9/04—Resonant antennas
    • H01Q9/0407—Substantially flat resonant element parallel to ground plane, e.g. patch antenna
    • H01Q9/045—Substantially flat resonant element parallel to ground plane, e.g. patch antenna with particular feeding means

Definitions

  • the present invention relates to an antenna device.
  • Patent Document 1 discloses a stacked patch antenna capable of emitting radio waves in two different frequency bands.
  • the stacked patch antenna disclosed in Patent Document 1 includes a ground plane, a low-frequency side feed element arranged thereon, and a high-frequency side feed element arranged thereon.
  • the angle between the polarization direction of the high-frequency side feed element and the polarization direction of the low-frequency side feed element is greater than 0° and less than 90°. This suppresses deterioration of antenna characteristics.
  • An object of the present invention is to provide an antenna device capable of increasing the degree of freedom in arranging a feeder line.
  • ground plane and a flat plate-like first feeding element a flat plate-shaped second feeding element; a first feed line connected to the first feed element; a second feed line connected to the second feed element,
  • the ground plane, the first feed element, and the second feed element are stacked in this order with a gap therebetween, At least part of the second feed line is arranged in the same layer as the ground plane, and is arranged in a position overlapping the first feed element when the ground plane is viewed in plan.
  • the second feeder line is arranged in a layer below the ground plane.
  • at least part of the second feed line is arranged in the same layer as the ground plane. That is, it is possible to increase the degree of freedom in arranging the feeder lines.
  • FIG. 1 is a sectional view of the antenna device according to the first embodiment.
  • FIG. 2A is a schematic perspective view of the antenna device according to the first embodiment, and FIG. 2B is an equivalent circuit diagram of the second feeder line of the antenna device according to the first embodiment.
  • 3A and 3B are perspective views showing two simulation models of the antenna device.
  • 4A and 4B are graphs showing the reflection coefficients of the simulation models of FIGS. 3A and 3B, respectively.
  • 5A and 5B are cross-sectional views of the antenna device to be simulated.
  • FIG. 6 is a graph showing simulation results of the antenna apparatus to be simulated shown in FIGS. 5A and 5B.
  • 7A and 7B are plan views focusing on the positions of the feeding points of the first feeding element and the second feeding element.
  • FIG. 1 is a sectional view of the antenna device according to the first embodiment.
  • FIG. 2A is a schematic perspective view of the antenna device according to the first embodiment
  • FIG. 2B is an equivalent circuit diagram of the
  • ) is a graph showing simulation results.
  • 9A and 9B are graphs showing simulation results of passage coefficients S(1,2) and S(1,3) to ports P2 and P3 when a high-frequency signal is input from port P1.
  • FIG. 10 is a graph showing the relationship between the passage coefficients S(1,2) and S(1,3) and the angle ⁇ .
  • FIG. 11 is a schematic perspective view of the antenna device according to the second embodiment.
  • 12A is a schematic perspective view of the antenna device according to the third embodiment
  • FIG. 12B is a plan view showing the positional relationship between the first feeding element and the second feeding element.
  • FIG. 13 is a cross-sectional view of an antenna module included in the communication device according to the fourth embodiment.
  • FIG. 14 is a block diagram of a communication device according to the fourth embodiment.
  • FIG. 15 is a sectional view of the antenna device according to the fifth embodiment.
  • FIG. 1 An antenna device according to a first embodiment will be described with reference to FIGS. 1 to 10.
  • FIG. 1 An antenna device according to a first embodiment will be described with reference to FIGS. 1 to 10.
  • FIG. 1 is a sectional view of the antenna device according to the first embodiment.
  • a dielectric multilayer substrate 50 includes a first conductor layer 21, a second conductor layer 22, a third conductor layer 23, a flat first feeding element 31, and a flat second feeding element 32.
  • the first conductor layer 21 includes a ground plane 21G and a second feeder line 21A.
  • the ground plane 21G, the first feed element 31, and the second feed element 32 are stacked in this order with a gap therebetween.
  • the side on which the first feeding element 31 is arranged when viewed from the first conductor layer 21 is defined as the upper side.
  • a second conductor layer 22 and a third conductor layer 23 are arranged in order under the first conductor layer 21 with a gap therebetween.
  • the second conductor layer 22 includes a ground plane 22G, a second feeder line 22A, and first feeder lines 22B and 22C.
  • the third conductor layer 23 includes a ground plane 23G.
  • the second feeder line 21A is arranged at a position overlapping the first feeder element 31 when the ground plane 21G is viewed from above.
  • the second feeder line 21A is arranged inside the outer peripheral line of the first feeder element 31 .
  • the second feeder line 21A is connected via a via V to the second feeder line 22A in the second layer.
  • the second feeder line 21A is connected to two feeder points 32A and 32B of the second feeder element 32 via two vias V passing through clearance holes provided in the first feeder element 31 .
  • a high frequency signal is supplied to the second feed element 32 through the second feed lines 21A and 22A.
  • the two vias V connecting the second feeder line 21A to the second feeder element 32 are arranged at positions different from the vias V connecting the second feeder line 21A to the second feeder line 22A in a plan view. It is In plan view, the first feeding element 31 and the second feeding element 32 partially overlap.
  • the first feed lines 22B and 22C are connected to feed points 31A and 31B of the first feed element 31 via vias V passing through clearance holes provided in the ground plane 21G of the first layer, respectively.
  • a high frequency signal is supplied to the first feed element 31 through the first feed lines 22B and 22C.
  • the dimensions of the first feed element 31 in plan view are larger than the dimensions of the second feed element 32 . That is, the resonance frequency of the first feed element 31 is lower than the resonance frequency of the second feed element 32 .
  • the area of the first feed element 31 is larger than the area of the second feed element 32 .
  • the dielectric multilayer substrate 50 examples include a low-temperature co-fired ceramics multilayer substrate (LTCC multilayer substrate), a multilayer substrate including a resin layer made of a liquid crystal polymer with a low dielectric constant, a multilayer substrate including a resin layer made of a fluororesin, and a ceramic multilayer substrate.
  • LTCC multilayer substrate low-temperature co-fired ceramics multilayer substrate
  • a multilayer substrate including a resin layer made of a liquid crystal polymer with a low dielectric constant a multilayer substrate including a resin layer made of a fluororesin
  • a ceramic multilayer substrate A substrate or the like is used.
  • the conductor portion for example, a metal containing Al, Cu, Au, Ag, or an alloy thereof as a main component is used.
  • FIG. 2A is a schematic perspective view of the antenna device according to the first embodiment.
  • illustration of the ground planes 21G, 22G, and 23G (FIG. 1) is omitted.
  • Both the first feeding element 31 and the second feeding element 32 are circular.
  • the center of the first feeding element 31 and the center of the second feeding element 32 match in plan view.
  • the first-layer second feeder line 21A has a circular shape in plan view, and is arranged inside the outer peripheral line of the first feeder element 31 .
  • the second feeder line 21A is indicated by a dashed line.
  • a second feeder line 22A in the second layer is connected to a second feeder line 21A in the second layer via a via V.
  • the second feed line 21A is connected to two feed points 32A and 32B of the second feed element 32 through two vias V, respectively. These two vias V pass through clearance holes provided in the first feeding element 31 .
  • a high-frequency signal is supplied from the port P1 to the feeding points 32A and 32B via the second feeding line 22A on the second layer and the second feeding line 21A on the first layer.
  • FIG. 2B is an equivalent circuit diagram of the second feeder line 21A.
  • the second feeder line 21A constitutes a 90° hybrid circuit. That is, the second feeder line 21A is configured by a combination of two transmission lines with a characteristic impedance of Z 0 and two transmission lines with a characteristic impedance of Z 0 /2 1/2 .
  • the width of the two transmission lines with characteristic impedance Z 0 /2 1/2 is greater than the width of the two transmission lines with characteristic impedance Z 0 .
  • Two transmission lines with a characteristic impedance of Z 0 and two transmission lines with a characteristic impedance of Z 0 /2 1/2 are alternately connected in a ring shape.
  • the electrical length of each transmission line is 1 ⁇ 4 of the wavelength corresponding to the resonance frequency of the second feeding element 32 .
  • a second feeder line 22A is connected to one of the four ports of the 90° hybrid circuit.
  • a high-frequency signal is input from the port P1 to the 90° hybrid circuit via the second feeder line 22A.
  • a port adjacent to the port connected to the second feed line 22A across a characteristic impedance Z 0 /2 1/2 is connected to the feed point 32A.
  • a port diagonal to the port connected to the second feed line 22A is connected to the feed point 32B.
  • the remaining one port of the 90° hybrid circuit is labeled Px.
  • the phase of the high-frequency signal output to one feeding point 32B lags the phase of the high-frequency signal output to the other feeding point 32A by 90°. No signal is output to port Px.
  • the high-frequency signal is output from the port P1 and not output to the port Px.
  • the second feed line 21A has a function of supplying high-frequency signals to the two feed points 32A and 32B with a phase difference of 90°.
  • a 90° hybrid circuit is configured by increasing or decreasing the width of the transmission line every 1/4 turn of the circular transmission line.
  • the widths of the portions facing each other across the center of the circumference are the same, and the widths of the adjacent portions are different. That is, the circumferential second feeder line 21A includes two relatively wide portions and two relatively narrow portions.
  • the second feeder line 21A may have a shape other than a circle, such as a shape along the outer circumference of a square. In this case, the thickness of the portions along the two sides facing each other should be made equal.
  • a line segment having both ends connected to the second feeding line 22A on the second layer and a point connected to the feeding point 32B passes through the center of the circumference.
  • the portion from the point connected to the second feed line 22A on the second layer to the point connected to the feeding point 32A is relatively thick, and the portion connected to the two feeding points 32A and 32B is relatively thin. .
  • the central angle formed by two radii extending from the center of the second feeding element 32 shown in FIG. 2A toward the two feeding points 32A and 32B is 90°. Since high-frequency signals having a phase difference of 90° are supplied to these two feeding points 32A and 32B, radio waves radiated from the second feeding element 32 are circularly polarized waves.
  • the central angle formed by two radii extending from the center of the first feeding element 31 shown in FIG. 2A to the two feeding points 31A and 31B is 90°.
  • a high-frequency signal is supplied to one of the feeding points 31A and 31B, radio waves radiated from the first feeding element 31 become linearly polarized waves.
  • high-frequency signals having a phase difference of 90° are supplied to each of the feeding points 31A and 31B, the radio waves radiated from the first feeding element 31 become circular polarized waves.
  • the first-layer ground plane 21G (FIG. 1), the first feeding element 31, and the second feeding element 32 constitute a stacked patch antenna.
  • the ground plane 21G (FIG. 1) is arranged over the entire area of the area overlapping the first feed element 31 in plan view, except for the clearance hole through which the feed via V passes.
  • the second feed line 21A is arranged on the same first conductor layer 21 (FIG. 1) as the ground plane 21G.
  • FIG. 3A and 3B are perspective views showing two simulation models of the antenna device.
  • the second feed line 21A is arranged in the first conductor layer 21 (FIG. 1), like the antenna device according to the first embodiment (FIGS. 1 and 2).
  • a high-frequency signal is supplied to the two feeding points 32A and 32B of the second feeding element 32 from the port P1 via the second feeding line 22A on the second layer and the second feeding line 21A on the first layer.
  • High-frequency signals are supplied to the two feeding points 31A and 31B of the first feeding element 31 from the ports P2 and P3 via the first feeding lines 22B and 22C, respectively.
  • the first-layer second feeder line 21A (FIG. 3A) is not arranged.
  • High-frequency signals are supplied from two ports P1 and P6 to two feeding points 32A and 32B of the second feeding element 32 via second feeding lines 22A and 22D, respectively.
  • Reflection coefficients S(2, 2) and S(3, 3) when high-frequency signals were input from ports P2 and P3 were obtained.
  • FIGS. 3A and 3B are graphs showing the reflection coefficients of the simulation models of FIGS. 3A and 3B, respectively.
  • the horizontal axis represents the frequency in the unit of "GHz”
  • the vertical axis represents the value of the S-parameter in the unit of "dB”.
  • the reflection coefficients S(2,2) and S(3,3) show downward peaks at the resonance frequency of 40 GHz of the first feeding element 31 .
  • This simulation confirms that the operation of the first feed element 31 is not greatly affected even if the second feed line 21A is placed on the same first conductor layer 21 as the ground plane 21G (FIG. 1). was done.
  • a ground plane is placed between the feed element and the feed line to increase the isolation between the two.
  • no ground plane is arranged between the second feeding element 32 (FIG. 1) and the second feeding line 21A (FIG. 1).
  • 5A and 5B are cross-sectional views of the simulation model of the antenna device.
  • a wiring 21X is arranged on the first conductor layer 21 instead of the second feeding line 21A of the antenna device according to the first embodiment. Both ends of the wiring 21X are connected to the wirings 22X and 22Y arranged on the second conductor layer 22, respectively.
  • the first feeder element 31 is arranged between the ground plane 21G and the wiring 21X arranged in the first conductor layer 21 and the second feeder element 32 .
  • a high-frequency signal is supplied to the second feeder element 32 from the second feeder line 22A arranged on the second conductor layer 22 via the via V penetrating the ground plane 21G and the first feeder element 31 .
  • the resonance frequency of the first feed element 31 is 40 GHz
  • the resonance frequency of the second feed element 32 is 60 GHz.
  • the first feeding element 31 is removed from the simulation model shown in FIG. 5A.
  • a second feeder line 22A is connected to port P1, and wires 22X and 22Y are connected to ports P4 and P5, respectively.
  • S-parameters S(1, 4) and S(1, 5) from port P1 to ports P4 and P5 when a high-frequency signal is input from port P1 were obtained by simulation.
  • FIG. 6 is a graph showing simulation results.
  • the horizontal axis represents the frequency in the unit of "GHz", and the vertical axis represents the calculated value of the S parameter in the unit of "dB".
  • a thick solid line and a thin solid line in the graph of FIG. 6 indicate the passage coefficients S(1,4) and S(1,5) of the simulation model shown in FIG. 5A, respectively.
  • a thick dashed line and a thin dashed line indicate the passage coefficients S(1,4) and S(1,5) of the simulation model shown in FIG. 5B, respectively.
  • FIG. 7A a preferred positional relationship between the feeding points 31A and 31B of the first feeding element 31 and the feeding points 32A and 32B of the second feeding element 32 will be described with reference to FIGS. 7A to 10.
  • FIG. 7A a preferred positional relationship between the feeding points 31A and 31B of the first feeding element 31 and the feeding points 32A and 32B of the second feeding element 32 will be described with reference to FIGS. 7A to 10.
  • FIG. 7A and 7B are plan views focusing on the positions of the feeding points of the first feeding element 31 and the second feeding element 32.
  • FIG. O is the geometric center of the first feed element 31 and the second feed element 32 in a plan view.
  • the central angles ⁇ formed by the radii of the books are both 90°.
  • FIG. 7A in plan view, the geometric center O, one feeding point 31A of the first feeding element 31, and one feeding point 32A of the second feeding element 32 are positioned on one straight line, and the geometric center O, The other feeding point 31B of the first feeding element 31 and the other feeding point 32B of the second feeding element 32 are also positioned on one straight line.
  • FIG. 7B shows a state in which the two feeding points 31A and 31B of the first feeding element 31 are rotated about the geometric center O by an angle ⁇ .
  • a high frequency signal is supplied from the port P1 to the two feeding points 32A and 32B of the second feeding element 32 via the second feeding lines 22A and 21A.
  • High-frequency signals are supplied from the ports P2 and P3 to the feeding points 31A and 31B of the first feeding element 31 via the first feeding lines 22B and 22C, respectively.
  • ) is a graph showing simulation results.
  • the horizontal axis represents the frequency in the unit of "GHz”
  • the vertical axis represents the calculated value of the S parameter in the unit of "dB”.
  • a solid line, a thick dashed line, and a thin dashed line in the graph indicate reflection coefficients S(1,1), S(2,2), and S(3,3), respectively. It can be seen that the first feed element 31 resonates near a frequency of 40 GHz, and the second feed element 32 resonates near a frequency of 60 GHz.
  • the trends of the reflection coefficients S(1,1), S(2,2), and S(3,3) did not change significantly even when the angle ⁇ was changed.
  • FIGS. 9A and 9B are graphs showing simulation results of passage coefficients S(1,2) and S(1,3) to ports P2 and P3 when a high-frequency signal is input from port P1.
  • the horizontal axis represents the frequency in the unit of "GHz”, and the vertical axis represents the calculated value of the S parameter in the unit of "dB".
  • a solid line and a broken line in the graph indicate passage coefficients S(1,2) and S(1,3), respectively.
  • the passage coefficients S(1,2) and S(1,3) were obtained by changing the angle ⁇ from 0° to 360°.
  • FIG. 10 is a graph showing the relationship between the passage coefficients S(1,2) and S(1,3) and the angle ⁇ .
  • the horizontal axis represents the angle ⁇ in units of "degrees", and the vertical axis represents the calculated values of the S parameters in units of "dB".
  • a thick dashed line and a thin dashed line in the graph represent the passage coefficients S(1,2) and S(1,3), respectively.
  • the thick solid line in the graph is a line connecting the pass coefficients of the pass coefficients S(1, 2) and S(1, 3) having the larger value (that is, the one with the worse characteristics).
  • a straight line passing through the geometric center O of the first feeding element 31 and one of the feeding points 31A and 31B and a straight line passing through the geometric center O of the second feeding element 32 and one of the feeding points 32A and 32B are drawn. It is preferable to dispose the feeding points so that the angle (the angle less than 90°) with the straight line is 35° or more and 55° or less.
  • the second feeder line 21A is arranged on the same first conductor layer 21 as the ground plane 21G (FIG. 1) functioning as a ground for the first feeder element 31 .
  • the degree of freedom in placement of the feeder line is increased. Since it is no longer necessary to arrange the second feed line 21A on another conductor layer, it is possible to obtain an excellent effect of increasing the degree of freedom in arranging wiring on another conductor layer. As a result, an increase in the number of conductor layers can be suppressed, and the thickness of the antenna device can be reduced. Further, as described with reference to FIGS. 3A to 6, even if the second feed line 21A is arranged on the same first conductor layer 21 as the ground plane 21G, the antenna characteristics are not affected. small.
  • the second feed line 21A for supplying high-frequency signals with a phase difference of 90° to the two feed points 32A and 32B of the second feed element 32 is composed of a 90° hybrid circuit.
  • a transmission line having another configuration may be used as the second feeder line 21A.
  • one transmission line may be branched into two transmission lines, and the two transmission lines after branching may be connected to the feeding points 32A and 32B, respectively.
  • the difference in the electrical length of the two transmission lines from the branch point to the two second feeding points 32A and 32B corresponds to the resonance frequency of the second feeding element 32. It should be 1/4 of the wavelength.
  • a parasitic element may be loaded on the second feeding element 32 .
  • a wider band can be achieved by causing the second feeding element 32 and the parasitic element to resonate multiple times.
  • FIG. 11 is a schematic perspective view of the antenna device according to the second embodiment.
  • the first feeding element 31 is provided with two feeding points 31A and 31B
  • the second feeding element 32 is provided with two feeding points 32A and 32B.
  • the first feeding element 31 is provided with one feeding point 31A
  • the second feeding element 32 is provided with one feeding point 32A.
  • the second feeder line 21A (FIG. 2) arranged in the first conductor layer 21 is circular, but in the second embodiment, the second feeder line 21A is, for example, linear. is.
  • One end of the second feed line 21A is connected via a via V to the feed point 32A of the second feed element 32 .
  • the other end of the second feeder line 21A is connected via a via V to the second feeder line 22A in the second layer.
  • the wiring 22E arranged on the second conductor layer 22 intersects the second feeder line 21A arranged on the first conductor layer 21 in plan view.
  • the feeding point 32A and the second feeding line 22A on the second layer are arranged on opposite sides of each other when viewed from the wiring 22E.
  • the angle between a straight line passing through the geometric center O of the first feeding element 31 and the feeding point 31A and a straight line passing through the geometric center O of the second feeding element 32 and the feeding point 32A is denoted by ⁇ . do.
  • the angle ⁇ is changed, the isolation between the first feed element 31 and the second feed element 32 is changed.
  • the second feed line 21A is arranged on the same first conductor layer 21 (FIG. 1) as the ground plane 21G (FIG. 1). Therefore, an excellent effect is obtained in that the degree of freedom in arranging the feeder lines is increased.
  • the wiring 22E crossing the second feeder line 21A can be placed in the same second conductor layer 22 (FIG. 1) as the second feeder line 22A.
  • linearly polarized radio waves are radiated from the first feeding element 31 and the second feeding element 32 .
  • the isolation between the first feed element 31 and the second feed element 32 is highest when the planes of polarization of the two linearly polarized waves are orthogonal.
  • one feeding point is provided for each of the first feeding element 31 and the second feeding element 32, but two feeding points may be provided for one of the feeding elements.
  • the second feeding element 32 is provided with two feeding points, the second feed element 32 is arranged so that the high-frequency signals supplied to the two feeding points have a phase difference of 90°, as in the first embodiment (FIG. 2).
  • 2 feeding lines 21A may be arranged.
  • FIG. 12A is a schematic perspective view of the antenna device according to the third embodiment
  • FIG. 12B is a plan view showing the positional relationship between the first feeding element 31 and the second feeding element 32.
  • the two feeding points 31A and 31B of the first feeding element 31 are arranged on a line connecting the midpoint of two mutually adjacent sides of the first feeding element 31 and the geometric center O of the first feeding element 31.
  • the two feeding points 32A and 32B of the second feeding element 32 are line segments connecting the midpoints of two mutually adjacent sides of the second feeding element 32 and the geometric center O of the second feeding element 32. placed above.
  • a straight line passing through the geometric center O of the first feeding element 31 and one feeding point 31A of the first feeding element 31, the geometric center O of the second feeding element 32 and the second feeding element 32 The angle (angle less than 90°) formed with a straight line passing through one feeding point 32A is denoted as ⁇ .
  • the second feed element 32 is arranged inside the outer peripheral line of the first feed element 31 in plan view.
  • the vicinity of the vertex of the second feeding element 32 may protrude outside the first feeding element 31 in plan view.
  • the second feed line 21A is arranged on the same first conductor layer 21 as the ground plane 21G.
  • the second feeder line 21A is shown linearly, but the second feeder line 21A may be circular as in the first embodiment (FIG. 2).
  • the excellent effects of the third embodiment will be described.
  • the third embodiment as in the first embodiment, it is possible to obtain the excellent effect of increasing the degree of freedom in arranging the feeder lines. Also, in order to increase the isolation between the first feeding element 31 and the second feeding element 32, it is preferable to set the angle ⁇ to 35° or more and 55° or less.
  • the shape of the first feeder element 31 and the second feeder element 32 in plan view is square, but they may be of other shapes.
  • a rectangular shape, a square shape with four corners notched into squares, or the like may be used.
  • one of the first feeding element 31 and the second feeding element 32 may be formed in a discharge shape, and the other may be formed in a circular shape.
  • the first feed element 31 and the second feed element 32 can have various shapes. It should be lower.
  • FIG. 13 and 14 a communication apparatus according to a fourth embodiment will be described with reference to FIGS. 13 and 14.
  • the communication device according to the fourth embodiment includes the antenna device according to any one of the first to third embodiments, or the antenna device according to modifications thereof.
  • FIG. 13 is a cross-sectional view of the antenna module 100 included in the communication device according to the fourth embodiment.
  • a plurality of antenna elements 30 are provided on one dielectric multilayer substrate 50 .
  • a plurality of antenna elements 30 are arranged in a one-dimensional or two-dimensional array to form an array antenna.
  • Each of the plurality of antenna elements 30 includes a first feeding element 31 and a second feeding element 32.
  • the dielectric multilayer substrate 50 includes therein a first conductor layer 21 and a multilayer wiring structure therebelow.
  • the first conductor layer 21 includes a ground plane 21G and a second feeder line 21A arranged for each antenna element 30 .
  • the configuration of the ground plane 21G, the second feeder line 21A, the first feeder element 31 and the second feeder element 32 is the same as that of the antenna device according to any one of the first through third embodiments. .
  • a high frequency integrated circuit element (RFIC) 110 is mounted on the lower surface of the dielectric multilayer substrate 50 .
  • the high-frequency integrated circuit element 110 is connected to the first feeding element 31 and the second feeding element 32 of the plurality of antenna elements 30 via wiring provided inside the dielectric multilayer substrate 50 .
  • FIG. 14 is a block diagram of a communication device according to the fourth embodiment.
  • a communication device according to the fourth embodiment includes an antenna module 100 and a baseband integrated circuit device (BBIC) 135 .
  • Antenna module 100 includes a high frequency integrated circuit element 110 and an antenna device 130 .
  • Antenna device 130 includes a plurality of antenna elements 30 .
  • the antenna module 100 up-converts the baseband signal or intermediate frequency signal input from the baseband integrated circuit element 135 into a high frequency signal and transmits the high frequency signal from the antenna device 130 . Furthermore, the high-frequency signal received by the antenna device 130 is down-converted and output to the baseband integrated circuit element 135 .
  • the high frequency integrated circuit device 110 has a plurality of transmission/reception systems 120 .
  • Each of the plurality of transmission/reception systems 120 includes a phase shifter 115, an attenuator 114, a switch 113, a power amplifier 112T, a low noise amplifier 112R, and a switch 111.
  • a demultiplexer 116, a switch 117, a mixer 118, and an amplifier circuit 119 are provided for each of the four transmission/reception systems.
  • the plurality of transmission/reception systems 120 include a transmission/reception system 120 for processing transmission/reception signals by the first feeding element 31 on the low frequency side of the antenna element 30 and a transmission/reception system 120 for processing transmission/reception signals by the second feeding element 32 on the high frequency side of the antenna element 30. is included.
  • a signal to be transmitted is input from the baseband integrated circuit element 135 to the amplifier circuit 119 .
  • the amplifier circuit 119 amplifies the input signal, and the mixer 118 up-converts the amplified signal.
  • the up-converted high-frequency signal is input to demultiplexer 116 via switch 117 .
  • a plurality of high-frequency signals demultiplexed by the demultiplexer 116 are input to the phase shifters 115 of the transmission/reception system 120, respectively.
  • a high-frequency signal that has undergone a predetermined phase delay in phase shifter 115 is supplied to antenna element 30 of antenna device 130 via attenuator 114, switch 113, power amplifier 112T, and switch 111.
  • a high-frequency signal received by the antenna element 30 is input to the demultiplexer 116 via the switch 111, the low-noise amplifier 112R, the switch 113, the attenuator 114, and the phase shifter 115.
  • the received signal combined by combiner 116 is input to mixer 118 via switch 117 .
  • Mixer 118 downconverts the received signal.
  • the signal down-converted by mixer 118 is input to baseband integrated circuit element 135 via amplifier circuit 119 .
  • a communication apparatus includes an antenna apparatus according to any one of the first to third embodiments. For this reason, similar to the first to third embodiments, the excellent effect of increasing the degree of freedom in arranging the feeder lines in the antenna device is obtained. Therefore, it is possible to suppress an increase in the number of conductor layers in the dielectric multilayer substrate 50 (FIG. 13). Since an increase in the number of conductor layers is suppressed, the thickness of the antenna module can be reduced.
  • FIG. 15 is a cross-sectional view of the antenna device according to the fifth embodiment.
  • the antenna device ( FIG. 1 ) according to the first embodiment includes two feed elements, a first feed element 31 and a second feed element 32 .
  • a plate-shaped third feeding element 33 is arranged apart from the second feeding element 32. contains.
  • the third feed element 33 partially overlaps the second feed element 32 . That is, the first feeding element 31, the second feeding element 32, and the third feeding element 33 are stacked in this order.
  • a third feeder line 24A is arranged below the third conductor layer 23 .
  • the third feeder line 24A is connected to the third feeder element 33 via a via V passing through clearance holes provided in the ground planes 23G, 22G, 21G, the first feeder element 31, and the second feeder element 32. .
  • the resonance frequency of the third feed element 33 is higher than the resonance frequency of the second feed element 32 .
  • the area of the third feed element 33 is smaller than the area of the second feed element 32 .
  • the antenna device according to the fifth embodiment can transmit and receive radio waves in three frequency bands. Further, as in the first embodiment, since the second feeder line 21A is arranged on the same first conductor layer 21 as the ground plane 21G, an excellent effect is obtained in that the degree of freedom in arranging the feeder line is increased. be done.
  • the resonance frequency of the third feed element 33 is higher than the resonance frequency of the second feed element 32, but conversely, the resonance frequency of the second feed element 32 is higher than the resonance frequency of the third feed element 33.
  • the resonance frequency of the first feed element 31 is lower than the resonance frequencies of both the second feed element 32 and the third feed element 33 .
  • the second feeder line 21A connected to the second feeder element 32 is arranged on the same first conductor layer 21 as the ground plane 21G.
  • a feeder line connected to the third feeder element 33 may be arranged in the first conductor layer 21 instead of or in addition to the second feeder line 21A.
  • the feeder line arranged in the first conductor layer 21 is preferably arranged inside the outer peripheral line of the first feeder element 31 in plan view.
  • the three feed elements of the first feed element 31, the second feed element 32, and the third feed element 33 are stacked, but four or more flat feed elements may be stacked.
  • the third feed line 24A connected to the third feed element 33 is arranged below the third conductor layer 23, but is arranged on the second conductor layer 22. You may
  • RFIC High frequency integrated circuit element
  • RFIC High frequency integrated circuit element

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  • Physics & Mathematics (AREA)
  • Electromagnetism (AREA)
  • Waveguide Aerials (AREA)
  • Variable-Direction Aerials And Aerial Arrays (AREA)
PCT/JP2022/024160 2021-07-06 2022-06-16 アンテナ装置 Ceased WO2023282015A1 (ja)

Priority Applications (3)

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CN202280047739.0A CN117642934A (zh) 2021-07-06 2022-06-16 天线装置
JP2023533496A JP7597221B2 (ja) 2021-07-06 2022-06-16 アンテナ装置
US18/404,905 US20240154315A1 (en) 2021-07-06 2024-01-05 Antenna device

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JP2021112219 2021-07-06
JP2021-112219 2021-07-06

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Publication number Priority date Publication date Assignee Title
WO2022004111A1 (ja) * 2020-07-01 2022-01-06 株式会社村田製作所 アンテナモジュールおよびそれを搭載した通信装置
KR20230011050A (ko) * 2021-07-13 2023-01-20 삼성전기주식회사 안테나 장치
TWI866089B (zh) * 2023-02-24 2024-12-11 立積電子股份有限公司 天線裝置

Citations (2)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JPH02202204A (ja) * 1989-01-31 1990-08-10 Sony Corp アンテナの給電装置
US20110032154A1 (en) * 2008-01-22 2011-02-10 Hang Leong James Chung Broadband circularly polarized patch antenna

Patent Citations (2)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JPH02202204A (ja) * 1989-01-31 1990-08-10 Sony Corp アンテナの給電装置
US20110032154A1 (en) * 2008-01-22 2011-02-10 Hang Leong James Chung Broadband circularly polarized patch antenna

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CN117642934A (zh) 2024-03-01

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