WO2023204723A1 - Dispositif émetteur-récepteur déterminé par logiciel - Google Patents

Dispositif émetteur-récepteur déterminé par logiciel Download PDF

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Publication number
WO2023204723A1
WO2023204723A1 PCT/RU2022/000131 RU2022000131W WO2023204723A1 WO 2023204723 A1 WO2023204723 A1 WO 2023204723A1 RU 2022000131 W RU2022000131 W RU 2022000131W WO 2023204723 A1 WO2023204723 A1 WO 2023204723A1
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WIPO (PCT)
Prior art keywords
signals
phase
processor
antenna
unit
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PCT/RU2022/000131
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English (en)
Russian (ru)
Inventor
Олеся Викторовна БОЛХОВСКАЯ
Вадим Сергеевич СЕРГЕЕВ
Антон Вадимович ЕЛОХИН
Original Assignee
Общество С Ограниченной Ответственностью "Радио Лаб Нн"
Олеся Викторовна БОЛХОВСКАЯ
Вадим Сергеевич СЕРГЕЕВ
Антон Вадимович ЕЛОХИН
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Application filed by Общество С Ограниченной Ответственностью "Радио Лаб Нн", Олеся Викторовна БОЛХОВСКАЯ, Вадим Сергеевич СЕРГЕЕВ, Антон Вадимович ЕЛОХИН filed Critical Общество С Ограниченной Ответственностью "Радио Лаб Нн"
Priority to PCT/RU2022/000131 priority Critical patent/WO2023204723A1/fr
Publication of WO2023204723A1 publication Critical patent/WO2023204723A1/fr

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Classifications

    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
    • H04B1/02—Transmitters
    • H04B1/04—Circuits
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
    • H04B1/38—Transceivers, i.e. devices in which transmitter and receiver form a structural unit and in which at least one part is used for functions of transmitting and receiving
    • H04B1/40—Circuits
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04W—WIRELESS COMMUNICATION NETWORKS
    • H04W8/00—Network data management
    • H04W8/22—Processing or transfer of terminal data, e.g. status or physical capabilities

Definitions

  • the invention relates to software-defined radio systems that can be used in the field of communications technology, radar, and mobile radio communication systems.
  • the idea behind existing SDR devices is that the hardware can be completely configured or defined by software.
  • the received radio signal is converted into digital format in a fairly universal receiving unit, and its further processing is carried out in the digital domain.
  • the transmitted signal is digitally generated according to user-specified configurations and converted to an analog signal in the transmitting unit.
  • the main advantage of this approach is that such transmitting and receiving equipment can be completely reconfigured by simply replacing the software and configured by the user to receive and transmit almost any signal-code structures in a given frequency range.
  • the ability to configure the software allows you to use equipment for receiving and transmitting radio signals built in accordance with new communication standards, explore various noise-resistant coding schemes and types of signal modulation without changing the hardware of the equipment.
  • the use of one hardware platform for the development and testing of various transceiver devices can significantly reduce development costs and improve the quality of products.
  • Multiple waveform software radio US6, 181,734 is known, which describes a radio station with software-defined functionality that can use different signal forms.
  • the radio has a memory that stores software for processing different types of signals and additionally includes one or more processors that retrieve waveform-specific software to process information when transmitting or receiving. All information processing between receiving or reproducing speech and transmitting or receiving radio frequency signals, respectively, is done in software.
  • the US6, 181,734 device meets the needs of so-called “dual mode" cell phones, where different modes refer to different waveforms.
  • the operator can switch from one waveform mode to another to communicate over various radio networks, such as Motorola, Inc.'s Iridium satellite communications network, TDMA and/or CDMA cellular networks, or other land mobile two-way radios, systems, or communications for all or several of them simultaneously.
  • radio networks such as Motorola, Inc.'s Iridium satellite communications network, TDMA and/or CDMA cellular networks, or other land mobile two-way radios, systems, or communications for all or several of them simultaneously.
  • Software defined cognitive radio US8,036,240 is known, which describes a computing device with a software-defined radio device, which has an architecture with separate components to provide control functions and data processing functions. Control components configure the processing components so that the software-defined radio provides the required performance characteristics. Components in the data layer may receive information characterizing operating conditions that may be provided to one or more control components. In response, control components can modify data-level components to regulate operating conditions.
  • the Software defined cognitive radio US8, 036,240 has an architecture with separate logical levels: a control level and a data level.
  • the data layer performs data processing operations associated with wireless communications.
  • the control plane allows the data plane to be reconfigured to change the wireless technology under which the radio operates or to adjust operating parameters without changing the wireless technology.
  • the software defined radio device can be configured or changed to support efficient communication using one or more wireless communication technologies.
  • a feedback channel can be easily formed between data plane components and control plane components.
  • Data plane components can generate status information about the communication channel being used, such as error rate and noise level.
  • Such information can be provided to a cognitive module in the control layer, which can identify adjustments required for components in the data layer that allow adaptation to current operating conditions.
  • Software defined radio and radio system US7,043,023 was selected as the closest to the invention (prototype), in which the software defined radio device contains: an antenna for transmitting and receiving radio signals, a radio frequency signal processing unit, a baseband signal processing unit, a control unit, storage storing software for defining a function of a software-defined radio and a specification criterion defining reference radio transmission characteristics, a measurement circuit for measuring the transmission characteristics of a radio signal transmitted from said software-defined radio device, and a switch coupled to said antenna, said radio frequency unit, and said measurement circuitry.
  • the control unit is configured to change the settings of the baseband signal processing unit and the RF signal processing unit so as to satisfy the target transmission and reception performance specification criteria.
  • said switch disconnects said RF unit from the antenna and connects it to the measurement circuit to redirect the signal to the measurement circuit.
  • the above examples of known SDR devices do not use multi-element antenna arrays and thus lack the ability to use a wide range of spatial signal processing technologies, such as forming steerable narrow beams using phased array antenna technology to increase communication range and reduce interference in unwanted areas. directions, the formation of several independent spatial subchannels through the use of transmission technology with multiple inputs and outputs (Multiple Input Multiple Output - MIMO) to increase the data transfer rate due to the simultaneous transmission of information in the same same frequency resources over different spatial subchannels, as well as other multi-antenna signal processing techniques.
  • Multiple Input Multiple Output - MIMO Multiple Input Multiple Output - MIMO
  • the problem to be solved by the invention is the creation of a transceiver device (RTD) with a controlled modular multi-element antenna system with a large number of antenna elements, which makes it possible to significantly expand the scope of application of the TRU: increase the communication range and data transmission speed, reduce mutual interference between stations along the compared to existing SDR devices using unsteered antennas.
  • RTD transceiver device
  • the technical result is the creation by the claimed PPU of a program-controlled radiation pattern with the ability to concentrate and/or attenuate emitted energy, as well as amplify and/or suppress received signals for one or more specified directions, amplify one or more useful signals and/or reduce interference in one or several specified directions, increasing the range and reliability of communication and data transmission speed when using software-defined shape, carrier frequency, bandwidth, signal-code structures and other signal parameters.
  • a software-defined transceiver device containing a processor with a digital signal processing (DSP) unit included in it, configured for digital processing of transmitted and/or received signals, a control and configuration unit, as well as storage connected to the processor, configured to store instructions for the processor, a multi-channel transceiver unit connected to the processor and configured for analog and/or radio frequency processing of transmitted and/or received signals, additionally contains arrays of antenna elements, beamforming units connected to the antenna arrays elements, and to a multi-channel transceiver unit, and to a processor, wherein the multi-channel transceiver unit contains ports, each of which is connected to one beamforming unit, and each beamforming unit is also connected to one array of antenna elements, and the processor configured with the ability to change the radiation pattern of the antenna element arrays.
  • DSP digital signal processing
  • the beamforming unit contains a power division device connected to the processor and configured to divide the power of transmitted signals between the antenna elements of the array connected to the beamformer and/or to sum the power of the signals received from the elements of the antenna array connected to the beamformer radiation patterns, as well as circuits for radio frequency processing of received and/or transmitted signals, each circuit connected to a power division device and to one antenna element of the array, which is connected to this beamforming unit.
  • the radio frequency processing circuit for received and/or transmitted signals is configured to adjust the phase of received and/or transmitted signals using configuration information coming from the processor.
  • a DSP digital signal processing unit including a digital processing unit for transmitted signals, in which a transmitter signal combinator is connected in series with the transmitter DSP pipeline, and a digital processing unit for received signals, in which a receiver signal combinator is connected in series with the receiver DSP pipeline, also contains a channel characteristics estimation unit communication connected to a digital processing unit for received signals, and a block for calculating radiation patterns connected to a unit for estimating communication channel characteristics, the operating parameters of which are determined by configuration and status information coming from the control and configuration unit algorithms executed by the processor.
  • the multi-channel transceiver unit is configured to process signals containing in-phase and quadrature components
  • the processor is configured to exchange with the multi-channel transceiver unit at least the first and second signals having in-phase and quadrature components for processing, respectively , the first and second channels of a multi-channel transceiver unit, wherein the in-phase and quadrature components of the second signal are a linear combination of the in-phase and quadrature components of the first signal.
  • the transceiver unit is also configured to process signals containing in-phase and quadrature components
  • the processor is configured to process at least one digital signal having in-phase and quadrature components
  • the processor is also configured to exchange with a multi-channel receiver - a transmitting unit, at least the first and second signals having in-phase and quadrature components, for processing, respectively, by the first and second channel of the multi-channel transceiver unit, wherein the in-phase and quadrature components of the first signal represent a first linear combination of the in-phase and quadrature components at least one digital signal, and the in-phase and quadrature components of the second signal are a second linear combination of the in-phase and quadrature components of the at least one digital signal.
  • the processor is configured to process at least one digital signal having in-phase and quadrature components, the processor also configured to exchange with the multi-channel transceiver unit at least first and second signals having in-phase and quadrature components, for processing, respectively, the first and second channel of the multi-channel transceiver unit, wherein the in-phase and quadrature components are at least , one digital signal are a linear combination of in-phase and quadrature components of at least the first and second signals.
  • FIG. 1 shows the specified transceiver device 11NU 1, which contains a processor 2, with a digital signal processing unit (DSP) 20 included in it, configured for digital processing of transmitted and/or received signals, a control and configuration unit 21, performing digital signal processing, control and configuration of PPU 1, storage 3, which includes a memory 30, connected to processor 2 and storing software for processor 2, as well as configuration parameters of PPU 1 blocks and modules, multi-channel transceiver unit 4, connected to processor 2 and carrying out analog and radio frequency processing of transmitted and received radio signals, antenna module 5, including N AAR antenna arrays 61 - 62 and N AAR radiation pattern formation blocks 51 - 52, where NAAR is an integer greater than or equal to two, each of the antenna arrays connected to the multi-channel transmitting and receiving unit 4 through one beamforming unit.
  • DSP digital signal processing unit
  • the antenna module 5 is connected to the multi-channel transmitting and receiving unit 4 and to the processor 2 and carries out, together with the processor 2, the digital-analog formation of the radiation pattern (AP) 33 of the antenna system from N AAR antenna arrays 61 - 62.
  • PPU 1 is used to exchange digital data 10 with other transceiver devices by transmitting and/or receiving NAAR radio signals 18 - 19 using antenna arrays 61 - 62.
  • digital signal processing (DSP) algorithms 20 convert between digital data 10 and NAAR digital signals, which the processor 2 exchanges with the multi-channel transceiver unit 4 through the digital port 12;
  • multi-channel transceiver unit 4 converts between N A AR digital signals of digital port 12 and N A AR radio frequency (RF) signals, which multi-channel transceiver unit 4 exchanges with antenna module 5 through N A AR RF ports 14 - 15;
  • antenna module 5 converts between N A AR RF signals of digital ports 14 - 15 and N A AR radio signals 18 - 19.
  • N A AR radio signals 18 - 19 are transmitted and/or received by NAAR antenna subarrays 61 - 62, respectively having N A AR radiation patterns (DP) 31 - 32, formed respectively by NAAR radiation pattern formation units (PDN) 51 - 52 of the antenna module 5.
  • Processor 2 controls the multi-channel transceiver unit 4 through the control port 25 and the antenna module 5 through the control port 26.
  • processor 2 is connected to user interface 8 to receive control information 23, based on which control and configuration algorithms 21 executed by processor 2 control the control panel 1, including loading user blocks and/or digital processing algorithms into processor 2 signals 20, the configuration of analog and radio frequency signal processing in the multi-channel transmitting and receiving unit 4, as well as the formation of DN 33 of PPU 1 based on N A AR DN 31 - 32 generated by the antenna module 5.
  • the control and configuration algorithms 21 accept the control information 23 from the user interface 8 and store it in storage 3 for future use.
  • the PPU 1 can be configured once for the purpose of autonomous operation as an independent station of the communication system without further use of the user interface 8.
  • the control and configuration algorithms 21 control the PPU 1 based on the control previously stored in the storage 3 information 22.
  • the antenna module 5 contains two antenna arrays 61 and 62 and two FDN units 51 and 52; the range of possible embodiments of the invention is not limited to these values.
  • the value of N AAR may be greater than two, that is, the antenna module 5 may contain more than two antenna arrays and, accordingly, more than two FDN units connected to these arrays, one FDN unit per antenna array.
  • DSP digital signal processing
  • DSP 20 algorithms contain a digital processing unit for transmitted signals 200.
  • Block 200 includes a transmitter DSP pipeline block 201 that converts transmitted digital data 101 into digital signals 204 having in-phase and quadrature components, and a transmitter signal combiner 203 that converts digital signals 204 into N AAR digital signals 121 - 122, also having in-phase and quadrature components obtained by implementing linear combinations of the in-phase and quadrature components of the signals 204.
  • DSP algorithms 20 also include a digital processing unit for received signals 210.
  • Unit 210 includes a receiver signal combinator 213 that converts N AAR of received digital signals 123 - 124, having in-phase and quadrature components, into digital signals 214, also having in-phase and quadrature components. components, by implementing a linear combination of in-phase and quadrature components N AAR of the received digital signals 123 - 124, and a receiver DSP pipeline unit 211 that converts the digital signals 214 into received digital data 11 1.
  • the operating parameters of the digital processing unit of transmitted signals 200, including the transmitter DSP pipeline unit 201 and the transmitter signal combinator 203, the digital processing unit of received signals 210, including the receiver DSP pipeline unit 211 and the receiver signal combinator 213, are determined by the configuration and status information 24 coming from the algorithms control and configuration 21 performed by the processor 2.
  • the configuration and status information 24 includes the coefficients of linear combinations of the in-phase and quadrature components of digital signals 204, performed by the transmitter signal combinator 203, as well as the coefficients of the linear combination of received signals 123 - 124, performed by the combinator receiver signals 213.
  • fig. 3 shows an example structure of digital signal processing (DSP) algorithms 20 executed by processor 2 in accordance with one embodiment of the present invention.
  • DSP digital signal processing
  • DSP algorithms 20 contain a digital processing unit for transmitted signals 200.
  • Unit 200 includes N TX _DSP blocks of transmitter DSP pipelines 201 - 202, where N TX _DSP ⁇ an integer greater than or equal to two, converting N TX _DSP of transmitted digital data 101 - 102 into N TX _DSP of digital signals 204 - 205, having in-phase and quadrature components, and a transmitter signal combiner 203, converting N TX DS P of digital signals 204 - 205 into NAAR of digital signals 121 - 122, also having in-phase and quadrature components obtained by implementing linear combinations of in-phase and quadrature components N TX DS p signals 204 - 205.
  • DSP algorithms 20 also contain a digital processing unit for received signals 210.
  • Unit 210 includes a receiver signal combinator 213 that converts N A AR received digital signals 123 - 124, having in-phase and quadrature components, into N RX DS p digital signals 214 - 215, where NRX DSP is an integer greater than or equal to two, also having in-phase and quadrature components, by implementing linear combinations of the in-phase and quadrature components of the received digital signals 123 - 124, and N RX _DSP blocks of receiver DSP pipelines 211 - 212, converting N RX _DSP of digital signals 214 - 215 in N ⁇ DSP of received digital data 1 11 - 112.
  • Operating parameters of the digital processing unit of transmitted signals 200 including the transmitter DSP pipeline blocks 201 - 202 and the transmitter signal combinator 203, the digital processing unit of received signals 210, including the receiver DSP pipeline blocks 211 - 212 and the receiver signal combinator 213 are determined by the configuration and status information 24 coming from the control algorithms and configuration 21 performed by processor 2.
  • configuration and status information 24 includes coefficients of linear combinations of in-phase and quadrature components of digital signals 204 - 205 performed by the transmitter signal combinator 203, as well as coefficients of linear combinations of received signals 123 - 124 performed by the combinator receiver signals 213.
  • DSP algorithms 20 contain two transmitter DSP pipeline blocks 201 and 202 and two receiver DSP pipeline blocks 211 and 212, the range of possible implementations of the invention is not limited to these values.
  • the values of N TX_DSP AND NRX DSP may be greater than two, that is, the DSP algorithms 20 may contain more than two blocks of transmitter DSP pipelines and more than two blocks of receiver DSP pipelines.
  • the DSP algorithms 20 also include a link performance estimator 220 that calculates estimated link performance 221 based on the received digital signals 123 - 124 processed by the received digital signal processing unit 210.
  • the estimated link performance 221 includes at least one of the following set of possible characteristics: power attenuation coefficient in the communication channel, one or more amplitude-frequency characteristics of the communication channel, one or more impulse characteristics of the communication channel, one or more directions to one or more remote transceiver devices.
  • the operating parameters of the communication channel characteristics evaluation unit 220 are determined by the configuration and status information 24 coming from the control and configuration algorithms 21 performed by the processor 2. In the embodiments of the invention shown in FIGS. 2 and fig.
  • the DSP algorithms 20 also include a block 230 for calculating radiation patterns.
  • Block 230 calculates the parameters of the radiation pattern 33 of the PPU 1 based on the estimated characteristics of the communication channel 221.
  • the parameters of the DP 33 calculated by the block 230 include the coefficients of linear combinations for the transmitter signal combinator 203 and the receiver signal combinator 213, as well as the parameters for the formation of the DP 31 - 32 blocks formation of radiation patterns (PDP) 51 - 52 of the antenna module 5, as will be described below with reference to FIG. 9 - 13.
  • PDP radiation patterns
  • the operating parameters of block 230 when calculating DN 33 of PPU 1 are determined by the configuring part of the configuration and status information 24 coming from control and configuration algorithms 21 performed by processor 2, and the parameters of DN 33 calculated by block 230 are supplied to the control and configuration algorithms in the form status part of configuration and status information 24.
  • the transmitter DSP pipeline 201 includes a noise-resistant coding block 251, a data interleaving block 252, a modulation symbol generation block 253, a block 254 for converting signals from the frequency domain into the time domain using an inverse discrete Fourier transform (IDFT), a block 255 for adding protective intervals (SI) in the sequence of digital signal samples, as well as blocks for adding various service signals and service sequences to the incoming information sequences (not shown in Fig. 4).
  • IDFT inverse discrete Fourier transform
  • SI protective intervals
  • the receiver DSP pipeline 21 1 includes a noise-tolerant decoding block 261, a data deinterleaving block 262, a
  • DFT discrete Fourier transform
  • GS guard intervals
  • the configuration information 24 includes parameters of the noise-correcting coding algorithms 251 and decoding 261.
  • encoding algorithms 251 and decoding algorithms 261 respectively encode and decode the bit stream of data to provide increased noise immunity to communication using a convolutional code or a code with a small parity check density (English, low density parity check - LDPC), using one of the possible coding rates, such as 1/2, 2/3, 3/4, 5/6, etc.
  • the error-correcting coding parameters are 251 and decoding 261 contained in the configuration information 24 determine the choice of one of the encoding/decoding types and one of the possible encoding rates.
  • the configuration information 24 also includes parameters of the bit sequence interleaving 252 and deinterleaving 262 algorithms that determine the method of interleaving and deinterleaving and the size of the bit block on which the bit sequence is interleaved/deinterleaved.
  • configuration information 24 also includes modulation and demodulation parameters 243 defining the type of modulation used and the number of bits per modulation symbol.
  • modulation algorithms 253 and demodulation algorithms 263 respectively modulate and demodulate the information flow using various modulation schemes, such as binary phase shift keying BPSK with one bit per modulation symbol, quadrature phase shift keying (QPSK) with two bits per modulation symbol, 16 quadrature amplitude modulation (16-QAM) with four bits per modulation symbol modulation symbol, 64-QAM with six bits per modulation symbol, etc.
  • the modulation 253 and demodulation 263 parameters contained in the configuration information 24 determine the choice of a particular modulation/demodulation method from among the possibilities.
  • configuration information 24 also includes parameters of the forward Fourier transform 264 and the inverse discrete Fourier transform 254, such as the size of the block of modulation symbols on which the Fourier transform is performed.
  • configuration information 24 also includes insert parameters 255 and removal 265 of guard intervals, defining the method of providing the guard interval, its size and frequency.
  • configuration information 24 also includes parameters for combining transmitted and received signals by signal combiners of transmitter 203 and receiver 213, respectively. These parameters include the coefficients of one or more linear combinations of the in-phase and quadrature components of one or more digital signals, such as signals 204 and 205, performed by the transmitter combinator 203, as well as the coefficients of linear combinations of the in-phase and quadrature components of received digital signals, such as signals 123 and 124 performed by the receiver combinator 213. These coefficients may be calculated, at least in part, based on the estimated characteristics 221 of the communication channel between the PPU 1 and one or more other transceiver devices.
  • Multichannel transceiver unit 4 contains a transmitting signal processing unit 40, including N AAR transmitter channels 401 - 402, and a received signal processing unit 41, including N AAR receiver channels 411 - 412.
  • Multichannel transmitting and receiving unit 4 carries out analogue processing N AAR transmitted signals 141 - 142 and N AAR received signals 143 - 144, which are exchanged with the antenna module 5 through N AAR radio frequency ports 14 - 15 in such a way that one transmitted and one received signal is exchanged through one port.
  • Multichannel receiver transmitting unit 4 also performs conversion N AAR of transmitted digital signals 121 - 122 from digital representation to analog and conversion from analog representation to digital representation N AAR of received digital signals 123 - 124.
  • Transmitted signal processing unit 40 receives from processor 2 through digital port 12 N AAR transmitted digital signals 121 - 122.
  • the transmitted signal processing unit 40 Based on the transmitted digital signals 121 - 122 using N AAR channels of the transmitter 401 - 402, the transmitted signal processing unit 40 generates N AAR radio frequency signals 141 - 142 and then transmits them to the antenna module 5 through N AAR radio frequency ports 14 - 15.
  • the received signal processing unit 41 receives N AAR radio frequency signals 143-144 from the antenna module 5 via N AAR radio frequency ports 14 - 15. Based on the radio frequency signals 143 - 144 using N AAR receiver channels 411 - 412, the received signal processing unit 41 generates N AAR received digital signals 123 - 124 and then transmits them to the processor 2 through the digital port 12.
  • the transceiver unit 4 contains two transmitter channels 401 and 402 and two receiver channels 411 and 412, the range of possible embodiments of the invention is not limited to these values. Thus, in other embodiments of the invention, the value of N AAR may be greater than two, that is, the transceiver unit 4 may contain more than two transmitter channels and more than two receiver channels.
  • fig. 7 shows an example implementation of a transmitter channel 401 in accordance with one embodiment of the present invention.
  • Transmitter channel 401 receives an input digital transmit signal 121 having in-phase and quadrature components 1210 and 1211, respectively.
  • the common mode component 1210 of the digital signal 121 is converted from digital to analog using digital analog converter (DAC) 4011.
  • the quadrature component 1211 of the digital signal 121 is converted from digital to analog form using a digital-to-analog converter (DAC) 4012.
  • DAC digital analog converter
  • the transmitter channel 401 performs operations on analog signals, including filtering using low-pass filters 4013 and 4014 of analog in-phase and quadrature signals, respectively, transferring to an intermediate and/or carrier frequency using mixers 4015 and 4016 of the filtered in-phase and quadrature signals, respectively, summing the transferred to the intermediate and/or carrier frequency of the in-phase and quadrature signals using an adder 4019, and amplifying the power of the sum signal using a power amplifier 4020.
  • the RF signal 141 obtained as a result of processing in block 401 is transmitted further to the antenna module 5 through an RF port, such as one from RF ports 14 - 15.
  • the transceiver unit 4 also generates a service sinusoidal signal at an intermediate and/or carrier frequency using a generator 4017 and separating the generated service sinusoidal signal into in-phase and quadrature components using a phase divider 4018.
  • Parameters for processing transmitted signals such as filter characteristics, carrier and/or intermediate frequency values, bandwidth of transmitted signals, digitization frequency of transmitted signals, etc., are set using configuration information coming from processor 2 through control port 25.
  • Receiver channel 41 1 receives an RF signal 143 from the antenna module 5 through an RF port, such as one of the RF ports 14 - 15.
  • the received RF signal 143 is amplified by a low noise amplifier 4119 and supplied to mixers 41 15 and 4116 for transfer to intermediate and/or fundamental (video) frequency, as well as for highlighting the in-phase and quadrature components of the received analog signals.
  • the in-phase and quadrature components of the analog signal are then subjected to further processing, including filtering using low-pass filters 4113 and 4114, respectively.
  • the transceiver unit 4 also generates a service sinusoidal signal at an intermediate and/or carrier frequency using generator 4117 and separating the generated service sinusoidal signal into in-phase and quadrature components using a phase divider 4118.
  • generators 4017 and 4117 can be configured as separate devices. In another embodiment, generators 4017 and 4117 may technically be the same device.
  • oscillator 4017 and phase divider 4018 are shown as being part of a transmitter channel, and oscillator 4117 and phase divider 41 18 are shown as being part of a receiver channel, the transmit/receive unit 4 may be configured such that one oscillator 4017 and one phase divider 4018 are used to provide overhead to multiple transmitter channels, such as transmitter channels 401 and 402, and one oscillator 4117 and one phase divider 4118 are used to provide overhead to multiple receiver channels, such as receiver channels 411 and 412 .
  • Parameters for processing received signals such as filter characteristics, carrier and/or intermediate frequency values, bandwidth of received signals, digitization frequency of received signals, etc., are set using configuration information coming from processor 2 through control port 25.
  • antenna module 5 is connected to the multi-channel transceiver unit 4 via NAAR RF ports 14 - 15, as well as to the processor 2 via control port 26.
  • antenna module 5 consists of N A AR beamforming units (PDN) 51 - 52, each of which is connected to one of the NAAR radio frequency ports 14 - 15, as well as N A AR antenna arrays 61 - 62 connected to N A AR of FDN blocks 51 - 52 in such a way that one grid is connected to one FDN block.
  • PDN AR beamforming units
  • the antenna module 5 contains two antenna arrays 61 and 62 and two FDN units 51 and 52; the range of possible embodiments of the invention is not limited to these values.
  • the value of N A AR may be greater than two, that is, the antenna module 5 may contain more than two antenna arrays and, accordingly, more than two FDN units connected to these arrays, one FDN unit per antenna array.
  • Each of the NAAR blocks FDN 51 - 52 exchanges through one of the NAAR radio frequency ports 14 - 15 with the multi-channel transceiver unit 4 one of the N A AR transmitted signals 141 - 142 and one of the NAAR received signals 143 - 144.
  • the FDN block 51 through the radio frequency port 14 exchanges with the transceiver unit 4 transmitted signals 141 and received signals 143
  • the FDN unit 52 through the radio frequency port 15 exchanges with the transceiver unit 4 transmitted signals 142 and received signals 144.
  • the FDN block 51 contains a radio frequency (RF) direction switch transmit-receiver 515, power divider 510 and NAE of RF signal processing circuits 511 - 514, where N AE is an integer greater than or equal to two, connected to N A E antenna elements 611 - 614 of antenna array 61 so that one RF circuit processing is connected to one antenna element.
  • the FDN unit 52 includes an RF transmit/receive direction switch 525, a power divider 520, and N A E RF signal processing circuits 521 - 524 coupled to N A E antenna elements 621 - 624 of antenna array 61 such that one RF circuit processing is connected to one antenna element.
  • An RF transmit/receive direction switch 515 connects a transmit signal 141 or a received signal 143 to a power divider 510.
  • An RF transmit/receive direction switch 525 connects a transmit signal 142 or a received signal 144 to a power divider 520.
  • RF processing circuits 511 - 514 are configured with the ability to regulate the phases of N AE signals 161 - 162 between the power division device 510 and antenna elements 611 - 614, and the RF processing circuits 521 - 524 are configured to regulate the phases of N AE signals 171 - 172 between the power division device 520 and antenna elements 621 - 624
  • a power divider 510 in the transmit direction divides the signal power from RF switch 515 between RF processing circuits 511 - 514, and in the receive direction it sums the power of the signals from RF processing circuits 511 - 514.
  • a power divider 520 in the transmit direction performs power division signal from the RF switch 525 between the RF processing circuits 521 - 524, and in the receiving direction it sums the power of the signals from the RF processing circuits 521 - 524.
  • FIG. 9 part of the RF processing circuits of the FDN blocks 51 and 52 and part of the antenna elements of the antenna arrays 61 and 62 are not shown and are replaced with ellipses. Specifically not shown, but implied to be included within the respective blocks, are the RF processing circuits 512, 513, 522, 523, as well as antenna elements 612, 613, 622, 623. However, it is assumed that these elements are present in the circuit and participate in the operation of antenna module 5.
  • the configuration information entering the antenna module 5 from the processor 2 through the control port 26 sets the direction of switching the reception and transmission of the signal by RF switches 515 - 525, as well as the values of phase shifts in the RF processing circuits 511 - 514 and 521 - 524.
  • RF processing circuit 511 performs the functions of at least one of RF signal processing circuits 511 - 514 and 521 - 524 in FIG. 9.
  • RF processing circuit 511 in FIG. 10 includes a 551 transmitter controlled phase shifter and a receiver controlled phase shifter
  • the configuration information supplied to the antenna module 5 from the processor 2 through the control port 26 specifies the direction of switching the reception and transmission of the RF signal by RF switches 553 and 554, as well as the values of the phase shifts for the transmitter phase shifter 551 and the receiver phase shifter 552.
  • RF processing circuit 511 may not include RF switches 553 and 554 for separating received and transmitted signals.
  • switches 553 and 554 can be performed by filters with amplitude-frequency characteristics selected to ensure sufficient isolation of received signals from transmitted ones and vice versa.
  • Embodiments of the present invention are possible in which the RF processing circuits 511 are implemented using a single bidirectional phase shifter capable of controlling the phase of both transmitted and received signals, eliminating the need for RF switches 553 and 554. It is also possible for embodiments of the present invention in which independent antenna elements connected to independent phase shifters are used to transmit and receive signals.
  • the PDN units may include separate power dividers for transmit and receive signals, such as power dividers 510 and 520 in FIG. 9 and may also not include RF switches, such as RF switches 515 and 525 in FIG. 9.
  • FIG. 11 shows an example of a linear phased array antenna 61, such as one of the arrays 61 - 62 in FIG. 1 and fig. 9, in accordance with one embodiment of the present invention.
  • the antenna array 61 consists of N A E antenna elements, such as antenna elements 611 - 614, located on the same line 615.
  • adjacent antenna elements for example, elements 611 and 612 or elements 612 and 613, or elements 613 and 614, are located at a distance d from each other.
  • Each of the antenna elements 611 - 614 is connected to one
  • the RF signal processing circuits of the FDN unit such as the FDN unit 51 of the antenna module, such as the antenna module 5, as shown in FIG. 9.
  • all antenna elements 611 - 614 radiate in phase a periodic signal with wavelength X.
  • the signals received from two adjacent elements will differ in phase by the amount Df A , called the differential phase shift and determined by the formula (r l .
  • the phase shifts imposed by the RF processing circuits are set such that the differential phase shift between adjacent elements of the antenna array is equal to -Df A .
  • the simplified theory of phased array antennas based on the model of geometric optics, in the direction 616, constructive summation of signals from all elements of the antenna array 61 is ensured, and the wave front 618 propagates predominantly in the direction 616.
  • the maximum DP of the antenna array 61 such like DN 31 in Fig. 1 or one of the DNs 31 1 or 312 in FIG. 9 appears to be directed along direction 616.
  • the received signal power is increased.
  • the data rate of receiver 620 to be increased and/or the signal-to-noise ratio of receiver 620 to be increased, thereby increasing communication reliability, and/or the communication range to be increased.
  • different phase shift values for antenna elements 611 - 614 may be set to increase and/or maximize the level of power received by receiver 620 at the antenna array 61 side.
  • the sharpness of the radiation pattern maximum is determined by the ratio of the aperture 637 of the antenna array 61 to the wavelength X of the emitted signal.
  • the larger the aperture of the antenna array 61 the faster the radiation power flux density of the antenna array 61 decreases when deviating from the direction of the maximum, and the sharper the pattern of the antenna array 61 becomes. Due to the decrease in the power flux density when deviating from the direction of the maximum, the pattern ensures a decrease in power interference in directions other than the direction of the maximum pattern of the antenna array 61.
  • the phase shifts specified by the RF processing circuits are set in such a way that the differential phase shift between adjacent elements of the antenna array is equal to 2 lx/? AE - Df A , where N AE is the number of antenna elements in the antenna array 61, and k is a positive integer.
  • N AE is the number of antenna elements in the antenna array 61
  • k is a positive integer.
  • the minimum or zero pattern of the antenna array 61 such as pattern 31 in FIG. . 1 or one of the DNs 31 1 or 312 in FIG. 9.
  • phase shift values for antenna elements 611 - 614 can be set to reduce and/or null the power level received by the receiver 620 from the antenna array 61.
  • phase shift values for antenna elements 611 - 614 can be calculated, at least in part, based on the estimated characteristics 221 of the communication channel between PPU 1 and one or more other PPUs.
  • FIG. 12 shows an example of an antenna system 6 of two antenna arrays 61 and 62 in accordance with one embodiment of the present invention.
  • the antenna arrays 61 and 62 are located in line at a distance D from each other, with their main axes 619 and 629 oriented parallel along the same direction, as shown in FIG. 12.
  • each of the antenna elements 611 - 614 of the array 61 is connected to one RF signal processing circuit of the FDN unit, such as the FDN unit 51 of the antenna module, such as the antenna module 5, and each of the antenna elements 621 - 624 of the array 62 is connected to one RF circuit signal processing unit FDN, such as FDN unit 52 of an antenna module, such as antenna module 5, as shown in FIG. 9.
  • the phase shifts specified by the RF processing circuits of the FDN block 51 are set in such a way that the wave front 618 created by the antenna array 61 propagates predominantly in the direction 616 at an angle of 0 A 1 to the main axis 619 of the array 61
  • the phase shifts specified by the radio frequency circuits processing unit FDN 52 are set in such a way that the wave front 628 created by the antenna array 62 propagates predominantly in the direction 626 at an angle of 0 A2 to the main axis 629 of the array 62, directions 616 and 626 are parallel to each other, and the phase shift for the antenna element 611 of the array 61 and antenna element 621 of the array 62 coincide.
  • the transmitted signal 141 arriving at the FDN block 51 is generated by the transmitter channel 401 based on the transmitted digital signal 121 generated by the DSP block 20 (see FIG. 6), and the transmitted signal 142 entering the FDN block 52 is generated by the channel transmitter 402 based on the transmitted digital signal 122 generated by the DSP unit 20 (Fig. 6).
  • the coefficients of linear combinations performed by the transmitter signal combinator 203 are set in such a way that the digital transmitted signals 121 and 122, generated by the DSP unit 20, differ in phase by the amount -Af 0 .
  • antenna system 6 contains more elements than individual arrays 61 or 62, direction 636 provides constructive summation of more transmitted signals from more antenna elements compared to just one array, and therefore the antenna system 6 provides greater gain than each of the arrays 61 or 62 individually. As a result, the speed and/or range and/or reliability of data transmission for the antenna system 6 is greater than for the arrays 61 or 62 separately.
  • the pattern of the antenna system 6 is sharper compared to the pattern of the grid 61 or the grid 62 separately.
  • the phase shift values for antenna elements 611 - 614 and 621 - 624 in FIG. 12 may be calculated, at least in part, based on the estimated characteristics 221 of the communication channel between PPU 1 and one or more other PPUs.
  • these phase shifts can be set together with setting the coefficients of linear combinations performed by the linear combinator of the transmitter 203.
  • these phase the shifts can be set in conjunction with the setting of linear combination coefficients performed by the linear combinator of the receiver 213.
  • FIG. 13 shows an example of an antenna system 6 of two antenna arrays 61 and 62 in accordance with one embodiment of the present invention.
  • the antenna elements of the arrays 61 and 62 are located in the same plane, and the antenna elements of each of the arrays 61 and 62 are spaced apart along the Z axis of the coordinate system 625 associated with the antenna system 6, the antenna elements 61 and 62 are spaced relative to each other along the Y axis of the coordinate system 625, and the directions of the main axes of both the array 61 and the array 62 are directed along the X axis of the coordinate system 625.
  • each of the antenna elements 611 - 614 array 61 is connected to one RF signal processing circuit of an FDN unit, such as an FDN unit 51 of an antenna module, such as antenna module 5, and each of the antenna elements 621 - 624 of array 62 is connected to one RF signal processing circuit of a FDN unit, such as an FDN unit 52 antenna module, such as antenna module 5 as shown in FIG. 9.
  • the phase shifts specified by the RF signal processing circuits of the FDN block 51 are set in such a way that the wavefront 618 created by the antenna array 61 propagates predominantly in the direction 616 at an angle of 0 Ai to the main axis 619 of the array 61 in the XZ plane of the coordinate system 625
  • the phase shifts specified by the RF signal processing circuits of the FDN block 52 are set in such a way that the wave front 628 created by the antenna array 62 propagates predominantly in the direction 626 at an angle of 0 A2 to the main axis 629 of the array 62 in the XZ plane of the coordinate system 625, the direction 616 and 626 are parallel to each other, and the phase shifts for antenna element 611 of array 61 and antenna element 621 of array 62 are the same.
  • the transmit signal 141 arriving at the FDN block 51 is generated by the transmitter channel 401 based on the digital transmit signal 121 generated by the DSP unit 20, and the transmit signal 142 entering the FDN block 52 is generated by the transmitter channel 402 based on the digital transmit signal. 122, generated by the DSP block 20.
  • the weighting coefficients of the transmitter signal combinator 203 are set in such a way that the digital transmitted signals 121 and 122, generated by the DSP block 20, differ in phase by the amount -Df o .
  • phased array antennas based on the model of geometric optics, in the direction 636, which differs from the directions 616 and 626 by the angle 0 DH in the XY plane of the coordinate system 625, constructive summation of signals from all elements is ensured both antenna arrays, and the wavefronts 618 and 628 are combined into a single wavefront 638, propagating predominantly in the direction 636.
  • the maximum beam pattern of the antenna system 6, such as beam pattern 33 in FIG. 1 or one of the DNs 331 and 332 in FIG. 9 appears to be directed along direction 636.
  • antenna system 6 contains more elements than individual arrays 61 or 62, direction 636 provides constructive summation of more transmitted signals from more antenna elements compared to just one array, and therefore the antenna system 6 provides greater gain than each of the arrays 61 or 62 individually. As a result, the speed and/or range and/or reliability of data transmission for the antenna system 6 is greater than for the arrays 61 or 62 separately.
  • the DP of the antenna system 6 is in the XY plane of the coordinate system 625 is sharper than the pattern of the grating 61 or the grating 62 separately, and in the XZ plane of the coordinate system 625 has the same sharpness as the pattern of each of the gratings 61 or 62 separately. This leads to a greater attenuation of the radiation power flux density in directions different in the XY plane of the coordinate system 625 from the direction of the maximum pattern of the antenna system 6 in comparison with the antennas of each of the arrays 61 or 62 separately.
  • the antenna system 6 in directions other than the direction of the maximum radiation pattern creates interference of less power than each of the antenna arrays 61 or 62 separately.
  • the phase shift values for antenna elements 611 - 614 and 621 - 624 in FIG. 13 may be calculated, at least in part, based on the estimated characteristics 221 of the communication channel between PPU 1 and one or more other PPUs.
  • these phase shifts can be set together with setting the coefficients of linear combinations performed by the linear combinator of the transmitter 203.
  • these phase the shifts can be set in conjunction with the set of coefficients of linear combinations performed by the linear combinator of the receiver 213.
  • sample 9 PPU 1 was manufactured, operating in the frequency ranges of 2.4 GHz and 5 GHz.
  • the block diagram of the manufactured sample 9 is shown in Fig. 14.
  • the functions of the processor 2, storage 3 and multi-channel transceiver unit 4 are performed by the system-on-module (English, system on module - SoM) ADRV9361-Z7035, supplied by Analog Devices.
  • This system is a Software-Defined Radio (SDR) platform that combines an analog AD9361 (Integrated RF Agile Transceiver) device used as a transceiver unit 4, and a digital Xilinx Z7035 Zynq-7000 device, used as processor 2 and coupled with memory 30, in a small form factor well suited for integration into the final product.
  • SDR Software-Defined Radio
  • Antenna module 5 was developed as a separate block containing two FDN boards 51 and 52, connected to the radio frequency inputs and outputs of SoM ADRV9361-Z7035 by high-frequency cables 121, 131, 122 and 132.
  • Samples of antenna arrays 61 and 62 are made in the form vertical columns of four dipole antenna elements each, similar to the antenna system 6 in the configuration shown in FIG. 13.
  • Antenna arrays 61 and 62 are located horizontally relative to each other.
  • Each of the antenna elements of the samples of both arrays 61 and 62 is connected to a separate RF signal processing circuit of the FDN blocks 51 and 52, respectively.
  • Each of the RF processing circuits of the antenna module sample 9 PPU 1 has two phase shifters - one for receiving and one for transmitting the signal, as shown in Fig. 10.
  • the phase adjustment step of the transmitter phase shifter and the receiver phase shifter is 22.5 degrees, providing 16 possible phase shift values ranging from 0 to 360 degrees.
  • the pattern of the antenna system in the vertical (angular) plane was mainly determined by the settings of the FDN blocks 51 and 52 of the antenna module 5, while the pattern in the horizontal (azimuth) plane was determined mainly by the parameters of the signal combiners 203 and 213 of the DSP block 20, made in the programmable logic 29 of the Xilinx Z7035 Zynq-7000 digital device.
  • GUI graphical user interface
  • Control of sample 9 of PPU 1 was carried out using graphical user interface (GUI) software 8 running on a personal computer 86 and allowing the user to configure the parameters of the DSP algorithms 20 using the DSP configuration block 82, reception parameters - transmitting unit 4 using analog processing configuration block 83, parameters for the formation of patterns by antenna module 5 using antenna module configuration block 84.
  • GUI 8 software also allows the user to save settings using the block 85 for saving configuration settings and process the results of experiments using the block 81 for processing and outputting measurement results.
  • cellular communication system 700 may include a base station 701 surrounded by multiple user devices, such as devices 702 and 703.
  • the locations of user devices 702 and 703 relative to base station 701 are characterized by distances 712 and 713 from user devices 702 and 703 to antenna system 6 base station 701, heights 722 and 723 of devices 702 and 703, respectively, above ground level, as well as elevation plane angles, such as angle 715 between direction 713 and the ground, and azimuth plane angles, such as angle 716 between axis 710 projection 711 antenna system 6 on the earth's surface and projection 714 on the earth's surface of the direction 712 to the user device 702.
  • the antenna system 6 of base station 701 is configured to direct the maximum of its beam pattern, such as beam pattern 33 in FIG. 1 or one of the DN 331 and/or DN 332 in FIG. 9 to user device 702.
  • user device 702 receives increased signal power compared to other peak directions of antenna system 6.
  • communication between the base station 701 and the user device 702 can be organized at distances greater than other directions of the antenna system 6 beam pattern maximum and/or communication between the base station 701 and the user device 702 can be organized at speeds greater than compared to other antenna system 6 pattern peak directions and/or communication between base station 701 and user device 702 may provide fewer transmission errors compared to other antenna system 6 pattern peak directions.
  • the antenna system 6 of the base station 701 generates two patterns, such as pattern 331 and/or pattern 332 in FIG. 9. At the same time at least one DN, for example DN 331 in FIG. 9 is directed to user device 702, and at least another AP, such as AP 332 in FIG. 9 is directed to user device 703.
  • base station 701 simultaneously sends first and second signals to two user devices 702 and 703 using DPs 332 and 331, respectively. directed to user device 702, user device 702 receives the first signals with minor interference from the second signals.
  • the minimum DP 332 is directed and the minimum DP 331 is not directed at the user device 703, the user device 703 receives the second signals with little interference from the first signals. This makes it possible, using the antenna system 6, to simultaneously transmit two signals in the same frequency band, thereby increasing the overall data transmission rate in the cellular communication network 700.
  • Preliminary comparative modeling of communication systems such as the 700 cellular system, with base stations equipped with either 4-array antenna systems of 4 elements each in a (1 x 4) x (4 x 1) configuration, or fully adaptive two-dimensional 16-element antennas arrays (4x4), or adaptive one-dimensional 4-element arrays (1 x4), showed that base stations with antenna systems of several arrays in a (1x4)x(4x1) configuration are no more than 5% inferior in data transfer speed base stations with fully adaptive two-dimensional 16-element antenna arrays (4x4) with the same number and geometric arrangement of antenna elements.
  • base stations with antenna systems of several arrays in the (1 x 4) x (4 x 1) configuration provide a gain in data transmission speed of up to 25% compared to base stations with one-dimensional adaptive arrays (1 x4).
  • the increase in data transfer rate is due to the larger aperture of the multi-array antenna system in the (1 x 4) x (4 x 1) configuration compared to the aperture of a one-dimensional adaptive array (1 x 4).
  • both antenna systems use the same number of radio frequency circuits, which practically equalizes the cost of manufacturing antenna systems of both types.
  • the simulation also showed that under the considered communication conditions, in order to achieve a 25% increase in transmission speed for a communication system with adaptive antenna arrays (1 x 4), the transmitter power would have to be increased fourfold, which confirms the high efficiency of the design of the proposed PPU.
  • the calculated value of the gain of the antenna array 61 was from 5.5 to 6 dB relative to a single antenna element, similar to antenna elements 611 - 614 and emitting a signal with just as full power, like the entire array 61.
  • the measured value of the gain of the antenna array 61 turned out to be less than the calculated value by an amount not exceeding 0.5 dB over the entire specified range of elevation angles.
  • a similar experiment was carried out for the antenna array 62 connected to the FDN unit 52, during which similar results were obtained.
  • the calculated value of the gain antenna system in this range of angles of deviation of the direction of radiation 636 was from 8.5 to 9 dB relative to a single antenna element, similar to antenna elements 611 - 614 and emitting a signal with the same total power as antenna system 6.
  • the measured gain of the antenna system 6 turned out to be less than the calculated value by an amount not exceeding 0.7 dB over the entire specified range of azimuthal angles.
  • the results of the first and second series of experiments show that by using a single 4-element array antenna, such as Array 61, at one end of a data link, it is possible to increase the signal power received by a remote receiver by up to 6 dB, allowing for increased range in free space communication up to 2 times without loss of quality and/or increase the data transfer rate by approximately 1 bit/s/Hz, and by using an antenna system 6 of two 4-element arrays it is possible to increase the received signal power by up to 9 dB, which allows you to increase the communication range to 2.8 in free space times without loss of quality and/or increase the data transfer rate by approximately 1.5 bps/Hz.
  • the results of the third series of experiments show that with the help of antenna system 6, consisting of two arrays connected to independent channels of analog (channels 401 and 402 in Fig. 6) and digital (channels 201 and 202 in Fig. 3) signal processing, in free space, it is possible to up to 2 times the data rate of a communications system, such as communications system 700 in FIG. 15, by simultaneously transmitting data to two users in the same frequency band.
  • antenna system 6 consisting of two arrays connected to independent channels of analog (channels 401 and 402 in Fig. 6) and digital (channels 201 and 202 in Fig. 3) signal processing, in free space, it is possible to up to 2 times the data rate of a communications system, such as communications system 700 in FIG. 15, by simultaneously transmitting data to two users in the same frequency band.

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  • Engineering & Computer Science (AREA)
  • Computer Networks & Wireless Communication (AREA)
  • Signal Processing (AREA)
  • Databases & Information Systems (AREA)
  • Variable-Direction Aerials And Aerial Arrays (AREA)

Abstract

L'invention concerne des systèmes radio configurables par logiciel qui peuvent être utilisés dans le domaine des techniques de communications, de radio-localisation, et des systèmes de radiocommunications mobiles. Ce dispositif émetteur-récepteur déterminé par logiciel (1) comprend un processeur (2) connecté à un processeur de stockage (3), une unité mono-canal d'émission-réception (4) connectée au processeur. Le dispositif comprend en outre des réseaux d'éléments d'antenne (61-62), des unités de génération de diagramme de directivité (51-52) connectées aux réseaux d'éléments d'antenne ainsi qu'à l'unité mono-canal d'émission-réception et au processeur; l'unité mono-canal d'émission-réception comprend des ports (14-15) qui sont chacun connectées à une unité de génération de diagramme de directivité, et chaque unité de génération de diagramme de directivité est également connectée à un réseau d'éléments d'antenne, tandis que le processeur est configuré de manière à pouvoir changer le diagramme de directivité des réseaux d'éléments d'antenne. L'invention a pour but de générer un diagramme de directivité commandé par logiciel de manière à pouvoir concentrer, atténuer l'énergie émise, ainsi qu'amplifier et/ou supprimer les signaux reçus pour des directions données, amplifier les signaux utiles, diminuer les interférences dans des directions données, augmenter la portée et la fiabilité de communication et la vitesse de transmission de données en utilisant des paramètres de signaux déterminés par logiciel.
PCT/RU2022/000131 2022-04-18 2022-04-18 Dispositif émetteur-récepteur déterminé par logiciel WO2023204723A1 (fr)

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Citations (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US5838268A (en) * 1997-03-14 1998-11-17 Orckit Communications Ltd. Apparatus and methods for modulation and demodulation of data
US20020144134A1 (en) * 2001-02-16 2002-10-03 Koji Watanabe Software defined radio and radio system
US8081045B1 (en) * 2008-08-08 2011-12-20 Lockheed Martin Corporation Beamformer power divider/combiner with transmission lines distributed between MMIC and associated PC board
WO2018102326A1 (fr) * 2016-11-29 2018-06-07 AMI Research & Development, LLC Réseau super-directif d'éléments d'antennes volumétriques pour applications de dispositif sans fil
US20220109458A1 (en) * 2019-02-27 2022-04-07 Hitachi Kokusai Electric Inc. Software-defined radio equipment

Patent Citations (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US5838268A (en) * 1997-03-14 1998-11-17 Orckit Communications Ltd. Apparatus and methods for modulation and demodulation of data
US20020144134A1 (en) * 2001-02-16 2002-10-03 Koji Watanabe Software defined radio and radio system
US8081045B1 (en) * 2008-08-08 2011-12-20 Lockheed Martin Corporation Beamformer power divider/combiner with transmission lines distributed between MMIC and associated PC board
WO2018102326A1 (fr) * 2016-11-29 2018-06-07 AMI Research & Development, LLC Réseau super-directif d'éléments d'antennes volumétriques pour applications de dispositif sans fil
US20220109458A1 (en) * 2019-02-27 2022-04-07 Hitachi Kokusai Electric Inc. Software-defined radio equipment

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