WO2023005270A1 - 开关电容谐振倍压整流变换器及其控制方法、控制系统 - Google Patents

开关电容谐振倍压整流变换器及其控制方法、控制系统 Download PDF

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WO2023005270A1
WO2023005270A1 PCT/CN2022/087560 CN2022087560W WO2023005270A1 WO 2023005270 A1 WO2023005270 A1 WO 2023005270A1 CN 2022087560 W CN2022087560 W CN 2022087560W WO 2023005270 A1 WO2023005270 A1 WO 2023005270A1
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module
positive
negative
switched capacitor
resonant
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PCT/CN2022/087560
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English (en)
French (fr)
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罗安
肖子衡
何志兴
陈燕东
陈峻岭
宁勇
徐千鸣
欧阳红林
刘阳
周乐明
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广东志成冠军集团有限公司
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Publication of WO2023005270A1 publication Critical patent/WO2023005270A1/zh

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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/02—Conversion of ac power input into dc power output without possibility of reversal
    • H02M7/04—Conversion of ac power input into dc power output without possibility of reversal by static converters
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

Definitions

  • the invention relates to a rectifier converter control technology, in particular to a switched capacitor resonant voltage doubler rectifier converter and its control method and control system.
  • High step-up ratio power frequency transformers are relatively easy to manufacture, but they have the disadvantages of large weight, large volume, and large output ripple; traditional voltage doubler rectifier converters require isolation transformers with a certain insulation voltage, and the leakage inductance and parasitic capacitance of the isolation transformer will It increases with the increase of transformer insulation voltage.
  • the high-voltage side of the isolation transformer is often wound with wires with a thicker insulation layer, which greatly reduces the window fill factor of the transformer, thereby restricting the increase in power density.
  • Most of the diodes in the traditional voltage doubler rectifier converter are in hard switching, which leads to a large peak when the diode is switched, and the diode has a certain loss during the commutation process.
  • the parasitic capacitance of the diode will affect the operation of the switch tube on the primary side of the transformer, which may cause waveform distortion or hard switching of the power switch tube on the primary side.
  • the technical problem to be solved by the present invention is to provide a switched capacitor resonant voltage doubler rectifier converter and its control method and control system to avoid the use of high insulation transformers and improve the power density and efficiency of the converter.
  • the input power of the active sub-module can be transmitted to the first positive module, the second positive module, the Up to the mth positive module, it can also be sequentially transmitted to the first negative module, the second negative module, and up to the nth negative module through a plurality of negative resonance branches.
  • the positive and negative ports of the active sub-module, the positive module and the negative module are connected in sequence to realize high voltage output.
  • the active sub-module transmits power sequentially to the positive module and the negative module.
  • the structure of the positive module and the negative module is the same, and the same circuit board can be used for splicing, which greatly reduces the complexity of circuit design and improves the modularization and power density of the converter.
  • the diodes in each positive and negative module can realize soft switching, which greatly improves the power density and efficiency of the converter.
  • m and n can be selected according to the required boost multiples. After the boost multiples are determined, m and n should be as close as possible, and it is optimal when m and n are equal. When m and n are equal, the number of positive modules and negative modules is equal, the power transmission and voltage and current stress between positive and negative modules with different corresponding serial numbers are the same, and the symmetry of the converter is the best.
  • the active sub-module adopts a full-bridge inverter circuit or a half-bridge inverter circuit.
  • a suitable active submodule topology can be selected for a particular occasion. In small current occasions, a half-bridge inverter structure can be used to reduce the use of power switch tubes, and in high-current occasions, a full-bridge inverter structure can be used.
  • the passive sub-module is a half-bridge rectifier circuit or a full-bridge rectifier circuit.
  • the half-bridge rectifier circuit contains two diodes and a DC capacitor, which is suitable for low-power applications; the full-bridge rectifier circuit contains four diodes and a DC capacitor, which is suitable for high-power applications.
  • Both the positive resonant branch and the negative resonant branch include a resonant capacitor and a resonant inductance connected in series with the resonant capacitor.
  • the series frequency of the resonant capacitor and resonant inductance is f r .
  • the structure of the resonant branch is simple, which further optimizes the structure of the converter.
  • the present invention also provides a control method for the above switched capacitor resonant voltage doubler rectifier converter, including:
  • the active sub-module is a half-bridge inverter circuit
  • the two switch tubes of the active sub-module are complementarily turned on
  • the active sub-module is a full-bridge inverter circuit
  • the two power switch tubes of the first bridge arm of the active sub-module are complementary conduction
  • the two power switch tubes of the second bridge arm are complementary conduction
  • the two power switch tubes of the first bridge arm are complementary conduction.
  • the switching signals of the first power switch tubes are the same, and the switching signals of the two power switch tubes of the second bridge arm are the same;
  • the switched capacitor resonant voltage doubler rectifier converter When the switched capacitor resonant voltage doubler rectifier converter operates in the closed-loop mode (that is, the switching frequency of the switched capacitor resonant voltage doubler rectifier converter changes with the output voltage): the reference of the output voltage of the switched capacitor resonant voltage doubler rectifier converter After making a difference between the value Vref and the sampled output voltage Vo, PI modulation is performed on the difference to obtain a driving signal, and the driving signal is used to control the on-off of the power switch tube of the active sub-module.
  • the control method is simple, and only isolation sampling is required. Since the converter does not adopt a structure in which the input is connected in parallel and the output is connected in series, the DC capacitors in the active sub-module and multiple passive sub-modules are connected in series, so the converter does not need high-voltage insulation treatment when sampling the output voltage, and isolation sampling is not necessary. Isolation amplifiers that require high-voltage isolation improve converter power density and efficiency.
  • the switching frequency fs of the power switch tube of the active sub-module is the same as the series resonant frequency fr of the positive resonance branch/negative resonance branch.
  • the switched capacitor resonant voltage doubler rectifier converter When the switched capacitor resonant voltage doubler rectifier converter operates in an open-loop mode, no additional control method is required, and all DC voltages can be naturally balanced and soft switching of all switching tubes can be realized. That is to say, the present invention can realize soft switching of all diodes, and the parasitic capacitance of the diodes will not affect the operation of the primary switching tube.
  • the present invention also provides a control system for a switched capacitor resonant voltage doubler rectifier converter, which includes a controller; the controller is configured or programmed to perform the steps of the control method of the present invention; the output control of the controller The signal is input to the gate of the power switch tube of the active sub-module of the switched capacitor resonant voltage doubler rectifier converter.
  • the present invention adopts modular technology, and both the passive sub-module and the resonant branch can be used as modular components, and any series of resonant voltage doubler rectifier converters can be realized by splicing the modular components.
  • the present invention can realize high-ratio step-up without a high-insulation transformer, reduces the cost of the converter, reduces the volume of the converter, and improves the power density of the converter.
  • each passive sub-module can generate the same voltage as the input voltage of the active sub-module, and the output of the passive sub-modules is connected in series, so that it can be used without using a transformer. large boost output voltage.
  • Multiple resonant branches provide soft switching conditions for the power switch tube of the active sub-module and the diode of the passive sub-module, which greatly reduces the switching loss of the active sub-module and the passive sub-module, thus making the voltage doubling resonant circuit Power density and efficiency are greatly improved.
  • the present invention can realize soft switching of all power switch tubes and diodes, and the parasitic capacitance of the diodes will not affect the operation of the power switch tubes, reducing converter loss and improving converter efficiency.
  • Fig. 1 is a circuit structure diagram of a switched capacitor resonant voltage doubler rectifier converter
  • Figure 2 is a topological structure diagram of active sub-module structure 1
  • Figure 3 is a topological structure diagram of active sub-module structure 2
  • Figure 4 is a topological structure diagram of passive sub-module structure 1
  • Figure 5 is a passive sub-module structure 2
  • Fig. 6 is a resonant branch topology diagram;
  • Figure 7 shows the implementation scheme of the switched capacitor resonant voltage doubler rectifier converter with the half-bridge inverter structure adopted by the active sub-module and the half-bridge rectification structure adopted by the passive sub-module.
  • Figure 8 shows when S 1 is disconnected and S 2 is closed , the equivalent circuit of the converter,
  • Figure 9 is the equivalent circuit of the converter when S 1 is closed and S 2 is disconnected;
  • Figure 10 is an implementation scheme of a switched capacitor resonant voltage doubler rectifier converter in which the active sub-module adopts a full-bridge inverter structure, and the passive sub-module also adopts a full-bridge rectification structure;
  • Figure 11 is the equivalent circuit of the converter when S 1 and S 4 are disconnected and S 2 and S 3 are closed;
  • Figure 12 is the equivalent circuit of the converter when S 1 and S 4 are closed and S 2 and S 3 are disconnected;
  • Fig. 23 is a control block diagram taking a switched capacitor resonant voltage doubler rectifier converter using a half-bridge active sub-module and a passive sub-module as an example.
  • Embodiment 1 of the present invention The structure of the switched capacitor resonant voltage doubler rectifier converter is shown in Fig. Consistent structure, collectively referred to as passive sub-modules), and m positive resonance branches and n negative resonance branches (positive resonance branches and negative resonance branches have the same structure, collectively referred to as resonance branches).
  • m and n are positive integers, and m and n may or may not be equal.
  • Active sub-modules have positive and negative ports (+/-) and AC ports (AC or AC 1 /AC 2 )
  • passive sub-modules have positive and negative ports (+/-) and AC ports (AC or AC 1 /AC 2 )
  • the resonant branch has an AC port (AC 1 /AC 2 ).
  • the positive port of the active sub-module is connected to the negative port of the first positive module, the positive port of the first positive module is connected to the negative port of the second positive module, and the positive port of the m-1th positive module is connected to the negative port of the mth positive module.
  • the positive port of the mth positive module is used as the positive port of the output voltage of the converter
  • the negative port of the active sub-module is connected to the positive port of the first negative module
  • the positive port of the second negative module is connected to the negative port of the first negative module
  • the negative port of the n-1th negative module is connected to the positive port of the nth negative module, and the negative port of the nth negative module is used as a negative port of the output voltage of the converter.
  • the resonant branch is connected between the adjacent active sub-module and the positive module, the active sub-module and the negative module, the adjacent positive module, and the adjacent negative module through the AC port.
  • the special feature of the present invention is that through the connection of the active sub-module, the positive module, the negative module and the resonant branch, the input power of the active sub-module can be sequentially transmitted to the first positive module, the second resonant branch through multiple positive resonant branches.
  • the second positive module, up to the mth positive module can also be sequentially transmitted to the first negative module, the second negative module, up to the nth negative module through a plurality of negative resonance branches.
  • the positive and negative ports of the active sub-module, the positive module and the negative module are connected in sequence to realize high voltage output.
  • the active sub-module, passive sub-module and resonant branch described in Fig. 1 are shown in Fig. 2 to Fig. 6.
  • the active sub-module can be structure 1 (half-bridge inverter structure, Fig. 2) or structure 2 (full-bridge inverter structure, Figure 3).
  • the passive sub-module can be structure 1 (half-bridge rectification structure, Fig. 4 ), or structure 2 (full-bridge rectification structure, Fig. 5 ), etc.
  • the active sub-module consists of a power switch tube and a DC capacitor.
  • the power switch tube can be IGBT, MOSFET, IGCT or GTO.
  • the half-bridge inverter structure includes a first power switch S 1 and a second power switch S 2 .
  • the first power switch tube and the second power switch tube are connected in parallel with the DC capacitor C0 after being connected in series, the positive and negative ends of the DC capacitor are respectively used as the positive and negative terminals of the active sub-module, and the midpoint of the two power switch tubes in series is used as the AC port AC.
  • the full-bridge inverter structure includes four power switch tubes S 1 , S 2 , S 3 , and S 4 (corresponding to the first to fourth power switch tubes), and the first power switch tube and the second power switch tube are connected in series to form the first power switch tube.
  • the bridge arm, the third power switch tube and the fourth power switch tube are connected in series to form the second bridge arm. After the two bridge arms are connected in parallel, they are connected in parallel with the DC capacitor C 0 .
  • the midpoint of the first bridge arm serves as the AC port AC 1
  • the midpoint of the second bridge arm serves as the AC port AC 2
  • Passive sub-modules consist of diodes and DC capacitors.
  • the half-bridge rectification structure includes a first diode D 1 and a second diode D 2 .
  • the first diode and the second diode are connected in parallel with the DC capacitor C1 after being connected in series, the positive and negative ends of the DC capacitor are respectively used as the positive and negative terminals of the passive sub-module, and the midpoint of the two diodes in series is used as the AC port AC.
  • the full-bridge rectification structure includes four diodes D 1 , D 2 , D 3 , and D 4 (corresponding to the first to fourth diodes), the first diode and the second diode are connected in series to form the first bridge arm, The third diode and the fourth diode are connected in series to form the second bridge arm, and the two bridge arms are connected in parallel with the DC capacitor C1 , and the positive and negative ends of the DC capacitor are respectively used as the positive and negative terminals of the passive sub-module,
  • the midpoint of the first bridge arm serves as the AC port AC 1
  • the midpoint of the second bridge arm serves as the AC port AC 2 .
  • the resonant branch includes a resonant capacitor C r and a resonant inductor L r .
  • One end of the resonant inductor is connected to the resonant capacitor, the other end is used as an AC port AC 1 , and the other end of the resonant capacitor is used as an AC port AC 2 .
  • the active sub-module adopts the half-bridge inverter structure and the full-bridge inverter structure
  • the passive sub-module also adopts the half-bridge rectification structure and the full-bridge rectification structure accordingly.
  • the active sub-module adopts a half-bridge inverter structure, and the passive sub-module also adopts a half-bridge rectification structure.
  • the DC capacitance of the active sub-module is C 0
  • S 1 and S 2 are two power switches MOSFETs
  • diodes and DC capacitances of the first to mth positive modules are D p11 , D p12 ... D pm1 , D pm2 and C p1 , C p2 ... C pm
  • the diodes and DC capacitors of the first to nth negative modules are respectively D n11 , D n12 . . . D nn1 , D nn2 and C n1 , C n2 .
  • the resonant capacitance and resonant inductance in the resonant branch connected to the active sub-module and the positive module are respectively C rp1 , C rp2 ...C rpm and L rp1 , L rp2 ...L rpm .
  • the resonant capacitance and resonant inductance in the resonant branch connected to the active sub-module and the negative module are respectively C rn1 , C rn2 ... C rnn and L rn1 , L rn2 ... L rnn .
  • C rpm and L rpm resonate in series, and the current direction is from right to left; C rn1 and L rn1 , C rn2 and L rn2 , ... C rnn and L rnn resonate in series, The current direction is also from right to left.
  • C rpm and L rpm resonate in series, and the current direction is from left to right; C rn1 and L rn1 , C rn2 and L rn2 , ... C rnn and L rnn resonate in series, The current direction is also from left to right.
  • the active sub-module adopts a full-bridge inverter structure, and the passive sub-module also adopts a full-bridge rectification structure, as shown in Figure 10.
  • the DC capacitance of the active sub-module is C 0 , S 1 , S 2 , S 3 and S 4 is four power switch MOSFETs, and the diodes and DC capacitances of the first to mth positive modules are D p11 , D p12 , D p13 , D p14 ... D pm1 , D pm2 , D pm3 , D pm4 and C p1 , C p2 ... C pm .
  • the diodes and DC capacitors of the first to nth negative modules are respectively D n11 , D n12 , D n13 , D n14 ... D nn1 , D nn2 , D nn3 , D nn4 and C n1 , C n2 ... C nn .
  • the resonant capacitance and resonant inductance in the resonant branch connected to the active sub-module and the positive module are respectively C rp11 , C rp12 , C rp21 , C rp22 ...
  • the resonant capacitance and resonant inductance in the resonant branch connected to the active sub-module and the negative module are C rn11 , C rn12 , C rn21 , C rn22 ... C rnn1 , C rnn2 and L rn11 , L rn12 , L rn21 , L rn22 ...L rnn1 ,L rnn2 .
  • C rp11 and L rp11 , C rp21 and L rp21 , ... C rpm1 and L rpm1 resonate in series, and the current direction is from left to right;
  • C rp12 and L rp12 , C rp22 and L rp22 , ... C rpm2 and L rpm2 resonate in series, The current direction is from right to left;
  • C rnn1 and L rnn1 resonate in series, and the current direction is also from right to left;
  • C rn12 and L rn12 , C rn22 and L rn22 , ...C rnn2 and L rnn2 resonate in series, and the current direction is also from left to right.
  • C rp11 and L rp11 , C rp21 and L rp21 , ... C rpm1 and L rpm1 resonate in series, and the current direction is from right to left;
  • C rp12 and L rp12 , C rp22 and L rp22 , ... C rpm2 and L rpm2 resonate in series, The current direction is from left to right;
  • C rnn1 and L rnn1 resonate in series, and the current direction is also from left to right;
  • C rn12 and L rn12 , C rn22 and L rn22 , ...C rnn2 and L rnn2 resonate in series, and the current direction is also from right to left.
  • Embodiment 2 control method of the present invention is as follows:
  • the frequency f s of all power switch tubes is the same as the series resonant frequency f r , and operates at a full duty cycle; at this time, the switched capacitor resonant voltage doubler rectifier transforms
  • the converter works at the series resonance point, which can realize the soft switching of all power switching tubes and high-frequency rectifying diodes.
  • the power switch tubes S 1 and S 2 are complementarily turned on;
  • the power switches S 1 and S 2 are turned on complementary, and the power switches S 3 and S 4 are turned on complementary, the switching signals of S 1 and S 3 are the same, and the switching signals of S 2 and S 4 are the same.
  • the reference value V ref of the output voltage of the switched capacitor resonant voltage doubler rectifier converter is set as a difference with the sampled output voltage V o and then sent to the PI
  • the PI controller outputs a drive signal with changing frequency, and the drive signal obtains a switch signal of the power switch tube of the active sub-module through the drive circuit.
  • the output voltage of the vibration doubler rectifier converter can be adjusted by the frequency f s of the switching tube. When the frequency f s of the switching tube increases, the output voltage decreases; when the frequency f s of the switching tube decreases, the output voltage increases.
  • the reference value V ref of the output port voltage and the sampled output port voltage V o are sent to the PI controller after making a difference (that is, PI modulation) , performing PI modulation on the difference to obtain a driving signal, and using the driving signal to control the on-off of the power switch tube of the active sub-module.
  • the frequency f s of the power switch can be lower than the series resonance frequency f r or greater than the series resonance frequency f r .
  • the controller can realize the static error-free tracking of the output voltage through the closed-loop control of the output voltage.
  • the input voltage V in 1kV
  • the capacitance of the DC capacitor is 9 ⁇ F
  • the switching frequency of the power switch tubes S 1 and S 2 is 100kHz
  • the duty ratio is 0.5
  • the open-loop control is used.
  • the output voltage is 11kV
  • the load resistance is 10k ⁇
  • the output power 12.1kW.
  • Fig. 13 is the current i(L rp1 ) of the resonant inductance L rp1 of the first positive resonant branch and the current i(L rn1 ) of the resonant inductance L rn1 of the first negative resonant branch.
  • Fig. 14 is the first positive module diode D p11 and currents i(D p11 ) and i(D p12 ) of D p12 .
  • Fig. 15 is the current i(L rp1 ), i(L rp2 ) and i of the resonant inductance L rp1 of the first positive resonant branch, the resonant inductance L rp2 of the second positive resonant branch and the resonant inductance L rp3 of the third positive resonant branch (L rp3 ).
  • Fig. 16 shows the voltage v(C rp1 ) , v( C rp2 ) and v (C rp3 ).
  • FIG. 17 shows the voltages v(C p1 ), v(C p2 ) and v(C p3 ) of the first positive module DC capacitor C p1 , the second positive module DC capacitor C p2 and the third positive module DC capacitor C p3 .
  • the input voltage V in 1kV
  • the capacitance of the DC capacitor is 9 ⁇ F
  • the switching frequency of the power switch tubes S 1 , S 2 , S 3 and S 4 is 100 kHz
  • the duty ratio is 0.5
  • the open-loop control is performed.
  • the output voltage is 11kV
  • the load resistance 10k ⁇
  • the output power is 12.1kW.
  • Figure 18 is the waveform of the current i(L rp11 ) of the resonant inductor L rp11 of the two first positive resonance branches and the current i(L rp12 ) of the resonant inductor L rp12
  • Figure 19 is the waveform of the first negative module diodes D n11 and D n12 Current i(D n11 ) and i(D n12 ).
  • Figure 20 is the current i(L rp12 ), i(L rp22 ) and i of the resonant inductance L rp12 of the first positive resonant branch, the resonant inductance L rp22 of the second positive resonant branch and the resonant inductance L rp23 of the third positive resonant branch ( Lrp32 ).
  • Fig. 21 shows the voltage v( C rp12 ) , v( C rp22 ) and v (C rp32 ).
  • FIG. 22 shows the voltages v(C p1 ), v(C p2 ) and v(C p3 ) of the first positive module DC capacitor C p1 , the second positive module DC capacitor C p2 and the third positive module DC capacitor C p3 .
  • the resonant inductor currents of the positive resonant branch and the negative resonant branch with different serial numbers decrease sequentially, and the resonant inductor current amplitudes of the first, second and third resonant branches are 25A, 20A and 15A in sequence.
  • the DC component of the resonant capacitor voltage of the positive resonance branch and the negative resonance branch of different serial numbers is 1kV, and the AC component decreases successively.
  • the DC capacitor voltage of all passive sub-modules is 1kV, and the voltage ripple is less than 10V.
  • the resonant inductor current waveforms of the positive module and negative module of the same serial number are intermittent A sine wave with an amplitude of about 12A and opposite phases.
  • the diode currents in all positive and negative modules were discontinuous half-wave sinusoidal with an amplitude of approximately 2.3A.
  • the resonant inductor currents of the positive resonant branch and the negative resonant branch with different serial numbers decrease successively, and the resonant inductor current amplitudes of the first, second and third resonant branches are 12A, 9A and 7.5A in sequence.
  • the DC component of the resonant capacitor voltage of the positive resonance branch and the negative resonance branch of different serial numbers is 1kV, and the AC component decreases successively.
  • the DC capacitor voltage of all passive sub-modules is 1kV, and the voltage ripple is less than 1V.
  • Fig. 23 is a control block diagram taking a switched capacitor resonant voltage doubler rectifier converter using a half-bridge active sub-module and a passive sub-module as an example.
  • the output voltage is isolated and sampled to obtain the output voltage V o , which is subtracted from the reference value V ref and then enters the PI controller.
  • the PI controller outputs a driving signal with changing frequency.
  • the driving signal is obtained by the driving circuit to obtain the active sub- The switch signal of the module power switch tube.

Abstract

本发明公开了一种开关电容谐振倍压整流变换器及其控制方法、控制系统，通过有源子模块、正模块、负模块以及谐振支路的连接，使得有源子模块的输入功率可以通过多个正谐振支路顺次传递至所有正模块，也可以通过多个负谐振支路顺次传递至所有负模块。有源子模块、正模块和负模块的正负端口顺次连接实现高压输出。本发明无需高绝缘变压器，倍压级数可以任意扩展，所有开关管和二极管均可以实现软开关，可有效减小开关损耗，提高整流电路的效率。

Description

开关电容谐振倍压整流变换器及其控制方法、控制系统
交叉引用
本申请要求2021年7月27日提交的中国专利申请号202110852407.7的权益，所述申请以引用的方式整体并入本申请。
技术领域
本发明涉及一种整流变换器控制技术，特别是一种开关电容谐振倍压整流变换器及其控制方法、控制系统。
背景技术
在高压直流发生器、工业微波磁控管电源、医疗电源等低压输入高压输出场合，需要将数百伏的低压输入提升至数千伏或者数十千伏的高压输出。上述高压输出场合中常采用高升压比工频变压器方案或者采用倍压整流变换器方案实现。高升压比工频变压器相对容易制作，但是具有重量大、体积大，输出纹波大的缺点；传统倍压整流变换器需要具有一定绝缘电压的隔离变压器，隔离变压器的漏感与寄生电容会随着变压器绝缘电压的提高而增大。隔离变压器的高压侧往往采用绝缘层较厚的导线绕制，这大幅减小了变压器的窗口填充系数，从而制约了功率密度的提升。传统倍压整流变换器中的大部分二极管处于硬开关，这导致二极管在开关时有较大的尖峰，且二极管在换流过程中具有一定的损耗。因此在二极管选型时需要采用更高电压等级的型号，运行时需要考虑添加散热器等。而且二极管的寄生电容会影响到变压器原边的开关管运行，可能造成原边功率开关管波形畸变或者硬开关等情况。
发明内容
本发明所要解决的技术问题是，针对现有技术不足，提供一种开关电容谐振倍压整流变换器及其控制方法、控制系统，避免使用高绝缘变压器，提高变换器功率密度和效率。
为解决上述技术问题，本发明所采用的技术方案是：一种开关电容谐振倍压整流变换器，包括串联的m个正模块、串联的n个负模块；第一个正模块、第一个负模块分别与有源子模块的负端、正端连接；第i个正模块与第i个、第i+1个正谐振支路连接；第j个负模块与第j个、第j+1个负谐振支路连接；第m个正模块与第m个正谐振支路连接；第n个负模块与第n个负谐振支路连接；所述有源子模块与第一个正谐振支路、第一个负谐振支路连接；第m个正模块的正端作为输出电压的正端；第n个负模块的负 端作为输出电压的负端；其中，m和n为正整数；i＝1，2，…，m-1；j＝1，2，…，n-1；所述正模块、负模块均采用无源子模块。
本发明通过有源子模块、正模块、负模块以及谐振支路的连接，使得有源子模块的输入功率可以通过多个正谐振支路顺次传递至第一正模块、第二正模块、直至第m正模块，也可以通过多个负谐振支路顺次传递至第一负模块、第二负模块、直至第n负模块。有源子模块、正模块和负模块的正负端口顺次连接实现高压输出。
本发明的变换器中，有源子模块向正模块和负模块顺序传输功率。正模块和负模块结构相同，可采用相同的电路板进行拼接，这大大降低了电路设计的复杂度，提高了变换器的模块化和功率密度。另一方面，由于采用了多个谐振支路，每个正模块和负模块中的二极管均可实现软开关，大幅提高了变换器的功率密度和效率。
m，n可以根据所需要的升压倍数选取，在升压倍数确定后，m和n尽量取接近的值，m和n相等时最优。在m和n相等时，正模块和负模块数量相等，不同对应序号的正负模块之间的功率传输和电压电流应力相同，变换器对称性最好。
所述有源子模块采用全桥逆变电路或半桥逆变电路。可以针对特定的场合选择合适的有源子模块拓扑结构。在小电流场合可以采用半桥逆变结构减少功率开关管的使用，在大电流场合可以采用全桥逆变结构。
所述无源子模块为半桥整流电路或者全桥整流电路。
半桥整流电路包含两个二极管和一个直流电容，适合于小功率场合应用；全桥整流电路包含四个二极管和一个直流电容，适合于大功率场合应用。
所述正谐振支路、负谐振支路均包括谐振电容和与所述谐振电容串联的谐振电感。谐振电容与谐振电感的串联频率为f r。谐振支路结构简单，进一步优化了变换器的结构。
本发明还提供了一种上述开关电容谐振倍压整流变换器的控制方法，包括：
当开关电容谐振倍压整流变换器运行在开环模式(即开关电容谐振倍压整流变换器的开关频率不随着输出电压的改变而改变)时：
若有源子模块为半桥逆变电路，则有源子模块的两个开关管互补导通；
若有源子模块为全桥逆变电路，则有源子模块第一桥臂的两个功率开关管互补导通，第二桥臂的两个功率开关管互补导通，第一桥臂两个功率开关管开关信号相同，第二桥臂两个功率开关管开关信号相同；
当开关电容谐振倍压整流变换器运行在闭环模式(即开关电容谐振倍压整流变换器的开关频率随着输出电压的改变而改变)时：将开关电容谐振倍压整流变换器输出电 压的参考值Vref与采样得到的输出电压Vo作差后，对差值进行PI调制，得到驱动信号，利用所述驱动信号控制有源子模块功率开关管的通断。
开关电容谐振倍压整流变换器运行在闭环模式时控制方法简单，只需要进行隔离采样即可。由于变换器没有采用输入并联输出串联的结构，有源子模块和多个无源子模块中的直流电容之间为串联关系，因此变换器在输出电压采样是不需要高压绝缘处理，隔离采样不需要高压隔离的隔离放大器，提高了变换器功率密度和效率。当开关电容谐振倍压整流变换器运行在开环模式时，有源子模块功率开关管的开关频率fs与正谐振支路/负谐振支路串联谐振频率fr相同。
开关电容谐振倍压整流变换器运行在开环模式时无需额外控制方法，即可实现所有直流电压自然均衡以及所有开关管的软开关。即本发明可以实现所有二极管软开关，且二极管寄生电容不会影响到原边开关管运行。
本发明还提供了一种开关电容谐振倍压整流变换器的控制系统，其包括控制器；所述控制器被配置或编程为用于执行本发明控制方法的步骤；所述控制器的输出控制信号输入到开关电容谐振倍压整流变换器有源子模块的功率开关管的门极。
与现有技术相比，本发明所具有的有益效果为：
1、本发明采用模块化技术，将无源子模块和谐振支路均可作为模块化组件，通过模块化组件的拼接可以实现任意级数的谐振倍压整流变换器。
2、本发明无需高绝缘变压器即可实现高变比升压，降低了变换器成本，降低了变换器体积，提高了变换器功率密度。
3、本发明通过开关电容谐振倍压整流技术，每个无源子模块均可以产生与有源子模块输入电压相同的电压，无源子模块输出串联，从而可以在不使用变压器的情况下极大的抬升输出电压。多个谐振支路为有源子模块的功率开关管和无源子模块的二极管提供了软开关条件，使得有源子模块和无源子模块的开关损耗大幅减少，从而使得倍压谐振电路的功率密度和效率大幅提高。
4、本发明可实现所有功率开关管和二极管的软开关，且二极管寄生电容不会影响功率开关管的运行情况，降低了变换器损耗，提高了变换器效率。
附图说明
图1为开关电容谐振倍压整流变换器电路结构框图；
图2为有源子模块结构1的拓扑结构图，图3为有源子模块结构2的拓扑结构图，图4为无源子模块结构1的拓扑结构图，图5为无源子模块结构2的拓扑结构图，图6 为谐振支路拓扑结构图；
图7为有源子模块采用半桥逆变结构，无源子模块也相应采用半桥整流结构的开关电容谐振倍压整流变换器实施方案，图8为在S 1断开，S 2闭合时，变换器的等效电路，图9为在S 1闭合，S 2断开时，变换器的等效电路；
图10为有源子模块采用全桥逆变结构，无源子模块也相应采用全桥整流结构的开关电容谐振倍压整流变换器实施方案；
图11为在S 1与S 4断开，S 2与S 3闭合时，变换器的等效电路；
图12为在S 1与S 4闭合，S 2与S 3断开时，变换器的等效电路；
图13为图7所示采用半桥有源子模块和无源子模块且m＝5，n＝5时的第一正模块和第一负模块谐振电流仿真波形；
图14为图7所示采用半桥有源子模块和无源子模块且m＝5，n＝5时的第一正模块和第一负模块中二极管电流仿真波形；
图15为图7所示采用半桥有源子模块和无源子模块且m＝5，n＝5时的第一正模块、第二正模块以及第三正模块谐振电流仿真波形；
图16为图7所示采用半桥有源子模块和无源子模块且m＝5，n＝5时的第一正模块、第二正模块以及第三正模块谐振电容电压仿真波形；
图17为图7所示采用半桥有源子模块和无源子模块且m＝5，n＝5时的第一正模块、第二正模块以及第三正模块直流电容电压仿真波形；
图18为图7所示采用全桥有源子模块和无源子模块且m＝5，n＝5时的第一正模块和第一负模块谐振电流仿真波形；
图19为图7所示采用全桥有源子模块和无源子模块且m＝5，n＝5时的第一正模块和第一负模块中二极管电流仿真波形；
图20为图7所示采用全桥有源子模块和无源子模块且m＝5，n＝5时的第一正模块、第二正模块以及第三正模块谐振电流仿真波形；
图21为图7所示采用全桥有源子模块和无源子模块且m＝5，n＝5时的第一正模块、第二正模块以及第三正模块谐振电容电压仿真波形；
图22为图7所示采用全桥有源子模块和无源子模块且m＝5，n＝5时的第一正模块、第二正模块以及第三正模块直流电容电压仿真波形；
图23为以采用半桥有源子模块和无源子模块的开关电容谐振倍压整流变换器为例的控制框图。
具体实施方式
本发明实施例1开关电容谐振倍压整流变换器结构如图1所示，开关电容谐振倍压整流变换器由一个有源子模块，m个正模块、n个负模块(正模块与负模块结构一致，统称为无源子模块)、以及m个正谐振支路与n个负谐振支路(正谐振支路与负谐振支路结构一致，统称为谐振支路)构成。其中，m和n为正整数，m和n可以相等也可以不相等。有源子模块有正负端口(+/-)和交流端口(AC或者AC 1/AC 2)，无源子模块有正负端口(+/-)和交流端口(AC或者AC 1/AC 2)，谐振支路有交流端口(AC 1/AC 2)。有源子模块的正端口与第一正模块的负端口相连，第一正模块的正端口与第二正模块的负端口相连，第m-1正模块的正端口与第m正模块的负端口相连，第m正模块的正端口作为变换器输出电压正端口，有源子模块的负端口与第一负模块的正端口相连，第二负模块的正端口与第一负模块的负端口相连，第n-1负模块的负端口与第n负模块的正端口相连，第n负模块的负端口作为变换器输出电压负端口。谐振支路通过交流端口连接于相邻的有源子模块与正模块、有源子模块与负模块、相邻的正模块、以及相邻的负模块之间。
本发明特别之处在于通过有源子模块、正模块、负模块以及谐振支路的连接，使得有源子模块的输入功率可以通过多个正谐振支路顺次传递至第一正模块、第二正模块、直至第m正模块，也可以通过多个负谐振支路顺次传递至第一负模块、第二负模块、直至第n负模块。有源子模块、正模块和负模块的正负端口顺次连接实现高压输出。
图1所述的有源子模块、无源子模块和谐振支路如图2至图6所示，有源子模块可以为结构1(半桥逆变结构，图2)，也可以为结构2(全桥逆变结构，图3)。无源子模块可以为结构1(半桥整流结构，图4)，也可以是结构2(全桥整流结构，图5)等。有源子模块由功率开关管和直流电容组成。功率开关管可以是IGBT、MOSFET、IGCT或GTO。半桥逆变结构包括第一功率开关管S 1、第二功率开关管S 2。第一功率开关管和第二功率开关管串联后与直流电容C 0并联，直流电容的正负两端分别作为有源子模块的正负端，两个功率开关管串联的中点作为交流端口AC。全桥逆变结构包括四个功率开关管S 1、S 2、S 3、S 4(对应第一～第四功率开关管)，第一功率开关管和第二功率开关管串联连接组成第一桥臂，第三功率开关管和第四功率开关管串联连接组成第二桥臂，两个桥臂并联后与直流电容C 0并联，直流电容的正负两端分别作为有源子模块的正负端，第一桥臂的中点作为交流端口AC 1，第二桥臂的中点作为交流端口AC 2。无源子模块由二极管和直流电容组成。半桥整流结构包括第一二极管D 1、第二二极管D 2。第一 二极管和第二二极管串联后与直流电容C 1并联，直流电容的正负两端分别作为无源子模块的正负端，两个二极管串联的中点作为交流端口AC。全桥整流结构包括四个二极管D 1、D 2、D 3、D 4(对应第一～第四二极管)，第一二极管和第二二极管串联连接组成第一桥臂，第三二极管和第四二极管串联连接组成第二桥臂，两个桥臂并联后与直流电容C 1并联，直流电容的正负两端分别作为无源子模块的正负端，第一桥臂的中点作为交流端口AC 1，第二桥臂的中点作为交流端口AC 2。谐振支路包括谐振电容C r和谐振电感L r，谐振电感的一端与谐振电容相连，另一端作为交流端口AC 1，谐振电容的另一端作为交流端口AC 2。
以图1所示的开关电容谐振倍压整流变换器，有源子模块采用半桥逆变结构和全桥逆变结构、无源子模块也相应采用半桥整流结构和全桥整流结构为例，介绍本发明实施例1的工作原理：
有源子模块采用半桥逆变结构，无源子模块也相应采用半桥整流结构的实施例如图7所示，有源子模块直流电容为C 0，S 1和S 2为两个功率开关管MOSFET，第一～第m正模块的二极管和直流电容分别为D p11,D p12…D pm1,D pm2和C p1,C p2…C pm。第一～第n负模块的二极管和直流电容分别为D n11,D n12…D nn1,D nn2和C n1,C n2…C nn。与有源子模块和正模块相连的谐振支路中的谐振电容和谐振电感分别为C rp1,C rp2…C rpm和L rp1,L rp2…L rpm。与有源子模块和负模块相连的谐振支路中的谐振电容和谐振电感分别为C rn1,C rn2…C rnn和L rn1,L rn2…L rnn。
在S 1断开，S 2闭合时，变换器的等效电路如图8所示。在图8中，箭头方向为电流流向，在这个过程中，D p11,D p21…D pm1与D n12,D n22…D nn2导通，D p12,D p22…D pm2与D n11,D n21…D nn1截止。C rp1与L rp1、C rp2与L rp2、…C rpm与L rpm串联谐振，电流方向为从右向左；C rn1与L rn1、C rn2与L rn2、…C rnn与L rnn串联谐振，电流方向也为从右向左。
在S 1闭合，S 2断开时，变换器的等效电路如图9所示。在图9中，箭头方向为电流流向，在这个过程中，D p12,D p22…D pm2与D n11,D n21…D nn1导通，D p11,D p21…D pm1与D n12,D n22…D nn2截止。C rp1与L rp1、C rp2与L rp2、…C rpm与L rpm串联谐振，电流方向为从左向右；C rn1与L rn1、C rn2与L rn2、…C rnn与L rnn串联谐振，电流方向也为从左向右。
有源子模块采用全桥逆变结构，无源子模块也相应采用全桥整流结构的实施例如图10所示，有源子模块直流电容为C 0，S 1、S 2、S 3和S 4为四个功率开关管MOSFET，第一～第m正模块的二极管和直流电容分别为D p11,D p12,D p13,D p14…D pm1,D pm2,D pm3,D pm4和C p1,C p2…C pm。第一～第n负模块的二极管和直流电容分别为D n11,D n12,D n13,D n14… D nn1,D nn2,D nn3,D nn4和C n1,C n2…C nn。与有源子模块和正模块相连的谐振支路中的谐振电容和谐振电感分别为C rp11,C rp12,C rp21,C rp22…C rpm1,C rpm2和L rp11,L rp12,L rp21,L rp22…L rpm1,L rpm2。与有源子模块和负模块相连的谐振支路中的谐振电容和谐振电感分别为C rn11,C rn12,C rn21,C rn22…C rnn1,C rnn2和L rn11,L rn12,L rn21,L rn22…L rnn1,L rnn2。
在S 1与S 4断开，S 2与S 3闭合时，变换器的等效电路如图11所示。在图11中，箭头方向为电流流向，在这个过程中，D p12,D p13,D p22,D p23…D pm2,D pm3与D n12,D n13,D n22,D n23…D nn2,D nn3导通，D p11,D p14,D p21,D p24…D pm1,D pm4与D n11,D n14,D n21,D n24…D nn2,D nn3截止。C rp11与L rp11、C rp21与L rp21、…C rpm1与L rpm1串联谐振，电流方向为从左向右；C rp12与L rp12、C rp22与L rp22、…C rpm2与L rpm2串联谐振，电流方向为从右向左；C rn11与L rn11、C rn21与L rn21、…C rnn1与L rnn1串联谐振，电流方向也为从右向左；C rn12与L rn12、C rn22与L rn22、…C rnn2与L rnn2串联谐振，电流方向也为从左向右。
在S 1与S 4闭合，S 2与S 3断开时，变换器的等效电路如图12所示。在图12中，箭头方向为电流流向，在这个过程中，，D p11,D p14,D p21,D p24…D pm1,D pm4与D n11,D n14,D n21,D n24…D nn2,D nn3导通，D p12,D p13,D p22,D p23…D pm2,D pm3与D n12,D n13,D n22,D n23…D nn2,D nn3截止。C rp11与L rp11、C rp21与L rp21、…C rpm1与L rpm1串联谐振，电流方向为从右向左；C rp12与L rp12、C rp22与L rp22、…C rpm2与L rpm2串联谐振，电流方向为从左向右；C rn11与L rn11、C rn21与L rn21、…C rnn1与L rnn1串联谐振，电流方向也为从左向右；C rn12与L rn12、C rn22与L rn22、…C rnn2与L rnn2串联谐振，电流方向也为从右向左。
本发明实施例2控制方法如下：
当所述开关电容谐振倍压整流变换器运行在开环模式中，所有功率开关管频率f s与串联谐振频率f r相同，满占空比运行；此时所述开关电容谐振倍压整流变换器工作在串联谐振点，可实现所有功率开关管和高频整流二极管的软开关。
当所述开关电容谐振倍压整流变换器运行在开环模式中，在有源子模块为半桥逆变结构时，功率开关管S 1、S 2互补导通；在有源子模块为全桥逆变结构时，功率开关管S 1、S 2互补导通，功率开关管S 3、S 4互补导通，S 1与S 3开关信号相同、S 2与S 4开关信号相同。当所述开关电容谐振倍压整流变换器运行在闭环模式时，将设定的开关电容谐振倍压整流变换器输出电压的参考值V ref与采样得到的输出电压V o作差后送入PI控制器，PI控制器输出频率变化的驱动信号，该驱动信号通过驱动电路得到有源子模块功率开关管的开关信号。可以通过开关管频率f s调节振倍压整流变换器的输出电压，开关管频率f s升高时，输出电压降低；开关管频率f s降低时，输出电压升高。
当所述开关电容谐振倍压整流变换器运行在闭环模式时，通过将输出端口电压的参考值V ref与采样得到的输出端口电压V o作差后送入PI控制器(即进行PI调制)，对差值进行PI调制，得到驱动信号，利用所述驱动信号控制有源子模块功率开关管的通断。在变频控制中，功率开关管频率f s可以小于串联谐振频率f r也可以大于串联谐振频率f r。当功率开关管频率f s大于串联谐振频率f r时，输出电压降低，当功率开关管频率f s小于串联谐振频率f r时，输出电压升高。在不同负载以及不同的V ref情况下，控制器可以通过输出电压闭环控制实现输出电压的无静差跟踪。
图13至图17为图7所示采用半桥有源子模块和无源子模块且m＝5，n＝5时的仿真波形，仿真参数设计如下：
输入电压V in＝1kV，直流电容的容值大小为9μF，谐振电感为L r＝11μH，谐振电容为C r＝162nF。功率开关管S 1与S 2的开关频率为100kHz，占空比为0.5，开环控制。输出电压为11kV，负载电阻为10kΩ，输出功率为12.1kW。
图13为第一正谐振支路谐振电感L rp1的电流i(L rp1)和第一负谐振支路谐振电感L rn1的电流i(L rn1)波形，图14为第一正模块二极管D p11和D p12的电流i(D p11)和i(D p12)。图15为第一正谐振支路谐振电感L rp1、第二正谐振支路谐振电感L rp2和第三正谐振支路谐振电感L rp3的电流i(L rp1)、i(L rp2)和i(L rp3)。图16为第一正谐振支路谐振电容C rp1、第二正谐振支路谐振电容C rp2和第三正谐振支路谐振电容C rp3的电压v(C rp1)、v(C rp2)和v(C rp3)。图17为第一正模块直流电容C p1、第二正模块直流电容C p2和第三正模块直流电容C p3的电压v(C p1)、v(C p2)和v(C p3)。
图18至图22为图10所示采用全桥有源子模块和无源子模块且m＝5，n＝5时的仿真波形，仿真参数设计如下：
输入电压V in＝1kV，直流电容的容值大小为9μF，谐振电感为L r＝11μH，谐振电容为C r＝162nF。功率开关管S 1、S 2、S 3与S 4的开关频率为100kHz，占空比为0.5，开环控制。输出电压为11kV，负载电阻为10kΩ，输出功率为12.1kW。
图18为两个第一正谐振支路谐振电感L rp11的电流i(L rp11)和谐振电感L rp12的电流i(L rp12)波形，图19为第一负模块二极管D n11和D n12的电流i(D n11)和i(D n12)。图20为第一正谐振支路谐振电感L rp12、第二正谐振支路谐振电感L rp22和第三正谐振支路谐振电感L rp23的电流i(L rp12)、i(L rp22)和i(L rp32)。图21为第一正谐振支路谐振电容C rp12、第二正谐振支路谐振电容C rp22和第三正谐振支路谐振电容C rp32的电压v(C rp12)、v(C rp22)和v(C rp32)。图22为第一正模块直流电容C p1、第二正模块直流电容C p2和第三正模块直流电容C p3 的电压v(C p1)、v(C p2)和v(C p3)。
从图13至图17可以看出，在采用半桥有源子模块和无源子模块的开关电容谐振倍压整流变换器中，同一序号的正模块和负模块的谐振电感电流波形均为断续正弦波，幅值约为25A，相位相反。所有的正模块和负模块中的二极管电流均为断续半波正弦且幅值约为2.3A。不同序号的正谐振支路和负谐振支路谐振电感电流依次递减，第一、第二、第三谐振支路谐振电感电流幅值依次为25A、20A以及15A。不同序号的正谐振支路和负谐振支路谐振电容电压直流分量均为1kV，交流分量依次递减。所有无源子模块的直流电容电压均为1kV，电压纹波小于10V。
从图18至图22可以看出，在采用全桥有源子模块和无源子模块的开关电容谐振倍压整流变换器中，同一序号的正模块和负模块谐振电感电流波形均为断续正弦波，幅值约为12A，相位相反。所有的正模块和负模块中的二极管电流均为断续半波正弦且幅值约为2.3A。不同序号的正谐振支路和负谐振支路谐振电感电流依次递减，第一、第二、第三谐振支路谐振电感电流幅值依次为12A、9A以及7.5A。不同序号的正谐振支路和负谐振支路谐振电容电压直流分量均为1kV，交流分量依次递减。所有无源子模块的直流电容电压均为1kV，电压纹波小于1V。
图23为以采用半桥有源子模块和无源子模块的开关电容谐振倍压整流变换器为例的控制框图。在图23中，输出电压通过隔离采样后得到输出电压V o，与参考值V ref相减后进入PI控制器，PI控制器输出频率变化的驱动信号，该驱动信号通过驱动电路得到有源子模块功率开关管的开关信号。

Claims (8)

  1. 一种开关电容谐振倍压整流变换器，其特征在于，包括串联的m个正模块、串联的n个负模块；第一个正模块、第一个负模块分别与有源子模块的负端、正端连接；第i个正模块与第i个、第i+1个正谐振支路连接；第j个负模块与第j个、第j+1个负谐振支路连接；第m个正模块与第m个正谐振支路连接；第n个负模块与第n个负谐振支路连接；所述有源子模块与第一个正谐振支路、第一个负谐振支路连接；第m个正模块的正端作为输出电压的正端；第n个负模块的负端作为输出电压的负端；其中，m和n为正整数；i＝1，2，…，m-1；j＝1，2，…，n-1；所述正模块、负模块均采用无源子模块。
  2. 根据权利要求1所述的开关电容谐振倍压整流变换器，其特征在于，所述有源子模块采用全桥逆变电路或半桥逆变电路。
  3. 根据权利要求1或2所述的开关电容谐振倍压整流变换器，其特征在于，所述无源子模块为半桥整流电路或者全桥整流电路。
  4. 根据权利要求1～3之一所述的开关电容谐振倍压整流变换器，其特征在于，所述正谐振支路、负谐振支路均包括谐振电容和与所述谐振电容串联的谐振电感。
  5. 根据权利要求1～4之一所述的开关电容谐振倍压整流变换器，其特征在于，m＝n。
  6. 一种权利要求1～5之一所述开关电容谐振倍压整流变换器的控制方法，其特征在于，包括：
    当开关电容谐振倍压整流变换器运行在开环模式时：
    若有源子模块为半桥逆变电路，则有源子模块的两个开关管互补导通；
    若有源子模块为全桥逆变电路，则有源子模块第一桥臂的两个功率开关管互补导通，第二桥臂的两个功率开关管互补导通，第一桥臂两个功率开关管开关信号相同，第二桥臂两个功率开关管开关信号相同；
    当开关电容谐振倍压整流变换器运行在闭环模式时：将开关电容谐振倍压整流变换器输出电压的参考值Vref与采样得到的输出电压Vo作差后，对差值进行PI调制，得到驱动信号，利用所述驱动信号控制有源子模块功率开关管的通断。
  7. 根据权利要求6所述的方法，其特征在于，当开关电容谐振倍压整流变换器运行在开环模式时，有源子模块功率开关管的开关频率fs与正谐振支路/负谐振支路串联谐振频率fr相同。
  8. 一种开关电容谐振倍压整流变换器的控制系统，其特征在于，其包括处理器和存储器；所述处理器用于执行所述存储器中存储的计算机程序；所述计算机程序被配置为用于执行权利要求6或7所述方法的步骤；所述控制器的输出控制信号输入到开关电容谐振倍压整流变换器有源子模块的功率开关管的门极。
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