WO2022176065A1 - 直流電源装置、モータ駆動装置、及び冷凍サイクル適用機器 - Google Patents

直流電源装置、モータ駆動装置、及び冷凍サイクル適用機器 Download PDF

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Publication number
WO2022176065A1
WO2022176065A1 PCT/JP2021/005939 JP2021005939W WO2022176065A1 WO 2022176065 A1 WO2022176065 A1 WO 2022176065A1 JP 2021005939 W JP2021005939 W JP 2021005939W WO 2022176065 A1 WO2022176065 A1 WO 2022176065A1
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Prior art keywords
switching element
state
power supply
capacitor
duty
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PCT/JP2021/005939
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English (en)
French (fr)
Japanese (ja)
Inventor
裕一 清水
和徳 畠山
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Mitsubishi Electric Corp
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Mitsubishi Electric Corp
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Priority to US18/256,799 priority Critical patent/US20240097576A1/en
Priority to CN202180093040.3A priority patent/CN116941174A/zh
Priority to PCT/JP2021/005939 priority patent/WO2022176065A1/ja
Priority to JP2023500186A priority patent/JP7442729B2/ja
Publication of WO2022176065A1 publication Critical patent/WO2022176065A1/ja
Anticipated expiration legal-status Critical
Ceased legal-status Critical Current

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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0067—Converter structures employing plural converter units, other than for parallel operation of the units on a single load
    • H02M1/007—Plural converter units in cascade
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M5/00—Conversion of AC power input into AC power output, e.g. for change of voltage, for change of frequency, for change of number of phases
    • H02M5/40—Conversion of AC power input into AC power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into DC
    • H02M5/42—Conversion of AC power input into AC power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into DC by static converters
    • H02M5/44—Conversion of AC power input into AC power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into DC by static converters using discharge tubes or semiconductor devices to convert the intermediate DC into AC
    • H02M5/453—Conversion of AC power input into AC power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into DC by static converters using discharge tubes or semiconductor devices to convert the intermediate DC into AC using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M5/458—Conversion of AC power input into AC power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into DC by static converters using discharge tubes or semiconductor devices to convert the intermediate DC into AC using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0048—Circuits or arrangements for reducing losses
    • H02M1/0054—Transistor switching losses
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/14—Arrangements for reducing ripples from DC input or output
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of DC power input into DC power output
    • H02M3/02—Conversion of DC power input into DC power output without intermediate conversion into AC
    • H02M3/04—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters
    • H02M3/10—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/156—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
    • H02M3/158—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of AC power input into DC power output; Conversion of DC power input into AC power output
    • H02M7/02—Conversion of AC power input into DC power output without possibility of reversal
    • H02M7/04—Conversion of AC power input into DC power output without possibility of reversal by static converters
    • H02M7/06—Conversion of AC power input into DC power output without possibility of reversal by static converters using discharge tubes without control electrode or semiconductor devices without control electrode
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of AC power input into DC power output; Conversion of DC power input into AC power output
    • H02M7/42—Conversion of DC power input into AC power output without possibility of reversal
    • H02M7/44—Conversion of DC power input into AC power output without possibility of reversal by static converters
    • H02M7/48—Conversion of DC power input into AC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode

Definitions

  • the present disclosure relates to a DC power supply device, a motor drive device, and a refrigeration cycle application device.
  • a DC power supply device has been proposed (see, for example, Patent Document 1).
  • the control unit controls the charging circuit to maintain a state in which the two capacitors connected in series are alternately charged, thereby realizing a boosting mode in which the output voltage between the output terminals is boosted, and controls the charging circuit.
  • a full-wave rectification mode is realized by keeping the two capacitors connected in series charged at the same time.
  • the total capacitance of two capacitors connected in series is smaller than the capacitance of one capacitor.
  • the sum of the capacitances of the two capacitors connected in series is half the capacitance of one capacitor. Therefore, in the above-described conventional DC power supply, ripples in the output voltage between the output terminals may increase during the period of the full-wave rectification mode. An increase in ripple causes an increase in power supply harmonics and a decrease in power factor, which may reduce the efficiency of the DC power supply.
  • the present disclosure has been made to solve the above problems, and includes a DC power supply device capable of suppressing an increase in ripple of an output voltage, a motor drive device having the DC power supply device, and the motor drive device.
  • An object of the present invention is to provide a refrigeration cycle application equipment.
  • a DC power supply device of the present disclosure includes a rectifier circuit that rectifies an alternating current, a reactor connected to the rectifier circuit, and a first capacitor connected in series between output terminals of the DC generated by the rectifier circuit and the reactor. and a second capacitor; a first switching element that charges the first capacitor when in an off state and uncharges the first capacitor when in an on state; a second switching element that brings the second capacitor into a charged state at a certain time and brings the second capacitor into a non-charged state when in an ON state; and each of the first and second switching elements. a control unit for controlling a switching operation, wherein the control unit maintains one switching element of the first and second switching elements in an off state and switches the other switching element of the first and second switching elements.
  • the device has a full wave rectification mode, which is a mode of operation in which the device is PWM controlled.
  • FIG. 1 is a diagram showing a configuration example of a DC power supply device according to Embodiment 1;
  • FIG. 2 is a diagram showing the relationship between the states of first and second switching elements of the charging circuit of the DC power supply device shown in FIG. 1 and current paths;
  • FIG. 2 is a diagram showing an example of operation modes of the DC power supply device shown in FIG. 1;
  • FIG. 1 When the DC power supply shown in FIG. 1 is operated in the full-wave rectification mode (comparative example) of FIG. and waveforms of voltages detected by the second detector.
  • the DC power supply shown in FIG. 1 is operated in the full-wave rectification mode (comparative example) of FIG. and another example of voltage waveforms detected by the second detector.
  • FIG. 3A is a diagram showing an example of an operation mode of the DC power supply according to Embodiment 1
  • FIG. 3B is a diagram showing an example of an operation mode of the DC power supply according to Embodiment 2
  • FIG. Input current to the rectifier circuit, output voltage detected by the third detector, and detected by the first and second detectors when the DC power supply according to Embodiment 1 is operated in full-wave rectification mode 3 shows examples of waveforms of the applied voltage, load, and on-duty of the first switching element. 8 shows waveforms of the input current shown in FIG.
  • FIG. 10 is a diagram showing an example of operation modes of a DC power supply device according to Embodiment 3; Input current to the rectifier circuit, output voltage detected by the third detector, and detected by the first and second detectors when the DC power supply according to Embodiment 3 is operated in full-wave rectification mode 3 shows examples of waveforms of the applied voltage, load, and on-duty of the second switching element.
  • FIG. 11 is a diagram showing a configuration example of a DC power supply device according to Embodiment 5; FIG.
  • FIG. 11 is a diagram showing a configuration example of a DC power supply device, a motor drive device, and a refrigeration cycle application device according to Embodiment 6; 14 is a flow chart showing an operation example of switching an energization pattern of the DC power supply device according to Embodiment 6.
  • FIG. The input current to the rectifier circuit, the output voltage detected by the third detection unit, the voltage detected by the first and second detection units when switching the energization pattern of the DC power supply according to Embodiment 6, 3 shows examples of on-duty waveforms of a load and a first switching element.
  • the input current to the rectifier circuit, the output voltage detected by the third detection unit, the voltage detected by the first and second detection units when switching the energization pattern of the DC power supply according to Embodiment 6, 3 shows another example of on-duty waveforms of the load and the first switching element.
  • the input current to the rectifier circuit, the output voltage detected by the third detection unit, the voltage detected by the first and second detection units when switching the energization pattern of the DC power supply according to Embodiment 6, 3 shows another example of on-duty waveforms of the load and the first switching element.
  • a DC power supply device according to an embodiment, a motor drive device having the DC power device, and a refrigeration cycle application device having the motor drive device will be described below with reference to the drawings.
  • the following embodiments are merely examples, and the embodiments can be combined as appropriate and each embodiment can be modified as appropriate.
  • the same reference numerals are given to the same or similar configurations.
  • FIG. 1 is a diagram showing a configuration example of a DC power supply device 101 according to Embodiment 1.
  • the DC power supply 101 converts the AC supplied from the AC power supply 1 to DC and supplies the DC to the load circuit 8 from the output terminals (that is, the connection points 6d and 6e). It is configured.
  • the load circuit 8 is, for example, an inverter that drives a compressor motor used in a refrigeration cycle device (refrigeration cycle device 301 described in Embodiment 6 below). Refrigeration cycle devices are used in air conditioners, heat pump water heaters, refrigerators, freezers, and the like. Note that the load circuit 8 is not limited to an inverter.
  • the DC power supply device 101 includes a rectifier circuit 2 that rectifies an alternating current (for example, a three-phase alternating current in FIG. 1), a reactor 3 connected to the rectifier circuit 2, and a DC output terminal generated by the rectifier circuit 2 and the reactor 3. (that is, connection points 6d and 6e) are provided with a first capacitor 6a and a second capacitor 6b connected in series.
  • a rectifier circuit 2 that rectifies an alternating current (for example, a three-phase alternating current in FIG. 1)
  • a reactor 3 connected to the rectifier circuit 2
  • a DC output terminal generated by the rectifier circuit 2 and the reactor 3. that is, connection points 6d and 6e
  • connection points 6d and 6e are provided with a first capacitor 6a and a second capacitor 6b connected in series.
  • the DC power supply device 101 includes a first switching element 4a that charges the first capacitor 6a when it is in the OFF state and a non-charged state when it is in the ON state; a second switching element 4b that brings the second capacitor 6b into a charged state when it is in the ON state and brings the second capacitor 6b into a non-charged state when it is in the ON state; the first and second switching elements 4a; and a control unit 10 for controlling each switching operation of 4b.
  • the DC power supply device 101 also includes a voltage detection unit 7 that is a voltage detection circuit that detects the output voltage V dc [V] between the output terminals (that is, the connection points 6d and 6e).
  • the first capacitor 6a and the second capacitor 6b form a charging circuit 9.
  • the reactor 3 is connected to the output side of the rectifier circuit 2 in FIG. 1
  • the reactor 3 may be connected to each phase on the input side of the rectifier circuit 2 .
  • the control unit 10 maintains one of the first and second switching elements 4a and 4b in an off state, and the other of the first and second switching elements 4a and 4b is PWM (Pulse Width Modulation). It has a controlled mode of operation, full-wave rectification mode. Further, the control unit 10 has a step-up mode, which is an operation mode for PWM-controlling each of the first and second switching elements 4a and 4b.
  • the voltage detection unit 7 includes a first detection unit 7a that detects the voltage V pc [V] of the first capacitor 6a and a second detection unit 7b that detects the voltage V nc [V] of the second capacitor 6b. and a third detector 7c for detecting an output voltage V dc [V], which is the voltage between the positive electrode of the first capacitor 6a and the negative electrode of the second capacitor 6b.
  • the voltage detection unit 7 may include any two of the first detection unit 7a, the second detection unit 7b, and the third detection unit 7c. . In other words, if the voltage detection unit 7 includes two or more detection units among the first detection unit 7a, the second detection unit 7b, and the third detection unit 7c, the voltage V pc [V] , V nc [V] and the output voltage V dc [V] can be obtained.
  • the charging circuit 9 includes a first switching element 4a that switches the first capacitor 6a between the charged state and the non-charged state, and a second switching element 4b that switches the second capacitor 6b between the charged state and the non-charged state.
  • a first backflow prevention element 5a that prevents the charge in the first capacitor 6a from flowing back to the first switching element 4a, and the charge in the second capacitor 6b is transferred to the second switching element 4b.
  • a second backflow prevention element 5b for preventing backflow.
  • the midpoint 4c of the series circuit formed by the first switching element 4a and the second switching element 4b is the midpoint 6c of the series circuit formed by the first capacitor 6a and the second capacitor 6b. It is connected to the. Between the collector 4d of the first switching element 4a, the first capacitor 6a, the load circuit 8 and the connection point 6d, a connection from the collector 4d of the first switching element 4a to the first capacitor 6a and the load circuit 8 is provided.
  • a first backflow prevention element 5a which is a diode whose forward direction is toward the point 6d, is connected.
  • a second switching element is connected from the connection point 6e between the second capacitor 6b and the load circuit 8 to the second switching element.
  • a second backflow prevention element 5b which is a diode whose forward direction is directed toward the emitter 4e of 4b, is connected.
  • capacitors with the same capacitance are used as the first capacitor 6a and the second capacitor 6b.
  • a semiconductor switching device such as a power transistor, a power MOSFET (Power Metal-Oxide-Semiconductor Field-Effect Transistor), or an IGBT (Insulated Gate Bipolar Transistor) elements may be used.
  • freewheeling diodes (not shown) may be connected in parallel to the semiconductor switching elements for the purpose of suppressing surge voltages caused by switching. good.
  • the freewheeling diode may be a parasitic diode of the semiconductor switching element.
  • the semiconductor switching element is a MOSFET, it is possible to realize a function similar to that of a freewheeling diode by turning on the semiconductor switching element at the timing of freewheeling.
  • a material constituting the semiconductor switching element is, for example, silicon (Si).
  • the material forming the semiconductor switching element is not limited to Si, and may be a material forming a wide bandgap semiconductor.
  • Wide bandgap semiconductors are composed of, for example, silicon carbide (SiC), gallium nitride (GaN), gallium oxide (Ga 2 O 3 ), or diamond.
  • SiC silicon carbide
  • GaN gallium nitride
  • Ga 2 O 3 gallium oxide
  • diamond diamond
  • the control unit 10 controls the output voltage V dc [V], which is a DC voltage supplied to the load circuit 8, by on/off controlling the first switching element 4a and the second switching element 4b.
  • the control unit 10 can be composed of an electric circuit such as an analog circuit or a digital circuit.
  • this electric circuit is composed of a discrete system having a CPU (Central Processing Unit), a DSP (Digital Signal Processor), or a microcomputer, which is a processor that executes a program that is software stored in a memory. may Switching control of the first switching element 4a and the second switching element 4b by the control unit 10 will be described below.
  • FIG. 2 is a diagram showing the relationship (that is, switching control) between the states of the first switching element 4a and the second switching element 4b of the charging circuit 9 of the DC power supply device 101 shown in FIG. 1 and the current paths. .
  • State A in FIG. 2 shows current paths when both the first switching element 4a and the second switching element 4b are controlled to be off.
  • state A both the first capacitor 6a and the second capacitor 6b are charged. That is, in state A, both the first capacitor 6a and the second capacitor 6b are in a charged state.
  • State B in FIG. 2 shows the current path when the first switching element 4a is controlled to be ON and the second switching element 4b is controlled to be OFF.
  • state B the second capacitor 6b is charged and the first capacitor 6a is not charged. That is, in state B, the first capacitor 6a is in a non-charged state and the second capacitor 6b is in a charged state.
  • State C in FIG. 2 shows the current path when the first switching element 4a is turned off and the second switching element 4b is turned on.
  • state C the first capacitor 6a is charged and the second capacitor 6b is not charged. That is, in state C, the first capacitor 6a is in a charged state and the second capacitor 6b is in a non-charged state.
  • State D in FIG. 2 shows the current path when both the first switching element 4a and the second switching element 4b are on-controlled (that is, in a short-circuit state).
  • state D the first capacitor 6a is not charged and the second capacitor 6b is not charged. That is, in state D, both the first capacitor 6a and the second capacitor 6b are in a non-charged state.
  • FIG. 3 is a diagram showing an example of operation modes of the DC power supply 101 shown in FIG.
  • the full-wave rectification mode (comparative example) is a conventional full-wave rectification mode in which both the first switching element 4a and the second switching element 4b are always turned off.
  • the DC power supply device 101 according to Embodiment 1 executes a full-wave rectification mode shown in FIG. 6A, which will be described later, instead of the full-wave rectification mode (comparative example) shown in FIG. Further, the DC power supply device 101 according to Embodiment 1 executes a boost mode in which the first switching element 4a and the second switching element 4b are controlled to be turned on and off at different timings.
  • FIG. 3 shows a boost mode a1, a boost mode a2, and a boost mode a3 as boost modes.
  • the boost mode includes a boost mode a1 (voltage doubler mode) in which the on-duty Da of the first switching element 4a is 50% and the on-duty Db of the second switching element 4b is 50%.
  • Boosting mode a2 in which each of the on-duty D a and D b of the switching element 4a and the second switching element 4b is less than 50%, and the on-duty D a of the first switching element 4a and the second switching element 4b , Db each greater than 50%.
  • the ON timing of the first switching element 4a and the OFF timing of the second switching element 4b are substantially the same, and the OFF timing of the first switching element 4a and the second switching element
  • the ON timing of 4b is almost the same, and the current path of state B in FIG. 2 and the current path of state C in FIG. 2 are alternately formed.
  • the output voltage at this time is approximately twice the output voltage in the full-wave rectification mode.
  • a simultaneous off period is provided in which both the first switching element 4a and the second switching element 4b are turned off. That is, the on-duties D a and D b of the first switching element 4a and the second switching element 4b are smaller than 50%.
  • state transitions in the order of state B, state A, state C, and state A in FIG. 2 are periodically repeated.
  • the output voltage at this time is in the range between the output voltage in the full-wave rectification mode and the output voltage in the boosting mode a1 (voltage doubler mode). As D a and D b approach 50%, the output voltage approaches the output voltage in boost mode a1 (voltage doubler mode).
  • a simultaneous ON period is provided in which both the first switching element 4a and the second switching element 4b are turned on. That is, the on-duties D a and D b of the first switching element 4a and the second switching element 4b are greater than 50%.
  • state transitions in the order of state D, state C, state D, and state B in FIG. 2 are periodically repeated.
  • Energy is stored in the reactor 3 during the simultaneous ON period of the first switching element 4a and the second switching element 4b (here, the period of the state D).
  • the output voltage in the boost mode a3 is equal to or higher than the output voltage in the boost mode a1 (voltage doubler mode).
  • the control unit 10 controls the DC output voltage V dc [V] supplied to the load circuit 8 by changing the on-duties D a and D b of the first switching element 4 a and the second switching element 4 b. It is possible.
  • the combined capacitance when the capacitance of the first capacitor 6a is C p , the capacitance of the second capacitor 6b is C n , and the first capacitor 6 a and the second capacitor 6 b are connected in series. is C pn , in the state A of FIG. 2, when the first capacitor 6 a and the second capacitor 6 b are connected in series, a charging current flows through both capacitors, so C pn ⁇ C p , C pn ⁇ C n . Also, when the capacitances Cp and Cn are the same, the combined capacitance Cpn is half the capacitance Cp or Cn . In particular, in the full-wave rectification mode (comparative example) shown in FIG. 3, since the state A continues, the combined capacitance Cpn is charged and discharged.
  • FIG. 4 shows the input current I 0 [A] to the rectifier circuit 2 when the DC power supply 101 is operated in the full-wave rectification mode (comparative example) of FIG. 2 shows examples of waveforms of the output voltage V dc [V] detected by the output voltage V dc [V], the voltage V pc [V] detected by the first detection unit 7a, and the voltage V nc [V] detected by the second detection unit 7b.
  • FIG. 4 shows an example of waveforms when the load W L [kW] consumed by the load circuit 8 is 15 kW.
  • FIG. 5 shows the input current I 0 [A] to the rectifier circuit 2 when the DC power supply 101 is operated in the full-wave rectification mode (comparative example) of FIG.
  • Another example of the waveforms of the output voltage V dc [V] detected by the output voltage V dc [V] detected by the first detection unit 7a, the voltage V pc [V] detected by the first detection unit 7a, and the voltage V nc [V] detected by the second detection unit 7b show.
  • FIG. 5 shows an example of waveforms when the load W L [kW] consumed by the load circuit 8 is 30 kW.
  • an operation mode in which the second switching element 4b is turned off and the first switching element 4a is PWM-controlled is executed as a full-wave rectification mode.
  • FIG. 6(a) is a diagram showing an example of operation modes of the DC power supply device 101 according to Embodiment 1.
  • FIG. FIG. 6B is a diagram showing an example of operation modes of the DC power supply device 102 according to Embodiment 2, which will be described later.
  • energization is performed according to the energization pattern shown in FIG.
  • FIG. 7 shows the input current I 0 [A] to the rectifier circuit 2 and the output detected by the third detection unit 7c when the DC power supply device 101 according to Embodiment 1 is operated in the full-wave rectification mode. Examples of waveforms of a voltage V dc [V], a voltage V pc [V] detected by the first detection unit 7a, and a voltage V nc [V] detected by the second detection unit 7b are shown.
  • FIG. 7 shows an example of waveforms when the load W L [kW] consumed by the load circuit 8 is 15 kW.
  • FIG. 7 shows operation waveforms when the magnitude of the load W L [kW] of the load circuit 8 and the on-duty D a of the first switching element 4a are increased linearly in the configuration shown in FIG.
  • FIG. 8 shows the input current I 0 [A] shown in FIG. 7, the output voltage V dc [V] which is the voltage detected by the third detection unit 7c, and the voltage V detected by the first detection unit 7a.
  • Waveforms of pc [V] and voltage V nc [V] detected by the second detection unit 7b are shown with an enlarged time axis.
  • the on-duty D a of the first switching element 4a may be increased stepwise. However, in order to prevent the peak of the charging current to the first capacitor 6a from becoming too large (that is, to suppress the peak), the on-duty Da can be increased linearly or in an S-order curve. desirable.
  • the second switching element 4b since the second switching element 4b is in the OFF state, the first capacitor 6a is discharged as the load W L [kW] of the load circuit 8 increases, and the voltage V pc [V] of the first capacitor 6a is discharged. decreases gradually.
  • the ripple of the output voltage V dc [V] is reduced without increasing the capacitance of the first capacitor 6a and the second capacitor 6b. can be suppressed from increasing, it is possible to contribute to reducing power source harmonics, increasing the power factor, and extending the life of the capacitor while suppressing an increase in the cost of the DC power supply device 101 .
  • FIG. 9 shows the input current I 0 [A] to the rectifier circuit 2 and the output detected by the third detection unit 7c when the DC power supply device 102 according to Embodiment 2 is operated in the full-wave rectification mode.
  • voltage V dc [V] voltage V pc [V] detected by the first detection unit 7a
  • voltage V nc [ V ] detected by the second detection unit 7b load WL [kW]
  • An example of the waveform of the on-duty Da of the first switching element 4a is shown.
  • FIG. 9 shows an example of waveforms when the load W L [kW] consumed by the load circuit 8 is 30 kW.
  • FIG. 9 shows that in the DC power supply device 102 according to Embodiment 2 shown in FIG.
  • Increasing the on-duty D a of the first switching element 4a is synonymous with increasing the proportion of state B in FIG. 2 and decreasing the proportion of state A in FIG. 2, as shown in FIG. 6(b). is.
  • the first capacitor 6a is more likely to be discharged.
  • the convergence time which is the time required to reach the steady state through the transient state, is shortened.
  • the on-duty of the first switching element 4a is set to 100%, the entire area of the energization pattern in FIG. In this case, since the first switching element 4a is always on, the occurrence of switching loss can be suppressed.
  • the convergence time until reaching the steady state through the transient state can be shortened, and can contribute to high efficiency.
  • the second embodiment is the same as the first embodiment.
  • the on-duty Db of the second switching element 4b is set to a value greater than 0% and less than or equal to 100% in a steady state.
  • 1 to 3 are also referred to in the description of the DC power supply device 103 according to the third embodiment.
  • FIG. 10 shows an example of operation modes of the DC power supply device 103 according to the third embodiment.
  • FIG. 11 shows the input current I 0 [A] to the rectifier circuit 2 when the DC power supply 103 according to Embodiment 3 is operated in the full-wave rectification mode of FIG. detected output voltage V dc [V], voltages V pc and V nc [V] detected by the first and second detection units 7a and 7b, the load W L [kW] of the load circuit 8, and the second An example of the waveform of the on-duty Db of the switching element 4b is shown.
  • FIG. 11 shows operation waveforms when the load W L [kW] and the on-duty D b of the second switching element 4b are increased linearly.
  • the load W L [kW] starts increasing at 0.1 seconds and increases to 30 kW at approximately 0.20 seconds, and the on-duty Db of the second switching element 4b reaches 0.1 seconds. It starts to increase from the time point and increases to 100% at about 0.20 seconds. Note that the slope of increase in the load W L [kW] is the same as in the first and second embodiments.
  • the on-duty Db of the second switching element 4b may be increased stepwise. However, in order to prevent the peak of the charging current to the second capacitor 6b from becoming too large (that is, to suppress the peak), the on-duty Db can be increased linearly or in an S-order curve. desirable.
  • the second switching element 4b when the first switching element 4a is used for on/off control, the second switching element 4b is always in the off state. A bootstrap circuit cannot be used for the power supply. However, when the second switching element 4b is used for on/off control, the first switching element 4a may be always off, so either a separate power supply circuit or a bootstrap circuit may be used for its gate drive. .
  • the degree of freedom in designing the power supply circuit configuration for driving the gate of the first switching element 4a can be improved, and the bootstrap circuit can be The circuit can be made at a lower cost, for example, by using
  • Embodiment 3 is the same as Embodiment 1 or 2.
  • Embodiment 4>> 1 to 3 are also referred to in the description of the DC power supply device 104 according to the fourth embodiment.
  • the DC power supply device 104 according to Embodiment 4 has a circuit configuration in which the conduction loss of the first switching element 4a is smaller than the conduction loss of the first backflow prevention element 5a.
  • the circuit configuration is such that the conduction loss in the first switching element 4a is smaller than the conduction loss in the first backflow prevention element 5a.
  • the on-duty D a is set to 100% or brought close to 100% to increase the proportion of the period of state B in the full-wave rectification mode using states A and B shown in FIG. 6(b).
  • the on-duty D a is not limited to 100%, and may be set so as to enable efficient operation based on the balance between switching loss and conduction loss.
  • the DC power supply device 104 has a circuit configuration in which the conduction loss in the second switching element 4b is smaller than the conduction loss in the second backflow prevention element 5b, and the second switching element 4b
  • the on-duty Db is brought to 100% or closer to 100% to increase the proportion of the period of state C in the full-wave rectification mode using states A and C shown in FIG .
  • the conduction loss of the circuit can be reduced more than in the full-wave rectification mode (comparative example) only in the state A shown in FIG. 3, and the efficiency can be improved.
  • the on-duty Db is not limited to 100%, and may be set so as to enable efficient operation based on the balance between switching loss and conduction loss.
  • the full-wave rectification mode in which the period of the state B is increased in FIG. 6B or the period of the state C in FIG. In the full-wave rectification mode, high efficiency can be realized.
  • Embodiment 4 is the same as any of Embodiments 1 to 3.
  • FIG. 12 is a diagram showing a configuration example of the DC power supply device 105 according to the fifth embodiment.
  • a DC power supply device 105 according to Embodiment 5 includes a relay circuit 11 as a low-loss switching circuit in parallel with the first switching element 4a. It is different from the power supply device 101 .
  • the relay circuit 11 is ON/OFF-controlled by the controller 10 .
  • the relay circuit 11 is also called a first relay circuit.
  • the relay circuit 11 is turned on to short-circuit the collector and emitter of the first switching element 4a.
  • the charging current of the second capacitor 6b passes through the relay circuit 11 having a resistance lower than that of the first switching element 4a, thereby reducing circuit loss.
  • the relay circuit 11 is turned on, it is not necessary to drive the first switching element 4a with an on-duty of 100%.
  • the relay circuit 11 may be connected in parallel with the second switching element 4b.
  • the relay circuit 11 is also called a second relay circuit.
  • a full-wave rectification mode combining state A and state C shown in FIG. 10 is performed, and the relay circuit 11 is turned on, the collector and emitter of the second switching element 4b are short-circuited.
  • the charging current of the first capacitor 6a passes through the relay circuit 11 having a resistance lower than that of the second switching element 4b, thereby reducing circuit loss.
  • the relay circuit 11 is turned on, it is not necessary to drive the second switching element 4b with an on-duty of 100%.
  • the timing for turning on the relay circuit 11 does not necessarily have to be the stage when the charging and discharging of the first capacitor 6a and the second capacitor 6b have converged and the state has reached a steady state.
  • the charging may be performed at an arbitrary timing that allows the charging current peak of the first capacitor 6a or the second capacitor 6b that occurs at that time.
  • two relay circuits may be connected in parallel with the first switching element 4a and the second switching element 4b, respectively.
  • the purpose of using the relay circuit 11 is to prepare a low-loss current path instead of the first switching element 4a or the second switching element 4b, and the full-wave rectification shown in FIG. 6(b) or FIG.
  • the relay circuit 11 may be arranged according to the energization pattern in the mode.
  • Embodiment 5 is the same as any of Embodiments 1 to 4.
  • Embodiment 6 relates to a DC power supply, a motor drive having a DC power supply and an inverter, and a refrigeration cycle apparatus having the motor drive and a refrigeration cycle.
  • FIG. 13 is a diagram showing a configuration example of a DC power supply device 106, a motor drive device 200, and a refrigeration cycle application device 300 according to Embodiment 6. As shown in FIG. Any one of the DC power supply devices 101 to 105 according to Embodiments 1 to 5 can be used as the DC power supply device 106 .
  • the load circuit of the DC power supply 106 is the inverter 30.
  • the inverter 30 converts the direct current supplied from the direct current power supply 106 into alternating current.
  • motor driving device 200 has DC power supply 106 and inverter 30 .
  • a refrigerating cycle device 300 has a motor drive device 200 and a refrigerating cycle device 301 .
  • the refrigeration cycle device 301 has a compressor 31, a four-way valve 32, an internal heat exchanger 33, an expansion mechanism 34, a heat exchanger 35, and a refrigerant pipe 36 connecting these.
  • the compressor 31 also has a compression mechanism 37 that compresses the refrigerant and a motor (that is, compressor motor) 38 that operates the compression mechanism 37 .
  • Motor 38 also receives power for driving from inverter 30 connected to DC power supply 106 .
  • the DC power supply device 106 sets the operation mode to a full-wave rectification mode (second 1 full-wave rectification mode) or a full-wave rectification mode (also referred to as a second full-wave rectification mode) of an energization pattern consisting of states A and C shown in FIG.
  • a full-wave rectification mode second 1 full-wave rectification mode
  • a full-wave rectification mode also referred to as a second full-wave rectification mode
  • the second capacitor 6b is charged and discharged in the full-wave rectification mode of the energization pattern shown in FIG. 6(b).
  • the first capacitor 6a is charged and discharged in the full-wave rectification mode of the energization pattern shown.
  • FIG. 14 is a flowchart showing an operation example of switching the energization pattern of the DC power supply device 106 according to the sixth embodiment.
  • control unit 10 determines whether or not there is a request for the full-wave rectification mode (step ST1). (step ST2).
  • the control unit 10 operates the charging circuit 9 according to the energization pattern shown in FIG.
  • the first capacitor 6a is charged and discharged, and the second capacitor 6b is charged (step ST3).
  • the control unit 10 operates the charging circuit 9 according to the energization pattern of FIG. Charge and discharge to charge the first capacitor 6a (step ST4).
  • control unit 10 shifts the operation mode to the boost mode shown in FIG. 3 (step ST5).
  • control unit 10 may use the operation time of the DC power supply 106, the operation time of the compressor 31, or the charge/discharge time of each capacitor as a trigger for switching capacitors to be charged and discharged.
  • the aim of the sixth embodiment is to extend the life of the capacitor as compared to the case where only one of the first capacitor 6a and the second capacitor 6b is continuously used as the capacitor used for charging and discharging in the full-wave rectification mode. be. Therefore, either the first capacitor 6a or the second capacitor 6b may be alternately used as a charging/discharging capacitor by the trigger, or the charging/discharging time of the two capacitors may be set equal to each other. , the charging and discharging time of each capacitor may be adjusted.
  • FIG. 15 shows the input current I 0 [A] to the rectifier circuit 2 and the output voltage V dc [ V], the voltages V pc [V] and V nc [V] detected by the first and second detection units 7a and 7b, the load W L [kW], and the on-duty D a of the first switching element 4a shows an example of the waveform of FIG. 15 shows an example of operation waveforms when the energization pattern of FIG. 6B is switched to the energization pattern of FIG.
  • the energization pattern of FIG. 6( b ) starts at 0.1 seconds, and the on-duty Da of the first switching element 4a gradually (for example, linearly) increases from 0% to 100%. is doing. After that, from the time point of 0.3 seconds, the on-duty Da of the first switching element 4a gradually (for example, linearly) decreases from 100% to 0%. Also, from the time point of 0.3 seconds, the on-duty Db of the second switching element 4b gradually increases from 0% and linearly increases to 100%. As a result, the second capacitor 6b operates as a charge/discharge capacitor until 0.3 seconds, and its voltage value becomes the voltage value obtained by the full-wave rectification of the rectifier circuit 2.
  • FIG. 15 the energization pattern of FIG. 6( b ) starts at 0.1 seconds, and the on-duty Da of the first switching element 4a gradually (for example, linearly) increases from 0% to 100%. is doing. After that, from the time point of 0.3 seconds, the on-duty Da of the
  • the first capacitor 6a operates as a charge/discharge capacitor during the period until the energization pattern in FIG.
  • the value is a voltage value that has been full-wave rectified by the rectifier circuit 2 .
  • both the first switching element 4a and the second switching element 4b are in switching operation, as shown in FIG. Since the operating state is one of the boosting modes a1, a2, and a3, the boosting operation is temporarily performed during this period.
  • the output voltage V dc [V] of the DC power supply when the energization pattern is switched becomes higher than the output voltage V dc [V] before the energization pattern is switched. energization patterns can be switched while the load circuit 8 is being driven.
  • 16 and 17 show the input current I 0 to the rectifier circuit 2 and the output voltage V dc [ V], the voltages V pc [V] and V nc [V] detected by the first and second detection units 7a and 7b, the load W L [kW], and the on-duty D a of the first switching element 4a shows another example of the waveform of If it is desired to suppress the voltage increase due to the boosting operation, as shown in FIG. ), it can be dealt with by increasing the on-duty Db of the second switching element 4b.
  • the on-duty Db of the second switching element 4b is similarly reduced, and then the on-duty Da of the first switching element 4a is reduced. should be increased.
  • the on-duty is changed linearly in the sixth embodiment, it may be changed stepwise or S-curve according to the charging current peak of the capacitor or the voltage level at the time of boosting.
  • the control unit 10 of the DC power supply device 106 maintains the second switching element 4b in the OFF state, and when the DC voltage becomes a steady state, the first A first full-wave rectification mode in which the on-duty of the switching element 4a is set to a value greater than 0% and less than or equal to 100%, and when the first switching element 4a is maintained in an off state and the DC voltage becomes a steady state.
  • a second full-wave rectification mode in which the on-duty of the second switching element 4b is set to a value greater than 0% and less than or equal to 100% can be alternately switched. Therefore, the cumulative charge/discharge time of the first and second capacitors 6a and 6b can be leveled, and the life of the DC power supply 106 can be extended.
  • control unit 10 of DC power supply device 106 gradually increases the on-duty of first switching element 4a in the transitional state of switching from the first full-wave rectification mode to the second full-wave rectification mode. and the period for gradually increasing the on-duty of the second switching element 4b are overlapped or partially overlapped to switch from the second full-wave rectification mode to the first full-wave rectification mode.
  • the period for gradually decreasing the on-duty of the second switching element 4b and the period for gradually increasing the on-duty of the first switching element 4a can be overlapped or partially overlapped. can. Therefore, continuous operation is possible without stopping the refrigeration cycle device 301 .
  • the transient state is such that the on-duty of both the first switching element 4a and the second switching element 4b is greater than 0% and less than or equal to 100%.
  • the output voltage Vdc can be greater than the voltage output from the rectifier circuit 2, including the period of driving individually in the range. Therefore, power shortage at the time of switching can be avoided.
  • the energization pattern can be switched while the motor 38 is being driven, and continuous operation is possible without stopping the refrigerating cycle device 301 .

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Dc-Dc Converters (AREA)
  • Rectifiers (AREA)
PCT/JP2021/005939 2021-02-17 2021-02-17 直流電源装置、モータ駆動装置、及び冷凍サイクル適用機器 Ceased WO2022176065A1 (ja)

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US18/256,799 US20240097576A1 (en) 2021-02-17 2021-02-17 Dc power supply device, motor driving device, and refrigeration cycle application apparatus
CN202180093040.3A CN116941174A (zh) 2021-02-17 2021-02-17 直流电源装置、马达驱动装置以及制冷循环应用设备
PCT/JP2021/005939 WO2022176065A1 (ja) 2021-02-17 2021-02-17 直流電源装置、モータ駆動装置、及び冷凍サイクル適用機器
JP2023500186A JP7442729B2 (ja) 2021-02-17 2021-02-17 直流電源装置、モータ駆動装置、及び冷凍サイクル適用機器

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Publication number Priority date Publication date Assignee Title
JP2009050109A (ja) * 2007-08-21 2009-03-05 Daihen Corp 電源装置及びアーク加工用電源装置
WO2015033437A1 (ja) * 2013-09-06 2015-03-12 三菱電機株式会社 直流電源装置、およびそれを備えた冷凍サイクル適用機器
WO2015125240A1 (ja) * 2014-02-19 2015-08-27 三菱電機株式会社 直流電源装置および、それを備えた電動機駆動装置、ならびに、それを備えた冷凍サイクル適用機器
JP2018514173A (ja) * 2015-02-25 2018-05-31 ゼネラル エレクトリック テクノロジー ゲゼルシャフト ミット ベシュレンクテル ハフツングＧｅｎｅｒａｌ Ｅｌｅｃｔｒｉｃ Ｔｅｃｈｎｏｌｏｇｙ ＧｍｂＨ デジタル出力回路における改善またはデジタル出力回路に関する改善

Patent Citations (4)

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Publication number Priority date Publication date Assignee Title
JP2009050109A (ja) * 2007-08-21 2009-03-05 Daihen Corp 電源装置及びアーク加工用電源装置
WO2015033437A1 (ja) * 2013-09-06 2015-03-12 三菱電機株式会社 直流電源装置、およびそれを備えた冷凍サイクル適用機器
WO2015125240A1 (ja) * 2014-02-19 2015-08-27 三菱電機株式会社 直流電源装置および、それを備えた電動機駆動装置、ならびに、それを備えた冷凍サイクル適用機器
JP2018514173A (ja) * 2015-02-25 2018-05-31 ゼネラル エレクトリック テクノロジー ゲゼルシャフト ミット ベシュレンクテル ハフツングＧｅｎｅｒａｌ Ｅｌｅｃｔｒｉｃ Ｔｅｃｈｎｏｌｏｇｙ ＧｍｂＨ デジタル出力回路における改善またはデジタル出力回路に関する改善

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