WO2022016856A1 - 基于空口信息融合的协作接收方法及系统 - Google Patents

基于空口信息融合的协作接收方法及系统 Download PDF

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WO2022016856A1
WO2022016856A1 PCT/CN2021/076436 CN2021076436W WO2022016856A1 WO 2022016856 A1 WO2022016856 A1 WO 2022016856A1 CN 2021076436 W CN2021076436 W CN 2021076436W WO 2022016856 A1 WO2022016856 A1 WO 2022016856A1
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signal
cooperative
channel
receiver
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刘安
刘冠颖
赵民建
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Zhejiang University
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Zhejiang University
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Priority claimed from CN202011157897.0A external-priority patent/CN112511270A/zh
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    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L1/00—Arrangements for detecting or preventing errors in the information received

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  • the present invention relates to the technical field of wireless communication, and in particular, to a cooperative receiving method and system based on air interface information fusion.
  • Cooperative reception technology improves wireless network capacity and bit error rate performance by combining received signals from multiple receivers in a wireless network to form a virtual antenna array to increase diversity and power gain, thereby increasing the likelihood of successfully decoding noisy transmissions potential. Cooperative reception may also result in increased communication range, increased data rate and/or reduced transmit power.
  • the existing cooperative reception technologies can be roughly divided into the following categories:
  • Each receiver broadcasts its received signal on the local area network, and then performs maximum ratio combining at the fusion center to achieve diversity gain.
  • this method has extremely high requirements on the throughput of the network, and it is difficult for the actual network to meet its requirements.
  • Some or all nodes among the receivers simply exchange hard decision information, and each receiver performs decoding and demodulation according to itself and the received hard decision information. Although this method has lower requirements on the throughput of the network, the exchange of hard-decision information may lead to a certain loss of the final decoding performance.
  • Each receiver in the receive cluster demodulates the transmission locally and generates a log-likelihood ratio. All receiving nodes (or a subset of nodes with better channel quality) quantize their log-likelihood ratios and broadcast all their quantized values over the network to other receiving nodes in the cluster. Each receiving node then combines the information received over the network with its local unquantized log-likelihood ratio and passes these results to its local block decoder for decoding. If any receiving node successfully decodes the message, it forwards the decoded message over the network to other receiving nodes in the cluster. Each receiving node will transmit the log-likelihood ratio value through the network, in order to avoid inter-node interference, each node needs to allocate orthogonal radio resources. In this method, when the number of receivers is large, the calculation latency will be greatly increased, so that the problem of poor network scalability will occur.
  • the current cooperative reception technology has defects such as high bit error rate, prolonged interaction time, and poor network scalability.
  • the present invention aims to solve one of the technical problems in the related art at least to a certain extent.
  • an object of the present invention is to propose a cooperative receiving method based on air interface information fusion.
  • Air interface fusion and fusion receivers use the log-likelihood ratio information of air interface fusion to decode four parts, which can greatly reduce the cooperative decoding delay, reduce the bit error rate, support more receivers to cooperate, and improve the scalability of the system .
  • Another object of the present invention is to propose a cooperative receiving system based on air interface information fusion.
  • an embodiment of the present invention proposes a cooperative receiving method based on air interface information fusion, which includes the following steps: simultaneously sending a first channel coded signal to N cooperative receivers, where N is a set constant; Rotate the phase of the first channel-coded signal to obtain a second channel-coded signal; calculate the signal-to-noise ratio of the second channel-coded signal of the N cooperative receivers, and select Q from the N cooperative receivers
  • the log-likelihood ratio is calculated according to the second channel coded signals of the Q cooperative receivers, where Q is a positive integer, Q ⁇ N; from the Q cooperative receivers randomly select a cooperative receiver in the machine as a fusion receiver, and transmit the log-likelihood ratios of the remaining (Q-1) cooperative receivers to the fusion receiver by means of air interface information fusion; control the The fusion receiver integrates the log-likelihood ratio information of the Q cooperative receivers, and decode
  • the cooperative receiving method based on air interface information fusion obtains the second channel coded signal by eliminating the phase rotation of the first channel coded signal by the channel; , control the calculation of the log-likelihood ratio, and transmit the log-likelihood ratio information of (Q-1) cooperative receivers to the remaining cooperative receivers by means of air interface information fusion; control the remaining cooperative receivers
  • the cooperative receiver integrates the log-likelihood ratio information of the Q cooperative receivers, and decodes the first channel coded signal according to the integrated log-likelihood ratio information to obtain a decoding result; thus, the cooperative decoding time can be greatly reduced. Delay, reduce the bit error rate, support more receivers to cooperate, and improve the scalability of the system.
  • the cooperative receiving method based on air interface information fusion may also have the following additional technical features:
  • the canceling the phase rotation of the first channel coded signal by the channel to obtain the second channel coded signal includes: sending a pilot signal to the N cooperative receivers; Estimate the channel according to the pilot signal by using the least square method or the minimum mean square error method, and calculate the signal-to-noise ratio of the pilot signal according to the channel estimation result; send the first signal to the N cooperative receivers Channel coded signal; use the signal-to-noise ratio of the pilot signal to cancel the phase rotation of the first channel coded signal to obtain the second channel coded signal.
  • the second channel coded signal is:
  • Y i [m, l] is expressed as the m-th block of the i-th receiver cooperating second channel encoded signal in the l-th transmission symbol
  • h i [m] is expressed as the first channel encoded signal
  • the forward link complex channel through which the mth block signal in the ith cooperative receiver passes through, X[m,l] is represented as the lth block signal in the mth block signal of the first channel coded signal
  • W i [m,l] is expressed as the baseband matching of the lth transmitted symbol in the mth block signal of the second channel coded signal by the ith cooperative receiver
  • the noise generated after filtering, W i [m,l] follows a complex Gaussian distribution with mean 0 and variance N 0.
  • the calculation formula of the signal-to-noise ratio of the second channel-coded signal is:
  • ⁇ i represents the signal-to-noise ratio of the mth block signal in the second channel coded signal of the ith cooperative receiver
  • h i [m] represents the mth block signal in the first channel coded signal the forward link complex channel passed to the i-th cooperative receiver
  • X[m,l] is the l-th transmitted symbol in the m-th block signal of the first channel-coded signal
  • E s is the first channel-coded signal.
  • E( ⁇ ) represents the mean value
  • k represents the number of transmitted symbols in the mth block of the first channel coded signal.
  • the calculation formula of the log-likelihood ratio is:
  • the method of transmitting the log-likelihood ratios of the remaining (Q-1) cooperative receivers to the fusion receiver by means of air interface information fusion includes: A normalized signal obtained by multiplying the log-likelihood ratio of the (Q-1) cooperative receivers by a normalization factor b, and the normalized signal is repeatedly sent to the fusion receiver Z times, Z is to set a constant; the fusion receiver receives the normalized signal through the normalization factor a to obtain a received signal, and the received signal is expressed as:
  • the zth received signal of the fusion receiver is the sum of the log-likelihood ratios of the (Q-1) cooperative receivers with respect to the kth transmitted symbol, is the channel coefficient between the i-th user and the fusion receiver, n z is the white Gaussian noise generated by the fusion receiver, represents the log-likelihood ratio of the i-th cooperative receiver with respect to the transmitted symbol x k, normalization factor and a z according to the received signal of Z times
  • the sum of the smallest received signal in and the log-likelihood ratio values of the (Q-1) receivers for the kth transmitted symbol The mean square error of the joint design.
  • the position sequence number of the l-th transmitted symbol in the m-th block signal in the set X that is: Where k * is the position sequence number of the lth transmitted symbol in the mth block signal of the first channel coded signal in the transmission set X; the decoding result obtained by the fusion receiver determined according to the position sequence number is: : in, is represented as the transmitted symbol of the k- th position sequence number in the transmitted symbol set X.
  • another embodiment of the present invention proposes a cooperative receiving system based on air interface information fusion, including: a transmitter for simultaneously sending a first channel coded signal to N cooperative receivers, where N is a setting constant; the cooperative receiver is used to eliminate the phase rotation of the channel to the first channel coded signal to obtain the second channel coded signal; the log-likelihood ratio calculation module is used to calculate the second channel coded signal of the N cooperative receivers The signal-to-noise ratio of the channel-coded signal, select Q cooperative receivers within the set signal-to-noise ratio range from the N cooperative receivers, and calculate the log-likelihood according to the second channel-coded signal of the Q cooperative receivers ratio, where Q is a positive integer, Q ⁇ N; the air interface information fusion transmission module is used to arbitrarily select a cooperative receiver from the Q cooperative receivers as a fusion receiver, and use the air interface information fusion method to fuse the remaining The log-likelihood ratios of the (Q-1) cooperative receiver
  • the cooperative receiving system based on air interface information fusion obtains the second channel coded signal by eliminating the phase rotation of the channel to the first channel coded signal; the selection is within the range of the set signal-to-noise ratio of the second channel coded signal. , control the calculation of the log-likelihood ratio, and transmit the log-likelihood ratio information of (Q-1) cooperative receivers to the remaining cooperative receivers by means of air interface information fusion; control the remaining cooperative receivers
  • the cooperative receiver integrates the log-likelihood ratio information of the Q cooperative receivers, and decodes the first channel coded signal according to the integrated log-likelihood ratio information to obtain a decoding result; thus, the cooperative decoding time can be greatly reduced. Delay, reduce the bit error rate, support more receivers to cooperate, and improve the scalability of the system.
  • the cooperative receiving system based on air interface information fusion may also have the following additional technical features:
  • the air interface information fusion transmission module includes: a normalized information transmission module, configured to multiply the log-likelihood ratios of the (Q-1) cooperative receivers by The normalized signal obtained by the normalization factor b is repeatedly sent to the fusion receiver Z times, and Z is a set constant; the normalization information receiving module is used to pass the fusion receiver through the normalization factor a. The normalized signal is received to obtain a received signal.
  • FIG. 1 is a flowchart of a cooperative receiving method based on air interface information fusion according to an embodiment of the present invention
  • FIG. 2 is a schematic structural diagram of a cooperative receiving system based on air interface information fusion according to an embodiment of the present invention
  • FIG. 3 is a relationship diagram of a transmitter and a cooperative receiver in a cooperative receiving system based on air interface information fusion according to an embodiment of the present invention.
  • the purpose of the present invention is to provide a cooperative receiving method and system based on air interface information fusion, so as to support more cooperative receivers to cooperate with each other, reduce the bit error rate and decoding delay, and improve the scalability of the system.
  • FIG. 1 is a flowchart of a cooperative reception method based on air interface information fusion according to an embodiment of the present invention.
  • the cooperative receiving method and system based on air interface information fusion includes the following steps:
  • step S101 the first channel coding signal is simultaneously sent to N cooperative receivers, where N is a set constant.
  • N cooperative receivers are receiving clusters.
  • step S102 the phase rotation of the channel to the first channel coded signal is eliminated to obtain the second channel coded signal.
  • step S102 includes:
  • Step S21 sending pilot signals to N cooperative receivers
  • Step S22 using the least square method or the minimum mean square error method to estimate the channel according to the pilot signal, and calculate the signal-to-noise ratio of the pilot signal according to the channel estimation result;
  • Step S23 sending the first channel coding signal to the N cooperative receivers
  • Step S24 cancel the phase rotation of the first channel coded signal by using the signal-to-noise ratio of the pilot signal to obtain the second channel coded signal.
  • the second channel coded signal is represented as:
  • Y i [m,l] represents the l-th transmitted symbol in the m-th block of the second channel-coded signal of the i-th cooperative receiver
  • hi [m] represents the m- th symbol in the first channel-coded signal
  • X[m,l] represents the l-th transmitted symbol in the m-th block signal of the first channel-coded signal
  • W i [m,l] represents the noise generated by the ith cooperative receiver performing baseband matched filtering on the lth transmitted symbol in the mth block signal of the second channel coded signal
  • W i [m,l] obeys A complex Gaussian distribution with
  • step S103 the signal-to-noise ratios of the second channel coded signals of the N cooperative receivers are calculated, and Q cooperative receivers within the set signal-to-noise ratio range are selected from the N cooperative receivers, and according to the Q cooperative receivers
  • the log-likelihood ratio is calculated from the second channel coded signal of the engine, where Q is a positive integer, and Q ⁇ N.
  • the calculation formula of the signal-to-noise ratio of the second channel coded signal is:
  • ⁇ i represents the SNR of the m-th block of the second channel signal i-th coded signal receiver in the cooperative
  • h i [m] is expressed as the m-th signal block a first channel encoded signal to the i-th
  • the forward link complex channel traversed by the cooperative receiver is the noise variance generated by the i-th cooperative receiver
  • X[m,l] is the l-th transmitted symbol in the m-th block signal of the first channel-coded signal
  • E s is the m-th signal of the first channel-coded signal.
  • the average energy of each transmitted symbol in the block signal, E( ⁇ ) represents the mean value
  • k represents the number of transmitted symbols in the mth block signal of the first channel-coded signal.
  • Error probability p i related to the channel transition probability.
  • the time required for all cooperative receivers to calculate the log-likelihood ratio can be shortened and the delay can be reduced;
  • the range of SNR can reduce the influence of cooperative receivers with low SNR, and use the log-likelihood ratio of cooperative receivers with high SNR to perform decoding, which can improve the accuracy of decoding and reduce the bit error rate.
  • step S104 randomly select one cooperative receiver from the Q cooperative receivers as a fusion receiver, and transmit the log-likelihood ratios of the remaining (Q-1) cooperative receivers by means of air interface information fusion. to the fusion receiver.
  • step S104 includes:
  • step S41 the normalized signal obtained by multiplying the log-likelihood ratios of the (Q-1) cooperative receivers by the normalization factor b is repeatedly sent to the fusion receiver Z times, where Z is a set constant;
  • Step S42 the fusion receiver receives the normalized signal through the normalization factor a to obtain the received signal; the received signal is expressed as:
  • the zth received signal of the fusion receiver is expressed as the sum of the log-likelihood ratios of the (Q-1) cooperative receivers about the kth transmitted symbol, is the channel coefficient between the ith user and the fusion receiver, n z is the white Gaussian noise generated by the fusion receiver, represents the log-likelihood ratio of the i-th cooperative receiver with respect to the transmitted symbol x k, normalization factor and a z according to the received signal of Z times.
  • P' is the peak power limit of each (Q-1) cooperative receiver.
  • the channels traversed by (Q-1) cooperative receivers That is, it can always be guaranteed that the users are sorted according to their channel strengths, and that the channel strengths passed by the (Q-1) cooperative receivers increase sequentially during the zth retransmission.
  • the normalization factor and the optimal coefficients of a z can be designed as Due to the sum of the log-likelihood ratios of the (Q-1) cooperative receivers received by the fusion receiver for the zth time with respect to the kth transmitted symbol There is noise, and the received signal is further reduced by combining after repeated transmission and the sum of the log-likelihood ratio values of the (Q-1) cooperative receivers for the kth transmitted symbol
  • the mean square error between the two can improve the signal-to-noise ratio of the received signal of the fusion receiver, thereby reducing the influence of noise when the received signal is subsequently used for decoding, improving the accuracy of decoding, and reducing the bit error rate.
  • the cooperative receiver uses the log-likelihood ratio of the superposition characteristic of the wireless channel to directly perform air interface information fusion.
  • the fusion receiver only needs to decode according to the sum of the log-likelihood ratios of Q receivers, without paying attention to each receiver. It can avoid that each cooperative receiver needs to broadcast its log-likelihood ratio to other receivers in a time-sharing manner.
  • the LLR transmission delay will be greatly increased.
  • the defects of low LLR transmission efficiency between cooperative receivers, large cooperative decoding delay, and poor system scalability will occur.
  • the transmission efficiency of log-likelihood ratio is improved, the cooperative decoding delay is reduced, and the scalability of the system is improved.
  • step S105 the fusion receiver is controlled to integrate the log-likelihood ratio information of the Q cooperative receivers, and decode the first channel coded signal according to the integrated log-likelihood ratio information to obtain a decoding result.
  • step S105 includes:
  • Step S51 control the fusion receiver to combine the received signals of the Z times to obtain the final log-likelihood ratio information
  • Step S54 determine the position sequence number of the lth transmission symbol in the set X corresponding to the mth block signal of the first channel-coded signal; namely: Wherein k * is the position sequence number of the lth transmission symbol in the transmission set X in the mth block signal of the first channel coded signal;
  • step S55 the decoding result obtained by the fusion receiver is determined according to the position sequence number as: in Expressed as a transmission symbol set X position of the first k * number of transmission symbol.
  • the transmitted symbol corresponding to the maximum value of the log-likelihood ratio information is the most likely symbol transmitted by the transmitter, and decoding is implemented.
  • step S106 the decoding result is broadcast to (N-1) cooperative receivers other than the fusion receiver.
  • the signal received by the cooperative receiver and the signal sent by the transmitter can be guaranteed.
  • the signal sent by the transmitter is decoded by using the log-likelihood ratio of the received signal of the cooperative receiver, the accuracy of the decoding result can be improved and the bit error rate can be reduced; It can shorten the time that all cooperative receivers need to calculate the log-likelihood ratio, and reduce the delay; the log-likelihood ratio of the cooperative receiver is used for air interface fusion and the fusion receiver utilizes the log-likelihood ratio.
  • the log-likelihood ratio information of air interface fusion is decoded, that is, the log-likelihood ratio of the wireless channel is used to directly fuse the air interface information.
  • Decoding without paying attention to the LLR of each receiver can avoid the need for each cooperative receiver to broadcast its own log-likelihood ratio to other receivers in time division.
  • LLR transmission The delay will be greatly increased, resulting in the defects of low LLR transmission efficiency between cooperative receivers, large cooperative decoding delay, and poor system scalability. Extend and improve the scalability of the system.
  • FIG. 2 is a schematic structural diagram of a cooperative receiving system based on air interface information fusion according to an embodiment of the present invention.
  • the cooperative receiving system based on air interface information fusion includes: a transmitter 100 , a cooperative receiver 200 , a log-likelihood ratio calculation module 300 , an air interface information fusion transmission module 400 , an information integration module 500 , and a decoding module 600 and propagation module 700.
  • the transmitter 100 is used to send the first channel coded signal to N cooperative receivers at the same time, and N is a set constant; the cooperative receiver 200 is used to cancel the phase rotation of the first channel coded signal by the channel to obtain the second channel code signal; the log-likelihood ratio calculation module 300 is used to calculate the signal-to-noise ratio of the second channel-coded signal of the N cooperative receivers, and select Q cooperative receivers within the set signal-to-noise ratio range from the N cooperative receivers machine, calculates the log-likelihood ratio according to the second channel coded signals of the Q cooperative receivers, wherein Q is a positive integer, Q ⁇ N; the air interface information fusion transmission module 400 is used to arbitrarily select one from the Q cooperative receivers The cooperative receiver acts as a fusion receiver, and transmits the log-likelihood ratios of the remaining (Q-1) cooperative receivers to the fusion receiver by means of air interface information fusion; the information integration module 500 is used to control the fusion receiver Integrate the log-likeli
  • the system 10 in this embodiment of the present invention sends the first encoded signal through the transmitter, the cooperative receiver calculates the log-likelihood ratio, the cooperative receiver performs air interface fusion on the log-likelihood ratio, and the fusion receiver uses air interface fusion. It can greatly reduce the cooperative decoding delay, reduce the bit error rate, support more receivers to cooperate, and improve the scalability of the system.
  • the relationship between the transmitter and the cooperative receiver in the cooperative receiving system based on air interface information fusion is shown in FIG. 3 .
  • the air interface information fusion transmission module includes: a normalized information sending module and a normalized information receiving module.
  • the normalized information sending module is used to multiply the normalized signals obtained by multiplying the log-likelihood ratios of the (Q-1) cooperative receivers by the normalization factor b, and repeatedly send them to the fusion receiver Z times, Z is a set constant; the normalization information receiving module is used to receive the normalized signal by the fusion receiver through the normalization factor a to obtain the received signal.
  • the signal received by the cooperative receiver and the signal sent by the transmitter can be guaranteed.
  • the signal sent by the transmitter is decoded by using the log-likelihood ratio of the received signal of the cooperative receiver, the accuracy of the decoding result can be improved and the bit error rate can be reduced; It can shorten the time that all cooperative receivers need to calculate the log-likelihood ratio, and reduce the delay; the log-likelihood ratio of the cooperative receiver is used for air interface fusion and the fusion receiver utilizes the log-likelihood ratio.
  • the log-likelihood ratio information of air interface fusion is decoded, that is, the log-likelihood ratio of the wireless channel is used to directly fuse the air interface information.
  • Decoding without paying attention to the LLR of each receiver can avoid the need for each cooperative receiver to broadcast its own log-likelihood ratio to other receivers in time division.
  • LLR transmission The delay will be greatly increased, resulting in the defects of low LLR transmission efficiency between cooperative receivers, large cooperative decoding delay, and poor system scalability. Extend and improve the scalability of the system.
  • first and second are only used for descriptive purposes, and should not be construed as indicating or implying relative importance or implying the number of indicated technical features. Thus, a feature delimited with “first”, “second” may expressly or implicitly include at least one of that feature.
  • plurality means at least two, such as two, three, etc., unless otherwise expressly and specifically defined.

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Abstract

本发明公开了一种基于空口信息融合的协作接收方法及系统，通过消除信道对第一信道编码信号的相位旋转，得到第二信道编码信号；选定在设定第二信道编码信号的信噪比范围内的协作接收机，控制其计算对数似然比，通过空口信息融合的方式将（Q-1）个协作接收机的对数似然比信息传输至剩下的协作接收机；控制剩下的协作接收机整合Q个协作接收机的对数似然比信息，并根据整合后的对数似然比信息对所述第一信道编码信号进行解码，得到解码结果。本发明可以大大降低协作解码时延，降低误码率，支持更多的接收机进行协作，提高系统的可扩展性。

Description

基于空口信息融合的协作接收方法及系统
相关申请的交叉引用
本申请要求浙江大学于2020年10月26日提交的、发明名称为“基于空口信息融合的协作接收方法及系统”的、中国专利申请号“202011157897.0”的优先权。
本申请要求浙江大学于2020年7月21日提交的、发明名称为“一种基于空口信息融合的协作接收方法及系统”的、中国专利申请号“202010702911.4”的优先权。
技术领域
本发明涉及无线通信技术领域，特别涉及一种基于空口信息融合的协作接收方法及系统。
背景技术
近年来，协作通信技术已经成为无线通信的热点研究领域之一。协作接收技术通过将无线网络中的多个接收机的接收信号结合，形成虚拟天线阵列，以增加分集和功率增益，从而提高成功解码噪声传输的可能性，具有改善无线网络容量和误码率性能的潜力。协作接收还可能导致通信范围增加，数据速率增加和/或发射功率降低。
现有的协作接收技术大致可分为以下几类：
a.每个接收机在局域网上广播其接收信号，然后在融合中心进行最大比合并来实现分集增益。但是，此方法对网络的吞吐量有着极高的要求，实际网络很难满足其需求。
b.接收机之间的一些或所有节点之间简单地交换硬判决信息，每个接收机根据自己以及接收到的硬判决信息，进行解码解调。该方法虽然对网络的吞吐量的要求较低，但是交换硬判决信息可能会导致最终解码的性能有一定的损失。
c.接收集群中的每个接收机都在本地对传输进行解调，并生成对数似然比。所有接收节点(或具有更好信道质量的节点的子集)对它们的对数似然比进行量化，并通过网络向集群中的其他接收节点广播其所有量化值。然后，每个接收节点将通过网络接收到的信息与其本地未量化的对数似然比进行组合，并将这些结果传递到其本地块解码器进行解码。如果有任何接收节点成功解码了该消息，则它将解码后的消息通过网络转发到群集中的其他接收节点。每个接收节点将通过网络传输对数似然比数值，为了避免节点间干扰，每个节点都需要分配正交的无线资源。该方法在接收机数目较大时，计算等待时延将会大大地增加，从而会出现网络扩展性较差问题。
由此可知，目前的协作接收技术存在误码率高、交互时延长、网络扩展性差等缺陷。
发明内容
本发明旨在至少在一定程度上解决相关技术中的技术问题之一。
为此，本发明的一个目的在于提出一种基于空口信息融合的协作接收方法，通过发射机发送第一编码信号、协作接收机计算对数似然比、协作接收机对对数似然比进行空口融合以及融合接收机利用空口融合的对数似然比信息进行解码四大部分，可以大大降低协作解码时延，降低误码率，支持更多的接收机进行协作，提高系统的可扩展性。
本发明的另一个目的在于提出一种基于空口信息融合的协作接收系统。
为达到上述目的，本发明一方面实施例提出了一种基于空口信息融合的协作接收方法，包括以下步骤：同时向N个协作接收机发送第一信道编码信号，N为设定常数；消除信道对所述第一信道编码信号的相位旋转，得到第二信道编码信号；计算所述N个协作接收机的第二信道编码信号的信噪比，从所述N个协作接收机中选取Q个在设定信噪比范围内的协作接收机，根据Q个协作接收机的第二信道编码信号计算对数似然比，其中，Q为正整数，Q≤N；从所述Q个协作接收机中任意选取一个协作接收机当作融合接收机，通过空口信息融合的方式将剩下的(Q-1)个协作接收机的对数似然比传输至所述融合接收机；控制所述融合接收机整合所述Q个协作接收机的对数似然比信息，并根据整合后的对数似然比信息对所述第一信道编码信号进行解码，得到解码结果；将所述解码结果广播给除所述融合接收机以外的(N-1)个协作接收机。
本发明实施例的基于空口信息融合的协作接收方法，通过消除信道对第一信道编码信号的相位旋转，得到第二信道编码信号；选定在设定第二信道编码信号的信噪比范围内的协作接收机，控制其计算对数似然比，通过空口信息融合的方式将(Q-1)个协作接收机的对数似然比信息传输至剩下的协作接收机；控制剩下的协作接收机整合Q个协作接收机的对数似然比信息，并根据整合后的对数似然比信息对所述第一信道编码信号进行解码，得到解码结果；从而可以大大降低协作解码时延，降低误码率，支持更多的接收机进行协作，提高系统的可扩展性。
另外，根据本发明上述实施例的基于空口信息融合的协作接收方法还可以具有以下附加的技术特征：
进一步地，在本发明的一个实施例中，所述消除信道对所述第一信道编码信号的相位旋转，得到第二信道编码信号，包括：向所述N个协作接收机发送导频信号；根据所述导频信号利用最小二乘法或最小化均方误差法对信道进行估计，根据信道估计结果计算所述导频信号的信噪比；向所述N个协作接收机发送所述第一信道编码信号；利用所述导频信号的信噪比消除所述第一信道编码信号的相位旋转，得到所述第二信道编码信号。
进一步地，在本发明的一个实施例中，所述第二信道编码信号为：
Y i[m,l]＝|h i[m]|X[m,l]+W i[m,l]，
其中，Y i[m,l]表示为第i个协作接收机的所述第二信道编码信号的第m块中第l个发送符号，h i[m]表示为所述第一信道编码信号中的第m块信号至所示第i个协作接收机时所经过的前向链路复数信道，X[m,l]表示为所述第一信道编码信号的第m块信号中的第l个发送符号，所述第一信道编码信号的第m块信号中共有k个发送符号，所述k个发送符号用集合表示为X＝{x 1,...,x k}，X[m,l]从集合X中进行等概率选取，W i[m,l]表示为第i个协作接收机对所述第二信道编码信号的第m块信号中的第l个发送符号进行基带匹配滤波后产生的噪声，W i[m,l]服从均值为0，方差为N 0的复高斯分布。
进一步地，在本发明的一个实施例中，所述第二信道编码信号的信噪比的计算公式为：
Figure PCTCN2021076436-appb-000001
Figure PCTCN2021076436-appb-000002
其中，ρ i表示第i个协作接收机的所述第二信道编码信号中的第m块信号的信噪比，h i[m]表示为所述第一信道编码信号中的第m块信号至所述第i个协作接收机时所经过的前向链路复数信道，
Figure PCTCN2021076436-appb-000003
表示为所述第i个协作接收机产生的噪声方差，X[m,l]表示为所述第一信道编码信号的第m块信号中的第l个发送符号，E s表示所述第一信道编码信号的第m块信号中每个发送符号的平均能量，E(·)表示均值，k表示所述第一信道编码信号的第m块信号中发送符号的个数。
进一步地，在本发明的一个实施例中，所述对数似然比的计算公式为：
Figure PCTCN2021076436-appb-000004
其中，
Figure PCTCN2021076436-appb-000005
表示为第i个协作接收机根据所述第二信道编码信号Y i[m,l]计算出的关于发送符号x k的对数似然比，x l为发送符号集合X＝{x 1,...,x k}中第l个发送符号，p Y/X(Y i[m,l])＝x l|X[m,l]＝x k表示为在所述发射机发送的是所述第一信道编码信号的第m块中第k个符号的条件下，第i个协作接收机解调后获得符号集合中的第l个符号的概率，p i表示差错概率。
进一步地，在本发明的一个实施例中，所述通过空口信息融合的方式将剩下的(Q-1)个协作接收机的对数似然比传输至所述融合接收机，包括：将所述(Q-1)个协作接收机的对数似然比乘以归一化因子b得到的归一化信号，将所述归一化信号重复发送至所述融合接收机Z次，Z为设定常数；将所述融合接收机通过归一化因子a对所述归一化信号进行接收，得到接收信号，所述接收信号表示为：
Figure PCTCN2021076436-appb-000006
其中，
Figure PCTCN2021076436-appb-000007
表示所述融合接收机第z次接收信号为所述(Q-1)个协作接收机关于第k个发送符号的对数似然比之和，
Figure PCTCN2021076436-appb-000008
为第i个用户与所述融合接收机之间的信道系数，n z为所述融合接收机产生的高斯白噪声，
Figure PCTCN2021076436-appb-000009
表示第i个协作接收机关于发送符号x k的对数似然比，归一化因子
Figure PCTCN2021076436-appb-000010
和a z根据Z次的接收信号
Figure PCTCN2021076436-appb-000011
中最小的接收信号与所述(Q-1)个接收机关于第k个发送符号的对数似然比数值的和
Figure PCTCN2021076436-appb-000012
的均方误差进行联合设计。
进一步地，在本发明的一个实施例中，所述控制所述融合接收机整合所述Q个协作接收机的对数似然比信息，包括：控制所述融合接收机对Z次的接收信号进行合并，获得最终的对数似然比信息，所述最终的对数似然比信息为：
Figure PCTCN2021076436-appb-000013
将所述最终的对数似然比信息r k与所述融合接收机的对数似然比
Figure PCTCN2021076436-appb-000014
相加，获得整合后的关于发送符号集合X＝{x 1,...,x k}中第k个符号的对数似然比信息
Figure PCTCN2021076436-appb-000015
进一步地，在本发明的一个实施例中，所述根据整合后的对数似然比信息对所述第一信道编码信号进行解码，得到解码结果，包括：确定发送符号集合X＝{x 1,...,x k}中每个发送符号进行空口融合后的对数似然比信息的最大值；根据所述对数似然比信息的最大值确定对应于所述第一信道编码信号的第m块信号中的第l个发送符号在所述集合X中的位置序号；即：
Figure PCTCN2021076436-appb-000016
其中k *为所述第一信道编码信号的第m块信号中的第l个发送符号在所述发送集合X中的位置序号；根据所述位置序号确定所述融合接收机得到的解码 结果为：
Figure PCTCN2021076436-appb-000017
其中，
Figure PCTCN2021076436-appb-000018
表示为所述发送符号集合X中第k *位置序号的发送符号。
为达到上述目的，本发明另一方面实施例提出了一种基于空口信息融合的协作接收系统，包括：发射机，用于同时向N个协作接收机发送第一信道编码信号，N为设定常数；协作接收机，用于消除信道对所述第一信道编码信号的相位旋转，得到第二信道编码信号；对数似然比计算模块，用于计算所述N个协作接收机的第二信道编码信号的信噪比，从所述N个协作接收机中选取Q个在设定信噪比范围内的协作接收机，根据Q个协作接收机的第二信道编码信号计算对数似然比，其中，Q为正整数，Q≤N；空口信息融合传输模块，用于从所述Q个协作接收机中任意选取一个协作接收机当作融合接收机，通过空口信息融合的方式将剩下的(Q-1)个协作接收机的对数似然比传输至所述融合接收机；信息整合模块，用于控制所述融合接收机整合所述Q个协作接收机的对数似然比信息；解码模块，用于根据整合后的对数似然比信息对所述第一信道编码信号进行解码，得到解码结果；传播模块，用于将所述解码结果广播给除所述融合接收机以外的(N-1)个协作接收机。
本发明实施例的基于空口信息融合的协作接收系统，通过消除信道对第一信道编码信号的相位旋转，得到第二信道编码信号；选定在设定第二信道编码信号的信噪比范围内的协作接收机，控制其计算对数似然比，通过空口信息融合的方式将(Q-1)个协作接收机的对数似然比信息传输至剩下的协作接收机；控制剩下的协作接收机整合Q个协作接收机的对数似然比信息，并根据整合后的对数似然比信息对所述第一信道编码信号进行解码，得到解码结果；从而可以大大降低协作解码时延，降低误码率，支持更多的接收机进行协作，提高系统的可扩展性。
另外，根据本发明上述实施例的基于空口信息融合的协作接收系统还可以具有以下附加的技术特征：
进一步地，在本发明的一个实施例中，所述空口信息融合传输模块包括：归一化信息发送模块，用于将所述(Q-1)个协作接收机的对数似然比乘以归一化因子b得到的归一化信号，重复发送至所述融合接收机Z次，Z为设定常数；归一化信息接收模块，用于将所述融合接收机通过归一化因子a对所述归一化信号进行接收，得到接收信号。
本发明附加的方面和优点将在下面的描述中部分给出，部分将从下面的描述中变得明显，或通过本发明的实践了解到。
附图说明
本发明上述的和/或附加的方面和优点从下面结合附图对实施例的描述中将变得明显和容易理解，其中：
图1为根据本发明一个实施例的基于空口信息融合的协作接收方法的流程图；
图2为根据本发明一个实施例的基于空口信息融合的协作接收系统的结构示意图；
图3为根据本发明一个实施例的基于空口信息融合的协作接收系统中发射机和协作接收机的关系图。
具体实施方式
下面详细描述本发明的实施例，所述实施例的示例在附图中示出，其中自始至终相同或类似的标号表示相同或类似的元件或具有相同或类似功能的元件。下面通过参考附图描述的实施例是示例性的，旨在用于解释本发明，而不能理解为对本发明的限制。
本发明的目的是提供一种基于空口信息融合的协作接收方法及系统，以支持更多协作接收机相互协作，降低误码率和解码时延，提高系统的可扩展性。
下面参照附图描述根据本发明实施例提出的基于空口信息融合的协作接收方法及系统，首先将参照附图描述根据本发明实施例提出的基于空口信息融合的协作接收方法。
图1是本发明一个实施例的基于空口信息融合的协作接收方法的流程图。
如图1所示，该基于空口信息融合的协作接收方法及系统包括以下步骤：
在步骤S101中，同时向N个协作接收机发送第一信道编码信号，N为设定常数。
其中，N个协作接收机为接收集群。
在步骤S102中，消除信道对第一信道编码信号的相位旋转，得到第二信道编码信号。
具体而言，步骤S102包括：
步骤S21，向N个协作接收机发送导频信号；
步骤S22，根据导频信号利用最小二乘法或最小化均方误差法对信道进行估计，根据信道估计结果计算导频信号的信噪比；
步骤S23，向N个协作接收机发送第一信道编码信号；
步骤S24，利用导频信号的信噪比消除第一信道编码信号的相位旋转，得到第二信道编码信号。
通过消除信道对第一信道编码信号的相位旋转，能够保证协作接收机接收到的信号与发射机发送的信号完全一致，进而利用协作接收机的接收信号的对数似然比对发射机发送的信号进行解码时，能够提高解码结果的准确度，降低误码率。
在本发明的一个实施例中，第二信道编码信号表示为：
Y i[m,l]＝|h i[m]|X[m,l]+W i[m,l]
其中，Y i[m,l]表示为第i个协作接收机的第二信道编码信号的第m块中第l个发送符号，h i[m]表示为第一信道编码信号中的第m块信号至第i个协作接收机时所经过的前向链路复数信道，X[m,l]表示为第一信道编码信号的第m块信号中的第l个发送符号，第一信道编码信号的第m块信号中共有k个发送符号，k个发送符号用集合表示为X＝{x 1,...,x k}， X[m,l]从集合X中进行等概率选取，W i[m,l]表示为第i个协作接收机对第二信道编码信号的第m块信号中的第l个发送符号进行基带匹配滤波后产生的噪声，W i[m,l]服从均值为0，方差为N 0的复高斯分布，即W i[m,l]～CN(0,N 0)。
在步骤S103中，计算N个协作接收机的第二信道编码信号的信噪比，从N个协作接收机中选取Q个在设定信噪比范围内的协作接收机，根据Q个协作接收机的第二信道编码信号计算对数似然比，其中，Q为正整数，Q≤N。
在本发明的一个实施例中，第二信道编码信号的信噪比的计算公式为：
Figure PCTCN2021076436-appb-000019
Figure PCTCN2021076436-appb-000020
其中，ρ i表示第i个协作接收机的第二信道编码信号中的第m块信号的信噪比，h i[m]表示为第一信道编码信号中的第m块信号至第i个协作接收机时所经过的前向链路复数信道，
Figure PCTCN2021076436-appb-000021
表示为第i个协作接收机产生的噪声方差，X[m,l]表示为第一信道编码信号的第m块信号中的第l个发送符号，E s表示第一信道编码信号的第m块信号中每个发送符号的平均能量，E(·)表示均值，k表示第一信道编码信号的第m块信号中发送符号的个数。
对数似然比的计算公式为：
Figure PCTCN2021076436-appb-000022
其中，
Figure PCTCN2021076436-appb-000023
表示为第i个协作接收机根据第二信道编码信号Y i[m,l]计算出的关于发送符号x k的对数似然比，x l为发送符号集合X＝{x 1,...,x k}中第l个发送符号，p Y/X(Y i[m,l])＝x l|X[m,l]＝x k表示为在发射机发送的是第一信道编码信号的第m块中第k个符号的条件下，第i个协作接收机解调后获得符号集合中的第l个符号的概率，p i表示差错概率，
Figure PCTCN2021076436-appb-000024
υ为设定常数。
差错概率p i与信道转移概率有关。例如，对于具有
Figure PCTCN2021076436-appb-000025
的BPSK调制方式，
Figure PCTCN2021076436-appb-000026
对于具有
Figure PCTCN2021076436-appb-000027
的QPSK调制方式，
Figure PCTCN2021076436-appb-000028
其中，
Figure PCTCN2021076436-appb-000029
erfc(β)＝1-erf(β)，erf为标准正态分布的累计函数，即：
Figure PCTCN2021076436-appb-000030
通过在设定信噪比范围内的协作接收机计算对数似然比，能够缩短所有协作接收机均需要计算对数似然比的时间，降低时延；而设定第二信道编码信号的信噪比范围，能够降低信噪比较低的协作接收机的影响，利用信噪比较高的协作接收机的对数似然比进行解码，能够提高解码的准确性，降低误码率。
在步骤S104中，从Q个协作接收机中任意选取一个协作接收机当作融合接收机，通过空口信息融合的方式将剩下的(Q-1)个协作接收机的对数似然比传输至融合接收机。
具体而言，步骤S104包括：
步骤S41，将(Q-1)个协作接收机的对数似然比乘以归一化因子b得到的归一化信号，重复发送至融合接收机Z次，Z为设定常数；
步骤S42，将融合接收机通过归一化因子a对归一化信号进行接收，得到接收信号；接收信号表示为：
Figure PCTCN2021076436-appb-000031
其中，
Figure PCTCN2021076436-appb-000032
表示的融合接收机第z次接收信号为(Q-1)个协作接收机关于第k个发送符号的对数似然比之和，
Figure PCTCN2021076436-appb-000033
为第i个用户与融合接收机之间的信道系数，n z为融合接收机产生的高斯白噪声，
Figure PCTCN2021076436-appb-000034
表示第i个协作接收机关于发送符号x k的对数似然比，归一化因子
Figure PCTCN2021076436-appb-000035
和a z根据Z次的接收信号
Figure PCTCN2021076436-appb-000036
中最小的接收信号与(Q-1)个接收机关于第k个发送符号的对数似然比数值的和
Figure PCTCN2021076436-appb-000037
的均方误差进行联合设计，
Figure PCTCN2021076436-appb-000038
P′为各(Q-1)个协作接收机的峰值功率限制。不失一般性，在第z次发送时，(Q-1)个协作接收机所经过的信道
Figure PCTCN2021076436-appb-000039
即总是可以保证对用户按其信道强度进行排序，保证第z次重传时，(Q-1)个协作接收机所经过的信道强度依次增加。为 实现较小的MSE，归一化因子
Figure PCTCN2021076436-appb-000040
和a z的最优系数可设计为
Figure PCTCN2021076436-appb-000041
由于融合接收机第z次接收到的(Q-1)个协作接收机关于第k个发送符号的对数似然比之和
Figure PCTCN2021076436-appb-000042
存在噪声，通过多次重复发送后进行合并，进一步减小接收信号
Figure PCTCN2021076436-appb-000043
与(Q-1)个协作接收机关于第k个发送符号的对数似然比数值的和
Figure PCTCN2021076436-appb-000044
之间的均方误差，提高融合接收机接收信号的信噪比，进而在后续利用接收信号进行解码时能够减小噪声的影响，提高解码的准确性，降低误码率。
通过协作接收机用无线信道的叠加特性对对数似然比直接进行空口信息融合，融合接收机只需要根据Q个接收机的对数似然比之和进行解码，而不关注每个接收机的LLR，能够避免每个协作接收机需要分时将自己的对数似然比广播给其他接收机，当协作接收机增多且信道条件较差时，LLR传输时延将会大大地增加，从而会出现协作接收机之间LLR传输效率低、协作解码时延大、系统可扩展性较差的缺陷，提高对数似然比的传输效率，降低协作解码时延并提高系统的可扩展性。
在步骤S105中，控制融合接收机整合Q个协作接收机的对数似然比信息，并根据整合后的对数似然比信息对第一信道编码信号进行解码，得到解码结果。
具体而言，步骤S105包括：
步骤S51，控制融合接收机对Z次的接收信号进行合并，获得最终的对数似然比信息
Figure PCTCN2021076436-appb-000045
步骤S52，将最终的对数似然比信息r k与融合接收机的对数似然比
Figure PCTCN2021076436-appb-000046
相加，获得整合后的关于发送符号集合X＝{x 1,...,x k}中第k个符号的对数似然比信息
Figure PCTCN2021076436-appb-000047
步骤S53，确定发送符号集合X＝{x 1,...,x k}中每个发送符号进行空口融合后的对数似然比信息的最大值，空口融合后的对数似然比信息为
Figure PCTCN2021076436-appb-000048
步骤S54，根据对数似然比信息的最大值确定对应于第一信道编码信号的第m块信号中的第l个发送符号在集合X中的位置序号；即：
Figure PCTCN2021076436-appb-000049
其中k *为第一信道编码信号的第m块信号中的第l个发送符号在发送集合X中的位置序号；
步骤S55，根据位置序号确定融合接收机得到的解码结果为：
Figure PCTCN2021076436-appb-000050
其中
Figure PCTCN2021076436-appb-000051
表示为发送符号集合X中第k *位置序号的发送符号。
需要说明的是，对数似然比信息的最大值对应的发送符号是发射机最有可能发送的符号，实现解码。
在步骤S106中，将解码结果广播给除融合接收机以外的(N-1)个协作接收机。
根据本发明实施例提出的基于空口信息融合的协作接收方法，通过对发射机发送的信号进行处理，消除信道对发送信号的相位旋转，能够保证协作接收机接收到的信号与发射机发送的信号完全一致，进而利用协作接收机的接收信号的对数似然比对发射机发送的信号进行解码时，能够提高解码结果的准确度，降低误码率；通过选取在设定信噪比范围内的协作接收机计算对数似然比，能够缩短所有协作接收机均需要计算对数似然比的时间，降低时延；通过协作接收机对对数似然比进行空口融合以及融合接收机利用空口融合的对数似然比信息进行解码，即利用无线信道的叠加特性对对数似然比直接进行空口信息融合，融合接收机只需要根据Q个接收机的对数似然比之和进行解码，而不关注每个接收机的LLR，能够避免每个协作接收机需要分时将自己的对数似然比广播给其他接收机，当协作接收机增多且信道条件较差时，LLR传输时延将会大大地增加，从而会出现协作接收机之间LLR传输效率低、协作解码时延大、系统可扩展性较差的缺陷，提高对数似然比的传输效率，降低协作解码时延并提高系统的可扩展性。
其次参照附图描述根据本发明实施例提出的基于空口信息融合的协作接收系统。
图2是本发明一个实施例的基于空口信息融合的协作接收系统的结构示意图。
如图2所示，该基于空口信息融合的协作接收系统包括：发射机100、协作接收机200、对数似然比计算模块300、空口信息融合传输模块400、信息整合模块500、解码模块600和传播模块700。
其中，发射机100用于同时向N个协作接收机发送第一信道编码信号，N为设定常数；协作接收机200用于消除信道对第一信道编码信号的相位旋转，得到第二信道编码信号；对数似然比计算模块300用于计算N个协作接收机的第二信道编码信号的信噪比，从N个协作接收机中选取Q个在设定信噪比范围内的协作接收机，根据Q个协作接收机的第二信道编码信号计算对数似然比，其中，Q为正整数，Q≤N；空口信息融合传输模块400用于从Q个协作接收机中任意选取一个协作接收机当作融合接收机，通过空口信息融合的方式将剩下的(Q-1)个协作接收机的对数似然比传输至融合接收机；信息整合模块500用于控制融合接收机整合Q个协作接收机的对数似然比信息；解码模块600，用于根据整合后的对数似然比信息对第一信道编码信号进行解码，得到解码结果；传播模块700用于将解码结果广播给除融合接收机以外的(N-1)个协作接收机。
可以理解的是，本发明实施例的系统10通过发射机发送第一编码信号、协作接收机计算对数似然比、协作接收机对对数似然比进行空口融合以及融合接收机利用空口融合的对数似然比信息进行解码四大部分，可以大大降低协作解码时延，降低误码率，支持更多的接收机进行协作，提高系统的可扩展性。其中，基于空口信息融合的协作接收系统中发射机和协作接收机的关系图如图3所示。
进一步地，在本发明的一个实施例中，空口信息融合传输模块包括：归一化信息发送模块和归一化信息接收模块。
其中，归一化信息发送模块，用于将(Q-1)个协作接收机的对数似然比乘以归一化因子b得到的归一化信号，重复发送至融合接收机Z次，Z为设定常数；归一化信息接收模块，用于将融合接收机通过归一化因子a对归一化信号进行接收，得到接收信号。
需要说明的是，前述对基于空口信息融合的协作接收方法实施例的解释说明也适用于该实施例的基于空口信息融合的协作接收系统，此处不再赘述。
根据本发明实施例提出的基于空口信息融合的协作接收系统，通过对发射机发送的信号进行处理，消除信道对发送信号的相位旋转，能够保证协作接收机接收到的信号与发射机发送的信号完全一致，进而利用协作接收机的接收信号的对数似然比对发射机发送的信号进行解码时，能够提高解码结果的准确度，降低误码率；通过选取在设定信噪比范围内的协作接收机计算对数似然比，能够缩短所有协作接收机均需要计算对数似然比的时间，降低时延；通过协作接收机对对数似然比进行空口融合以及融合接收机利用空口融合的对数似然比信息进行解码，即利用无线信道的叠加特性对对数似然比直接进行空口信息融合，融合接收机只需要根据Q个接收机的对数似然比之和进行解码，而不关注每个接收机的LLR，能够避免每个协作接收机需要分时将自己的对数似然比广播给其他接收机，当协作接收机增多且信道条件较差时，LLR传输时延将会大大地增加，从而会出现协作接收机之间LLR传输效率低、协作解码时延大、系统可扩展性较差的缺陷，提高对数似然比的传输效率，降低协作解码时延并提高系统的可扩展性。
此外，术语“第一”、“第二”仅用于描述目的，而不能理解为指示或暗示相对重要性或者隐含指明所指示的技术特征的数量。由此，限定有“第一”、“第二”的特征可以明示或者隐含地包括至少一个该特征。在本发明的描述中，“多个”的含义是至少两个，例如两个，三个等，除非另有明确具体的限定。
在本说明书的描述中，参考术语“一个实施例”、“一些实施例”、“示例”、“具体示例”、或“一些示例”等的描述意指结合该实施例或示例描述的具体特征、结构、材料或者特点包含于本发明的至少一个实施例或示例中。在本说明书中，对上述术语的示意性表述不是必须针对的是相同的实施例或示例。而且，描述的具体特征、结构、材料或者特点可以在任一个或多个实施例或示例中以合适的方式结合。此外，在不相互矛盾的情况 下，本领域的技术人员可以将本说明书中描述的不同实施例或示例以及不同实施例或示例的特征进行结合和组合。
尽管上面已经示出和描述了本发明的实施例，可以理解的是，上述实施例是示例性的，不能理解为对本发明的限制，本领域的普通技术人员在本发明的范围内可以对上述实施例进行变化、修改、替换和变型。

Claims (10)

  1. 一种基于空口信息融合的协作接收方法，其特征在于，包括以下步骤：
    同时向N个协作接收机发送第一信道编码信号，N为设定常数；
    消除信道对所述第一信道编码信号的相位旋转，得到第二信道编码信号；
    计算所述N个协作接收机的第二信道编码信号的信噪比，从所述N个协作接收机中选取Q个在设定信噪比范围内的协作接收机，根据Q个协作接收机的第二信道编码信号计算对数似然比，其中，Q为正整数，Q≤N；
    从所述Q个协作接收机中任意选取一个协作接收机当作融合接收机，通过空口信息融合的方式将剩下的(Q-1)个协作接收机的对数似然比传输至所述融合接收机；
    控制所述融合接收机整合所述Q个协作接收机的对数似然比信息，并根据整合后的对数似然比信息对所述第一信道编码信号进行解码，得到解码结果；
    将所述解码结果广播给除所述融合接收机以外的(N-1)个协作接收机。
  2. 根据权利要求1所述的方法，其特征在于，所述消除信道对所述第一信道编码信号的相位旋转，得到第二信道编码信号，包括：
    向所述N个协作接收机发送导频信号；
    根据所述导频信号利用最小二乘法或最小化均方误差法对信道进行估计，根据信道估计结果计算所述导频信号的信噪比；
    向所述N个协作接收机发送所述第一信道编码信号；
    利用所述导频信号的信噪比消除所述第一信道编码信号的相位旋转，得到所述第二信道编码信号。
  3. 根据权利要求2所述的方法，其特征在于，所述第二信道编码信号为：
    Y i[m,l]＝|h i[m]|X[m,l]+W i[m,l]，
    其中，Y i[m,l]表示为第i个协作接收机的所述第二信道编码信号的第m块中第l个发送符号，h i[m]表示为所述第一信道编码信号中的第m块信号至所示第i个协作接收机时所经过的前向链路复数信道，X[m,l]表示为所述第一信道编码信号的第m块信号中的第l个发送符号，所述第一信道编码信号的第m块信号中共有k个发送符号，所述k个发送符号用集合表示为X＝{x 1,...,x k}，X[m,l]从集合X中进行等概率选取，W i[m,l]表示为第i个协作接收机对所述第二信道编码信号的第m块信号中的第l个发送符号进行基带匹配滤波后产生的噪声，W i[m,l]服从均值为0，方差为N 0的复高斯分布。
  4. 根据权利要求1至3中任一项所述的方法，其特征在于，所述第二信道编码信号的 信噪比的计算公式为：
    Figure PCTCN2021076436-appb-100001
    Figure PCTCN2021076436-appb-100002
    其中，ρ i表示第i个协作接收机的所述第二信道编码信号中的第m块信号的信噪比，h i[m]表示为所述第一信道编码信号中的第m块信号至所述第i个协作接收机时所经过的前向链路复数信道，
    Figure PCTCN2021076436-appb-100003
    表示为所述第i个协作接收机产生的噪声方差，X[m,l]表示为所述第一信道编码信号的第m块信号中的第l个发送符号，E s表示所述第一信道编码信号的第m块信号中每个发送符号的平均能量，E(·)表示均值，k表示所述第一信道编码信号的第m块信号中发送符号的个数。
  5. 根据权利要求1至4中任一项所述的方法，其特征在于，所述对数似然比的计算公式为：
    Figure PCTCN2021076436-appb-100004
    其中，
    Figure PCTCN2021076436-appb-100005
    表示为第i个协作接收机根据所述第二信道编码信号Y i[m,l]计算出的关于发送符号x k的对数似然比，x l为发送符号集合X＝{x 1,...,x k}中第l个发送符号，p Y/X(Y i[m,l])＝x l|X[m,l]＝x k表示为在所述发射机发送的是所述第一信道编码信号的第m块中第k个符号的条件下，第i个协作接收机解调后获得符号集合中的第l个符号的概率，p i表示差错概率。
  6. 根据权利要求1至5中任一项所述的方法，其特征在于，所述通过空口信息融合的方式将剩下的(Q-1)个协作接收机的对数似然比传输至所述融合接收机，包括：
    将所述(Q-1)个协作接收机的对数似然比乘以归一化因子b得到的归一化信号，将所述归一化信号重复发送至所述融合接收机Z次，Z为设定常数；
    将所述融合接收机通过归一化因子a对所述归一化信号进行接收，得到接收信号，所述接收信号表示为：
    Figure PCTCN2021076436-appb-100006
    其中，
    Figure PCTCN2021076436-appb-100007
    表示所述融合接收机第z次接收信号为所述(Q-1)个协作接收机关于第k个发送符号的对数似然比之和，
    Figure PCTCN2021076436-appb-100008
    为第i个用户与所述融合接收机之间的信道系数，n z为所述融合接收机产生的高斯白噪声，
    Figure PCTCN2021076436-appb-100009
    表示第i个协作接收机关于发送符号x k的对数似然比，归一化因子
    Figure PCTCN2021076436-appb-100010
    和a z根据Z次的接收信号
    Figure PCTCN2021076436-appb-100011
    中最小的接收信号与所述(Q-1)个接收机关于第k个发送符号的对数似然比数值的和
    Figure PCTCN2021076436-appb-100012
    的均方误差进行联合设计。
  7. 根据权利要求6所述的方法，其特征在于，所述控制所述融合接收机整合所述Q个协作接收机的对数似然比信息，包括：
    控制所述融合接收机对Z次的接收信号进行合并，获得最终的对数似然比信息，所述最终的对数似然比信息为：
    Figure PCTCN2021076436-appb-100013
    将所述最终的对数似然比信息r k与所述融合接收机的对数似然比
    Figure PCTCN2021076436-appb-100014
    相加，获得整合后的关于发送符号集合X＝{x 1,...,x k}中第k个符号的对数似然比信息
    Figure PCTCN2021076436-appb-100015
  8. 根据权利要求1至7中任一项所述的方法，其特征在于，所述根据整合后的对数似然比信息对所述第一信道编码信号进行解码，得到解码结果，包括：
    确定发送符号集合X＝{x 1,...,x k}中每个发送符号进行空口融合后的对数似然比信息的最大值；
    根据所述对数似然比信息的最大值确定对应于所述第一信道编码信号的第m块信号中的第l个发送符号在所述集合X中的位置序号；即：
    Figure PCTCN2021076436-appb-100016
    其中k *为所述第一信道编码信号的第m块信号中的第l个发送符号在所述发送集合X中的位置序号；
    根据所述位置序号确定所述融合接收机得到的解码结果为：
    Figure PCTCN2021076436-appb-100017
    其中，
    Figure PCTCN2021076436-appb-100018
    表示为所述发送符号集合X中第k *位置序号的发送符号。
  9. 一种基于空口信息融合的协作接收系统，其特征在于，包括：
    发射机，用于同时向N个协作接收机发送第一信道编码信号，N为设定常数；
    协作接收机，用于消除信道对所述第一信道编码信号的相位旋转，得到第二信道编码信号；
    对数似然比计算模块，用于计算所述N个协作接收机的第二信道编码信号的信噪比，从所述N个协作接收机中选取Q个在设定信噪比范围内的协作接收机，根据Q个协作接收机的第二信道编码信号计算对数似然比，其中，Q为正整数，Q≤N；
    空口信息融合传输模块，用于从所述Q个协作接收机中任意选取一个协作接收机当作融合接收机，通过空口信息融合的方式将剩下的(Q-1)个协作接收机的对数似然比传输至所述融合接收机；
    信息整合模块，用于控制所述融合接收机整合所述Q个协作接收机的对数似然比信息；
    解码模块，用于根据整合后的对数似然比信息对所述第一信道编码信号进行解码，得到解码结果；
    传播模块，用于将所述解码结果广播给除所述融合接收机以外的(N-1)个协作接收机。
  10. 根据权利要求9所述的系统，其特征在于，所述空口信息融合传输模块包括：
    归一化信息发送模块，用于将所述(Q-1)个协作接收机的对数似然比乘以归一化因子b得到的归一化信号，重复发送至所述融合接收机Z次，Z为设定常数；
    归一化信息接收模块，用于将所述融合接收机通过归一化因子a对所述归一化信号进行接收，得到接收信号。
PCT/CN2021/076436 2020-07-21 2021-02-10 基于空口信息融合的协作接收方法及系统 Ceased WO2022016856A1 (zh)

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