WO2022001966A1 - 双向dc变换器及其控制方法、控制模块、存储介质 - Google Patents

双向dc变换器及其控制方法、控制模块、存储介质 Download PDF

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Publication number
WO2022001966A1
WO2022001966A1 PCT/CN2021/102783 CN2021102783W WO2022001966A1 WO 2022001966 A1 WO2022001966 A1 WO 2022001966A1 CN 2021102783 W CN2021102783 W CN 2021102783W WO 2022001966 A1 WO2022001966 A1 WO 2022001966A1
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Prior art keywords
switch tube
bidirectional
converter
duty cycle
pole
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PCT/CN2021/102783
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English (en)
French (fr)
Inventor
周建平
王恰
刘明明
林国仙
鄂本
崔玉龙
Original Assignee
中兴通讯股份有限公司
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Application filed by 中兴通讯股份有限公司 filed Critical 中兴通讯股份有限公司
Priority to EP21833767.3A priority Critical patent/EP4175147A4/en
Priority to JP2022581495A priority patent/JP7521017B2/ja
Priority to US18/013,497 priority patent/US20230344353A1/en
Publication of WO2022001966A1 publication Critical patent/WO2022001966A1/zh
Priority to ZA2023/01138A priority patent/ZA202301138B/en

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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
    • H02M3/158—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
    • H02M3/1584—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load with a plurality of power processing stages connected in parallel
    • H02M3/1586—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load with a plurality of power processing stages connected in parallel switched with a phase shift, i.e. interleaved
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
    • H02M3/158—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
    • H02M3/1582—Buck-boost converters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
    • H02M3/158—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0003—Details of control, feedback or regulation circuits
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
    • H02M1/088—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters for the simultaneous control of series or parallel connected semiconductor devices
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
    • H02M3/158—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
    • H02M3/1584—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load with a plurality of power processing stages connected in parallel
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

Definitions

  • the present application relates to the field of electronic equipment, and in particular, to a control method for a bidirectional DC converter, a control module for a bidirectional DC converter, a bidirectional DC converter, and a computer-readable storage medium.
  • a DC/DC converter is a power device that converts one DC voltage to another DC voltage, wherein the bidirectional DC converter can not only convert one DC voltage to another DC voltage, but also Energy flows bidirectionally between the input side and the output side of the bidirectional DC converter.
  • the four-switch bidirectional DC converter includes a first bridge arm, a second bridge arm, and a connection between the first bridge arm and the second bridge arm. between the inductance L1.
  • the first bridge arm includes a first switch tube VT1 and a second switch tube VT2, the first pole of the first switch tube VT1 is electrically connected to the positive pole of the input end of the bidirectional DC converter, and the first switch tube VT1 is electrically connected.
  • the second pole is electrically connected to the first pole of the second switch tube VT2, and the second pole of the second switch tube VT2 is electrically connected to the negative pole of the input end of the bidirectional DC converter.
  • the second bridge arm includes a third switch tube VT3 and a fourth switch tube VT4.
  • the first pole of the third switch tube VT3 is electrically connected to the negative pole of the output end of the bidirectional DC converter
  • the second pole of the third switch tube VT3 is electrically connected to the first pole of the fourth switch tube VT4
  • the fourth switch tube VT4 The second pole of the bidirectional DC converter is electrically connected to the positive pole of the output end of the bidirectional DC converter.
  • the first end of the inductor L1 is electrically connected to the first pole of the first switch tube VT1, and the second end of the inductor L1 is electrically connected to the first pole of the fourth switch tube VT4.
  • the working modes of the bidirectional DC converter include a buck (Buck) mode, a boost (Boost) mode and a Buck/Boost mode.
  • the first bridge arm works, the first switch VT1 and the second switch VT2 are turned on alternately, the third switch VT3 in the second bridge arm is always off, and the fourth switch in the second bridge arm Tube VT4 is always on.
  • the first bridge arm and the second bridge arm work at the same time, the first switch VT1 and the third switch VT3 are turned on and off synchronously, and the second switch VT2 and the fourth switch VT4 are turned on and off synchronously. .
  • the first switch VT1 and the second switch VT2 are alternately turned on and off, and the third switch VT3 and the fourth switch VT4 are alternately turned on and off.
  • the second bridge arm works, the third switch tube VT3 and the fourth switch tube VT4 are turned on alternately, the first switch tube VT1 in the first bridge arm is always turned on, and the second switch tube VT2 is always turned off.
  • the purpose of the present disclosure is to provide a control method of a bidirectional DC converter, a control module of a bidirectional DC converter, a bidirectional DC converter, and a computer-readable storage medium.
  • the bidirectional DC converter includes at least one power conversion unit, and the power conversion unit includes a first bridge arm, a second bridge arm, and an inductor , the first bridge arm includes a first switch tube and a second switch tube, the first pole of the first switch tube is electrically connected to the positive pole of the input end of the bidirectional DC converter, and the first pole of the first switch tube is electrically connected to the positive pole of the input end of the bidirectional DC converter.
  • the diode is electrically connected to the first pole of the second switch tube, the second pole of the second switch tube is electrically connected to the negative pole of the input end of the bidirectional DC converter, and the second bridge arm includes a third switch tube and a fourth switch tube, the first pole of the third switch tube is electrically connected to the negative pole of the output end of the bidirectional DC converter, and the second pole of the third switch tube is electrically connected to the second pole of the fourth switch tube One pole is electrically connected, the second pole of the fourth switch tube is electrically connected to the positive pole of the output end of the bidirectional DC converter, the first end of the inductor is electrically connected to the second pole of the first switch tube, The second end of the inductor is electrically connected to the first pole of the fourth switch tube; the control method includes: determining the working mode of the bidirectional DC converter according to the input voltage and the output voltage; according to the bidirectional DC conversion The duty cycle of the drive signal of the first switch tube, the duty cycle of the drive signal of the second switch tube, the duty cycle of the
  • a control module for a bidirectional DC converter includes at least one power conversion unit, and the power conversion unit includes a first bridge arm and a second bridge arm and inductor, the first bridge arm includes a first switch tube and a second switch tube, the first pole of the first switch tube is electrically connected to the positive pole of the input end of the bidirectional DC converter, the first switch tube The second pole of the second switch tube is electrically connected to the first pole of the second switch tube, the second pole of the second switch tube is electrically connected to the negative pole of the input end of the bidirectional DC converter, and the second bridge arm includes the first pole of the second switch tube.
  • the first pole of the third switch tube is electrically connected to the negative pole of the output end of the bidirectional DC converter
  • the second pole of the third switch tube is electrically connected to the fourth switch tube
  • the first pole of the inductance is electrically connected to the first pole
  • the second pole of the fourth switch tube is electrically connected to the positive pole of the output end of the bidirectional DC converter
  • the first end of the inductor is electrically connected to the second pole of the first switch tube.
  • the control module includes: a signal processing unit, the signal processing unit is configured to determine the The working mode of the bidirectional DC converter, and the duty cycle of the driving signal of the first switch tube, the duty cycle of the driving signal of the second switch tube, the duty cycle of the driving signal of the second switch tube, and the The duty cycle of the drive signal of the third switch tube and the duty cycle of the drive signal of the fourth switch tube, the duty cycle of the drive signal of the first switch tube, the drive signal of the second switch tube.
  • the duty cycle of , the duty cycle of the drive signal of the third switch tube, the duty cycle of the drive signal of the fourth switch tube and the operating mode of the bidirectional DC converter satisfy the following relationship: when all When the bidirectional DC converter works in the step-down Buck mode, the maximum value of the duty cycle of the driving signal of the first switch tube is the first duty cycle threshold; when the bidirectional DC converter works in the boost boost mode In the mode, the minimum value of the duty cycle of the driving
  • the drive unit is configured In order to output the drive signal of the first switch tube from the first output terminal according to the duty cycle of the drive signal of the first switch tube, and output the drive signal of the second switch tube from the second switch tube according to the duty cycle of the drive signal of the second switch tube.
  • the output terminal outputs the drive signal of the second switch tube, outputs the drive signal of the third switch tube from the third output terminal according to the duty cycle of the drive signal of the third switch tube, and outputs the drive signal of the fourth switch tube from the third output end
  • the duty cycle of the signal outputs the drive signal of the fourth switch tube from the fourth output terminal.
  • a bidirectional DC converter comprising: at least one power conversion unit, the power conversion unit includes a first bridge arm, a second bridge arm and an inductor, the first bridge arm includes a first switch tube and a second switch tube, the first pole of the first switch tube is electrically connected to the positive pole of the input end of the bidirectional DC converter, and the second pole of the first switch tube is electrically connected to the second switch tube The first pole of the second switch tube is electrically connected to the first pole of the second switch tube, and the second pole of the second switch tube is electrically connected to the negative pole of the input end of the bidirectional DC converter.
  • the second bridge arm includes a third switch tube and a fourth switch tube, so The first pole of the third switch tube is electrically connected to the negative pole of the output end of the bidirectional DC converter, the second pole of the third switch tube is electrically connected to the first pole of the fourth switch tube, and the second pole of the third switch tube is electrically connected to the first pole of the fourth switch tube.
  • the second pole of the four-switch tube is electrically connected to the positive pole of the output end of the bidirectional DC converter, the first end of the inductor is electrically connected to the second pole of the first switch tube, and the second end of the inductor is electrically connected to the The first pole of the fourth switch tube is electrically connected; the control module according to the second aspect of the present disclosure.
  • a computer-readable storage medium is provided.
  • An executable program is stored on the computer-readable storage medium.
  • the executable program is called, the claims provided by the present disclosure can be realized. the above control method.
  • FIG. 1 is a schematic circuit diagram of a bidirectional DC converter in some situations in the art
  • FIG. 2 is a schematic structural diagram of an embodiment of a bidirectional DC converter provided by the present application.
  • FIG. 3 is a schematic diagram of three operating modes of the bidirectional DC converter involved in the present application.
  • Fig. 5 is each driving waveform diagram of three modes switching in embodiment 1;
  • Embodiment 6 is a division diagram of three mode switching hysteresis control intervals in Embodiment 2;
  • Fig. 7 is each driving waveform diagram of three modes switching in embodiment 2;
  • Embodiment 8 is a circuit structure diagram of two power conversion units in Embodiment 4.
  • FIG. 9 is a schematic flowchart of step S110.
  • the control methods of bidirectional DC converters working in Buck/Boost mode mainly include single-carrier dual-modulated wave and single-carrier single-modulated wave.
  • the single-carrier dual-modulated wave control method two modulation methods are used.
  • the wave controls the on-off of the switch tube in the second left bridge arm respectively.
  • the problem is that the duty cycle of the switch tube drive signal is infinitely close to 1 or infinitely close to 0.
  • the duty cycle is infinitely close to 1
  • a control method of a bidirectional DC converter is provided.
  • the bidirectional DC converter includes at least one power conversion unit 100 , and the power conversion unit 100 includes a first bridge arm, a second bridge arm and an inductor L1 .
  • the first bridge arm includes a first switch tube VT1 and a second switch tube VT2, the first pole of the first switch tube VT1 is electrically connected to the positive terminal Vin+ of the input terminal of the bidirectional DC converter, and the first switch tube VT1 is electrically connected.
  • the second pole is electrically connected to the first pole of the second switch tube VT2, and the second pole of the second switch tube VT2 is electrically connected to the negative Vin ⁇ of the input terminal of the bidirectional DC converter.
  • the second bridge comprises a third switch tube VT3 and VT4 fourth switching transistor, a first electrode of the third switching transistor VT3 output terminal of the bidirectional DC converter of the negative Vo- - electrically connected to the third switch
  • the second pole of the tube is electrically connected to the first pole of the fourth switch tube, and the second pole of the fourth switch tube is electrically connected to the positive pole Vo + of the output end of the bidirectional DC converter.
  • the first end of the inductor L1 is electrically connected to the second pole of the first switch tube VT1, and the second end of the inductor L1 is electrically connected to the first pole of the fourth switch tube VT4.
  • control method includes:
  • step S110 the working mode of the bidirectional DC converter is determined according to the input voltage and the output voltage
  • step S120 the duty cycle of the driving signal of the first switch transistor, the duty cycle of the drive signal of the second switch transistor, and the third switch are respectively determined according to the working mode of the bidirectional DC converter. the duty cycle of the driving signal of the tube and the duty cycle of the driving signal of the fourth switch tube;
  • step S130 a drive signal is provided to the gate of the first switch tube according to the determined duty cycle of the drive signal of the first switch tube, and a drive signal is provided to the second switch tube according to the determined duty cycle of the drive signal of the second switch tube.
  • the gate of the third switch tube provides the drive signal, according to the determined duty cycle of the drive signal of the third switch tube, provides the drive signal to the gate of the third switch tube, according to the determined duty cycle of the drive signal of the fourth switch tube to the fourth switch tube.
  • the gate of the switch tube provides the drive signal.
  • the duty cycle of the drive signal of the first switch tube, the duty cycle of the drive signal of the second switch tube, the duty cycle of the drive signal of the third switch tube and the fourth switch tube is satisfied between the duty cycle of the driving signal and the operating mode of the bidirectional DC converter:
  • the maximum value of the duty cycle of the driving signal of the first switch tube is the first duty cycle threshold
  • the minimum value of the duty cycle of the driving signal of the third switch tube is the second duty cycle threshold
  • the duty cycle of the drive signal of the first switch tube is a constant value
  • the duty cycle of the drive signal of the third switch tube is adjusted to achieve
  • the difference between the first duty cycle threshold and the constant value does not exceed a predetermined difference ⁇ .
  • the duty cycle of the driving signal of the third switch tube satisfies:
  • D 11 is the constant value
  • K1 is the step-down coefficient of the bidirectional DC converter, 0.9 ⁇ K1 ⁇ 1;
  • K2 is the boost coefficient of the bidirectional DC converter, 1 ⁇ K2 ⁇ 1.1.
  • the switching frequencies of the switches of different bidirectional DC converters are set differently, and the models of the switches and the parameters of the drive circuits that generate each drive signal are different from each other.
  • the drive signal of each switch must meet a minimum duty cycle requirement. Otherwise, due to factors such as delay and parasitic capacitance of the driving circuit generating the driving signal, the duty cycle of the driving signal finally provided to the switch tube will be reduced, so that the switch tube cannot be fully turned on.
  • the values of the step-down coefficient K1 and the step-up coefficient K2 are both fixed, so as to meet the requirements of the DC converter for normal operation.
  • D 1 is the duty cycle of the driving signal VG1 provided to the gate of the first switch tube VT1.
  • the duty cycle of the driving signal VG1 provided to the gate of the first switch transistor VT1 also increases.
  • the duty cycle D1 exists in the Buck mode. the maximum value (ie, the first duty cycle threshold, denoted by D 1max).
  • K1 is the step-down coefficient.
  • Vo (D 11 ⁇ Vin)/(1-D 2 ).
  • the first switch drive signal VG1 holding tube VT1 drive signals VG1 accounted D 11 of the first cycle of the switch VT1 maximum duty cycle D 1max in close Buck mode,
  • the duty cycle of the driving signal VG1 of the first switch VT1 does not undergo a large sudden change during the transition from the Buck mode to the Buck/Boost mode, and can ensure that each switch is effectively turned on and off. Since the driving signals of the first switch VT1 and the second switch VT2 work complementary, the duty cycle of the driving signal VG2 of the second switch VT2 will not occur during the process of switching from the Buck mode to the Buck/Boost mode. big mutation.
  • the fourth switch VT4 When the bidirectional DC converter is in the Buck mode, the fourth switch VT4 is in a normally-on state. At this time, the drive signal VG4 of the fourth switch VT4 remains in a high level state. After entering the Buck/Boost mode, the first The driving signal VG4 of the four-switch VT4 starts to operate at the same switching frequency as the first switch VT1.
  • the duty cycle of the drive signal VG3 of the third switch VT3 satisfies the above-mentioned "1-D 11 /K1 ⁇ D2 ⁇ 1-D 11 /K2 ”
  • the duty cycle of the drive signal VG3 of the third switch VT3 is slightly greater than 0, and can ensure the effective conduction of the third switch VT3, thus ensuring that the bidirectional DC converter from Buck mode In the process of switching to Buck/Boost mode, it is slightly increased from 0, and no big mutation of duty cycle will occur.
  • the duty cycle of the driving signal VG4 of the fourth switch VT4 is from 1 is slightly reduced, and no large sudden change in duty cycle occurs.
  • the first switch VT1 works in a normally-on state.
  • the duty cycle of the driving signal VG1 of the first switch VT1 is 1, and the second switch VT2 is normally off.
  • the duty cycle of the driving signal VG2 of the second switch tube VT2 is 0.
  • a third switch drive signal VT3 tube of the duty cycle is gradually increased with an increase of the output voltage
  • the third switch drive signal VT3 VG2 duty cycle D is just entering the Boost mode 2 is slightly greater than zero to ensure that the
  • the duty cycle of the drive signal VG3 of the third switch VT3 does not undergo a sudden change, and similarly the duty cycle of the drive signal of the fourth switch VT4 is also No major mutation will occur.
  • ⁇ is not particularly limited in the present disclosure.
  • the predetermined difference satisfies the following relationship:
  • the first duty cycle threshold may be 0.95 and the constant value may be 0.92.
  • the duty cycle VG1 of the driving signal of the first switch VT1 is kept at 0.92, which is very close to the maximum duty cycle of the driving signal VG1 in the Buck mode, which is 0.95, thereby ensuring that the bidirectional DC
  • the step S110 may include:
  • step S111 the input voltage and the output voltage are sampled respectively
  • step S112 compare the input voltage obtained by sampling with the output voltage obtained by sampling
  • step S113 when Vo ⁇ K1 ⁇ Vin, it is determined that the working mode of the bidirectional DC converter is Buck mode; when K1 ⁇ Vin ⁇ Vo ⁇ K2 ⁇ Vin, it is determined that the working mode of the bidirectional DC converter is Buck/Boost mode; when K2 ⁇ Vin ⁇ Vo, it is determined that the working mode of the bidirectional DC converter is the Boost mode.
  • step S113 hysteresis judgment may be added at each switching point.
  • the first hysteresis judgment coefficient K1' and the step-down coefficient K1 should be close, and in some examples, the difference between the two should not exceed 0.05. For example, when K1 is 0.95, K1' may be 0.92.
  • the second hysteresis judgment coefficient K2' and the boost coefficient K1 should also be close, and the difference between the two should not exceed 0.05 in some examples.
  • K2' may be 1.02.
  • the first duty cycle threshold D 1max is the same as K1 .
  • K1 and D 1max are both 0.95.
  • the second duty cycle threshold satisfies the following relationship:
  • D 2min is the second duty cycle threshold.
  • a control module 200 for a bidirectional DC converter is provided. As shown in FIG. 2 , the control module 200 includes a signal processing unit 210 and a driving unit 220 .
  • the signal processing unit 210 is configured to determine the operation mode of the bidirectional DC converter according to the input voltage and the output voltage, and respectively determine the duty cycle of the driving signal VG1 of the first switch tube VT1 according to the operation mode of the bidirectional DC converter , the duty cycle of the drive signal VG2 of the second switch tube VT2, the duty cycle of the drive signal VG3 of the third switch tube VT3, and the duty cycle of the drive signal VG4 of the fourth switch tube VT4.
  • the duty cycle of the drive signal VG1 of the first switch tube VT1, the duty cycle of the drive signal VG2 of the second switch tube VT2, the duty cycle of the drive signal VG3 of the third switch tube VT3, and the drive signal of the fourth switch tube VT4 satisfies the following relationship:
  • the maximum value of the duty cycle of the driving signal VG1 of the first switch tube VT1 is the first duty cycle threshold
  • the maximum value of the duty cycle of the driving signal of the first switch tube is the first duty cycle threshold
  • the minimum value of the duty cycle of the driving signal of the third switch tube is the second duty cycle threshold
  • the duty cycle of the driving signal of the first switch tube is a constant value, and the difference between the first duty cycle threshold value and the constant value does not exceed the predetermined difference, and the duty cycle of the driving signal of the third switch tube satisfies:
  • D 11 is the constant value
  • K1 is the step-down coefficient of the bidirectional DC converter, 0.9 ⁇ K1 ⁇ 1;
  • K2 is the boost coefficient of the bidirectional DC converter, 1 ⁇ K2 ⁇ 1.1;
  • the driving unit 220 has at least one output terminal group, and each output terminal group includes a first output terminal electrically connected to the gate of the first switching transistor VT1 and a second output terminal electrically connected to the gate of the second switching transistor VT2 , a third output terminal electrically connected to the gate of the third switch tube VT3, and a fourth output terminal electrically connected to the gate of the fourth switch tube VT4.
  • the driving unit 220 is configured to output the driving signal VG1 of the first switching transistor VT1 according to the duty cycle of the driving signal VG1 of the first switching transistor VT1 and the duty cycle of the driving signal of the second switching transistor VT2 from the first output terminal
  • the drive signal VG2 of the second switch tube VT2 is output from the second output terminal
  • the drive signal of the third switch tube VT3 is output from the third output terminal according to the duty cycle of the drive signal of the third switch tube VT3.
  • VG3 and the driving signal VG4 of the fourth switching transistor are output from the fourth output terminal according to the duty cycle of the driving signal of the fourth switching transistor VT4.
  • the control module 200 is configured to execute the above-mentioned control method provided by the present disclosure.
  • the principles and intended effects of the control method have been described in detail above, and will not be repeated here.
  • control module further includes:
  • the input voltage sampling unit 230 is configured to collect the input voltage of the bidirectional DC converter
  • An output voltage sampling unit 240 the output voltage sampling unit 240 is configured to collect the output voltage of the bidirectional DC converter.
  • the predetermined difference satisfies the following relationship:
  • ⁇ is the predetermined difference.
  • the signal processing unit 210 determines that the working mode of the bidirectional DC converter is the Buck mode.
  • the signal processing unit 210 determines that the working mode of the bidirectional DC converter is the Buck/Boost mode.
  • the signal processing unit 230 determines that the working mode of the bidirectional DC converter is the Boost mode.
  • the signal processing unit 210 determines that the working mode of the bidirectional DC converter is the Buck mode, wherein, K1' is the first hysteresis judgment coefficient, 0 ⁇ K1' ⁇ K1.
  • the signal processing unit 210 determines that the working mode of the bidirectional DC converter is the Buck/Boost mode, K2' is the second hysteresis judgment coefficient, 1 ⁇ K2' ⁇ K2.
  • the first duty cycle threshold is the same as K1, and the second duty cycle threshold satisfies the following relationship:
  • D 2min is the second duty cycle threshold.
  • Vo (D 11 ⁇ Vin)/(1-D 2 ), wherein D 2 is the duty cycle of the driving signal of the third switch tube, and D 11 is the constant value.
  • a bidirectional DC converter is provided. As shown in FIG. 2 , the bidirectional DC converter includes at least one power conversion unit 100 and the aforementioned control module 200 provided by the present disclosure.
  • the power conversion unit 100 includes a first bridge arm, a second bridge arm and an inductor L1.
  • the first bridge arm includes a first switch tube VT1 and a second switch tube VT2, the first pole of the first switch tube VT1 is electrically connected to the positive terminal Vin+ of the input terminal of the bidirectional DC converter, and the first switch tube VT1 is electrically connected.
  • the second pole is electrically connected to the first pole of the second switch tube VT2, and the second pole of the second switch tube VT2 is electrically connected to the negative Vin ⁇ of the input terminal of the bidirectional DC converter.
  • the second bridge comprises a third switch tube VT3 and VT4 fourth switching transistor, a first electrode of the third switching transistor VT3 output terminal of the bidirectional DC converter of the negative Vt - electrically connected to the third switch tube
  • the second pole of the fourth switch tube is electrically connected to the first pole of the fourth switch tube, and the second pole of the fourth switch tube is electrically connected to the positive pole V + of the output terminal of the bidirectional DC converter.
  • the first end of the inductor L1 is electrically connected to the second pole of the first switch tube VT1, and the second end of the inductor L1 is electrically connected to the first pole of the fourth switch tube VT4.
  • the number of the power output units 100 is not particularly limited.
  • the bidirectional DC converter includes two power output units 100 connected in parallel.
  • an input filter capacitor Cin may be connected between the positive pole of the input terminal and the negative pole of the input terminal of the bidirectional DC converter
  • an output filter capacitor Co may be connected between the positive pole of the output terminal and the negative pole of the output terminal of the DC converter.
  • the switching frequencies of the first bridge arm and the second bridge arm are both set to 25KHz.
  • the step-down coefficient K1 is 0.95, and the step-up coefficient K2 is 1.05.
  • the input voltage sampling unit 230 samples the input voltage signal and sends it to the signal processing unit 210
  • the output voltage sampling unit 240 samples the output voltage signal and sends it to the signal processing unit 210
  • the signal processing unit 210 detects 0.95 ⁇ Vin ⁇ Vo ⁇ K2 ⁇ Vin, the signal processing unit 210 determines that the output voltage is relatively close to the input voltage, and further determines that the power conversion unit 100 is in the Buck/Boost mode, and is set in this mode
  • the duty cycle D2 of the signal VG3 adjusts the output voltage, so in Buck/Boost mode 0.032 ⁇ D 22 ⁇ 0.124, the on-time of the third switch VT3 is 1.28 ⁇ S ⁇ T ⁇ 4.96 ⁇ S.
  • the driving signal VG4 of the fourth switch tube VT4 After entering the Buck/Boost mode, the driving signal VG4 of the fourth switch tube VT4 starts to operate at the same switching frequency as the first switch tube VT1. And the driving high-level signal of the fourth switch tube VT4 and the high-level signal of the first switch tube VT1 are center-symmetrical.
  • a schematic diagram of waveforms of each driving signal in each mode is shown in FIG. 5 .
  • the duty cycle of the signal VG3 increases from 0 to the range of 0.032 to 0.124 during the process of switching from the Buck mode to the Buck/Boost mode, and a large-scale sudden change of the duty cycle does not occur.
  • the duty cycle (1-D 22 ) of the driving signal VG4 of the fourth switch tube VT4 is switched from the Buck mode to the Buck/Boost mode during the process is reduced from 1 to the range of 0.968 to 0.876, so that the duty cycle of the driving signal VG4 does not undergo a large sudden change.
  • the signal processing unit 210 When the signal processing unit 210 detects that 1.05 ⁇ Vin ⁇ Vo, the signal processing unit 210 will consider that the output voltage is greater than the input voltage, determine that the power output unit 100 is working in the boost mode, and set the first switch VT1 to work in the normally-on state , at this time, the duty cycle of the driving signal VG1 of the first switch VT1 is 1, and the second switch VT2 is set to be in a normally off state. At this time, the duty cycle of the driving signal VG2 of the second switch VT2 is 0.
  • the mode enters the Boost mode it changes from 0.124 to 0.048, which also makes the duty cycle of the drive signal VG3 not change greatly when switching from Buck/Boost mode to Boost mode.
  • the duty cycle of the drive signal VG4 changes from Buck/Boost mode to Boost mode.
  • the Boost mode is switched to the Boost mode, it changes from 0.876 to 0.952, and there is no big mutation.
  • the above description is the description of the process of changing the duty cycle of each switch when the input voltage remains unchanged and the output voltage gradually increases.
  • the output voltage gradually decreases from a high voltage.
  • the inverse process of the duty cycle of each switch is changed in the opposite direction, and it is also smooth and excessive without major sudden change, which is not described in detail here.
  • Switching can add hysteresis judgment at each switching point.
  • the hysteresis setting is shown in Figure 6. In the figure, when the input voltage remains unchanged and the output voltage rises above 0.95Vin, the circuit enters Buck/Boost mode from Buck mode.
  • the circuit When the voltage is lower than 0.92Vin, the circuit enters Buck mode from Buck/Boost mode; also when the output voltage rises above 1.05Vin, the circuit enters Boost mode from Buck/Boost mode, and when the output voltage is lower than 1.02Vin, the circuit switches from Boost mode enters Buck/Boost mode.
  • Embodiment 2 The difference from Embodiment 1 is that in this embodiment, the rising edge of the driving signal VG3 of the third switching transistor VT3 and the rising edge of the driving signal VG1 of the first switching transistor VT1 are generated at the same time.
  • a schematic diagram of waveforms of each driving signal in each mode in Embodiment 2 is shown in FIG. 7 .
  • the duty cycle range in /Boost mode is:
  • the turn-on time of the third switch VT3 in the Buck/Boost mode is 1.48 ⁇ S ⁇ T ⁇ 3.24 ⁇ S.
  • the bidirectional DC converter in this embodiment includes two independent power output units 100 , the input ends of the two power input units are connected in parallel, the output ends are connected in parallel, and the second circuit 180° phase staggered work with the first channel.
  • a computer-readable storage medium is provided, and an executable program is stored on the computer-readable storage medium.
  • the executable program is called, the above-mentioned provided by the present disclosure can be implemented. Control Method.
  • the duty cycle of the driving signal of each switch tube can be prevented from changing greatly, thereby Avoid the phenomenon of voltage imbalance.
  • Such software may be distributed on computer-readable media, which may include computer storage media (or non-transitory media) and communication media (or transitory media).
  • computer storage media includes both volatile and nonvolatile implemented in any method or technology for storage of information such as computer readable instructions, data structures, program modules or other data flexible, removable and non-removable media.
  • Computer storage media include, but are not limited to, RAM, ROM, EEPROM, flash memory or other memory technology, CD-ROM, digital versatile disk (DVD) or other optical disk storage, magnetic cartridges, magnetic tape, magnetic disk storage or other magnetic storage devices, or may Any other medium used to store desired information and which can be accessed by a computer.
  • communication media typically embodies computer readable instructions, data structures, program modules, or other data in a modulated data signal such as a carrier wave or other transport mechanism, and can include any information delivery media, as is well known to those of ordinary skill in the art .

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Abstract

一种双向DC变换器的控制方法、控制模块、DC变换器和计算机可读存储介质，控制方法包括：根据输入电压和输出电压确定双向DC变换器的工作模式(S110)；根据双向DC变换器的工作模式分别确定第一开关管的驱动信号的占空度、第二开关管的驱动信号的占空度、第三开关管的驱动信号的占空度和第四开关管的驱动信号的占空度(S120)；根据确定的第一开关管的驱动信号的占空度向第一开关管的栅极提供驱动信号、根据确定的第二开关管的驱动信号的占空度向第二开关管的栅极提供驱动信号、根据确定的第三开关管的驱动信号的占空度向第三开关管的栅极提供驱动信号、根据确定的第四开关管的驱动信号的占空度向第四开关管的栅极提供驱动信号(S130)。

Description

双向DC变换器及其控制方法、控制模块、存储介质
相关申请的交叉引用
本申请基于申请号为202010605231.0、申请日为2020年6月29日的中国专利申请提出，并要求该中国专利申请的优先权，该中国专利申请的全部内容在此引入本申请作为参考。
技术领域
本申请涉及电子设备领域，具体地，涉及一种双向DC变换器的控制方法、一种双向DC变换器的控制模块、一种双向DC变换器和一种计算机可读存储介质。
背景技术
DC/DC变换器是一种将一种直流电压转换层另一种直流电压的功率装置，其中，双向DC变换器除了能够将一种直流电压转换层另一种直流电压之外，还能够实现能量在双向DC变换器的输入侧和输出侧之间双向流动。
图1中所示的是一种常见的四开关双向DC变换器，具体地，该四开关双向DC变换器包括第一桥臂、第二桥臂和连接在第一桥臂和第二桥臂之间的电感L1。
所述第一桥臂包括第一开关管VT1和第二开关管VT2，所述第一开关管VT1的第一极与所述双向DC变换器的输入端正极电连接，第一开关管VT1的第二极与第二开关管VT2的第一极电连接，第二开关管VT2的第二极与所述双向DC变换器的输入端负极电连接。所述第二桥臂包括第三开关管VT3和第四开关管VT4。第三开关管VT3的第一极与所述双向DC变换器的输出端负极电连接，第三开关管VT3的第二极与第四开关管VT4的第一极电连接，第四开关管VT4的第二极与所述双向DC变换器的输出端正极电连接。
电感L1的第一端与所述第一开关管VT1的第一极电连接，电感L1的第二端与第四开关管VT4的第一极电连接。
双向DC变换器的工作模式包括降压(Buck)模式、升压(Boost)模式和Buck/Boost模式。
在Buck模式下，第一桥臂工作，第一开关管VT1和第二开关管VT2交替导通，第二桥臂中的第三开关管VT3常关断，第二桥臂中的第四开关管VT4常导通。
在Buck/Boost模式中，第一桥臂和第二桥臂同时工作，第一开关管VT1和第三开关管VT3同步地通断，第二开关管VT2和第四开关管VT4同步地通断。第一开关管VT1和第二开关管VT2交替地通断，第三开关管VT3和第四开关管VT4交替地通断。
在Boost模式中，第二桥臂工作，第三开关管VT3和第四开关管VT4交替导通，第一桥臂中的第一开关管VT1常导通，第二开关管VT2常关断。
在三模态工作方式下，特别是由Buck模式过渡到Buck/Boost模式，或者从Buck/Boost模式过渡到Boost模式时现有控制方法，有的会存在电压失调的问题。
发明内容
本公开的目的在于提供一种双向DC变换器的控制方法、一种双向DC变换器的控制模块、一种双向DC变换器和一种计算机可读存储介质。
作为本公开的第一个方面，提供一种双向DC变换器的控制方法，所述双向DC变换器包括至少一个功率变换单元，所述功率变换单元包括第一桥臂、第二桥臂和 电感，所述第一桥臂包括第一开关管和第二开关管，所述第一开关管的第一极与所述双向DC变换器的输入端正极电连接，所述第一开关管的第二极与所述第二开关管的第一极电连接，所述第二开关管的第二极与所述双向DC变换器的输入端负极电连接，所述第二桥臂包括第三开关管和第四开关管，所述第三开关管的第一极与所述双向DC变换器的输出端负极电连接，所述第三开关管的第二极与所述第四开关管的第一极电连接，所述第四开关管的第二极与所述双向DC变换器的输出端正极电连接，所述电感的第一端与所述第一开关管的第二极电连接，所述电感的第二端与所述第四开关管的第一极电连接；所述控制方法包括：根据输入电压和输出电压确定所述双向DC变换器的工作模式；根据所述双向DC变换器的工作模式分别确定所述第一开关管的驱动信号的占空度、所述第二开关管的驱动信号的占空度、所述第三开关管的驱动信号的占空度和所述第四开关管的驱动信号的占空度；根据确定的第一开关管的驱动信号的占空度向第一开关管的栅极提供驱动信号、根据确定的第二开关管的驱动信号的占空度向第二开关管的栅极提供驱动信号、根据确定的第三开关管的驱动信号的占空度向第三开关管的栅极提供驱动信号、根据确定的第四开关管的驱动信号的占空度向第四开关管的栅极提供驱动信号；其中，所述第一开关管的驱动信号的占空度、所述第二开关管的驱动信号的占空度、所述第三开关管的驱动信号的占空度和所述第四开关管的驱动信号的占空度与所述双向DC变换器的工作模式之间满足以下关系：当所述双向DC变换器工作在降压Buck模式下时，所述第一开关管的驱动信号的占空度的最大值为第一占空度阈值；当所述双向DC变换器工作在升压Boost模式下时，所述第三开关管的驱动信号的占空度的最小值为第二占空度阈值；当所述双向DC变换器工作在Buck/Boost模式下时，所述第一开关管的驱动信号占空度为恒定值，所述第一占空度阈值与所述恒定值之间的差值不超过预定差值，并且，所述第三开关管的驱动信号的占空度满足：1-D 11/K1＜D2＜1-D 11/K2，其中，D 11为所述恒定值；K1为所述双向DC变换器的降压系数，0.9≤K1＜1；K2为所述双向DC变换器的升压系数，1＜K2＜1.1。
作为本公开的第二个方面，提供一种用于双向DC变换器的控制模块，所述双向DC变换器包括至少一个功率变换单元，所述功率变换单元包括第一桥臂、第二桥臂和电感，所述第一桥臂包括第一开关管和第二开关管，所述第一开关管的第一极与所述双向DC变换器的输入端正极电连接，所述第一开关管的第二极与所述第二开关管的第一极电连接，所述第二开关管的第二极与所述双向DC变换器的输入端负极电连接，所述第二桥臂包括第三开关管和第四开关管，所述第三开关管的第一极与所述双向DC变换器的输出端负极电连接，所述第三开关管的第二极与所述第四开关管的第一极电连接，所述第四开关管的第二极与所述双向DC变换器的输出端正极电连接，所述电感的第一端与所述第一开关管的第二极电连接，所述电感的第二端与所述第四开关管的第一极电连接；所述控制模块包括：信号处理单元，所述信号处理单元被配置为根据输入电压和输出电压确定所述双向DC变换器的工作模式、并根据所述双向DC变换器的工作模式分别确定所述第一开关管的驱动信号的占空度、所述第二开关管的驱动信号的占空度、所述第三开关管的驱动信号的占空度和所述第四开关管的驱动信号的占空度，所述第一开关管的驱动信号的占空度、所述第二开关管的驱动信号的占空度、所述第三开关管的驱动信号的占空度和 所述第四开关管的驱动信号的占空度与所述双向DC变换器的工作模式之间满足以下关系：当所述双向DC变换器工作在降压Buck模式下时，所述第一开关管的驱动信号的占空度的最大值为第一占空度阈值；当所述双向DC变换器工作在升压Boost模式下时，所述第三开关管的驱动信号的占空度的最小值为第二占空度阈值；当所述双向DC变换器工作在Buck/Boost模式下时，所述第一开关管的驱动信号占空度为恒定值，所述第一占空度阈值与所述恒定值之间的差值不超过预定差值，并且，所述第三开关管的驱动信号的占空度满足：1-D 11/K1＜D2＜1-D 11/K2，其中，D 11为所述恒定值；K1为所述双向DC变换器的降压系数，0.9≤K1＜1；K2为所述双向DC变换器的升压系数，1＜K2＜1.1；驱动单元，所述驱动单元具有至少一个输出端组，每个输出端组都包括与所述第一开关管的栅极电连接的第一输出端、与所述第二开关管的栅极电连接的第二输出端、与所述第三开关管的栅极电连接的第三输出端、与所述第四开关管的栅极电连接的第四输出端，所述驱动单元被配置为根据所述第一开关管的驱动信号的占空度从所述第一输出端输出第一开关管的驱动信号、根据所述第二开关管的驱动信号的占空度从所述第二输出端输出第二开关管的驱动信号、根据所述第三开关管的驱动信号的占空度从所述第三输出端输出第三开关管的驱动信号和根据所述第四开关管的驱动信号的占空度从所述第四输出端输出第四开关管的驱动信号。
作为本公开的第三个方面，提供一种双向DC变换器，包括：至少一个功率变换单元，所述功率变换单元包括第一桥臂、第二桥臂和电感，所述第一桥臂包括第一开关管和第二开关管，所述第一开关管的第一极与所述双向DC变换器的输入端正极电连接，所述第一开关管的第二极与所述第二开关管的第一极电连接，所述第二开关管的第二极与所述双向DC变换器的输入端负极电连接，所述第二桥臂包括第三开关管和第四开关管，所述第三开关管的第一极与所述双向DC变换器的输出端负极电连接，所述第三开关管的第二极与所述第四开关管的第一极电连接，所述第四开关管的第二极与所述双向DC变换器的输出端正极电连接，所述电感的第一端与所述第一开关管的第二极电连接，所述电感的第二端与所述第四开关管的第一极电连接；本公开的第二个方面所述的控制模块。
作为本公开的第四个方面，提供一种计算机可读存储介质，所述计算机可读存储介质上存储有可执行程序，当所述可执行程序被调用时，能够实现权利要求本公开所提供的上述控制方法。
附图说明
附图是用来提供对本申请的进一步理解，并且构成说明书的一部分，与下面的具体实施方式一起用于解释本申请，但并不构成对本申请的限制。在附图中：
图1是本领域一些情形中双向DC转换器的电路示意图；
图2是本申请所提供的双向DC转换器的一种实施方式的结构示意图；
图3是本申请中所涉及的双向DC转换器的三种工作模式工作范围示意图；
图4为本申请第一个方面所提供的控制方法的一种实施方式的流程图；
图5为实施例1中三种模式切换各驱动波形图；
图6为实施例2中三种模式切换滞环控制区间划分图；
图7为实施例2中三种模式切换各驱动波形图；
图8为实施例4中两个功率变换单元的电路结构图；
图9是步骤S110的流程示意图。
具体实施方式
以下结合附图对本发明的具体实施方式进行详细说明。应当理解的是，此处所描述的具体实施方式仅用于说明和解释本发明，并不用于限制本发明。
在本领域一些情形中，工作在Buck/Boost模式下的双向DC变换器，控制方法主要有单载波双调制波和单载波单调制波两种方法，在单载波双调制波控制方法中两调制波分别控制左第二桥臂中开关管的通断，存在的问题在于开关管驱动信号的占空度有无限接近于1或者接无限近于0的情况，当占空度无限趋近于1或无限趋近于0时都会存在电压失调的问题。另外一种如果在Buck和Boost模式使用单载波双调制波然后在进入Buck/Boost模式后切换到单载波单调制波时又会出现开关管驱动信号占空度突变的情况，这样就会有电感电流发生突变，输出电压指标变差的问题。
有鉴于此，作为本公开的第一个方面，提供一种双向DC变换器的控制方法。
如图2所示，在本公开中，所述双向DC变换器包括至少一个功率变换单元100，该功率变换单元100包括第一桥臂、第二桥臂和电感L1。所述第一桥臂包括第一开关管VT1和第二开关管VT2，第一开关管VT1的第一极与所述双向DC变换器的输入端正极Vin +电连接，第一开关管VT1的第二极与第二开关管VT2的第一极电连接，第二开关管VT2的第二极与所述双向DC变换器的输入端负极Vin -电连接。
所述第二桥臂包括第三开关管VT3和第四开关管VT4，第三开关管VT3的第一极与所述双向DC变换器的输出端负极Vo- -电连接，所述第三开关管的第二极与所述第四开关管的第一极电连接，所述第四开关管的第二极与所述双向DC变换器的输出端正极Vo +电连接。
电感L1的第一端与第一开关管VT1的第二极电连接，电感L1的第二端与第四开关管VT4的第一极电连接。
如图4所示，所述控制方法包括：
在步骤S110中，根据输入电压和输出电压确定所述双向DC变换器的工作模式；
在步骤S120中，根据所述双向DC变换器的工作模式分别确定所述第一开关管的驱动信号的占空度、所述第二开关管的驱动信号的占空度、所述第三开关管的驱动信号的占空度和所述第四开关管的驱动信号的占空度；
在步骤S130中，根据确定的第一开关管的驱动信号的占空度向第一开关管的栅极提供驱动信号、根据确定的第二开关管的驱动信号的占空度向第二开关管的栅极提供驱动信号、根据确定的第三开关管的驱动信号的占空度向第三开关管的栅极提供驱动信号、根据确定的第四开关管的驱动信号的占空度向第四开关管的栅极提供驱动信号。
其中，所述第一开关管的驱动信号的占空度、所述第二开关管的驱动信号的占空度、所述第三开关管的驱动信号的占空度和所述第四开关管的驱动信号的占空度与所述双向DC变换器的工作模式之间满足以下关系：
当所述双向DC变换器工作在降压Buck模式下时，所述第一开关管的驱动信号的占空度的最大值为第一占空度阈值；
当所述双向DC变换器工作在升压Boost模式下时，所述第三开关管的驱动信号的占空度的最小值为第二占空度阈值；
当所述双向DC变换器工作在Buck/Boost模式下时，所述第一开关管的驱动信号占空度为恒定值，并且，调节所述第三开关管的驱动信号的占空度以实现所述双向DC变换器在Buck/Boost模式下的输出，所述第一占空度阈值与所述恒定值之间的差值不超过预定差值Δ。并且，所述第三开关管的驱动信号的占空度满足：
1-D 11/K1＜D2＜1-D 11/K2，其中，
D 11为所述恒定值；
K1为所述双向DC变换器的降压系数，0.9≤K1＜1；
K2为所述双向DC变换器的升压系数，1＜K2＜1.1。
不同的双向DC变换器的开关管开关频率设置不同、并且开关管的型号、产生各个驱动信号的驱动电路的参数等互不相同，每个开关管的驱动信号都要满足一个最小占空度需求，否则就会由于受到产生驱动信号的驱动电路的延迟和寄生电容等因素影响，造成最终提供给开关管的驱动信号占空度的缩小、而使得开关管无法完全导通。对于每个DC变换器而言，所述降压系数K1、所述升压系数K2的数值都是固定不变的，以满足DC变换器正常工作的需求。
在本公开所提供的控制方法中，当所述双向DC变换器工作在Buck模式下时，输出电压Vo与输入电压Vin之间的关系如下：
Vo＝D 1×Vin。
其中，D 1为提供给第一开关管VT1的栅极的驱动信号VG1的占空度。在Buck模式下，随着输出电压Vo的上升，提供给第一开关管VT1的栅极的驱动信号VG1的占空度也随之上升，如上文中所述，占空度D1在Buck模式下存在最大值(即，所述第一占空度阈值，用D 1max表示)。
K1为降压系数，在当所述双向DC变换器工作在Buck模式下时，输出电压Vo与输入电压Vin之间还满足以下关系：
Vo≤K1×Vin。
当双向DC变换器的工作模式从Buck模式转换为Buck/Boost时，由于提供给第一开关管VT1的栅极的驱动信号VG1的占空度D1为所述恒定值(用D 11表示)，可以通过调节提供给第三开关管VT3的栅极的控制信号VG3的占空度D 2来调节输出电压。在Buck/Boost模式下，输入电压Vin和输出电压Vo的关系式为：
Vo＝(D 11×Vin)/(1-D 2)。
当所述双向DC变换器工作在Buck/Boost模式下时，输出电压Vo与输入电压Vin之间还满足以下关系：
K1×Vin＜Vo＜K2×Vin。
通过上述不等式可知，当所述双向DC变换器工作在Buck/Boost模式下时，输出电压Vo与输入电压Vin比较接近。
由于在进入Buck/Boost模式后，第一开关管VT1的驱动信号VG1的占空度保持D 11不变，因此，调节第三开关管VG3的占空度D 2可以调节输出电压，以满足双向DC变换器在Buck/Boost模式下的正常输出。
在所述DC变换器进入Buck/Boost模式后，保持第一开关管VT1的驱动信号 VG1占空度D 11与第一开关VT1的驱动信号VG1在Buck模式下的最大占空度D 1max接近，以确保第一开关VT1的驱动信号VG1的占空度在由Buck模式转换到Buck/Boost模式过程中不发生大的突变，并且可以确保各个开关管的有效导通和关断。由于第一开关管VT1和第二开关管VT2的驱动信号是互补工作的，所以，从Buck模式切换到Buck/Boost模式过程中第二开关管VT2的驱动信号VG2的占空度也不会发生大的突变。
在所述双向DC变换器在Buck模式下，第四开关管VT4是保持常通状态的，此时第四开关管VT4的驱动信号VG4保持高电平状态，当进入Buck/Boost模式后，第四开关管VT4的驱动信号VG4开始以和第一开关管VT1相同的开关频率动作。
根据在Buck/Boost模式下输入输出电压的关系，可以得到第三开关管VT3的驱动信号VG3的占空度满足上文中所述的“1-D 11/K1＜D2＜1-D 11/K2”这一不等式，由此可知，第三开关管VT3的驱动信号VG3的占空度既略大于0、又能保证第三开关管VT3的有效导通，从而保证了双向DC变换器从Buck模式切换到Buck/Boost模式的过程中，是从0略有增大的，不会发生占空度的大突变。由于第三开关管VT3和第四开关管VT4是互补工作的，所以双向DC变换器从Buck模式切换到Buck/Boost模式的过程中，第四开关管VT4的驱动信号VG4的占空度是从1略有减小，不会发生占空度的大突变。
双向DC变换器工作在Boost模式时，第一开关管VT1工作在常导通状态，此时第一开关管VT1的驱动信号VG1的占空度为1，第二开关管VT2为常关断状态，此时第二开关管VT2的驱动信号VG2的占空度为0，在Boost模式下，输入电压和输出电压的关系式为Vo＝Vin/(1-D 2)，在进入Boost模式后，第三开关管VT3的驱动信号的占空度将随着输出电压的上升逐渐增大，刚进入Boost模式时第三开关管VT3的驱动信号VG2占空度D 2略比0大，保证了在双相DC变换器在从Buck/Boost模式切换到Boost模式时，第三开关管VT3的驱动信号VG3的占空度不发生大的突变，同样第四开关管VT4的驱动信号的占空度也不会发生大的突变。
由于四开关的双相DC转换器可以实现能量的双向流动，所以，无论双相DC转换器哪个端口是功率输入端，在不增加硬件电路和改变电路结构的条件下，利用本公开所提供的控制方法均可以实现不同模式的平滑切换。
在本公开中Δ的具体数值不做特殊的限定，在一些示例中，所述预定差值满足以下关系：
0＜Δ≤0.05。
在一些示例中，所述第一占空度阈值可以为0.95，所述恒定值可以为0.92。
在进入Buck/Boost模式阶段，保持第一开关管VT1的驱动信号占空VG1为0.92，与Buck模式下的驱动信号VG1的占空度最大值0.95非常接近，由此可以确保在所述双向DC变换器的工作模式由Buck模式进入Buck/Boost模式后，第一开关管VT1的驱动信号的占空度不会发生大的突变。由于第一开关管VT1和第二开关管VT2的驱动信号是互补工作的，因此，第二开关VT2的驱动信号VG2的占空度从Buck模式下的1-D 1max＝0.05切换到Buck/Boost模式过程中的1-D 11＝0.8，也没有发生大的变化。
在本公开中，对如何根据输入电压和输出电压确定所述双向DC变换器的步骤 S110不做特殊的限定，在一些示例中，如图9所示，步骤S110可以包括：
在步骤S111中，分别对输入电压和输出电压进行采样；
在步骤S112中，对采样获得的输入电压和采样获得的输出电压进行比较；
在步骤S113中：当Vo≤K1×Vin时，判定所述双向DC变换器的工作模式为Buck模式；当K1×Vin≤Vo≤K2×Vin时，判定所述双向DC变换器的工作模式为Buck/Boost模式；当K2×Vin≤Vo时，判定所述双向DC变换器的工作模式为Boost模式。
为了保证在各个工作模式切换时不会出现摩天的频繁切换，在一些示例中，可以在各切换点增加滞环判断。具体地，在步骤S113中：
在双向DC变换器的工作模式从Buck模式切换为Buck/Boost模式的情况下，当Vo＜K1’×Vin时，判定所述双向DC变换器的工作模式为Buck模式，其中，K1’为第一滞环判断系数，0＜K1’＜K1；
在双向DC变换器的工作模式从Boost模式切换为Buck/Boost模式的情况下，当Vo＜K2’×Vin时，判定所述双向DC变换器的工作模式为Buck/Boost模式，K2’为第二滞环判断系数，1＜K2’＜K2。
需要指出的是，第一滞环判断系数K1’和降压系数K1应当是接近的，在一些示例中二者的差值不超过0.05。例如，当K1为0.95时，K1’可以为0.92。
第二滞环判断系数K2’和升压系数K1也应当是接近的，在一些示例中二者的差值不超过0.05。例如，当K2为1.05时，K2’可以为1.02。
在一些示例中，所述第一占空度阈值D 1max与K1相同。例如，K1和D 1max均为0.95.。
在一些示例中，所述第二占空度阈值满足以下关系：
D 2min＝1-1/K2；
其中，D 2min为所述第二占空度阈值。
作为本公开的第二个方面，提供一种用于双向DC变换器的控制模块200。如图2所示，控制模块200包括信号处理单元210和驱动单元220。
信号处理单元210被配置为根据输入电压和输出电压确定所述双向DC变换器的工作模式、并根据所述双向DC变换器的工作模式分别确定第一开关管VT1的驱动信号VG1的占空度、第二开关管VT2的驱动信号VG2的占空度、第三开关管VT3的驱动信号VG3的占空度和第四开关管VT4的驱动信号VG4的占空度。
第一开关管VT1的驱动信号VG1的占空度、第二开关管VT2的驱动信号VG2的占空度、第三开关管VT3的驱动信号VG3的占空度和第四开关管VT4的驱动信号VG4的占空度满足以下关系：
当所述双向DC变换器工作在降压Buck模式下时，第一开关管VT1的驱动信号VG1的占空度的最大值为第一占空度阈值；
当所述双向DC变换器工作在降压Buck模式下时，所述第一开关管的驱动信号的占空度的最大值为第一占空度阈值；
当所述双向DC变换器工作在升压Boost模式下时，所述第三开关管的驱动信号的占空度的最小值为第二占空度阈值；
当所述双向DC变换器工作在Buck/Boost模式下时，所述第一开关管的驱动信 号占空度为恒定值，所述第一占空度阈值与所述恒定值之间的差值不超过预定差值，并且，所述第三开关管的驱动信号的占空度满足：
1-D 11/K1＜D 2＜1-D 11/K2，其中，
D 11为所述恒定值；
K1为所述双向DC变换器的降压系数，0.9≤K1＜1；
K2为所述双向DC变换器的升压系数，1＜K2＜1.1；
驱动单元220具有至少一个输出端组，每个输出端组都包括与第一开关管VT1的栅极电连接的第一输出端、与第二开关管VT2的栅极电连接的第二输出端、与第三开关管VT3的栅极电连接的第三输出端、与第四开关管VT4的栅极电连接的第四输出端。
驱动单元220被配置为根据第一开关管VT1的驱动信号VG1的占空度从所述第一输出端输出第一开关管VT1的驱动信号VG1、根据第二开关管VT2的驱动信号的占空度从所述第二输出端输出第二开关管VT2的驱动信号VG2、根据所述第三开关管VT3的驱动信号的占空度从所述第三输出端输出第三开关管VT3的驱动信号VG3和根据第四开关管VT4的驱动信号的占空度从所述第四输出端输出第四开关管的驱动信号VG4。
控制模块200被配置为执行本公开所提供的上述控制方法，上文中已经对所述控制方法的原理和有意效果进行了详细的描述，这里不再赘述。
为了便于确定所述双向DC变换器的工作模式，在一些示例中，如图2所示，所述控制模块还包括：
输入电压采样单元230，该输入电压采样单元230被配置为采集所述双向DC变换器的输入电压；
输出电压采样单元240，该输出电压采样单元240被配置为采集所述双向DC变换器的输出电压。
在一些示例中，所述预定差值满足以下关系：
0＜Δ≤0.05，
其中，Δ为所述预定差值。
当Vo≤K1×Vin时，信号处理单元210判定所述双向DC变换器的工作模式为Buck模式。
当K1×Vin≤Vo≤K2×Vin时，信号处理单元210判定所述双向DC变换器的工作模式为Buck/Boost模式。
当K2×Vin≤Vo时，信号处理单元230判定所述双向DC变换器的工作模式为Boost模式。
在双向DC变换器的工作模式从Buck模式切换为Buck/Boost模式的情况下，当Vo＜K1’×Vin时，信号处理单元210判定所述双向DC变换器的工作模式为Buck模式，其中，K1’为第一滞环判断系数，0＜K1’＜K1。
在双向DC变换器的工作模式从Boost模式切换为Buck/Boost模式的情况下，当Vo＜K2’×Vin时，信号处理单元210判定所述双向DC变换器的工作模式为Buck/Boost模式，K2’为第二滞环判断系数，1＜K2’＜K2。
所述第一占空度阈值与K1相同，所述第二占空度阈值满足以下关系：
D 2min＝1-1/K2；
其中，D 2min为所述第二占空度阈值。
当所述双向DC变换器工作在Buck/Boost模式下时，所述第三开关管的驱动信号的占空度满足以下公式：
Vo＝(D 11×Vin)/(1-D 2)，其中，D 2为第三开关管的驱动信号的占空度，D 11为所述恒定值。
作为本公开的第三个方面，提供一种双向DC变换器，如图2所示，双向DC变换器包括至少一个功率变换单元100和本公开所提供的上述控制模块200。
具体地，功率变换单元100包括第一桥臂、第二桥臂和电感L1。所述第一桥臂包括第一开关管VT1和第二开关管VT2，第一开关管VT1的第一极与所述双向DC变换器的输入端正极Vin +电连接，第一开关管VT1的第二极与第二开关管VT2的第一极电连接，第二开关管VT2的第二极与所述双向DC变换器的输入端负极Vin -电连接。
所述第二桥臂包括第三开关管VT3和第四开关管VT4，第三开关管VT3的第一极与所述双向DC变换器的输出端负极Vt -电连接，所述第三开关管的第二极与所述第四开关管的第一极电连接，所述第四开关管的第二极与所述双向DC变换器的输出端正极V +电连接。
电感L1的第一端与第一开关管VT1的第二极电连接，电感L1的第二端与第四开关管VT4的第一极电连接。
在本公开中，对功率输出单元100的数量不做特殊的限定。例如，在图8中所示的实施方式中，双向DC变换器包括并联的两个功率输出单元100。
在一些示例中，双向DC变换器的输入端正极和输入端负极之间还可以连接有输入滤波电容Cin，DC变换器的输出端正极和输出端负极之间还可以连接有输出滤波电容Co。
下面结合具体实施例对本公开所提供的双向DC变换器的工作原理进行详细描述。
实施例1
在本实施例中设定第一桥臂和第二桥臂的开关频率均为25KHz。降压系数K1为0.95，升压系数K2为1.05。
输入电压采样单元230将输入电压信号采样后送入信号处理单元210，输出电压采样单元240将输出电压信号采样后送入信号处理单元210，信号处理单元210接收输入输出电压采样信号后进行比较判断，当Vo≦K1×Vin，此时系统判断Vo<Vin，功率变换单元100工作在Buck模式，设置开关管VT1的占空度为D1，在Buck模式下Vo＝D1×Vin，随着输出电压Vo的上升D1值会随之上升，占空度D1在Buck模式下存在着最大值D 1max＝0.95。
当信号处理单元210检测到0.95×Vin<Vo<K2×Vin，此时信号处理单元210判定输出电压与输入电压比较接近，并进一步判定功率变换单元100在Buck/Boost模式，设置在此模式下第一开关管VT1的驱动信号VG1的占空度恒定为D 11＝0.92，设置在此模式下第二开关管VT2的驱动信号VG2的占空度为D 22，在Buck/Boost模式下输入电压和输出电压以及各占空度的关系表达式为Vo＝(0.92×Vin)/(1-D 22)，由于 在进入Buck/Boost模式后保持D 11不变，调节第三开关管VT3的驱动信号VG3占空度D2来调节输出电压，所以在Buck/Boost模式下0.032<D 22<0.124，第三开关管VT3的导通时间为1.28μS<T<4.96μS。
在进入Buck/Boost模式阶段，保持第一开关管VT1的驱动信号VG1占空度D 11＝0.92，与Buck模式下的最大占空度D 1max＝0.95很接近，由此可以确保第一开关管VT1的驱动信号VG1的占空度在由Buck模式转换到Buck/Boost模式过程中不发生大的突变。由于第一开关管VT1的驱动信号VG1和第二开关管VT2的驱动信号VG2是互补工作的，所以第二开关管VT2的占空度从Buck模式下的1-D 1max＝0.05切换到Buck/Boost模式过程中的1-D 11＝0.08也不会发生大的突变。
在Buck模式下第三开关管VT3是常关断的，第三开关管VT3的驱动信号VG3的占空度为D 2＝0，第四开关管VT4是保持常通状态的，此时第四开关管VT4的驱动信号VG4的占空度为1-D 2＝1，当进入Buck/Boost模式后，第四开关管VT4的驱动信号VG4开始以和第一开关管VT1相同的开关频率动作，且第四开关管VT4的驱动高电平信号与第一开关管管VT1的高电平信号中心对称。具体各驱动信号在个模态下的波形示意图如附图5所示。
在此实施例中根据在Buck/Boost模式下输入输出电压的关系式，得到在此模式下第三开关管VT3的驱动信号的占空度为1-D 11/0.95<D 22<1-D 11/1.05，其中D 11＝0.92，所以得到在Buck/Boost模式下的第三开关管VT3的驱动信号占空度范围为0.032<D 22<0.124，如此设置保证了第三开关管VT3的驱动信号VG3的占空度从Buck模式切换到Buck/Boost模式过程中是从0增大到0.032至0.124的范围内的，不会发生占空度的大幅度突变。由于第三开关管VT3和第四开关管VT4的驱动信号是互补工作的，所以第四开关管VT4的驱动信号VG4占空度(1-D 22)从Buck模式切换到Buck/Boost模式过程中是从1缩小到0.968至0.876的范围内，如此可使得驱动信号VG4的占空度不发生大的突变。
当信号处理单元210检测到，1.05×Vin≦Vo，此时信号处理单元210会认为输出电压大于输入电压，判定功率输出单元100工作在Boost模式，设置第一开关管VT1工作在常导通状态，此时第一开关管VT1的驱动信号VG1的占空度为1，设置第二开关管VT2为常关断状态，此时第二开关管VT2的驱动信号VG2的占空度为0，在Boost模式下输入电压和输出电压的关系式为Vo＝Vin/(1-D23)，在进入Boost模式后，第三开关管VT3的驱动信号VG3的占空度将从D 23＝1-1/1.05＝0.048随着输出电压的上升逐渐增大，所以刚进入Boost模式时第三开关管VT3的驱动信号VG3的占空度D 23＝0.048，这样驱动信号VG3的占空度在从Buck/Boost模式进入Boost模式时是从0.124变化到0.048，也使得驱动信号VG3的占空度在从Buck/Boost模式切换到Boost模式时不发生大的突变，同样驱动信号VG4的占空度在从Buck/Boost模式切换到Boost模式时是从0.876变化到0.952，也不会发生大的突变。
本实施例中以上叙述是输入电压不变，输出电压逐渐上升的过程中各开关管占空度变过过程的叙述，当输入电压保持不变，输出电压从高电压逐渐下降的过程是上述过程的反过程，各开关管的占空度变化是反向变化的，也是平滑过度不会出现大的突变的，此处不在详细叙述，另外为保证在各模态切换时不出现模态的频繁切换可以在各切换点增加滞环判断，滞环设置如附图6所示，图中当输入电压保持不 变，输出电压上升到0.95Vin以上时电路由Buck模式进入Buck/Boost模式，当输出电压低于0.92Vin时，电路才从Buck/Boost模式进入Buck模式；同样当输出电压上升到1.05Vin以上时电路由Buck/Boost模式进入到Boost模式，当输出电压低于1.02Vin时电路才从Boost模式进入Buck/Boost模式。
实施例2
与实施例1不同之处在于，本实施例中第三开关管VT3的驱动信号VG3的上升沿与第一开关管VT1的驱动信号VG1的上升沿同一时刻产生。实施例2中各驱动信号在各模态下的波形示意图如附图7所示。
可以看出，功率输出单元100在不同工作模式间切换时，各个驱动信号的占空度均没有大幅度的改变。
实施例3
与实施例1不同的方在于，本实施例采取的驱动信号频率为50KHz，设置的D 11值为D 11＝0.88，此实施例中第三开关管VT3的驱动信号VG3的占空度在Buck/Boost模式下的占空度范围为：
1-D 11/0.95<D 22<1-D11/1.05，即0.074<D22<0.162。
第三开关管VT3在Buck/Boost模式下的导通时间为1.48μS<T<3.24μS。
实施例4
与实施例1不同的地方在于，如图8所示，本实施例中双向DC变换器包含两个独立的功率输出单元100，两路功率输入单元的输入端并联，输出端并联，第二路与第一路之间相位交错180°工作。
作为本公开的第四个方面，提供一种计算机可读存储介质，所述计算机可读存储介质上存储有可执行程序，当所述可执行程序被调用时，能够实现本公开所提供的上述控制方法。
利用本公开所提供的控制方法对本公开所提供的双向DC转换器进行控制时，当工作模式之间发生切换时，可以避免各个开关管的驱动信号的占空度发生较大幅度的变化，从而避免电压失调的现象。
本领域普通技术人员可以理解，上文中所公开方法中的全部或某些步骤、系统、装置中的功能模块/单元可以被实施为软件、固件、硬件及其适当的组合。在硬件实施方式中，在以上描述中提及的功能模块/单元之间的划分不一定对应于物理组件的划分；例如，一个物理组件可以具有多个功能，或者一个功能或步骤可以由若干物理组件合作执行。某些物理组件或所有物理组件可以被实施为由处理器，如中央处理器、数字信号处理器或微处理器执行的软件，或者被实施为硬件，或者被实施为集成电路，如专用集成电路。这样的软件可以分布在计算机可读介质上，计算机可读介质可以包括计算机存储介质(或非暂时性介质)和通信介质(或暂时性介质)。如本领域普通技术人员公知的，术语计算机存储介质包括在用于存储信息(诸如计算机可读指令、数据结构、程序模块或其它数据)的任何方法或技术中实施的易失性和非易失性、可移除和不可移除介质。计算机存储介质包括但不限于RAM、ROM、EEPROM、闪存或其它存储器技术、CD-ROM、数字多功能盘(DVD)或其它光盘存储、磁盒、磁带、磁盘存储或其它磁存储装置、或者可以用于存储期望的信息并且可以被计算机访问的任何其它的介质。此外，本领域普通技术人员公知的是，通 信介质通常包含计算机可读指令、数据结构、程序模块或者诸如载波或其它传输机制之类的调制数据信号中的其它数据，并且可包括任何信息递送介质。
可以理解的是，以上实施方式仅仅是为了说明本发明的原理而采用的示例性实施方式，然而本发明并不局限于此。对于本领域内的普通技术人员而言，在不脱离本发明的精神和实质的情况下，可以做出各种变型和改进，这些变型和改进也视为本发明的保护范围。

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  1. 一种双向DC变换器的控制方法，所述双向DC变换器包括至少一个功率变换单元，所述功率变换单元包括第一桥臂、第二桥臂和电感，所述第一桥臂包括第一开关管和第二开关管，所述第一开关管的第一极与所述双向DC变换器的输入端正极电连接，所述第一开关管的第二极与所述第二开关管的第一极电连接，所述第二开关管的第二极与所述双向DC变换器的输入端负极电连接，所述第二桥臂包括第三开关管和第四开关管，所述第三开关管的第一极与所述双向DC变换器的输出端负极电连接，所述第三开关管的第二极与所述第四开关管的第一极电连接，所述第四开关管的第二极与所述双向DC变换器的输出端正极电连接，所述电感的第一端与所述第一开关管的第二极电连接，所述电感的第二端与所述第四开关管的第一极电连接；所述控制方法包括：
    根据输入电压和输出电压确定所述双向DC变换器的工作模式；
    根据所述双向DC变换器的工作模式分别确定所述第一开关管的驱动信号的占空度、所述第二开关管的驱动信号的占空度、所述第三开关管的驱动信号的占空度和所述第四开关管的驱动信号的占空度；
    根据确定的第一开关管的驱动信号的占空度向第一开关管的栅极提供驱动信号、根据确定的第二开关管的驱动信号的占空度向第二开关管的栅极提供驱动信号、根据确定的第三开关管的驱动信号的占空度向第三开关管的栅极提供驱动信号、根据确定的第四开关管的驱动信号的占空度向第四开关管的栅极提供驱动信号；其中，所述第一开关管的驱动信号的占空度、所述第二开关管的驱动信号的占空度、所述第三开关管的驱动信号的占空度和所述第四开关管的驱动信号的占空度与所述双向DC变换器的工作模式之间满足以下关系：
    当所述双向DC变换器工作在降压Buck模式下时，所述第一开关管的驱动信号的占空度的最大值为第一占空度阈值；
    当所述双向DC变换器工作在升压Boost模式下时，所述第三开关管的驱动信号的占空度的最小值为第二占空度阈值；
    当所述双向DC变换器工作在Buck/Boost模式下时，所述第一开关管的驱动信号占空度为恒定值，所述第一占空度阈值与所述恒定值之间的差值不超过预定差值，并且，所述第三开关管的驱动信号的占空度满足：
    1-D 11/K1＜D2＜1-D 11/K2，其中，
    D 11为所述恒定值；
    K1为所述双向DC变换器的降压系数，0.9≤K1＜1；
    K2为所述双向DC变换器的升压系数，1＜K2＜1.1。
  2. 根据权利要求1所述的控制方法，其中，所述预定差值满足以下关系：
    0＜Δ≤0.05，
    其中，Δ为所述预定差值。
  3. 根据权利要求1所述的控制方法，其中，根据输入电压和输出电压确定所述双向DC变换器的工作模式的步骤包括：
    分别对输入电压和输出电压进行采样；
    对采样获得的输入电压和采样获得的输出电压进行比较；
    当Vo≤K1×Vin时，判定所述双向DC变换器的工作模式为Buck模式；
    当K1×Vin≤Vo≤K2×Vin时，判定所述双向DC变换器的工作模式为Buck/Boost模式；
    当K2×Vin≤Vo时，判定所述双向DC变换器的工作模式为Boost模式。
  4. 根据权利要求3所述的控制方法，其中，在根据输入电压和输出电压确定所述双向DC变换器的工作模式的步骤中，
    在双向DC变换器的工作模式从Buck模式切换为Buck/Boost模式的情况下，当Vo＜K1’×Vin时，判定所述双向DC变换器的工作模式为Buck模式，其中，K1’为第一滞环判断系数，0＜K1’＜K1；
    在双向DC变换器的工作模式从Boost模式切换为Buck/Boost模式的情况下，当Vo＜K2’×Vin时，判定所述双向DC变换器的工作模式为Buck/Boost模式，K2’为第二滞环判断系数，1＜K2’＜K2。
  5. 根据权利要求1至4中任意一项所述的控制方法，其中，所述第一占空度阈值与K1相同，所述第二占空度阈值满足以下关系：
    D 2min＝1-1/K2；
    其中，D 2min为所述第二占空度阈值。
  6. 根据权利要求1至4中任意一项所述的控制方法，其中，当所述双向DC变换器工作在Buck/Boost模式下时，所述第三开关管的驱动信号的占空度满足以下公式：
    Vo＝(D 11×Vin)/(1-D 2)，其中，D 2为第三开关管的驱动信号的占空度，D 11为所述恒定值。
  7. 一种用于双向DC变换器的控制模块，所述双向DC变换器包括至少一个功率变换单元，所述功率变换单元包括第一桥臂、第二桥臂和电感，所述第一桥臂包括第一开关管和第二开关管，所述第一开关管的第一极与所述双向DC变换器的输入端正极电连接，所述第一开关管的第二极与所述第二开关管的第一极电连接，所述第二开关管的第二极与所述双向DC变换器的输入端负极电连接，所述第二桥臂包括第三开关管和第四开关管，所述第三开关管的第一极与所述双向DC变换器的输出端负极电连接，所述第三开关管的第二极与所述第四开关管的第一极电连接，所述第四开关管的第二极与所述双向DC变换器的输出端正极电连接，所述电感的第一端与所述第一开关管的第二极电连接，所述电感的第二端与所述第四开关管的第一极电连接；
    所述控制模块包括：
    信号处理单元，所述信号处理单元被配置为根据输入电压和输出电压确定所述双向DC变换器的工作模式、并根据所述双向DC变换器的工作模式分别确定所述第一开关管的驱动信号的占空度、所述第二开关管的驱动信号的占空度、所述第三开关管的驱动信号的占空度和所述第四开关管的驱动信号的占空度，所述第一开关管的驱动信号的占空度、所述第二开关管的驱动信号的占空度、所述第三开关管的驱动信号的占空度和所述第四开关管的驱动信号的占空度与所述双向DC变换器的工作模式之间满足以下关系：
    当所述双向DC变换器工作在降压Buck模式下时，所述第一开关管的驱 动信号的占空度的最大值为第一占空度阈值；
    当所述双向DC变换器工作在升压Boost模式下时，所述第三开关管的驱动信号的占空度的最小值为第二占空度阈值；
    当所述双向DC变换器工作在Buck/Boost模式下时，所述第一开关管的驱动信号占空度为恒定值，所述第一占空度阈值与所述恒定值之间的差值不超过预定差值，并且，所述第三开关管的驱动信号的占空度满足：
    1-D 11/K1＜D2＜1-D 11/K2，其中，
    D 11为所述恒定值；
    K1为所述双向DC变换器的降压系数，0.9≤K1＜1；
    K2为所述双向DC变换器的升压系数，1＜K2＜1.1；
    驱动单元，所述驱动单元具有至少一个输出端组，每个输出端组都包括与所述第一开关管的栅极电连接的第一输出端、与所述第二开关管的栅极电连接的第二输出端、与所述第三开关管的栅极电连接的第三输出端、与所述第四开关管的栅极电连接的第四输出端，所述驱动单元被配置为根据所述第一开关管的驱动信号的占空度从所述第一输出端输出第一开关管的驱动信号、根据所述第二开关管的驱动信号的占空度从所述第二输出端输出第二开关管的驱动信号、根据所述第三开关管的驱动信号的占空度从所述第三输出端输出第三开关管的驱动信号和根据所述第四开关管的驱动信号的占空度从所述第四输出端输出第四开关管的驱动信号。
  8. 根据权利要求7所述的控制模块，其中，所述双向DC变换器还包括：
    输入电压采样单元，所述输入电压采样单元被配置为采集所述双向DC变换器的输入电压；
    输出电压采样单元，所述输出电压采样单元被配置为采集所述双向DC变换器的输出电压。
  9. 根据权利要求7所述的控制模块，其中，所述预定差值满足以下关系：
    0＜Δ≤0.05，
    其中，Δ为所述预定差值。
  10. 根据权利要求11所述的控制模块，其中，
    当Vo≤K1×Vin时，所述信号处理单元判定所述双向DC变换器的工作模式为Buck模式；
    当K1×Vin≤Vo≤K2×Vin时，所述信号处理单元判定所述双向DC变换器的工作模式为Buck/Boost模式；
    当K2×Vin≤Vo时，所述信号处理单元判定所述双向DC变换器的工作模式为Boost模式。
  11. 根据权利要求10所述的控制模块，其中，
    在双向DC变换器的工作模式从Buck模式切换为Buck/Boost模式的情况下，当Vo＜K1’×Vin时，所述信号处理单元判定所述双向DC变换器的工作模式为Buck模式，其中，K1’为第一滞环判断系数，0＜K1’＜K1；
    在双向DC变换器的工作模式从Boost模式切换为Buck/Boost模式的情况下，当Vo＜K2’×Vin时，所述信号处理单元判定所述双向DC变换器的工作模式为Buck/Boost模式，K2’为第二滞环判断系数，1＜K2’＜K2。
  12. 根据权利要求7至11中任意一项所述的控制模块，其中，所述第一占空度阈值与K1相同，所述第二占空度阈值满足以下关系：
    D 2min＝1-1/K2；
    其中，D 2min为所述第二占空度阈值。
  13. 根据权利要求7至11中任意一项所述的控制模块，其中，当所述双向DC变换器工作在Buck/Boost模式下时，所述第三开关管的驱动信号的占空度满足以下公式：
    Vo＝(D 11×Vin)/(1-D 2)，其中，D 2为第三开关管的驱动信号的占空度，D 11为所述恒定值。
  14. 一种双向DC变换器，包括：
    至少一个功率变换单元，所述功率变换单元包括第一桥臂、第二桥臂和电感，所述第一桥臂包括第一开关管和第二开关管，所述第一开关管的第一极与所述双向DC变换器的输入端正极电连接，所述第一开关管的第二极与所述第二开关管的第一极电连接，所述第二开关管的第二极与所述双向DC变换器的输入端负极电连接，所述第二桥臂包括第三开关管和第四开关管，所述第三开关管的第一极与所述双向DC变换器的输出端负极电连接，所述第三开关管的第二极与所述第四开关管的第一极电连接，所述第四开关管的第二极与所述双向DC变换器的输出端正极电连接，所述电感的第一端与所述第一开关管的第二极电连接，所述电感的第二端与所述第四开关管的第一极电连接；
    权利要求7至13中任意一项所述的控制模块。
  15. 一种计算机可读存储介质，存储有可执行程序，其中，当所述可执行程序被调用时，能够实现权利要求1至6中任意一项所述的控制方法。
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