WO2021253531A1 - 适应宽输入电压的dcdc转换电路以及车载充电机 - Google Patents

适应宽输入电压的dcdc转换电路以及车载充电机 Download PDF

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WO2021253531A1
WO2021253531A1 PCT/CN2020/101137 CN2020101137W WO2021253531A1 WO 2021253531 A1 WO2021253531 A1 WO 2021253531A1 CN 2020101137 W CN2020101137 W CN 2020101137W WO 2021253531 A1 WO2021253531 A1 WO 2021253531A1
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switch
primary
conversion module
transformer
input voltage
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PCT/CN2020/101137
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English (en)
French (fr)
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冯颖盈
姚顺
徐金柱
陈振龙
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深圳威迈斯新能源股份有限公司
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33569—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
    • H02M3/33576—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements having at least one active switching element at the secondary side of an isolation transformer
    • B—PERFORMING OPERATIONS; TRANSPORTING
    • B60—VEHICLES IN GENERAL
    • B60L—PROPULSION OF ELECTRICALLY-PROPELLED VEHICLES; SUPPLYING ELECTRIC POWER FOR AUXILIARY EQUIPMENT OF ELECTRICALLY-PROPELLED VEHICLES; ELECTRODYNAMIC BRAKE SYSTEMS FOR VEHICLES IN GENERAL; MAGNETIC SUSPENSION OR LEVITATION FOR VEHICLES; MONITORING OPERATING VARIABLES OF ELECTRICALLY-PROPELLED VEHICLES; ELECTRIC SAFETY DEVICES FOR ELECTRICALLY-PROPELLED VEHICLES
    • B60L53/00—Methods of charging batteries, specially adapted for electric vehicles; Charging stations or on-board charging equipment therefor; Exchange of energy storage elements in electric vehicles
    • B60L53/20—Methods of charging batteries, specially adapted for electric vehicles; Charging stations or on-board charging equipment therefor; Exchange of energy storage elements in electric vehicles characterised by converters located in the vehicle
    • B60L53/22—Constructional details or arrangements of charging converters specially adapted for charging electric vehicles
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0048—Circuits or arrangements for reducing losses
    • H02M1/0054—Transistor switching losses
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02T—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO TRANSPORTATION
    • Y02T10/00—Road transport of goods or passengers
    • Y02T10/60—Other road transportation technologies with climate change mitigation effect
    • Y02T10/70—Energy storage systems for electromobility, e.g. batteries
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02T—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO TRANSPORTATION
    • Y02T10/00—Road transport of goods or passengers
    • Y02T10/60—Other road transportation technologies with climate change mitigation effect
    • Y02T10/7072—Electromobility specific charging systems or methods for batteries, ultracapacitors, supercapacitors or double-layer capacitors
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02T—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO TRANSPORTATION
    • Y02T10/00—Road transport of goods or passengers
    • Y02T10/60—Other road transportation technologies with climate change mitigation effect
    • Y02T10/72—Electric energy management in electromobility
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02T—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO TRANSPORTATION
    • Y02T10/00—Road transport of goods or passengers
    • Y02T10/80—Technologies aiming to reduce greenhouse gasses emissions common to all road transportation technologies
    • Y02T10/92—Energy efficient charging or discharging systems for batteries, ultracapacitors, supercapacitors or double-layer capacitors specially adapted for vehicles
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02T—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO TRANSPORTATION
    • Y02T90/00—Enabling technologies or technologies with a potential or indirect contribution to GHG emissions mitigation
    • Y02T90/10—Technologies relating to charging of electric vehicles
    • Y02T90/14—Plug-in electric vehicles

Definitions

  • the invention belongs to the technical field of power supplies, and in particular relates to a DCDC conversion circuit adapted to a wide input voltage and a vehicle-mounted charger.
  • the PFC-level bus capacitor voltage when the on-board charger is in single-phase AC input, the PFC-level bus capacitor voltage is approximately 400V; when in three-phase AC input, the PFC-level bus capacitor voltage is approximately 800V, which is a wide input voltage for the subsequent DCDC.
  • the output voltage of the DCDC stage is approximately 400V.
  • the PFC bus capacitor voltage When the input is three-phase AC, the PFC bus capacitor voltage is approximately 800V, and the high-voltage output voltage requires 400V.
  • the transformer needs to be configured with an approximate 2:1 turns ratio to achieve the optimal efficiency point; when the input is single-phase AC, the PFC bus capacitor The voltage is approximately 400V, and the high-voltage output voltage requires 400V. According to the transformer's 2:1 turns ratio, the DCDC gain must be greater than 1. For traditional LLC, the excitation current is large at this time, which increases the DCDC conduction loss and reduces the converter efficiency .
  • the present invention proposes a DCDC conversion circuit suitable for a wide input voltage and an on-board charger.
  • the technical scheme adopted by the present invention is to design a DCDC conversion circuit that adapts to a wide input voltage, which includes connecting a primary conversion module, a transformer T1, a secondary conversion module, and a controller in sequence.
  • the first and second bridge arms composed of switches are provided with a switching module between the middle point of the first bridge arm E and the primary side of the transformer T1, and between the negative bus of the primary conversion module and the primary winding of the transformer T1;
  • the bus voltage of the side conversion module controls the switching module to perform a switching action to switch the primary side conversion module to a full-bridge structure or a half-bridge structure.
  • the DCDC conversion circuit includes a charging mode and an inverter mode; when the bus voltage is higher than the threshold value M in the charging mode, the primary side conversion module is controlled to switch to a half-bridge structure; in the charging mode, the bus voltage is not higher than the threshold value At M, control the primary-side conversion module to switch to the full-bridge structure; in the inverter mode, control the primary-side conversion module to switch to the full-bridge structure.
  • the threshold value M is 600 volts.
  • the primary conversion module includes a first switch Q1, a second switch Q2, a third switch Q3, and a fourth switch Q4.
  • the first switch Q1 and the third switch Q3 are connected in series to form a first bridge arm, and the first switch Q1 and The connection point of the third switch Q3 is the middle point of E;
  • the second switch Q2 and the fourth switch Q4 are connected in series to form a second bridge arm, and the connection point of the second switch Q2 and the fourth switch Q4 is the middle point of F;
  • the module includes a first switch Relay1 and a second switch Relay2, the middle point of E is connected to the static contact of the first switch Relay1, the middle point of F is connected to the first moving contact of the first switch Relay1, and the middle point of F is connected One end of the primary winding of the transformer T1, the other end of the primary winding of the transformer T1 is connected to the second movable contact of the first switch Relay1, and the other end of the primary winding of the transformer T1 is connected to the negative electrode of the
  • the primary winding of the transformer T1 is connected in series with the first capacitor C1.
  • the primary winding of the transformer T1 is connected in series with the first inductor L1.
  • the first switch Relay1 is a single-pole double-throw relay or a selector switch
  • the second switch Relay2 is a single-pole single-throw relay.
  • the secondary side conversion module includes a secondary side high voltage conversion module and a secondary side low voltage conversion module.
  • the present invention also designs a vehicle-mounted charger adapting to a wide input voltage, and the vehicle-mounted charger adopts the above-mentioned DCDC conversion circuit adapting to a wide input voltage.
  • the topology structure of the existing charger of the present invention adds a small number of switch switches to realize the switching of half bridge and full bridge, and is compatible with single-phase and three-phase input power grids, so that the charger has a DCDC level when single-phase AC input and three-phase AC input are used.
  • the charging efficiency of the charger is improved; in addition, the present invention can reduce the circulating current of the DCDC-level resonant cavity, reduce the conduction loss of the power device, and improve the efficiency; in addition, when the charger is in the inverter mode, the present invention
  • the DCDC operating frequency is reduced, the switching loss of the power device is reduced, and the efficiency is improved.
  • Figure 1 is a schematic circuit diagram of a preferred embodiment of the present invention.
  • Figure 2 is a schematic diagram of a full-bridge structure switching module switching
  • Figure 3 is a waveform diagram of the voltage across the primary winding of the transformer T1 in the full-bridge structure
  • Figure 4 is a schematic diagram of the switching of the half-bridge structure switching module
  • Figure 5 is a waveform diagram of the voltage across the primary winding of the transformer T1 in the half-bridge structure
  • Fig. 6 is a comparison diagram of the full bridge gain curve between the prior art and the present invention.
  • Fig. 7 is a waveform of a full-bridge excitation current in the prior art
  • Figure 8 is the excitation current waveform of the present invention.
  • Fig. 9 is a comparison diagram of the full bridge operating frequency between the prior art and the present invention.
  • the invention discloses a DCDC conversion circuit adapted to a wide input voltage, which includes a primary side conversion module, a transformer T1, a secondary side conversion module, and a controller connected in sequence.
  • the primary side conversion module includes a first side conversion module composed of four power switches.
  • the first and second bridge arms are equipped with switching modules between the middle point of the first bridge arm E and the primary side of the transformer T1, and between the negative bus of the primary side conversion module and the primary winding of the transformer T1;
  • the bus voltage control switching module performs the switching action to switch the primary side conversion module to a full-bridge structure or a half-bridge structure.
  • the present invention actually utilizes the topology structure of the existing charger and adds a small number of switch switches. According to the work needs, the switch between half bridge and full bridge will be realized, compatible with single-phase and three-phase input power grids, so that the charger can input single-phase AC input. , When three-phase AC input, the DCDC level is at the best operating frequency point, which improves the charging efficiency of the charger.
  • the DCDC conversion circuit includes a charging mode and an inverter mode; in the charging mode, when the bus voltage is higher than the threshold value M, the primary side conversion module is controlled to switch to a half-bridge structure; When the bus voltage is not higher than the threshold value M, the primary-side conversion module is controlled to switch to the full-bridge structure; in the inverter mode, the primary-side conversion module is controlled to switch to the full-bridge structure.
  • the threshold M is 600 volts.
  • different input power grids can be connected externally, which can be a three-phase power grid or a single-phase power grid.
  • the bus voltage is higher than the threshold value M, which means that the charger is connected to the three-phase power grid.
  • the bus voltage is not higher than the threshold value M, which means that the charger is connected to a single-phase power grid.
  • the primary side conversion module includes a first switch Q1, a second switch Q2, a third switch Q3, and a fourth switch Q4.
  • the first switch Q1 and the third switch Q3 are connected in series.
  • Form the first bridge arm, the connection point of the first switch Q1 and the third switch Q3 is the middle point of E;
  • the second switch Q2 and the fourth switch Q4 are connected in series to form the second bridge arm, the second switch Q2 and the fourth switch Q4
  • the connection point is the F intermediate point;
  • the switching module includes a first switch Relay1 and a second switch Relay2, the E intermediate point is connected to the static contact (point O) of the first switch Relay1, and the F intermediate point is connected to the first switch Relay1.
  • the first movable contact (point A) of the switch Relay1 is connected to one end of the primary winding of the transformer T1
  • the other end of the primary winding of the transformer T1 is connected to the second movable contact of the first switch Relay1 Contact (point B)
  • the second switch Relay2 is connected in series between the other end of the primary winding of the transformer T1 and the negative bus of the primary conversion module.
  • the primary winding of the transformer T1 is connected in series with the first capacitor C1.
  • the primary winding of the transformer T1 is connected in series with the first inductor L1.
  • a control circuit is used to control the on and off of the Relay1 and Relay2 switches in FIG. 1 to switch the working mode of the DCDC converter, so that the DC converter is compatible with two working modes of half bridge and full bridge.
  • the input voltage is approximately 400V
  • the first switch Relay1 points O and B are closed
  • the second switch Relay2 is opened to form a full bridge circuit, which is added to the primary windings C and D of the transformer T1
  • the voltage at both ends is shown in Figure 3.
  • the peak-to-peak value is approximately 800V
  • the unilateral voltage is approximately 400V.
  • the output voltage is required to be approximately 400V
  • the optimum operating frequency of LLC with a gain of 1 can be achieved; when three-phase AC input is used
  • the input voltage is approximately 800V
  • the first switch Relay1O and A are closed
  • the second switch Relay2 is closed.
  • FIG. 6 shows a comparison diagram of the full-bridge gain curve between the prior art and the present invention. From the comparison diagram, it can be seen that the gain requirement of the present application is significantly lower than that of the traditional full-bridge topology.
  • the present invention can reduce the conduction loss of the charger.
  • the bus capacitor voltage is approximately 800V
  • the high-voltage output voltage demand is 400V
  • the transformer needs to be configured with a 2:1 turns ratio to achieve the best efficiency operating point with a gain of 1.
  • the bus capacitor voltage is approximately 400V
  • the high-voltage output voltage demand is 400V.
  • the gain needs to reach 2 to meet the high-voltage output voltage 400V demand.
  • the ratio of the magnetizing inductance to the resonance inductance is For K.
  • a half-bridge full-bridge switching topology is used, whether it is a three-phase AC input or a single-phase AC input, the gain requirement is 1, and the transformer is configured as 1:1.
  • the ratio of the magnetizing inductance to the resonance inductance is Approximately 2K. It can be concluded that in the present invention, the magnetizing inductance is configured to be twice that of the traditional full-bridge circuit, thereby reducing the loop current of the resonant cavity, reducing the conduction loss, and improving the efficiency.
  • Fig. 7 shows the waveform of the excitation current of the full bridge in the prior art
  • Fig. 8 shows the waveform of the excitation current of the present invention. It can be seen from the comparison diagram that the excitation current of the present invention is obviously smaller than that of the prior art full-bridge excitation current.
  • the present invention can reduce the switching loss in the inverter mode.
  • the PFC bus capacitor voltage is approximately 800V
  • the high-voltage output voltage requires 400V
  • the transformer needs to be configured with an approximate 2:1 turns ratio to achieve the optimal efficiency point; follow this transformer configuration circuit
  • the gain requirement is about 0.5
  • the switching frequency is higher, thereby increasing the switching loss.
  • the circuit is configured as a half bridge, which can maintain a 1:1 transformer turns ratio, reduce the gain requirement, thereby reduce the frequency, reduce the switching loss, and improve the efficiency of the inverter state.
  • the first switch Relay1 is a single-pole double-throw relay or a selector switch
  • the second switch Relay2 is a single-pole single-throw relay
  • the secondary side conversion module includes a secondary side high voltage conversion module and a secondary side low voltage conversion module.
  • the invention is applied to a vehicle-mounted charger, the secondary side high-voltage conversion module is connected to the high-voltage power battery in the vehicle, and the secondary side low-voltage conversion module is connected to the low-voltage battery in the vehicle and the entire vehicle electrical equipment.
  • the first conversion module of the secondary side adopts a full-bridge structure, and includes a fifth power switch Q5, a sixth power switch Q6, a seventh power switch Q7, and an eighth power switch Q8;
  • the fifth power switch Q5 and the seventh power switch Q7 are a pair of bridge arms
  • the sixth power switch Q6 and the eighth power switch Q8 are a pair of bridge arms
  • the fifth power switch Q5 and the sixth power switch Q6 are upper bridge arms.
  • the seventh power switch Q7 and the eighth power switch Q8 are lower bridge arms.
  • the first power switch Q1, the second power switch Q2, the third power switch Q3, the fourth power switch Q4, the fifth power switch Q5, the sixth power switch Q6, the seventh power switch Q7, and the eighth power switch Q8 are adopted One of MOSFET, SiC MOSFET, IGBT parallel diode, and GAN HEMT.
  • the secondary side low voltage conversion module includes a ninth power switch Q9, a tenth power switch Q10, and an eleventh power switch Q11; the drain of the ninth power switch Q9 is connected to the end of the same name of the fourth secondary winding W3, the The drain of the tenth power switch Q10 is connected to the synonymous end of the third secondary winding W4, the synonymous end of the fourth secondary winding W3 is connected to the same end of the third secondary winding W4, and then the eleventh power switch Q11 is connected in series with the output The inductor L2 is then connected to the positive output terminal of the low-voltage conversion module on the secondary side, and the sources of the ninth power switch Q9 and the tenth power switch Q10 are grounded.
  • the invention also discloses a vehicle-mounted charger adapting to a wide input voltage, and the vehicle-mounted charger adopts the above-mentioned DCDC conversion circuit adapting to the wide input voltage.

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Abstract

一种适应宽输入电压的DCDC转换电路以及车载充电机，DCDC转换电路包括依次连接的原边转换模块、变压器（T1）、副边转换模块，以及控制器，原边转换模块包括由四个功率开关（Q1~Q4）组成的第一和第二桥臂，在第一桥臂中间点（E）与变压器（T1）原边之间、以及原边转换模块负极母线与变压器（T1）原边绕组（W1）之间设有切换模块（Relay1，Relay2）；控制器根据原边转换模块的母线电压控制切换模块（Relay1，Relay2）进行切换动作，将原边转换模块切换为全桥结构或半桥结构；相对于现有充电机的拓扑结构，适应宽输入电压的DCDC转换电路以及车载充电机增加少量的切换开关，实现半桥、全桥的切换，使得充电机在单相交流输入、三相交流输入时DCDC级处于最佳工作频率点，提高充电机充电效率。

Description

适应宽输入电压的DCDC转换电路以及车载充电机 技术领域
本发明属于电源技术领域，具体涉及一种适应宽输入电压的DCDC转换电路以及车载充电机。
背景技术
在现有技术中，车载充电机在单相交流输入时，PFC级母线电容电压近似为400V；三相交流输入时PFC级母线电容电压近似为800V，对于后级DCDC而言为宽输入电压，DCDC级输出电压近似400V。当输入为三相交流电时，PFC母线电容电压近似为800V，高压输出电压需求400V，变压器需配置为近似2：1匝比才能达到最优效率点；当输入为单相交流电时，PFC母线电容电压近似为400V，高压输出电压需求400V，按照变压器2：1的匝比，DCDC增益需大于1，对于传统LLC而言，此时励磁电流较大，从而增加DCDC导通损耗，降低变换器效率。
因此，如何设计一种适应单三相输入电压，降低功率器件导通损耗，提高充电机充电效率的充电机，是业界亟待解决的技术问题。
发明内容
为了解决现有技术中存在的上述缺陷，本发明提出一种适应宽输入电压的DCDC转换电路以及车载充电机。
本发明采用的技术方案是设计一种适应宽输入电压的DCDC转换电路，包括依次连接原边转换模块、变压器T1、副边转换模块，以及控制器，所述原边转换模块包括由四个功率开关组成的第一和第二桥臂，在第一桥臂E中间点与变压器T1原边之间、以及原边转换模块负极母线与变压器T1原边绕组之间设有切换模块；控制器原边转换模块的母线电压控制切换模块进行切换动作，将原边转换模块切换为全桥结构或半桥结构。
所述DCDC转换电路包括充电模式、逆变模式；在充电模式中所述母线电压高于阈值M时，控制原边转换模块切换为半桥结构；在充电模式中所述母 线电压不高于阈值M时，控制原边转换模块切换为全桥结构；在逆变模式中，控制原边转换模块切换为全桥结构。
所述阈值M为600伏。
所述原边转换模块包括第一开关Q1、第二开关Q2、第三开关Q3、第四开关Q4，所述第一开关Q1和第三开关Q3串联组成第一桥臂，第一开关Q1和第三开关Q3的连接点为E中间点；所述第二开关Q2和第四开关Q4串联组成第二桥臂，第二开关Q2和第四开关Q4的连接点为F中间点；所述切换模块包括第一开关Relay1和第二开关Relay2，所述E中间点连接第一开关Relay1的静触头，所述F中间点连接第一开关Relay1的第一动触头，所述F中间点连接所述变压器T1原边绕组的一端，所述变压器T1原边绕组的另一端连接所述第一开关Relay1的第二动触头，所述变压器T1原边绕组的另一端与原边转换模块负极母线之间串接所述第二开关Relay2。
所述变压器T1原边绕组串联第一电容C1。
所述变压器T1原边绕组串联第一电感L1。
所述第一开关Relay1采用单刀双掷继电器或选择开关，所述第二开关Relay2采用单刀单掷继电器。
所述副边转换模块包括副边高压转换模块和副边低压转换模块。
本发明还设计了一种适应宽输入电压的车载充电机，所述车载充电机采用上述的适应宽输入电压的DCDC转换电路。
本发明提供的技术方案的有益效果是：
本发明现有充电机的拓扑结构，增加少量的切换开关，实现半桥、全桥的切换，兼容单相、三相输入电网，使得充电机在单相交流输入、三相交流输入时DCDC级处于最佳工作频率点，提高充电机充电效率；此外，本发明可以使得DCDC级谐振腔环流减小，降低功率器件导通损耗，提高效率；此外，本发明在充电机处于逆变模式时，使得DCDC工作频率降低，降低功率器件开关损耗，提高效率。
附图说明
下面结合实施例和附图对本发明进行详细说明，其中：
图1是本发明较佳实施例电路原理图；
图2是全桥结构切换模块切换示意图；
图3是全桥结构中变压器T1原边绕组两端电压波形图；
图4是半桥结构切换模块切换示意图；
图5是半桥结构中变压器T1原边绕组两端电压波形图；
图6是现有技术与本发明全桥增益曲线对比图；
图7是现有技术全桥励磁电流波形；
图8是本发明励磁电流波形；
图9是现有技术与本发明全桥工作频率对比图。
具体实施方式
为了使本发明的目的、技术方案及优点更加清楚明白，以下结合附图及实施例，对本发明作进一步详细说明。应当理解，此处所描述的具体实施例仅仅用于解释本发明，并不用于限定本发明。
本发明公开了一种适应宽输入电压的DCDC转换电路，包括依次连接原边转换模块、变压器T1、副边转换模块，以及控制器，所述原边转换模块包括由四个功率开关组成的第一和第二桥臂，在第一桥臂E中间点与变压器T1原边之间、以及原边转换模块负极母线与变压器T1原边绕组之间设有切换模块；控制器原边转换模块的母线电压控制切换模块进行切换动作，将原边转换模块切换为全桥结构或半桥结构。
本发明实际是利用现有充电机的拓扑结构，增加少量的切换开关，根据工作需要，将实现半桥、全桥的切换，兼容单相、三相输入电网，使得充电机在单相交流输入、三相交流输入时DCDC级处于最佳工作频率点，提高充电机充电效率。
在较佳实施例中，所述DCDC转换电路包括充电模式、逆变模式；在充电模式中所述母线电压高于阈值M时，控制原边转换模块切换为半桥结构；在充电模式中所述母线电压不高于阈值M时，控制原边转换模块切换为全桥结构；在逆变模式中，控制原边转换模块切换为全桥结构。
在较佳实施例中，所述阈值M为600伏。
本发明运用到充电机中时，外部可以连接不同输入电网，可以是三相电网，也可以是单相电网。母线电压高于阈值M，代表充电机连接三相电网。母线电压不高于阈值M，代表充电机连接单相电网。
参看图1示出的较佳实施例，所述原边转换模块包括第一开关Q1、第二开关Q2、第三开关Q3、第四开关Q4，所述第一开关Q1和第三开关Q3串联组成第一桥臂，第一开关Q1和第三开关Q3的连接点为E中间点；所述第二开关Q2和第四开关Q4串联组成第二桥臂，第二开关Q2和第四开关Q4的连接点为F中间点；所述切换模块包括第一开关Relay1和第二开关Relay2，所述E中间点连接第一开关Relay1的静触头(O点)，所述F中间点连接第一开关Relay1的第一动触头(A点)，所述F中间点连接所述变压器T1原边绕组的一端，所述变压器T1原边绕组的另一端连接所述第一开关Relay1的第二动触头(B点)，所述变压器T1原边绕组的另一端与原边转换模块负极母线之间串接所述第二开关Relay2。所述变压器T1原边绕组串联第一电容C1。所述变压器T1原边绕组串联第一电感L1。
下面结合附图，对本发明工作原理进行说明。本例中通过控制电路控制图1中Relay1、Relay2开关的导通与闭合，以切换DCDC直流转换器的工作模式，使得直流转换器兼容半桥和全桥两种工作模式。
如图2，单相AC交流输入时，输入电压近似400V，第一开关Relay1的O点和B点闭合，第二开关Relay2断开，构成全桥电路，加在变压器T1原边绕组C、D两端电压如图3所示，峰峰值近似为800V，单边电压近似为400V，在要求输出电压为近似400V的场合可以实现增益为1的LLC最佳工作频率点；三相AC交流输入时，如图4，输入电压近似800V，第一开关Relay1O点和A点闭合，第二开关Relay2闭合，此时Q1、Q2并联，Q3、Q4并联，构成半桥电路，由于电容C1的存在，加载由原边绕组C、D两端电压如图5所示，峰峰值近似为800V，单边电压近似为400V，在要求输出电压为近似400V的场合也可以实现增益为1的LLC最佳工作点，从而实现DCDC在单相、三相的应用条件下都处于LLC功率级的最佳工作频率点。图6示出的是现有技术与本发明全桥增益曲线对比图，从对照图中可以看出，本申请的增益需求明显比传统全桥拓扑的增益需求低。
另外，本发明可以降低充电机导通损耗。在全桥拓扑中，当三相交流输入时，母线电容电压近似为800V，高压输出电压需求为400V，变压器需配置为2：1匝比以达到增益为1的最佳效率工作点；当单相交流输入时，母线电容电压近似为400V，高压输出电压需求为400V，按照2：1的变压器匝比配置，增益需要达到2才能满足高压输出电压400V的需求，此时励磁电感与谐振电感比值为K。在本发明实施例电路中，使用半桥全桥切换拓扑，无论是三相交流输入还是单相交流输入，增益需求都为1，变压器均配置为1：1，此时励磁电感与谐振电感比值近似为2K。可以得出，在本发明中，励磁电感配置为传统全桥电路的2倍，从而降低谐振腔环路电流，降低导通损耗，提高效率。图7示出的是现有技术全桥励磁电流波形；图8示出的是本发明励磁电流波形。从对照图中可以看出，本发明励磁电流明显比现有技术全桥励磁电流小。
另外，本发明可以降低逆变模式下的开关损耗。结合图9示出的现有技术与本发明全桥谐振频率对比图。传统全桥电路中，当输入为三相交流电时，PFC母线电容电压近似为800V，高压输出电压需求400V，变压器需配置为近似2：1匝比才能达到最优效率点；按此变压器配置电路处于单相逆变状态，增益需求约为0.5，开关频率较高，从而增加开关损耗。按照本发明实施例电路配置为半桥，可以维持1：1变压器匝比，降低增益需求，从而降低频率，降低开关损耗，提升逆变状态效率。
在较佳实施例中，所述第一开关Relay1采用单刀双掷继电器或选择开关，所述第二开关Relay2采用单刀单掷继电器。
所述副边转换模块包括副边高压转换模块和副边低压转换模块。本发明运用到车载充电机中，副边高压换模块连接车内高压动力电池，副边低压转换模块连接车内低压电池和整车用电设备。
图1示出的较佳实施例中，所述副边第一转换模块采用全桥结构，包括第五功率开关Q5、第六功率开关Q6、第七功率开关Q7、第八功率开关Q8；其中第五功率开关Q5和第七功率开关Q7为一对桥臂，第六功率开关Q6和第八功率开关Q8为一对桥臂，并且第五功率开关Q5和第六功率开关Q6为上桥臂，第七功率开关Q7和第八功率开关Q8为下桥臂。所述第一功率开关Q1、 第二功率开关Q2、第三功率开关Q3、第四功率开关Q4、第五功率开关Q5、第六功率开关Q6、第七功率开关Q7、第八功率开关Q8采用MOSFET、SiC MOSFET、IGBT并联二极管、GAN HEMT中的一种。
所述副边低压转换模块包括第九功率开关Q9、第十功率开关Q10、第十一功率开关Q11；所述第九功率开关Q9的漏极连接第四副边绕组W3的同名端，所述第十功率开关Q10的漏极连接第三副边绕组W4的异名端，第四副边绕组W3的异名端与第三副边绕组W4同名端连接后串联第十一功率开关Q11和输出电感L2、之后连接副边低压转换模块的正极输出端，第九功率开关Q9和第十功率开关Q10的源极接地。
本发明还公开了一种适应宽输入电压的车载充电机，所述车载充电机采用上述的适应宽输入电压的DCDC转换电路。
以上实施例仅为举例说明，非起限制作用。任何未脱离本申请精神与范畴，而对其进行的等效修改或变更，均应包含于本申请的权利要求范围之中。

Claims (9)

  1. 一种适应宽输入电压的DCDC转换电路，包括依次连接原边转换模块、变压器T1、副边转换模块，以及控制器，所述原边转换模块包括由四个功率开关组成的第一和第二桥臂，其特征在于：在第一桥臂E中间点与变压器T1原边之间、以及原边转换模块负极母线与变压器T1原边绕组之间设有切换模块；控制器原边转换模块的母线电压控制切换模块进行切换动作，将原边转换模块切换为全桥结构或半桥结构。
  2. 如权利要求1所述的适应宽输入电压的DCDC转换电路，其特征在于：所述DCDC转换电路包括充电模式、逆变模式；
    在充电模式中所述母线电压高于阈值M时，控制原边转换模块切换为半桥结构；
    在充电模式中所述母线电压不高于阈值M时，控制原边转换模块切换为全桥结构；
    在逆变模式中，控制原边转换模块切换为全桥结构。
  3. 如权利要求2所述的适应宽输入电压的DCDC转换电路，其特征在于：所述阈值M为600伏。
  4. 如权利要求1所述的适应宽输入电压的DCDC转换电路，其特征在于：所述原边转换模块包括第一开关Q1、第二开关Q2、第三开关Q3、第四开关Q4，所述第一开关Q1和第三开关Q3串联组成第一桥臂，第一开关Q1和第三开关Q3的连接点为E中间点；所述第二开关Q2和第四开关Q4串联组成第二桥臂，第二开关Q2和第四开关Q4的连接点为F中间点；所述切换模块包括第一开关Relay1和第二开关Relay2，所述E中间点连接第一开关Relay1的静触头，所述F中间点连接第一开关Relay1的第一动触头，所述F中间点连接所述变压器T1原边绕组的一端，所述变压器T1原边绕组的另一端连接所述第一开关Relay1的第二动触头，所述变压器T1原边绕组的另一端与原边转换模块负极母线之间串接所述第二开关Relay2。
  5. 如权利要求4所述的适应宽输入电压的DCDC转换电路，其特征在于：所述变压器T1原边绕组串联第一电容C1。
  6. 如权利要求5所述的适应宽输入电压的DCDC转换电路，其特征在于： 所述变压器T1原边绕组串联第一电感L1。
  7. 如权利要求4所述的适应宽输入电压的DCDC转换电路，其特征在于：所述第一开关Relay1采用单刀双掷继电器或选择开关，所述第二开关Relay2采用单刀单掷继电器。
  8. 如权利要求1至7任一项所述的适应宽输入电压的DCDC转换电路，其特征在于：所述副边转换模块包括副边高压转换模块和副边低压转换模块。
  9. 一种适应宽输入电压的车载充电机，其特征在于：所述车载充电机采用权利要求1至8任一项所述的适应宽输入电压的DCDC转换电路。
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