WO2020019550A1 - 基于多同步旋转坐标系的多功能并网逆变器谐波治理方法 - Google Patents

基于多同步旋转坐标系的多功能并网逆变器谐波治理方法 Download PDF

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WO2020019550A1
WO2020019550A1 PCT/CN2018/111903 CN2018111903W WO2020019550A1 WO 2020019550 A1 WO2020019550 A1 WO 2020019550A1 CN 2018111903 W CN2018111903 W CN 2018111903W WO 2020019550 A1 WO2020019550 A1 WO 2020019550A1
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grid
connected inverter
coordinate system
harmonic
reference current
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PCT/CN2018/111903
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English (en)
French (fr)
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岳东
陈剑波
柏少童
窦春霞
刘钊
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南京邮电大学
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J3/00—Circuit arrangements for ac mains or ac distribution networks
    • H02J3/01—Arrangements for reducing harmonics or ripples
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J3/00—Circuit arrangements for ac mains or ac distribution networks
    • H02J3/38—Arrangements for parallely feeding a single network by two or more generators, converters or transformers
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02E—REDUCTION OF GREENHOUSE GAS [GHG] EMISSIONS, RELATED TO ENERGY GENERATION, TRANSMISSION OR DISTRIBUTION
    • Y02E40/00—Technologies for an efficient electrical power generation, transmission or distribution
    • Y02E40/40—Arrangements for reducing harmonics

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  • the invention relates to a method for controlling harmonics, in particular to a method for controlling harmonics of a multifunctional grid-connected inverter based on a multi-synchronous rotating coordinate system, and belongs to the field of power quality improvement.
  • the grid-connected inverter is a device used to connect the distributed power supply system and the power grid to realize power transmission and exchange.
  • the grid-connected inverter can also work in a non-grid state, that is, it is independent of the power grid and supplies power to users.
  • the power quality problems caused by harmonics, three-phase imbalances, voltage sags, and voltage swells are extremely high.
  • the earth has reduced the power quality of the power grid, which has led to pollution of the power grid, degradation of power quality, failure of power supply and power equipment, and even serious fire accidents, which constantly threatened the safe, economic and stable operation of the power system.
  • the first is the addition of additional power quality improvement devices, which are mainly divided into: passive filter devices, active filter devices and reactive power compensation devices; although passive filters are extremely low-cost, economical and simple, the ability to suppress harmonics is compared Weak, the effect is not good, such as LC series filters; for active filters, active filters can be compensated in time without adding capacitive components of the power grid, the filtering effect is better, but because of active filters Limited by the development of power electronic components withstand voltage and rated current, the cost is extremely high, and its production is much more complicated and more expensive than passive filters, such as active filters (APF); a reasonable choice of reactive power compensation
  • the device can minimize the loss of the network and improve the quality of the power grid. However, if it is not selected or used properly, it can cause many factors such as the power supply system, voltage fluctuations, and even harmonics. For example, the static reactive power compensator ( SVC) and so on.
  • SVC static reactive power compensator
  • the second is to modify the algorithm based on the active output of the inverter, so that the inverter can compensate the system's harmonics, imbalance and reactive power based on the active output, that is, a multifunctional grid-connected inverter ( MGFTI).
  • MGFTI multifunctional grid-connected inverter
  • This method does not need to increase the initial investment cost and makes full use of the remaining capacity of the inverter, which is a more economical and effective way to solve the problem of power quality.
  • the common methods for analyzing the harmonic components of load current include instantaneous reactive power theory (pq theory) and fast Fourier transform (FFT).
  • the purpose of the present invention is to solve the above-mentioned shortcomings of the prior art, and provides a multifunctional grid-connected inverter harmonic management method based on a multi-synchronous rotating coordinate system.
  • the quantity is converted into a DC quantity in the corresponding rotating coordinate system, and the DC quantity is packaged and sent to the multi-function grid-connected inverter side as a harmonic control instruction. Therefore, on the basis of the active output, the control of the load harmonics is realized, so as to solve the limitation that the existing multifunctional inverter must locally collect the load information.
  • a multi-functional grid-connected inverter harmonic control method based on a multi-synchronous rotating coordinate system includes the following steps:
  • the Park voltage is used to transform the system voltage from the abc stationary coordinate system to the dq coordinate system.
  • the dq axis voltage in the dq coordinate system and the given active power P and reactive power Q calculate The corresponding dq-axis reference current;
  • S33 Package and send the DC components of the harmonic components to the multi-function grid-connected inverter
  • the multi-function grid-connected inverter performs inverse Park conversion on the DC component of the harmonic component at an appropriate multiple of the fundamental frequency, thereby synthesizing the harmonic reference current in the abc coordinate system locally;
  • the multi-functional grid-connected inverter is a three-phase three-wire system, and the DC side capacitor of the multi-functional grid-connected inverter is connected in parallel with the distributed power source or the energy storage DC output terminal; The output is connected to the power distribution network.
  • the distributed power source or energy storage DC output terminal is: a wind turbine rectifier output terminal, a photovoltaic equipment output terminal, a fuel cell output terminal, a gas turbine output terminal, a battery pack output terminal, a flywheel energy storage output terminal, and a super capacitor.
  • a wind turbine rectifier output terminal a photovoltaic equipment output terminal
  • a fuel cell output terminal a fuel cell output terminal
  • a gas turbine output terminal a gas turbine output terminal
  • a battery pack output terminal a flywheel energy storage output terminal
  • a super capacitor One or more of the outputs.
  • the output of the multi-functional grid-connected inverter is connected to the power distribution network in such a way that the output of the multi-function grid-connected inverter is directly connected to the power distribution network through a filter, or the multi-function grid-connected inverter is connected to the grid.
  • the output of the inverter is connected to the distribution network through filters and transformers.
  • the filter is an RL filter, an LC filter or an LCL filter.
  • the reference current of the multi-functional grid-connected inverter in step S5 includes a fundamental reference current and a harmonic reference current, and the fundamental reference current is determined by an upper-layer energy management system or a maximum output power.
  • the basic task of the phase locked loop in step S1 is to quickly and accurately track the frequency and phase of the grid signal
  • the phase-locked loop includes a phase detector, a loop filter, and a voltage-controlled oscillator; the basic principle of the phase-locked loop is: the grid voltage v abc is converted to the ⁇ reference system through Clarke transformation, and then to the dq reference system , After comparing the q-axis component v q of the grid voltage under the dq reference system with a given 0 signal, the PI controller obtains the reference angular frequency ⁇ t . After integrating ⁇ t , the phase angle ⁇ of the grid voltage is obtained.
  • step S2 The formula of Park transformation in step S2 is:
  • the dq-axis reference current in step S21 The calculation method includes the following steps:
  • S213 calculates the dq-axis reference current according to the upper-layer energy management system or the maximum output power command P * , Q *
  • the method for acquiring the d-axis current for compensating the system loss in step S22 is to collect a difference between the actual value of the capacitor voltage and a given DC-side voltage, and then perform PI closed-loop control.
  • the calculation formula of the reference current of the multi-function grid-connected inverter in step S4 is:
  • the transfer function of the proportional resonance controller in step S5 is:
  • ⁇ c is the cutoff frequency
  • ⁇ h is the natural angular frequency of the fundamental wave and harmonics
  • K P is the proportional gain of the PR controller
  • K r is the resonance integral coefficient of the PR controller.
  • the invention provides a multifunctional grid-connected inverter harmonic management method based on a multi-synchronous rotating coordinate system.
  • the method converts a harmonic AC quantity into a DC quantity through multi-synchronous rotating coordinate transformation, so that the DC quantity can be packed.
  • the low-bandwidth channel is sent from the load side to the inverter side, and after performing the Park inverse conversion on the inverter side, the harmonic components that need to be controlled can be reproduced.
  • This method eliminates the need for the inverter to directly collect harmonic information on the load side, and it is not necessary to ensure that the load is electrically downstream of the inverter, so it is more flexible.
  • a proportional resonance controller in a three-phase stationary coordinate system, the reference current tracking control algorithm is simplified, and the calculation efficiency is improved.
  • FIG. 1 is a schematic diagram of the present invention
  • FIG. 2 is a power-side current harmonic analysis when the multi-functional grid-connected inverter in the present invention is not turned on;
  • 3 is a power-side current harmonic analysis of the multi-function grid-connected inverter in the present invention that compensates only harmonics below 25th;
  • Multi-function grid-connected inverter harmonic control method based on multi-synchronous rotating coordinate system, wherein the multi-function grid-connected inverter is a three-phase three-wire system, and the DC-side capacitor and distributed power of the multi-function grid-connected inverter Or the DC output end of the energy storage is connected in parallel; the output end of the multi-function grid-connected inverter is connected to the power distribution network.
  • the distributed power (DG) or energy storage DC output terminals are: wind turbine rectifier output terminal, photovoltaic equipment output terminal, fuel cell output terminal, gas turbine output terminal, battery pack output terminal, flywheel energy storage output terminal, super One or more of the capacitor output terminals.
  • the distributed power or energy storage DC output terminals are: wind turbine rectifier output terminal, photovoltaic equipment output terminal, fuel cell output terminal, gas turbine output terminal, battery pack output terminal, flywheel energy storage output terminal, and super Capacitor output.
  • connection of the output end of the multi-function grid-connected inverter to the distribution network is: the output end of the multi-function grid-connected inverter is directly connected to the distribution network through a filter, or the multi-function grid-connected inverter
  • the output of the transformer is connected to the distribution network through a filter and a transformer respectively;
  • the filter is an RL filter, an LC filter or an LCL filter.
  • the output end of the multi-function grid-connected inverter is connected to the power distribution network through a filter and a transformer, respectively, and the filter is an LC filter.
  • a multifunctional grid-connected inverter harmonic control method based on a multi-synchronous rotating coordinate system, as shown in FIG. 1, includes the following steps:
  • S1 Acquisition of the fundamental angular frequency; by designing a phase-locked loop (PLL), the phase voltage of the system voltage is simultaneously phase-locked on the load side with the multifunctional grid-connected inverter to obtain the angular frequency value;
  • PLL phase-locked loop
  • phase locked loop The basic task of a phase locked loop is to quickly and accurately track the frequency and phase of the grid signal
  • the phase-locked loop includes a phase detector, a loop filter and a voltage-controlled oscillator.
  • the basic principle of the phase-locked loop is: the grid voltage v abc is transformed into the ⁇ reference system through Clarke transformation, and then into the dq reference system.
  • the q-axis component v q of the grid voltage under the dq reference system is compared with a given 0 signal and the reference angular frequency ⁇ t is obtained by a proportional-derivative (PI) controller.
  • PI proportional-derivative
  • the calculation method of the fundamental reference current includes the following steps:
  • the Park voltage is used to transform the system voltage from the abc stationary coordinate system to the dq coordinate system, and the dq axis voltage in the dq coordinate system and the given active power P and reactive power Q are calculated.
  • the corresponding dq-axis reference current; the dq-axis reference current includes the following steps:
  • S213 calculates the dq-axis reference current according to the upper-layer energy management system or the maximum output power command P * , Q *
  • the method of obtaining the d-axis current to compensate the system loss is obtained by collecting the actual value of the capacitor voltage and the given DC-side voltage, and then performing PI closed-loop control.
  • S33 Package and send the DC components of the harmonic components to the multi-function grid-connected inverter
  • the multi-function grid-connected inverter performs inverse Park conversion on the DC component of the harmonic component at an appropriate multiple of the fundamental frequency, thereby synthesizing the harmonic reference current in the abc coordinate system locally;
  • S5 Tracking of reference current of multi-function grid-connected inverter; in the abc static coordinate system, by designing the proportional coefficient and resonance coefficient of a proportional proportional controller and providing infinite gain at the resonance point, the AC is realized.
  • the multi-functional grid-connected inverter reference current includes the fundamental reference current and the harmonic reference current, and the fundamental reference current is determined by the upper-layer energy management system or the maximum output power.
  • the transfer function of the proportional resonance controller is:
  • ⁇ c is the cutoff frequency
  • ⁇ h is the natural angular frequency of the fundamental wave and harmonics
  • K P is the proportional gain of the PR controller
  • K r is the resonance integral coefficient of the PR controller.
  • This embodiment provides a multifunctional grid-connected inverter harmonic control method based on a multi-synchronous rotating coordinate system.
  • the multifunctional inverter topology is a three-phase three-wire system, so there are no zero-sequence components and 3n-th harmonic components in the circuit.
  • the DC side of the inverter is a capacitor in parallel with the DC power supply.
  • DC power is used to simulate distributed power or energy storage DC output, specifically: wind turbine rectifier output, photovoltaic equipment output, fuel cell output, gas turbine output, battery pack / flywheel energy storage / super capacitor output end.
  • a resistor in series with the DC power supply is used to simulate the internal resistance of the power supply.
  • the non-linear load consists of a resistive uncontrolled rectifier circuit, which contains only 6n ⁇ 1 harmonic components in the load current.
  • the work flow is: extract the load current i L and use the ⁇ t obtained by the phase-locked loop to carry out the Parker transformation.
  • the obtained data is packaged and sent to the multi-function grid-connected inverter (MGFTI), and the harmonic components in it are reversed by Parker transformation and summed with the filter inductor current and the fundamental reference current, and then passed through the proportional resonance (PR) controller.
  • MFTI multi-function grid-connected inverter
  • PR proportional resonance
  • PWM pulse width modulation
  • phase-locked technology is used to obtain the angular frequency value.
  • the basic task of a phase-locked loop is to quickly and accurately track the frequency and phase of the grid signal. It is mainly composed of a phase detector, a loop filter, and a voltage-controlled oscillator.
  • a single synchronous coordinate system software phase-locked loop (SSRF-SPLL) is used to implement phase-locking of the voltage vector.
  • the basic principle of SSRF-SPLL is: the grid voltage v abc is transformed into the ⁇ reference system through the Clark transform, and then converted to the dq reference system.
  • the q-axis component v q of the grid voltage under the dq reference frame is compared with a given 0 signal to obtain the reference angular frequency ⁇ t through the PI controller, and the phase angle ⁇ of the grid voltage can be obtained after integrating ⁇ t .
  • the system voltage is transformed from the abc stationary coordinate system to the dq coordinate system through Park transformation.
  • the corresponding dq axis voltage and the given active power P and reactive power Q are calculated using the dq coordinate system.
  • dq axis reference current In order to maintain the stability of the DC-side voltage, in addition to the grid-connected current, the d-axis needs to provide additional active current to compensate for system losses.
  • PI control is performed to obtain the d-axis current to compensate the system loss.
  • the Park inverse transformation is performed with the q-axis currents to obtain the fundamental reference current in the abc stationary coordinate system.
  • the phase voltage v abc of the acquisition system can be converted into a DC component on the dq axis by using Park transformation.
  • the corresponding dq-axis reference current can be calculated.
  • the DC-side capacitor voltage is collected and compared with the reference value. After doing poor, PI closed-loop control.
  • the output of the PI controller is the fundamental component of the d-axis reference current to compensate the inverter loss
  • the final d-axis component of the fundamental reference current is given by versus It consists of two parts. Perform the Park inverse transformation on the dq-axis fundamental wave component to obtain the fundamental wave reference current in the abc stationary coordinate system
  • the grid-connected inverter does not directly collect the harmonic current at the load, but receives the harmonic components sent by the load end, and then reproduces the harmonic components locally.
  • This solution has a certain flexibility for the load and the installation position of the inverter.
  • the harmonic components in the load current can be analyzed first.
  • n is an integer
  • the non-linear load in this example is a resistive uncontrolled rectifier circuit, its load current contains only 6n ⁇ 1 harmonic components, of which 6n + 1 harmonics are positive sequence components and 6n-1 harmonics are negative Ordinal component.
  • the load current is Park-transformed at (6n + 1) times the fundamental wave angular frequency, and the corresponding DC component is obtained by low-pass filtering the component under the dq axis.
  • the load current is Park-transformed at (1-6n) times the fundamental frequency, and the corresponding DC component is obtained by low-pass filtering the component under the dq axis.
  • the load current I Labc is Park-transformed at the phase angles of (6n + 1) ⁇ t t and (1-6n) ⁇ t t, respectively, to obtain the cross variables on the dq axis.
  • the second-order low-pass filter can be used to extract the DC component in the dq axis, thereby obtaining the dq axis amplitude of the 6n ⁇ 1 harmonic component in the load current.
  • the designer can choose a single harmonic component or a harmonic component that is less than 25 or less than 50, and send the harmonic component to the inverter side for harmonic compensation.
  • the inverter side After receiving the harmonic component information on the load current side, the inverter side performs Park inverse transformation on the DC component corresponding to the higher harmonic at (6n + 1) or (1-6n) times the fundamental frequency. Harmonic reference current in abc coordinate system is synthesized locally Combining this harmonic reference current with the fundamental reference current is the final reference current of the multifunctional grid-connected inverter.
  • the final fundamental wave reference current is calculated as:
  • the commonly used PI controller cannot track the steady state error of the AC component.
  • the steady-state error tracking of the AC component can be achieved, thereby realizing the active output and harmonic control functions.
  • the transfer function of the PR controller is as follows:
  • ⁇ c represents the cut-off frequency
  • ⁇ h represents the natural angular frequency of the fundamental wave and harmonics
  • K P is the proportional gain of the PR controller
  • K r is the resonance integral coefficient of the PR controller.
  • K P Is 10 and K r is 4400.
  • the steady-state error tracking of the inverter reference current can be realized.
  • FIG. 2 shows a simulation result diagram of a multi-function grid-connected inverter harmonic management method based on the multi-synchronous rotating coordinate system of the present invention.
  • the multi-functional grid-connected inverter is put into operation.
  • the harmonic control and active grid connection function of the inverter at 0.2s, only the harmonic control function of the multi-function grid-connected inverter is enabled. It can be seen from Figure 3 that after the multi-functional grid-connected inverter compensates for the harmonic components below 25 times in the load current, the total harmonic distortion rate at the PCC point is reduced to 1.58%, which is in line with the national standard of 5%. Requirements.
  • the multi-function grid-connected inverter receives the upper-layer energy management system or the maximum power output instruction, thereby realizing the harmonic control function and outputting active current, thereby reducing the load from Fundamental current drawn on the power supply side.
  • Figure 4 shows the output current and corresponding power supply side current of the multi-function grid-connected inverter in different operating modes.
  • the invention uses a multi-rotation synchronous coordinate system method to convert each high-harmonic alternating component in the load current into a direct current quantity in the corresponding coordinate system, so that data can be sent to the MFGTI end with a lower bandwidth.
  • This method is particularly suitable for situations where the load is installed upstream of the MGFTI electrical. This method concisely solves the problem of harmonic pollution caused by non-linear loads, improves the reliability of power quality, and helps improve energy efficiency.

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Abstract

本发明揭示了一种基于多同步旋转坐标系的多功能并网逆变器谐波治理方法，首先利用锁相环得到Park变换所需的负载电流的基波角频率，并利用多同步旋转坐标系方法，将负载电流中交变的谐波分量转化为相应坐标系下的直流量，进而将直流量打包发送到多功能并网逆变器侧。逆变器将直流量合成为相应的交变电流，作为谐波补偿分量。多功能并网逆变器在获得基波参考分量与谐波补偿分量后，在abc坐标系下利用比例谐振控制器对该交流分量进行跟踪，从而实现多功能并网逆变器的谐波治理功能。本发明可以较低带宽将数据发送到多功能并网逆变器端，另外，该方法简洁地解决了非线性负载带来的谐波污染问题，提高了电能质量的可靠性，有助于提高能源利用效率。

Description

基于多同步旋转坐标系的多功能并网逆变器谐波治理方法 技术领域
本发明涉及一种谐波治理方法，尤其涉及一种基于多同步旋转坐标系的多功能并网逆变器谐波治理方法，属于电能质量改善领域。
背景技术
并网逆变器是用来连接分布式供电系统和电网，实现电能传送和交换的设备。当然，并网逆变器也可以工作于不并网状态，即独立于电网、单独向用户供电。实际上，目前电网中由于非线性负载的大量接入，及电力系统电力电子化程度不断加深，由此引发的谐波、三相不平衡、电压暂降、电压暂升等电能质量问题，极大地降低了电网的电能质量，从而导致电网污染、电力品质下降，引起供电及用电设备故障，甚至引发严重火灾事故等，不断威胁着电力系统的安全经济稳定运行。
目前改善电能质量主要有两个方向：
一是添加额外的电能质量改善装置，主要分为：无源滤波装置、有源滤波装置及无功补偿装置；虽然无源滤波器的成本极低、经济且简便，但是抑制谐波的能力比较弱，效果不好，例如LC串联滤波器；对于有源滤波器而言，有源滤波器能做到适时补偿，且不增加电网的容性元件，滤波效果较好，但是由于有源滤波器受到电力电子元件耐压、额定电流的发展限制，成本极高，其制作也比无源滤波器复杂得多，成本也高很多，例如，有源滤波器(APF)；合理的选择无功补偿装置可以做到最大限度的减少网络的损耗，使电网质量提高，但是，如果选择或使用不当，可造成供电系统、电压波动，甚至谐波增大等诸多因素，例如，静态无功补偿器(SVC)等等。
二是在逆变器有功输出的基础上修改算法，使得逆变器可以在有功输出的基础上，对系统的谐波、不平衡与无功等进行补偿，即多功能并网逆变器(MGFTI)。这种方法不需要加大初始投资费用，并充分利用逆变器的剩余容量，是解决电能质量问题的一种较为经济有效的途径。在多功能并网逆变器 中，分析负载电流的谐波分量的常见方法有瞬时无功功率理论(pq理论)与快速傅里叶变换(FFT)。
综上所述，如何提供一种基于多功能并网逆变器治理谐波，就成为本领域技术人员亟待解决的问题。
发明内容
本发明的目的是为了解决现有技术的上述缺陷，提供了一种基于多同步旋转坐标系的多功能并网逆变器谐波治理方法，通过锁相环得到派克变换(Park变换)将交流量转换为相应旋转坐标系下的直流量，该直流量被打包发送到多功能并网逆变器侧，作为谐波治理指令。从而在有功输出的基础上，实现了负载谐波的治理，以解决现有多功能逆变器必须本地采集负荷信息的限制。
本发明的技术解决方案是：
基于多同步旋转坐标系的多功能并网逆变器谐波治理方法，包括如下步骤：
S1：基波角频率的获取；通过设计锁相环，在负载侧与多功能并网逆变器同时对系统电压进行锁相得到角频率的值；
S2：基波参考电流的计算，包括如下步骤：
S21：在逆变器侧，通过Park变换将系统电压从abc静止坐标系转换到dq坐标系下，利用dq坐标系下的dq轴电压与给定的有功功率P与无功功率Q，计算出相应的dq轴参考电流；
S22：将d轴电流与补偿系统损耗的d轴电流相加，再与q轴电流进行Park反变换，从而得到abc静止坐标系下的基波参考电流；
S3：谐波参考电流的计算，包括如下步骤：
S31：在负载侧，分析负载电流中的谐波成分；
S32：对于不同的谐波分量，分别将负载电流以合适倍基波角频率进行Park变换，对dq轴下的分量进行低通滤波后得到相应的直流分量，得到负载电流中的谐波成分的直流分量；
S33：将谐波成分的直流分量打包并发送至多功能并网逆变器侧；
S34：多功能并网逆变器再对谐波成分的直流分量以合适倍基波角频率进行Park反变换，从而在本地合成出abc坐标系下的谐波参考电流；
S4：多功能并网逆变器参考电流的合成；将步骤S2中的基波参考电流与S3中的谐波参考电流合成为多功能并网逆变器参考电流；
S5：多功能并网逆变器参考电流的跟踪；在abc静止坐标系下，交流分量的无稳态误差跟踪是通过设计合适的比例谐振控制器的比例系数与谐振系数，及在谐振点处提供无限增益的方式实现。
优选地，所述多功能并网逆变器为三相三线制，多功能并网逆变器的直流侧的电容与分布式电源或储能直流输出端并联；多功能并网逆变器的输出端与配电网相连接。
优选地，所述分布式电源或储能直流输出端为：风力发电机整流输出端、光伏设备输出端、燃料电池输出端、燃气轮机输出端、蓄电池组输出端、飞轮储能输出端、超级电容器输出端中的一种或几种。
优选地，所述多功能并网逆变器的输出端与配电网的连接方式为：多功能并网逆变器的输出端通过滤波器直接与配电网相连接，或多功能并网逆变器的输出端分别通过滤波器、变压器与配电网相连接。
优选地，所述滤波器为RL滤波器、LC滤波器或LCL滤波器。
优选地，所述步骤S5中多功能并网逆变器参考电流包括基波参考电流与谐波参考电流，所述基波参考电流由上层能量管理系统或最大可输出功率决定。
优选地，所述步骤S1中的锁相环的基本任务是快速准确地跟踪电网信号的频率和相位；
所述锁相环包括鉴相器、环路滤波器及压控振荡器；锁相环的基本原理为：将电网电压v abc经过克拉克变换转换到αβ参考系下，再转换到dq参考系 下，把dq参考系下的电网电压的q轴分量v q和给定的0信号进行比较后经PI控制器得到基准角频率ω t，将ω t积分后即得到电网电压的相位角θ。
优选地，
所述步骤S2中Park变换的公式为：
Figure PCTCN2018111903-appb-000001
所述步骤S21中的所述dq轴参考电流
Figure PCTCN2018111903-appb-000002
的计算方法包括如下步骤：
S211：利用Park变换公式将系统电压v abc转换为dq轴上的电压分量，
Figure PCTCN2018111903-appb-000003
则dq坐标系下的瞬时功率的计算公式为：
Figure PCTCN2018111903-appb-000004
S212：在给定的有功功率P与无功功率Q的情况下，dq轴电流分量的计算公式为：
Figure PCTCN2018111903-appb-000005
S213根据所述上层能量管理系统或最大可输出功率指令P *，Q *，从而计算出dq轴参考电流
Figure PCTCN2018111903-appb-000006
所述步骤S22中的所述abc静止坐标系下的基波参考电流
Figure PCTCN2018111903-appb-000007
为：
Figure PCTCN2018111903-appb-000008
其中，
Figure PCTCN2018111903-appb-000009
为d轴参考电流中用以补偿逆变器损耗的基波分量；
所述步骤S22中的补偿系统损耗的d轴电流的获取方法是通过采集电容电压的实际值与给定直流侧电压做差，然后进行PI闭环控制。
优选地，所述步骤S4中的多功能并网逆变器参考电流的计算公式为：
Figure PCTCN2018111903-appb-000010
优选地，所述步骤S5中比例谐振控制器的传递函数为：
Figure PCTCN2018111903-appb-000011
式中的ω c为截止频率，ω h为基波和谐波的自然角频率，K P是PR控制器的比例增益，K r是PR控制器的谐振积分系数。
本发明提供了一种基于多同步旋转坐标系的多功能并网逆变器谐波治理方法，该方法通过多同步旋转坐标变换将谐波交流量转化为直流量，从而可将直流量打包后通过低带宽信道从负载侧发送到逆变器侧，在逆变器侧进行Park反变换后，即可复现出所需治理的谐波分量。这种方法使得逆变器无需直接采集负载侧的谐波信息，无需保证负载在逆变器的电气下游，因而更具灵活性。此外，通过在三相静止坐标系下采用比例谐振控制器，简化了参考电流跟踪控制算法，提高了计算效率。
以下便结合实施例附图，对本发明的具体实施方式作进一步的详述，以使本发明技术方案更易于理解、掌握。
附图说明
图1为本发明的示意图；
图2为本发明中多功能并网逆变器未投入时的电源侧电流谐波分析；
图3为本发明中多功能并网逆变器仅对25次以下谐波补偿的电源侧电流谐波分析；
图4电源侧电流I s及多功能逆变器输出电流I g。
具体实施方式
基于多同步旋转坐标系的多功能并网逆变器谐波治理方法，其中，多功能并网逆变器为三相三线制，多功能并网逆变器的直流侧的电容与分布式电源或储能直流输出端并联；多功能并网逆变器的输出端与配电网相连接。
进一步地，分布式电源(DG)或储能直流输出端为：风力发电机整流输出端、光伏设备输出端、燃料电池输出端、燃气轮机输出端、蓄电池组输出端、飞轮储能输出端、超级电容器输出端中的一种或几种。在本实施例中，分布式电源或储能直流输出端为：风力发电机整流输出端、光伏设备输出端、燃料电池输出端、燃气轮机输出端、蓄电池组输出端、飞轮储能输出端及超级电容器输出端。
更进一步地，多功能并网逆变器的输出端与配电网的连接方式为：多功能并网逆变器的输出端通过滤波器直接与配电网相连接，或多功能并网逆变器的输出端分别通过滤波器、变压器与配电网相连接；滤波器为RL滤波器、LC滤波器或LCL滤波器。在本发明的技术方案中，多功能并网逆变器的输出端是分别通过滤波器、变压器与配电网相连接的，且滤波器为LC滤波器。
基于多同步旋转坐标系的多功能并网逆变器谐波治理方法，如图1所示，包括如下步骤：
S1：基波角频率的获取；通过设计锁相环(PLL)，在负载侧与多功能并网逆变器同时对系统电压进行锁相得到角频率的值；
锁相环的基本任务是快速准确地跟踪电网信号的频率和相位；
锁相环包括鉴相器、环路滤波器及压控振荡器；锁相环的基本原理为：将电网电压v abc经过克拉克变换转换到αβ参考系下，再转换到dq参考系下，把dq参考系下的电网电压的q轴分量v q给定的0信号进行比较后经比例-微分(PI)控制器得到基准角频率ω t，将ω t积分后即得到电网电压的相位角θ。
S2：基波参考电流的计算，其中，所涉及到的Park变换的公式为
Figure PCTCN2018111903-appb-000012
基波参考电流的计算方法，包括如下步骤：
S21：在逆变器侧，通过Park变换将系统电压从abc静止坐标系转换到dq坐标系下，利用dq坐标系下的dq轴电压与给定的有功功率P与无功功率Q，计算出相应的dq轴参考电流；所述dq轴参考电流
Figure PCTCN2018111903-appb-000013
的计算方法包括如下步骤：
S211：利用Park变换公式将系统电压v abc转换为dq轴上的电压分量，
Figure PCTCN2018111903-appb-000014
则dq坐标系下的瞬时功率的计算公式为：
Figure PCTCN2018111903-appb-000015
S212：在给定的有功功率P与无功功率Q的情况下，dq轴电流分量的计算公式为：
Figure PCTCN2018111903-appb-000016
S213根据所述上层能量管理系统或最大可输出功率指令P *，Q *，从而计 算出dq轴参考电流
Figure PCTCN2018111903-appb-000017
S22：将d轴电流与补偿系统损耗的d轴电流相加，再与q轴电流进行Park反变换，从而得到abc静止坐标系下的基波参考电流；所述abc静止坐标系下的基波参考电流
Figure PCTCN2018111903-appb-000018
为：
Figure PCTCN2018111903-appb-000019
其中，
Figure PCTCN2018111903-appb-000020
为d轴参考电流中用以补偿逆变器损耗的基波分量；
补偿系统损耗的d轴电流的获取方法是通过采集电容电压的实际值与给定直流侧电压做差，然后进行PI闭环控制得到的。
S3：谐波参考电流的计算，包括如下步骤：
S31：在负载侧，分析负载电流中的谐波成分；
S32：对于不同的谐波分量，分别将负载电流以合适倍基波角频率进行Park变换，对dq轴下的分量进行低通滤波后得到相应的直流分量，得到负载电流中的谐波成分的直流分量；
S33：将谐波成分的直流分量打包并发送至多功能并网逆变器侧；
S34：多功能并网逆变器再对谐波成分的直流分量以合适倍基波角频率进行Park反变换，从而在本地合成出abc坐标系下的谐波参考电流；
S4：多功能并网逆变器参考电流的合成；将步骤S2中的基波参考电流与S3中的谐波参考电流合成为多功能并网逆变器参考电流，即多功能并网逆变器参考电流的计算公式为：
Figure PCTCN2018111903-appb-000021
S5：多功能并网逆变器参考电流的跟踪；在abc静止坐标系下，通过设计合适的比例谐振控制器的比例系数与谐振系数，及在谐振点处提供无限增益的方式，实现对交流分量的无稳态误差跟踪。其中，多功能并网逆变器参考电流 包括基波参考电流与谐波参考电流，且基波参考电流由上层能量管理系统或最大可输出功率决定。其中，比例谐振控制器的传递函数为：
Figure PCTCN2018111903-appb-000022
式中的ω c为截止频率，ω h为基波和谐波的自然角频率，K P是PR控制器的比例增益，K r是PR控制器的谐振积分系数。
下面将结合附图对本发明的实施例作详细说明，本实施例在以本发明技术方案为前提下进行实施，给出了详细的实施方式和具体的操作过程，但本发明的保护范围不限于下述的实施例。
本实施例提供了一种基于多同步旋转坐标系的多功能并网逆变器谐波治理方法。
如图1所示，在本实施例中，采用多功能逆变器拓扑结构为三相三线制，因此电路中无零序分量及3n次谐波分量。逆变器直流侧为电容与直流电源并联。直流电源用于模拟分布式电源或储能直流输出端，具体指：风力发电机整流输出端、光伏设备输出端、燃料电池输出端、燃气轮机输出端、蓄电池组/飞轮储能/超级电容器的输出端。与直流电源串联的电阻用于模拟电源内电阻。非线性负载由阻性不控整流电路组成，该电路负载电流中仅含有6n±1次谐波分量。
工作流程为：提取负载电流i L,利用锁相环得到的ω t进行派克变换。将得到的数据打包发送到多功能并网逆变器端(MGFTI)，将其中的谐波分量进行反派克变换后与滤波电感电流和基波参考电流求和，经过比例谐振(PR)控制器跟踪控制后进入到脉冲宽度调制(PWM)发生器中生成控制信号输送到逆变器端口调节开关管的开断。具体操作过程如下:
S1：基波角频率的计算
在Park变换的过程中，需要用到系统电压的基波角频率，这时要使用锁相技术来得到角频率的值。锁相环的基本任务是快速准确地跟踪电网信号的频率和相位，它主要是由鉴相器、环路滤波器、压控振荡器构成。本实施例采用单同步坐标系软件锁相环(SSRF-SPLL)实现电压矢量的锁相。SSRF-SPLL的基本原理是：将电网电压v abc经过克拉克变换转换到αβ参考系下，再转换到dq参考系下。把dq参考系下的电网电压的q轴分量v q和给定的0信号进行比较后经PI控制器得到基准角频率ω t，将ω t积分后即可得到电网电压的相位角θ。
S2：基波参考电流的计算
在逆变器侧，通过Park变换将系统电压从abc静止坐标系转换到dq坐标系下，利用dq坐标系下的dq轴电压与给定的有功功率P与无功功率Q，计算出相应的dq轴参考电流。为维持直流侧电压的稳定，d轴除了并网电流外，还需要提供额外的有功电流，以补偿系统损耗。通过采集电容电压的实际值与给定直流侧电压做差后，进行PI控制，得到为补偿系统损耗的d轴电流。将两种d轴电流相加后，与q轴电流进行Park反变换，从而得到abc静止坐标系下的基波参考电流。
本方法采用的Park变换公式如下：
Figure PCTCN2018111903-appb-000023
采集系统的相电压v abc,利用Park变换可将其转化为dq轴上的直流分量。
Figure PCTCN2018111903-appb-000024
在dq坐标系下的瞬时功率计算公式如下：
p＝v di d+v qi q
q＝v qi d-v di q
则在跟定有功功率P和无功功率Q的情况下，dq轴电流分量的计算公式如下：
Figure PCTCN2018111903-appb-000025
由此，根据上层能量管理系统或最大输出功率指令P *，Q *，可计算出相应的dq轴参考电流
Figure PCTCN2018111903-appb-000026
如图1所示，为维持直流侧电压U dc稳定，通过采集直流侧电容电压并与参考值
Figure PCTCN2018111903-appb-000027
做差后进行PI闭环控制。PI控制器的输出端为d轴参考电流中用以补偿逆变器损耗的基波分量
Figure PCTCN2018111903-appb-000028
因此，最终的基波参考电流d轴分量由
Figure PCTCN2018111903-appb-000029
与
Figure PCTCN2018111903-appb-000030
两部分组成。对dq轴基波分量进行Park反变换，即可得出abc静止坐标系下的基波参考电流
Figure PCTCN2018111903-appb-000031
Figure PCTCN2018111903-appb-000032
S3：谐波参考电流的计算
如图1所示，并网逆变器并非直接采集负载处的谐波电流，而是接收由负载端发送的谐波分量，进而在本地复现出谐波成分。该方案对负载与逆变器的安装位置无关，具有一定的灵活性。
在负载侧，可先分析出负载电流中的谐波成分。如三相三线制系统中，无3n次(n为整数)谐波分量，从而可大大减少所需的Park变换与反变换次数。由于本例中非线性负载为阻性不控整流电路，其负载电流中仅含6n±1次谐波分量，其中，6n+1次谐波为正序分量，6n-1次谐波为负序分量。
对于6n+1次谐波分量，将负载电流以(6n+1)倍基波角频率进行Park变换，对dq轴下的分量进行低通滤波后得到相应的直流分量。
对于6n-1次谐波分量，将负载电流以(1-6n)倍基波角频率进行Park变换，对dq轴下的分量进行低通滤波后得到相应的直流分量。
负载电流I Labc分别以(6n+1)ω tt、(1-6n)ω tt的相角进行Park变换，得到dq轴上的交变量。利用二阶低通滤波器可将dq轴中的直流分量提取出来，从而获得负载电流中6n±1次谐波分量的dq轴幅值。根据实际的应用场景与逆变器容量，设计者可选择单次或25次以下或50次以下的谐波分量，将该谐波分量打包发送至逆变器侧进行谐波补偿。
S4：多功能并网逆变器参考电流的合成
逆变器侧在接收到负载电流侧的谐波分量信息后，通过对高次谐波对应的直流分量以(6n+1)或(1-6n)倍基波角频率进行Park反变换，从而在本地合成出abc坐标系下的谐波参考电流
Figure PCTCN2018111903-appb-000033
将该谐波参考电流与基波参考电流合成，即为多功能并网逆变器最终的参考电流。最终的基波参考电流的计算公式为：
Figure PCTCN2018111903-appb-000034
S5：多功能并网逆变器参考电流的跟踪
在abc静止坐标系下，常用的PI控制器无法对交流分量进行无稳态误差跟踪。通过设计合适的比例谐振控制器的比例系数与谐振系数，通过在谐振点处提供无限增益的方式，可实现对交流分量的无稳态误差跟踪，从而实现有功输出与谐波治理功能。
PR控制器的传递函数如下:
Figure PCTCN2018111903-appb-000035
式中的ω c代表截止频率，ω h代表基波和谐波的自然角频率，K P是PR控制器的比例增益，K r是PR控制器的谐振积分系数，本实施例中取K P为10，K r为4400。
根据所设计的PR控制器可以实现对逆变器参考电流的无稳态误差跟踪。
图2显示了本发明的一种基于多同步旋转坐标系的多功能并网逆变器谐波治理方法的仿真结果图
如图2所示，在0.2s前，并网逆变器并未投入运行，负载电流中的谐波分量完全注入到公共耦合点(PCC)。从PCC点处10个周期电流波形的傅里叶分析结果可知，负载电流中的谐波分量以5、7、11、13次谐波为主，总谐波畸变率为24.5％，远远大于5％的国家标准。
在0.2s时，多功能并网逆变器投入运行。为清楚显示逆变器的谐波治理与有功并网功能，在0.2s时，仅开通多功能并网逆变器的谐波治理功能。从图3中可以看出，在多功能并网逆变器对负载电流中25次以下谐波分量进行补偿后，PCC点处的总谐波畸变率降为1.58％，符合国家标准中5％的要求。
从图3中可以看出，在0.4s时，多功能并网逆变器接收上层能量管理系统或最大功率输出指令，从而在实现谐波治理功能的同时，输出有功电流，从而降低了负载从电源侧汲取的基波电流。
电源侧电流及多功能并网逆变器的输出电流如图4所示。图4显示了多功能并网逆变器在不同工作模态下的输出电流与相应的电源侧电流。
本发明利用多旋转同步坐标系方法将负载电流中各高次谐波交变分量转化为相应坐标系下的直流量，从而可以较低带宽将数据发送到MFGTI端。该方法尤其适用于负载安装在MGFTI电气上游的情形。该方法简洁地解决了非线性负载带来的谐波污染问题，提高了电能质量的可靠性，有助于提高能源利用效率。
应该注意的是，上述实施例对本发明进行说明而不是对本发明进行限制，并且本领域技术人员在不脱离所附权利要求的范围的情况下可设计出替换实施例。

Claims (10)

  1. 基于多同步旋转坐标系的多功能并网逆变器谐波治理方法，其特征在于，包括如下步骤：
    S1：基波角频率的获取；通过设计锁相环，在负载侧与多功能并网逆变器同时对系统电压进行锁相得到角频率的值；
    S2：基波参考电流的计算，包括如下步骤：
    S21：在逆变器侧，通过Park变换将系统电压从abc静止坐标系转换到dq坐标系下，利用dq坐标系下的dq轴电压与给定的有功功率P与无功功率Q，计算出相应的dq轴参考电流；
    S22：将d轴电流与补偿系统损耗的d轴电流相加，再与q轴电流进行Park反变换，从而得到abc静止坐标系下的基波参考电流；
    S3：谐波参考电流的计算，包括如下步骤：
    S31：在负载侧，分析负载电流中的谐波成分；
    S32：对于不同的谐波分量，分别将负载电流以合适倍基波角频率进行Park变换，对dq轴下的分量进行低通滤波后得到相应的直流分量，得到负载电流中的谐波成分的直流分量；
    S33：将谐波成分的直流分量打包并发送至多功能并网逆变器侧；
    S34：多功能并网逆变器再对谐波成分的直流分量以合适倍基波角频率进行Park反变换，从而在本地合成出abc坐标系下的谐波参考电流；
    S4：多功能并网逆变器参考电流的合成；将步骤S2中的基波参考电流与S3中的谐波参考电流合成为多功能并网逆变器参考电流；
    S5：多功能并网逆变器参考电流的跟踪；在abc静止坐标系下，交流分量的无稳态误差跟踪是通过设计合适的比例谐振控制器的比例系数与谐振系数，及在谐振点处提供无限增益的方式实现。
  2. 根据权利要求1所述的基于多同步旋转坐标系的多功能并网逆变器谐波治理方法，其特征在于：所述多功能并网逆变器为三相三线制，多功能并网逆 变器的直流侧的电容与分布式电源或储能直流输出端并联；多功能并网逆变器的输出端与配电网相连接。
  3. 根据权利要求2所述的基于多同步旋转坐标系的多功能并网逆变器谐波治理方法，其特征在于：所述分布式电源或储能直流输出端为：风力发电机整流输出端、光伏设备输出端、燃料电池输出端、燃气轮机输出端、蓄电池组输出端、飞轮储能输出端、超级电容器输出端中的一种或几种。
  4. 根据权利要求2所述的基于多同步旋转坐标系的多功能并网逆变器谐波治理方法，其特征在于：所述多功能并网逆变器的输出端与配电网的连接方式为：多功能并网逆变器的输出端通过滤波器直接与配电网相连接，或多功能并网逆变器的输出端分别通过滤波器、变压器与配电网相连接。
  5. 根据权利要求4所述的基于多同步旋转坐标系的多功能并网逆变器谐波治理方法，其特征在于：所述滤波器为RL滤波器、LC滤波器或LCL滤波器。
  6. 根据权利要求1所述的基于多同步旋转坐标系的多功能并网逆变器谐波治理方法，其特征在于：所述步骤S5中多功能并网逆变器参考电流包括基波参考电流与谐波参考电流，所述基波参考电流由上层能量管理系统或最大可输出功率决定。
  7. 根据权利要求1所述的基于多同步旋转坐标系的多功能并网逆变器谐波治理方法，其特征在于：所述步骤S1中的锁相环的基本任务是快速准确地跟踪电网信号的频率和相位；
    所述锁相环包括鉴相器、环路滤波器及压控振荡器；锁相环的基本原理为：将电网电压v abc经过克拉克变换转换到αβ参考系下，再转换到dq参考系下，把dq参考系下的电网电压的q轴分量v q和给定的0信号进行比较后经PI控制器得到基准角频率ω t，将ω t积分后即得到电网电压的相位角θ。
  8. 根据权利要求6所述的基于多同步旋转坐标系的多功能并网逆变器谐波治理方法，其特征在于：
    所述步骤S2中Park变换的公式为：
    Figure PCTCN2018111903-appb-100001
    所述步骤S21中的所述dq轴参考电流
    Figure PCTCN2018111903-appb-100002
    的计算方法包括如下步骤：
    S211：利用Park变换公式将系统电压v abc转换为dq轴上的电压分量，
    Figure PCTCN2018111903-appb-100003
    则dq坐标系下的瞬时功率的计算公式为：
    Figure PCTCN2018111903-appb-100004
    S212：在给定的有功功率P与无功功率Q的情况下，dq轴电流分量的计算公式为：
    Figure PCTCN2018111903-appb-100005
    S213根据所述上层能量管理系统或最大可输出功率指令P *，Q *，从而计算出dq轴参考电流
    Figure PCTCN2018111903-appb-100006
    所述步骤S22中的所述abc静止坐标系下的基波参考电流
    Figure PCTCN2018111903-appb-100007
    为：
    Figure PCTCN2018111903-appb-100008
    其中，
    Figure PCTCN2018111903-appb-100009
    为d轴参考电流中用以补偿逆变器损耗的基波分量；
    所述步骤S22中的补偿系统损耗的d轴电流的获取方法是通过采集电容电压的实际值与给定直流侧电压做差，然后进行PI闭环控制。
  9. 根据权利要求1所述的基于多同步旋转坐标系的多功能并网逆变器谐波治理方法，其特征在于：所述步骤S4中的多功能并网逆变器参考电流的计算公式为：
    Figure PCTCN2018111903-appb-100010
  10. 根据权利要求1所述的基于多同步旋转坐标系的多功能并网逆变器谐波治理方法，其特征在于：所述步骤S5中比例谐振控制器的传递函数为：
    Figure PCTCN2018111903-appb-100011
    式中的ω c为截止频率，ω h为基波和谐波的自然角频率，K p是PR控制器的比例增益，K r是PR控制器的谐振积分系数。
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Cited By (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US11901734B2 (en) 2021-11-30 2024-02-13 Vestas Wind Systems A/S Grid side inverter system arranged for controlling current injection when a phase locked loop controller is misaligned

Families Citing this family (7)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN109599878B (zh) * 2018-12-07 2020-06-02 南京工程学院 一种面向电能质量优化需求的储能变流器控制方法
CN110994649A (zh) * 2019-12-10 2020-04-10 东北电力大学 三相不平衡负荷电流有源补偿控制方法
CN111446716B (zh) * 2020-03-31 2022-04-29 东南大学 一种vsg并网系统的谐波电压与谐波电流抑制方法
CN111641228B (zh) * 2020-06-10 2024-01-26 国网天津市电力公司电力科学研究院 多功能光伏并网逆变器等效负载电流检测环节的构建方法
CN113459901B (zh) * 2021-06-26 2023-04-28 深圳欣锐科技股份有限公司 燃料电池输出控制方法、装置、设备以及存储介质
CN116093953B (zh) * 2023-04-03 2023-06-23 深圳市鸿嘉利新能源有限公司 一种锁相环的控制方法、锁相环、逆变器及存储介质
CN118487279A (zh) * 2024-04-26 2024-08-13 深圳市启点新能源科技有限公司 无功发生器的谐振抑制方法、设备及存储介质

Citations (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN101697420A (zh) * 2009-10-23 2010-04-21 湖南大学 一种微网逆变系统及适用于该微网逆变系统的电能质量控制方法
CN102664413A (zh) * 2012-05-14 2012-09-12 重庆大学 抑制风电并网用全功率变流器谐波电流控制方法及控制器
KR20130021134A (ko) * 2011-08-22 2013-03-05 엘에스산전 주식회사 인버터의 전류 제어 장치
CN103199720A (zh) * 2013-04-17 2013-07-10 湖南大学 一种三相功率变流器的综合控制方法
CN103595278A (zh) * 2013-11-18 2014-02-19 河南师范大学 太阳能发电系统网侧变换器功率平衡谐振控制方法

Family Cites Families (7)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN103501149B (zh) * 2013-10-13 2016-06-01 中国船舶重工集团公司第七一二研究所 一种多相感应电机指定次谐波电流抑制方法
CN104466966B (zh) * 2014-12-24 2016-11-09 安徽一天电能质量技术有限公司 一种多同步旋转坐标系apf的分次谐波补偿的计算方法
CN104852661B (zh) * 2015-04-29 2017-09-26 同济大学 基于坐标变换谐波补偿的永磁同步电机转矩脉动抑制方法
CN106532705B (zh) * 2015-12-31 2021-03-19 安徽一天电能质量技术有限公司 多同步旋转坐标系下的三相四线制apf计算方法
CN107834558B (zh) * 2017-10-25 2021-07-13 南京邮电大学 一种用于改善电能质量的混合补偿方法
CN107959289A (zh) * 2017-11-30 2018-04-24 华夏天信（北京）智能低碳技术研究院有限公司 一种有源电力滤波器改进型指定次谐波电流补偿控制方法
CN109687460A (zh) * 2018-12-12 2019-04-26 广东电网有限责任公司 一种基于改进pi+重复控制的光伏逆变器谐波抑制方法

Patent Citations (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN101697420A (zh) * 2009-10-23 2010-04-21 湖南大学 一种微网逆变系统及适用于该微网逆变系统的电能质量控制方法
KR20130021134A (ko) * 2011-08-22 2013-03-05 엘에스산전 주식회사 인버터의 전류 제어 장치
CN102664413A (zh) * 2012-05-14 2012-09-12 重庆大学 抑制风电并网用全功率变流器谐波电流控制方法及控制器
CN103199720A (zh) * 2013-04-17 2013-07-10 湖南大学 一种三相功率变流器的综合控制方法
CN103595278A (zh) * 2013-11-18 2014-02-19 河南师范大学 太阳能发电系统网侧变换器功率平衡谐振控制方法

Cited By (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US11901734B2 (en) 2021-11-30 2024-02-13 Vestas Wind Systems A/S Grid side inverter system arranged for controlling current injection when a phase locked loop controller is misaligned

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