WO2020012802A1 - Converter device, control signal specifying method and program - Google Patents

Converter device, control signal specifying method and program Download PDF

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Publication number
WO2020012802A1
WO2020012802A1 PCT/JP2019/021030 JP2019021030W WO2020012802A1 WO 2020012802 A1 WO2020012802 A1 WO 2020012802A1 JP 2019021030 W JP2019021030 W JP 2019021030W WO 2020012802 A1 WO2020012802 A1 WO 2020012802A1
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Prior art keywords
input current
period
current
current value
control signal
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PCT/JP2019/021030
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French (fr)
Japanese (ja)
Inventor
貴政 渡辺
真一 小宮
清水　健志
角藤　清隆
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三菱重工サーマルシステムズ株式会社
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Publication of WO2020012802A1 publication Critical patent/WO2020012802A1/en

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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/02—Conversion of ac power input into dc power output without possibility of reversal
    • H02M7/04—Conversion of ac power input into dc power output without possibility of reversal by static converters
    • H02M7/12—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/02—Conversion of ac power input into dc power output without possibility of reversal
    • H02M7/04—Conversion of ac power input into dc power output without possibility of reversal by static converters
    • H02M7/12—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/21—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal

Definitions

  • the present invention relates to a converter device, a control signal specifying method, and a program.
  • the converter device is a device that converts AC power into DC power.
  • the converter device is required to improve conversion efficiency when converting AC power to DC power.
  • Patent Literature 1 discloses, as a related technique, a technique relating to synchronous rectification control for improving efficiency by turning on a MOS transistor even during a part of a period during which an input current of a converter device flows.
  • the object of the present invention is to provide a converter device, a control signal specifying method, and a program that can solve the above-mentioned problems.
  • the converter device has an input current acquisition unit that acquires a current value of an input current input from an AC power supply, and whether the current value of the input current is equal to or less than a predetermined current value
  • An input current determination unit that determines whether or not, when the input current determination unit determines that the current value of the input current is equal to or less than a predetermined current value, for a half cycle of the AC voltage output from the AC power supply,
  • a first period specifying unit that specifies a first period that is a certain period in which the input current of the current value is expected to flow, and a control that specifies a control signal that turns on the switching element based on the first period
  • a signal specifying unit specifies a control signal that turns on the switching element based on the first period
  • the control signal specifying unit may specify a control signal for turning on a switching element based on the first period or the third period.
  • the third period may be within the half cycle.
  • the converter device according to any one of the first to third aspects has two switching elements, and rectifies the power output from the AC power supply. And a control signal output unit that outputs the control signal to one of the two switching elements in the half cycle in which the control signal is applied.
  • the current value of the input current is less than a half cycle before the control signal is applied.
  • the current value of the input current in a half cycle may be used.
  • the current value of the input current is a current value of the input current in a half cycle immediately before a half cycle to which the control signal is applied. You may.
  • the current value of the input current is the current value of the input current in a plurality of past half cycles. May be the average value.
  • the converter device includes a zero-crossing detector that detects a zero-crossing point of the AC voltage, and a converter based on the zero-crossing point.
  • a reference specifying unit that specifies a reference timing of the half cycle.
  • the converter device according to any one of the first to eighth aspects further comprises an input current that specifies a current value of the input current based on a physical quantity related to the input current.
  • An input current obtaining unit configured to obtain the current value specified by the input current specifying unit.
  • a control signal specifying method includes obtaining a current value of an input current input from an AC power supply, and determining whether the current value of the input current is equal to or less than a predetermined current value. And determining that the current value of the input current is equal to or less than a predetermined current value, it is expected that the input current of the current value flows for a half cycle of the AC voltage output from the AC power supply. Specifying a first period, which is a predetermined period, and specifying a control signal for turning on the switching element based on the first period.
  • the program obtains a current value of an input current input from an AC power supply, and determines whether the current value of the input current is equal to or less than a predetermined current value. And determining that the current value of the input current is equal to or less than a predetermined current value, it is expected that the input current of the current value flows for a half cycle of the AC voltage output from the AC power supply. Specifying a first period, which is a predetermined period, and specifying a control signal for turning on the switching element based on the first period.
  • the control signal specifying method, and the program according to the embodiment of the present invention when performing synchronous rectification control in the converter device, efficiency can be improved regardless of the magnitude of the input current of the converter device.
  • FIG. 1 is a diagram illustrating a configuration of a motor drive device according to an embodiment of the present invention.
  • FIG. 3 is a diagram illustrating an example of a power supply voltage, an input current, and a control signal according to an embodiment of the present invention.
  • FIG. 3 is a diagram illustrating a configuration of a converter control unit according to an embodiment of the present invention.
  • FIG. 4 is a diagram for explaining a period during which a switching element is turned on in one embodiment of the present invention.
  • FIG. 3 is a diagram illustrating an example of a configuration of a control signal generation unit according to an embodiment of the present invention.
  • FIG. 4 is a diagram illustrating a processing flow of a converter control unit according to an embodiment of the present invention.
  • FIG. 9 is a diagram illustrating an example of a power supply voltage, an input current, and a control signal according to another embodiment of the present invention.
  • FIG. 2 is a schematic block diagram illustrating a configuration of a computer according to at least one embodiment.
  • FIG. 1 is a diagram showing a configuration of a motor drive device 1 according to one embodiment of the present invention.
  • the motor drive device 1 includes a converter device 2 and an inverter device 3, as shown in FIG.
  • a first terminal of converter device 2 is connected to a first terminal of AC power supply 4.
  • a second terminal of converter device 2 is connected to a second terminal of AC power supply 4.
  • the third terminal of converter device 2 is connected to the first terminal of inverter device 3.
  • the fourth terminal of converter device 2 is connected to the second terminal of inverter device 3.
  • the third terminal of the inverter device 3 is connected to the first terminal of the motor 5.
  • the fourth terminal of the inverter device 3 is connected to the second terminal of the motor 5.
  • the fifth terminal of the inverter device 3 is connected to the third terminal of the motor 5.
  • the motor driving device 1 is a device that converts AC power from an AC power supply 4 into DC power by a converter device 2, converts the DC power into three-phase AC power by an inverter device 3, and outputs the three-phase AC power to a motor 5.
  • the AC power supply 4 supplies single-phase AC power to the converter device 2.
  • the AC power supply 4 supplies, for example, a voltage described as a power supply voltage in FIG. 2 and a current described as an input current in FIG.
  • the motor 5 rotates according to the three-phase AC power supplied from the inverter device 3.
  • the motor 5 is, for example, a compressor motor used in an air conditioner.
  • the converter device 2 includes a rectifier circuit 21, an input current identification unit 22, a zero-cross detection unit 23, and a converter control unit 24, as shown in FIG.
  • the rectifier circuit 21 includes a bridge circuit 200, a reactor 211, and a capacitor 216, as shown in FIG.
  • the bridge circuit 200 includes diodes 212a and 213a, capacitors 212b and 213b, resistors 212c and 213c, and switching elements 214 and 215.
  • Converter device 2 performs switching element 214 or 215 during a certain first period including at least a part of a period in which the input current is expected to flow when the input current supplied from AC power supply 4 is equal to or less than a predetermined current value.
  • Converter device 2 outputs the DC power to inverter device 3.
  • the first terminal of the reactor 211 is connected to the anode of the diode 212a, the first terminal of the resistor 212c, and the first terminal of the switching element 214, respectively.
  • the cathode of the diode 212a is connected to the first terminal of the capacitor 212b, the cathode of the diode 213a, the first terminal of the capacitor 213b, and the first terminal of the capacitor 216, respectively.
  • a second terminal of the capacitor 212b is connected to a second terminal of the resistor 213c.
  • the anode of the diode 213a is connected to the first terminal of the resistor 213c and the first terminal of the switching element 215, respectively.
  • the second terminal of the switching element 214 is connected to the second terminal of the switching element 215 and the second terminal of the capacitor 216, respectively.
  • the second terminal of the reactor 211 is connected to the first terminal of the rectifier circuit 21.
  • the anode of the diode 213a is connected to the second terminal of the rectifier circuit 21.
  • the cathode of the diode 212a is connected to the third terminal of the rectifier circuit 21.
  • the second terminal of the switching element 214 is connected to the fourth terminal of the rectifier circuit 21.
  • the third terminal of the switching element 214 is connected to the fifth terminal of the rectifier circuit 21.
  • the third terminal of the switching element 215 is connected to the sixth terminal of the rectifier circuit 21.
  • a circuit including the diode 212a, the capacitor 212b, and the resistor 212c is referred to as a first circuit 212.
  • a circuit including the diode 213a, the capacitor 213b, and the resistor 213c is referred to as a second circuit 213.
  • the first terminal of the rectifier circuit 21 is connected to the first terminal of the input current specifying unit 22 and the first terminal of the zero-cross detecting unit 23, respectively.
  • a second terminal of the rectifier circuit 21 is connected to a second terminal of the zero-cross detector 23.
  • the fifth terminal of the rectifier circuit 21 is connected to the first terminal of the converter control unit 24.
  • a sixth terminal of the rectifier circuit 21 is connected to a second terminal of the converter control unit 24.
  • a second terminal of the input current specifying unit 22 is connected to a third terminal of the converter control unit 24.
  • a third terminal of the zero-crossing detector 23 is connected to a fourth terminal of the converter controller 24.
  • the first terminal of the rectifier circuit 21 is connected to the first terminal of the converter device 2.
  • the second terminal of the rectifier circuit 21 is connected to the second terminal of the converter device 2.
  • the third terminal of the rectifier circuit 21 is connected to the third terminal of the converter device 2.
  • the fourth terminal of the rectifier circuit 21 is connected to the fourth terminal of the converter device 2.
  • Reactor 211 is a reactor provided to realize a boost operation.
  • the bridge circuit 200 rectifies AC power to DC power based on the control of the converter control unit 24.
  • Each of the switching elements 214 and 215 is, for example, a super-junction MOSFET (Metal-Oxide Semiconductor Field-Effect Transistor), an IGBT (Insulated Gate Bipolar Transistor), or the like.
  • FIG. 1 shows an example in which each of the switching elements 214 and 215 is a super junction MOSFET.
  • the first terminal is a drain
  • the second terminal is a source
  • the third terminal is a gate. As shown in FIG.
  • the switching element 214 has a transistor part 214a and a parasitic diode 214b between the source and the drain. Further, as shown in FIG. 1, the switching element 215 has a transistor portion 215a and a parasitic diode 215b between the source and the drain.
  • the capacitor 216 is a capacitor for smoothing the DC power output from the bridge circuit 200. By the capacitor 216, a DC voltage with a small fluctuation in the voltage value is supplied from the converter device 2 to the inverter device 3.
  • the capacitor 216 is, for example, an electrolytic capacitor.
  • the input current specifying unit 22 specifies the current value of the input current supplied from the AC power supply 4 to the converter device 2 for each cycle sufficiently shorter than the cycle of the AC voltage output from the AC power supply 4.
  • the input current specifying unit 22 includes a current sensor provided between the AC power supply 4 and the converter device 2, and specifies a current value (an example of a physical quantity related to the input current) of the input current read by the current sensor. I do.
  • the input current specifying unit 22 includes a shunt resistor provided between the AC power supply 4 and the converter device 2, and the potential difference between both ends of the shunt resistor (an example of a physical quantity related to the input current) is represented by a resistance value.
  • the current value may be specified by division.
  • the input current specifying unit 22 gives the current value of the detected input current to the converter control unit 24.
  • the zero-crossing detector 23 detects the zero-crossing point of the voltage output from the AC power supply 4.
  • the zero-cross point indicates a timing at which the voltage output from the AC power supply 4 crosses zero volts, and the timing becomes a reference timing in the processing of the motor driving device 1.
  • the zero-cross detection unit 23 generates a zero-cross signal including information on a zero-cross point.
  • the zero-cross detector 23 outputs a zero-cross signal to the converter controller 24.
  • Converter control unit 24 receives input current information from input current specifying unit 22.
  • the converter control unit 24 controls a period during which each of the switching elements 214 and 215 is turned on and a period during which the switching elements 214 and 215 are turned off.
  • the converter control unit 24 does not turn on both the switching elements 214 and 215 at the same time, turns off both the switching elements 214 and 215, or turns off the switching element 214 and turns on the switching element 215.
  • the converter control unit 24 does not turn on both of the switching elements 214 and 215 at the same time. Are turned off, or the switching element 214 is turned on and the switching element 215 is turned off.
  • each of the switching elements 214 and 215 is a super junction MOSFET, the potential of the first terminal of the AC power supply 4 is higher than the potential of the second terminal, and the converter control unit 24 turns off both the switching elements 214 and 215.
  • condition 1 current flows from the first terminal of the AC power supply 4 to the reactor 211, the first circuit 212, the capacitor 216, the parasitic diode 215b, and the second terminal of the AC power supply 4, and the capacitor 216 is charged. Is done.
  • each of the switching elements 214 and 215 is a super junction MOSFET, the potential of the first terminal of the AC power supply 4 is higher than the potential of the second terminal, and the switching element 214 is off and the switching element 215 is on.
  • condition 2 current flows from the first terminal of the AC power supply 4 to the reactor 211, the first circuit 212, the capacitor 216, the transistor unit 215a, and the second terminal of the AC power supply 4, and the capacitor 216 is charged. Is done.
  • condition 2 the voltage between the source and the drain of the transistor portion 215a is almost zero, whereas in the case of the condition 1, a voltage drop of a forward voltage occurs in the parasitic diode 215b. Therefore, when supplying current to converter device 2 from the first terminal of AC power supply 4, converter control unit 24 sets switching element 215 to a lower state than switching switching element 215 to an off state and flowing current to parasitic diode 215 b.
  • the efficiency can be improved by the amount of the forward voltage generated by the parasitic diode 215b.
  • each of the switching elements 214 and 215 is a super junction MOSFET, the potential of the first terminal of the AC power supply 4 is lower than the potential of the second terminal, and the converter control unit 24 turns off both the switching elements 214 and 215.
  • condition 3 current flows from the second terminal of the AC power supply 4 to the second circuit 213, the capacitor 216, the parasitic diode 214b, the reactor 211, and the first terminal of the AC power supply 4, and the capacitor 216 is charged. Is done.
  • the switching elements 214 and 215 are each a super junction MOSFET, the potential of the first terminal of the AC power supply 4 is lower than the potential of the second terminal, and the switching element 214 is on and the switching element 215 is off.
  • the converter control unit 24 turns off the switching element 215 to flow the current to the parasitic diode 215b when supplying the current from the first terminal of the AC power supply 4 to the converter device 2. Rather, it is a control unit that improves the efficiency by turning on the switching element 215 and causing a current to flow through the transistor unit 215a. Further, the converter control unit 24 according to the embodiment of the present invention turns off the switching element 214 to flow the current to the parasitic diode 214b when supplying the current to the converter device 2 from the second terminal of the AC power supply 4. Rather, it is a control unit that improves efficiency by turning on the switching element 214 and flowing current to the transistor unit 214a.
  • the converter control unit 24 includes a reference specifying unit 241, an input current acquisition unit 242, a control signal generation unit 243, and a storage unit 244, as shown in FIG.
  • the reference specifying unit 241 specifies a reference timing.
  • the reference specifying unit 241 acquires a zero cross signal from the zero cross detection unit 23.
  • the reference specifying unit 241 specifies a reference timing indicated by the acquired zero-cross signal.
  • the reference specifying unit 241 outputs the specified reference timing to the control signal generation unit 243.
  • the input current obtaining unit 242 detects the current value of the input current from the input current specifying unit 22 (that is, the current value of the input current input from the AC power supply 4 to the converter device 2) and detects the input current of the input current specifying unit 22. Acquire at each timing.
  • the input current acquisition unit 242 outputs the acquired current value to the control signal generation unit 243.
  • the control signal generation unit 243 acquires the reference timing from the reference identification unit 241. Further, the control signal generation unit 243 acquires the current value of the input current from the input current acquisition unit 242. The control signal generation unit 243 sets the phase at the reference timing acquired from the reference identification unit 241 as the reference 0 degree of the phase ⁇ . Then, the control signal generator 243 calculates the effective value of the input current based on the reference of the phase ⁇ . For example, the control signal generation unit 243 calculates the effective value of the input current by averaging the integrated value of the current values of the input current acquired from the input current acquisition unit 242 according to the phase of the phase ⁇ from the reference. .
  • the input current specifying unit 22 includes a current sensor (for example, a current transformer)
  • the input current is full-wave rectified by the bridge circuit 200 via the current transformer, and charges the capacitor 216.
  • the control signal generator 243 reads the voltage level in a state smoothed by the capacitor 216. Then, the control signal generator 243 may calculate the effective value of the input current by converting the read voltage value into a current value that is associated with the voltage value on a one-to-one basis.
  • a conversion table indicating the correspondence between the voltage value and the current value is created in advance and stored in the storage unit 244, and the control signal generation unit 243 reads the conversion table. Then, the read voltage value may be converted into the effective value of the current.
  • the control signal generator 243 compares the calculated effective value of the input current with the effective value of the input current in the data table TBL1.
  • the control signal generation unit 243 specifies the effective value of the input current closest to the calculated effective value of the input current in the data table TBL1 based on the comparison result.
  • the control signal generation unit 243 specifies the adjustment amount of the phase associated with the specified input current in the data table TBL1.
  • the control signal generation unit 243 adjusts the phase by the amount of phase adjustment specified based on the phase of the power supply voltage (that is, based on the zero-cross point). Then, the control signal generation unit 243 outputs the control signal whose phase has been adjusted to each of the switching elements 214 and 215.
  • the control signal generation unit 243 switches the switching element during a certain first period including at least a part of a period in which the input current is expected to flow. A signal for turning on the switch is specified.
  • the control signal generation unit 243 causes the switching element (the switching element 214 or 215) that is controlled to be in the off state from the phase 0 degree to 180 degrees to the phase 0 level. (The timing when the input current starts to flow in the second period is an example of the first timing, and the input current flows in the second period).
  • the signal to be turned on is specified in a third period which is the sum of a period in which the period disappears is an example of a second timing) and a period extended to at least one of immediately before and after the period.
  • the control signal generation unit 243 may set a current threshold value larger than the noise (for example, the current threshold value shown in FIG. 4) so that the noise when the current value of the input current is zero is not erroneously detected as the input current. (Threshold value 3 amps) is set in advance. Each time the control signal generation unit 243 obtains the current value of the input current from the input current identification unit 22, it compares the obtained current value of the input current with the current threshold value.
  • the control signal generation unit 243 specifies a period in which the current value of the input current exceeds the current threshold (for example, a period ⁇ 1 shown in FIG. 4) based on the comparison result. For each value of the period ⁇ 1 during which the current value of the input current exceeds the current threshold value (the phase difference between the start phase and the end phase of the period ⁇ 1), the period from when the input current starts flowing until when the input current ends (for example, the storage unit 244 stores in advance a period ⁇ 2 shown in FIG. 4), that is, ⁇ 1 and ⁇ 2, which are phase correction values for specifying the second period, in association with each other.
  • the correction value ⁇ 1 is a correction value for extending the period immediately before.
  • the correction value ⁇ 2 is a correction value for extending the period immediately after.
  • the control signal generation unit 243 determines that there is a period ⁇ 1 in which the current value of the input current exceeds the current threshold based on the comparison result, the control unit 243 extends the period ⁇ 1 by ⁇ 1 immediately before and ⁇ 2 by immediately after.
  • the period ⁇ 2 is a period in which ⁇ is extended both immediately before and immediately after the period ⁇ 2 by at least one of ⁇ and the period ⁇ 2.
  • the three periods are specified as periods during which the switching elements are turned on.
  • control signal generation unit 243 determines that there is no period ⁇ 1 in which the current value of the input current exceeds the current threshold based on the comparison result, the control signal generation unit 243 performs a certain first period (see, for example, FIG. The period ⁇ 3) is specified as a period during which the switching element is turned on. Then, the control signal generation unit 243 specifies a signal for turning on the switching element during the specified period. The control signal generation unit 243 delays the phase of the specified signal by 180 degrees, and uses the switching element (switching element 214) as a first control signal that is a control signal of the next half cycle (an example of a half cycle in which the control signal is applied). Or 215).
  • control signal generation unit 243 outputs a second control signal for turning the switching element, which has been controlled to the on state during the phase of 0 to 180 degrees, to the off state for the next half cycle from the phase of 0 to 180 degrees. Identify between degrees. Then, the control signal generation unit 243 outputs the second control signal specified in the next half cycle to a switching element (switching element 215 or 214) different from the switching element that outputs the first control signal. Note that the extension to the third period including the second period in which the input current is detected is limited at the beginning of the half period. Further, the extension to the third period including the second period in which the input current is detected is limited at the end of the half period.
  • control signal generation unit 243 performs control to turn on the switching element 215 during the phase from 0 degrees to 180 degrees, and the input current identification unit 22 detects the input current shown in FIG.
  • the unit 243 specifies a signal whose period has been extended by the phase ⁇ before and after the period in which the input current shown in FIG. 2 has a positive current value.
  • the control signal generator 243 adds a phase of 180 degrees to the phase of the generated signal. That is, the control signal generation unit 243 sets the specified signal as a control signal for the switching element 214 in the next half cycle (a period from a phase of 180 degrees to a phase of 360 degrees).
  • the control signal generator 243 outputs the control signal to the switching element 214 during a period from 180 degrees to 360 degrees in phase.
  • the control signal generation unit 243 specifies a control signal that turns off the switching element 215 during a period from 180 degrees to 360 degrees in phase.
  • the control signal generation unit 243 outputs the specified control signal to the switching element 215 during a period from 180 degrees to 360 degrees in phase. Thereafter, the control signal generation unit 243 performs the same process as the above process also during the period in which the input current shown in FIG. 2 is a negative current value, so that the next half cycle is performed based on the third period every half cycle.
  • the control signal of the cycle is specified, and the specified control signal is output to each of the switching elements 214 and 215.
  • the control signal generation unit 243 includes an example of an input current determination unit, an example of a first period identification unit, an example of a second period identification unit, an example of a third period identification unit, an example of a control signal identification unit, and an example of a control signal output unit. This is an example. That is, as shown in FIG. 5, the control signal generation unit 243 includes an input current determination unit, a first period identification unit, a second period identification unit, a third period identification unit, a control signal identification unit, and a control signal output unit. .
  • the input current determination unit determines whether the current value of the input current is equal to or less than a predetermined current value.
  • the first period identification unit determines the input current of the current value for a half cycle of the AC voltage output from the AC power supply 4 Is specified as a first period, which is a certain period in which is expected to flow.
  • the control signal specifying unit specifies a control signal for turning on the switching element based on the first period.
  • the second period identification unit determines a half cycle of the AC voltage output from the AC power supply 4 based on the current value of the input current.
  • the third period specifying unit specifies a third period that is a sum of the extended period when extending to at least one of immediately before the first timing or immediately after the second timing and the second period.
  • the control signal output unit outputs the control signal to one of the two switching elements in a half cycle of the AC voltage to which the control signal is applied.
  • the control signal specifying section may specify a control signal for turning on the switching element based on the first period or the third period.
  • the storage unit 244 stores various information necessary for the processing performed by the converter control unit 24.
  • the storage unit 244 stores, for each value of the period ⁇ 1 in which the current value of the input current exceeds the current threshold, a period from the start of the input current to the end of the flow (for example, a period ⁇ 2 illustrated in FIG. 4), That is, ⁇ 1 and ⁇ 2, which are the phase correction values for specifying the second period, are stored in advance in association with each other.
  • the inverter device 3 includes an IPM (Intelligent Power Module) 31 and an inverter control unit 32.
  • the IPM 31 generates three-phase AC power from DC power based on control by the inverter control unit 32.
  • the IPM 31 supplies the generated three-phase AC power to the motor.
  • the IPM 31 is, for example, a bridge circuit including six switching elements.
  • the inverter control unit 32 controls the IPM 31. Specifically, inverter control unit 32 causes IPM 31 to generate three-phase AC power from DC power. For example, when the IPM 31 is a bridge circuit including six switching elements, the inverter control unit 32 switches between a period in which each of the six switching elements is turned on and a period in which the six switching elements are turned off. , The IPM 31 generates three-phase AC power from DC power.
  • the input current specifying unit 22 detects an input current supplied from the AC power supply 4 to the converter device 2 at every cycle that is sufficiently shorter than the cycle of the AC voltage output from the AC power supply 4.
  • the input current specifying unit 22 gives the current value of the detected input current to the converter control unit 24.
  • the zero-crossing detector 23 detects the zero-crossing point of the voltage output from the AC power supply 4.
  • the zero-cross detection unit 23 generates a zero-cross signal including information on a zero-cross point.
  • the zero-cross detector 23 outputs a zero-cross signal to the converter controller 24.
  • the reference specifying unit 241 acquires a zero-cross signal from the zero-cross detection unit 23 (Step S1).
  • the reference specifying unit 241 specifies a reference timing indicated by the acquired zero-cross signal (Step S2).
  • the reference specifying unit 241 outputs the specified reference timing to the control signal generation unit 243.
  • the input current acquisition unit 242 acquires the current value of the input current from the input current identification unit 22 for each input current detection timing of the input current identification unit 22 (step S3).
  • the input current acquisition unit 242 outputs the acquired current value to the control signal generation unit 243.
  • the control signal generation unit 243 acquires the reference timing from the reference identification unit 241. Further, the control signal generation unit 243 acquires the current value of the input current from the input current acquisition unit 242. The control signal generation unit 243 sets the phase at the reference timing acquired from the reference identification unit 241 as the reference 0 degree of the phase ⁇ (Step S4). The control signal generation unit 243 turns on the switching element (the switching element 214 or 215) that is controlled to be in the off state from the phase 0 to 180 degrees in the third period from the phase 0 to 180 degrees. The first control signal to be set is specified (Step S5).
  • the control signal generation unit 243 sets a current threshold value larger than the noise (for example, as shown in FIG. 4) so that the noise when the current value of the input current is zero is not erroneously detected as the input current.
  • the current threshold value shown is 3 amps).
  • the control signal generation unit 243 sets the current value of the acquired input current every time the current value of the input current is acquired from the input current identification unit 22 in each half cycle, with the half cycle as one period based on the phase 0 degree. And its current threshold value (Step S5a).
  • the control signal generator 243 determines whether the current value of the input current exceeds the current threshold (Step S5b).
  • step S5c determines whether the target half cycle has ended.
  • the control signal generation unit 243 returns to the process of step S5a.
  • the control signal generation unit 243 sets the switching element to the ON state for a certain first period (for example, period ⁇ 3 shown in FIG. 4). The first control signal for turning on the switching element during the first period is specified (step S5d).
  • control signal generating section 243 When determining that the current value of the input current has exceeded the current threshold value (YES in step S5b), control signal generating section 243 specifies the phase at that time as the phase indicating the start of period ⁇ 1 (step S5e). ). The control signal generator 243 compares the current value of the next input current with the current threshold (step S5f). The control signal generation unit 243 determines whether or not the current value of the input current is equal to or smaller than the current threshold in the comparison result (Step S5g). When the control signal generation unit 243 determines that the current value of the input current is not equal to or smaller than the first current threshold value (NO in step S5g), the process returns to step S5f.
  • control signal generation section 243 specifies the phase at that time as the phase indicating the end of period ⁇ 1 (step S5g). S5h). That is, the control signal generation unit 243 specifies the value of the period ⁇ 1.
  • the control signal generation unit 243 specifies the correction values ⁇ 1 and ⁇ 2 of the phase associated with the value of the specified period ⁇ 1 in the storage unit 244 (Step S5i).
  • the control signal generation unit 243 extends the period ⁇ 1 by the phase ⁇ 1 immediately before and by the phase ⁇ 2 immediately after. That is, the control signal generation unit 243 specifies the period ⁇ 2 (Step S5j).
  • the control signal generator 243 extends the period ⁇ 2 by the phase ⁇ immediately before and immediately after (step S5k), sets the extended period as a third period in which the switching element is turned on, and sets the switching element in the third period.
  • the first control signal to be turned on is specified (step S51).
  • the control signal generation unit 243 delays the phase of the first control signal specified by the processing of step S5d or step S51 by 180 degrees, and switches the first control signal to the switching element (switching element 214 or 215) in the next half cycle. (Step S6). Further, the control signal generation unit 243 converts the second control signal that turns the switching element, which has been controlled to the on state during the phase of 0 to 180 degrees, to the off state for the next half cycle, from the phase of 0 to 180 degrees (Step S7). The control signal generator 243 delays the phase of the specified second control signal by 180 degrees, and outputs the second control signal to the switching element (switching element 215 or 214) during the next half cycle (step S8). ). The control signal generator 243 returns the process to step S1.
  • input current obtaining section 242 obtains a current value of an input current input from AC power supply 4.
  • the control signal generation unit 243 determines whether the current value of the input current is equal to or less than a predetermined current value.
  • the control signal generation unit 243 determines the current value for a half cycle of the AC voltage output from the AC power supply 4. A first period, which is a fixed period in which the input current having a value is expected to flow, is specified.
  • the control signal generating unit 243 (an example of a control signal specifying unit) specifies a control signal for turning on the switching element based on the first period. By doing so, the converter device 2 of the motor drive device 1 can perform synchronous rectification even during a period in which the input current is a relatively small current value equal to or less than the predetermined current value.
  • the predetermined current value can be set to an arbitrary current value as long as noise is not erroneously detected.
  • the converter device 2 reliably improves the efficiency by the voltage drop due to the forward voltage of the diode as compared with a rectifier circuit that does not perform synchronous rectification. Can be. Therefore, when synchronous rectification control is performed in converter device 2, regardless of the magnitude of the input current of converter device 2, efficiency can be improved even when the magnitude of the input current is relatively small.
  • the control signal generator 243 controls the switching element 214 or 215 to be turned off every half cycle from the reference timing.
  • the control signal generation unit 243 instead of controlling the switching element 214 or 215 to be in the OFF state every half cycle from the reference timing, the control signal generation unit 243 outputs the input current from the AC power supply 4.
  • a PAM (Pulse Amplitude Modulation) control signal as shown in FIG. 7 is used so as to approach the cycle of the AC voltage and approximate a sine wave (that is, to reduce the harmonic distortion to a desired distortion rate or less).
  • the PAM control may be performed.
  • the control signal generation unit 243 may use a PWM (Pulse Width Modulation) generation technique of generating a PAM control signal according to the input current.
  • PWM Pulse Width Modulation
  • the input current changes from the waveform shown by the solid line in FIG. 7 to, for example, the waveform shown by the broken line in FIG.
  • the distortion rate is improved. Note that the extension of the input current to the third period immediately before the detected second period is limited to the beginning of the half period. The extension of the input current to the third period immediately after the detected second period is limited to the end of the half cycle.
  • the control signal generation unit 243 switches from the second period in which the input current is detected to the third cycle. Do not extend the period.
  • the bridge circuit 200 has been described as including the first circuit 212 including the diode 212a and the second circuit 213 including the diode 213a.
  • the first circuit 212 and the second circuit 213 may be switching elements.
  • the bridge circuit 200 according to the embodiment of the present invention includes the first circuit 212 and the second circuit 213 which are switching elements because diodes, resistors, and capacitors are generally cheaper than switching elements. An effect that it can be realized at lower cost than in another embodiment can be expected.
  • control signal generation unit 243 has been described as specifying the control signal of the next half cycle based on the input current in the immediately preceding half cycle.
  • the control signal generation unit 243 replaces the immediately preceding half cycle with a half cycle before the immediately preceding half cycle (however, there is no sharp change in the input current, that is, the control signal
  • the control signal may be specified based on the input current in an arbitrary half cycle in the past period that was the same as the input current when applying the signal.
  • control signal generator 243 may specify the control signal based on the average current value of the input current in a plurality of past half cycles.
  • the storage unit and other storage devices in each embodiment of the present invention may be provided anywhere as long as appropriate information is transmitted and received.
  • a plurality of storage units and other storage devices may exist in a range where appropriate information is transmitted and received, and may store data in a distributed manner.
  • the order of the processes may be changed within a range where an appropriate process is performed.
  • FIG. 8 is a schematic block diagram illustrating a configuration of a computer according to at least one embodiment.
  • the computer 50 includes a CPU 60, a main memory 70, a storage 80, and an interface 90.
  • each of the above-described converter control unit 24, inverter control unit 32, and other control devices is implemented in a computer 50.
  • each processing unit described above is stored in the storage 80 in the form of a program.
  • the CPU 60 reads the program from the storage 80, expands the program in the main memory 70, and executes the above-described processing according to the program. Further, the CPU 60 secures a storage area corresponding to each of the above-described storage units in the main memory 70 according to a program.
  • Examples of the storage 80 include a hard disk drive (HDD), a solid state drive (SSD), a magnetic disk, a magneto-optical disk, a CD-ROM (Compact Disc Read Only Memory), and a DVD-ROM (Digital Documentary Discrete Memory). And a semiconductor memory.
  • the storage 80 may be an internal medium directly connected to the bus of the computer 50, or may be an external medium connected to the computer 50 via the interface 90 or a communication line. When the program is distributed to the computer 50 via a communication line, the computer 50 that has received the program may load the program into the main memory 70 and execute the above-described processing.
  • storage 80 is a non-transitory tangible storage medium.
  • the program may implement a part of the functions described above. Further, the program may be a file that can realize the above-described functions in combination with a program already recorded in the computer system, that is, a so-called difference file (difference program).
  • difference file difference program
  • the control signal specifying method, and the program according to the embodiment of the present invention when performing synchronous rectification control in the converter device, efficiency can be improved regardless of the magnitude of the input current of the converter device.

Abstract

A converter device comprises: an input current acquisition unit that acquires a current value of an input current inputted from an AC power source; an input current determination unit that determines whether or not the current value of the input current is equal to or less than a predetermined current value; a first period specifying unit that, when the input current determination unit determines that the current value of the input current is equal to or less than a predetermined current value, specifies a first period, which is a constant period in which the input current of said current value is expected to flow, with respect to a half cycle of an AC voltage output from the AC power source; and a control signal specifying unit that specifies a control signal for turning on a switching element based on the first period.

Description

コンバータ装置、制御信号特定方法及びプログラムConverter device, control signal specifying method, and program
　本発明は、コンバータ装置、制御信号特定方法及びプログラムに関する。
　本願は、２０１８年７月１３日に日本に出願された特願２０１８－１３３１２５号について優先権を主張し、その内容をここに援用する。 The present invention relates to a converter device, a control signal specifying method, and a program.
This application claims the priority of Japanese Patent Application No. 2018-133125 filed on July 13, 2018, the contents of which are incorporated herein by reference.
　コンバータ装置は、交流電力を直流電力に変換する装置である。コンバータ装置では、交流電力を直流電力に変換するときの変換効率の向上が求められている。
　特許文献１には、関連する技術として、コンバータ装置の入力電流が流れている期間のごく一部においてもＭＯＳトランジスタをオン状態にして、効率を改善する同期整流制御に関する技術が記載されている。 The converter device is a device that converts AC power into DC power. The converter device is required to improve conversion efficiency when converting AC power to DC power.
Patent Literature 1 discloses, as a related technique, a technique relating to synchronous rectification control for improving efficiency by turning on a MOS transistor even during a part of a period during which an input current of a converter device flows.
特開２０１８－００７３２８号公報JP 2018-007328 A
　ところで、コンバータ装置において同期整流制御を行う場合、コンバータ装置の入力電流の大きさに関わらず（すなわち、入力電流が大きい場合であっても、比較的小さい場合であっても）、効率を向上させることのできる技術が求められる。 By the way, when synchronous rectification control is performed in the converter device, the efficiency is improved regardless of the magnitude of the input current of the converter device (that is, whether the input current is large or relatively small). Technology that can do it is required.
　本発明は、上記の課題を解決することのできるコンバータ装置、制御信号特定方法及びプログラムを提供することを目的としている。 The object of the present invention is to provide a converter device, a control signal specifying method, and a program that can solve the above-mentioned problems.
　本発明の第１の態様によれば、コンバータ装置は、交流電源から入力される入力電流の電流値を取得する入力電流取得部と、前記入力電流の電流値が所定の電流値以下であるか否かを判定する入力電流判定部と、前記入力電流判定部が前記入力電流の電流値が所定の電流値以下であると判定した場合、前記交流電源から出力される交流電圧の半周期について、当該電流値の入力電流が流れると予想した一定の期間である第１期間を特定する第１期間特定部と、前記第１期間に基づいて、スイッチング素子をオン状態にする制御信号を特定する制御信号特定部と、を備える。 According to the first aspect of the present invention, the converter device has an input current acquisition unit that acquires a current value of an input current input from an AC power supply, and whether the current value of the input current is equal to or less than a predetermined current value An input current determination unit that determines whether or not, when the input current determination unit determines that the current value of the input current is equal to or less than a predetermined current value, for a half cycle of the AC voltage output from the AC power supply, A first period specifying unit that specifies a first period that is a certain period in which the input current of the current value is expected to flow, and a control that specifies a control signal that turns on the switching element based on the first period A signal specifying unit.
　本発明の第２の態様によれば、第１の態様におけるコンバータ装置は、前記入力電流判定部が前記入力電流の電流値が所定の電流値を超えると判定した場合、前記入力電流の電流値に基づいて、前記交流電源から出力される交流電圧の半周期について、前記入力電流が流れ始める第１タイミングから流れなくなる第２タイミングまでの第２期間を特定する第２期間特定部と、前記第１タイミングの直前または前記第２タイミングの直後の少なくとも一方に延長したときの延長した期間と、前記第２期間との総和である第３期間を特定する第３期間特定部と、を備え、前記制御信号特定部は、前記第１期間または前記第３期間に基づいて、スイッチング素子をオン状態にする制御信号を特定するものであってもよい。 According to a second aspect of the present invention, in the converter device according to the first aspect, when the input current determination unit determines that the current value of the input current exceeds a predetermined current value, the current value of the input current A second period specifying unit that specifies a second period from a first timing at which the input current starts flowing to a second timing at which the input current stops flowing, for a half cycle of the AC voltage output from the AC power supply, based on A third period specifying unit that specifies a third period that is a sum of an extended period when extending to at least one of immediately before one timing or immediately after the second timing, and a third period that is a sum of the second period; The control signal specifying unit may specify a control signal for turning on a switching element based on the first period or the third period.
　本発明の第３の態様によれば、第２の態様におけるコンバータ装置において、前記第３期間は、前記半周期内にあってもよい。 According to a third aspect of the present invention, in the converter device according to the second aspect, the third period may be within the half cycle.
　本発明の第４の態様によれば、第１の態様から第３の態様の何れか１つにおけるコンバータ装置は、２つのスイッチング素子を有し、前記交流電源の出力する電力を整流するブリッジ回路と、前記制御信号を適用する前記半周期において、前記２つのスイッチング素子の一方へ前記制御信号を出力する制御信号出力部と、を備えるものであってもよい。 According to a fourth aspect of the present invention, the converter device according to any one of the first to third aspects has two switching elements, and rectifies the power output from the AC power supply. And a control signal output unit that outputs the control signal to one of the two switching elements in the half cycle in which the control signal is applied.
　本発明の第５の態様によれば、第１の態様から第４の態様の何れか１つにおけるコンバータ装置において、前記入力電流の電流値は、前記制御信号が適用される半周期より前の半周期における入力電流の電流値であってもよい。 According to a fifth aspect of the present invention, in the converter device according to any one of the first to fourth aspects, the current value of the input current is less than a half cycle before the control signal is applied. The current value of the input current in a half cycle may be used.
　本発明の第６の態様によれば、第５の態様におけるコンバータ装置において、前記入力電流の電流値は、前記制御信号が適用される半周期の直前の半周期における入力電流の電流値であってもよい。 According to a sixth aspect of the present invention, in the converter device according to the fifth aspect, the current value of the input current is a current value of the input current in a half cycle immediately before a half cycle to which the control signal is applied. You may.
　本発明の第７の態様によれば、第１の態様から第４の態様の何れか１つにおけるコンバータ装置において、前記入力電流の電流値は、過去の複数の半周期における入力電流の電流値の平均値であってもよい。 According to a seventh aspect of the present invention, in the converter device according to any one of the first to fourth aspects, the current value of the input current is the current value of the input current in a plurality of past half cycles. May be the average value.
　本発明の第８の態様によれば、第１の態様から第７の態様の何れか１つにおけるコンバータ装置は、前記交流電圧のゼロクロス点を検出するゼロクロス検出部と、前記ゼロクロス点に基づいて前記半周期の基準となるタイミングを特定する基準特定部と、を備えるものであってもよい。 According to an eighth aspect of the present invention, the converter device according to any one of the first to seventh aspects includes a zero-crossing detector that detects a zero-crossing point of the AC voltage, and a converter based on the zero-crossing point. A reference specifying unit that specifies a reference timing of the half cycle.
　本発明の第９の態様によれば、第１の態様から第８の態様の何れか１つにおけるコンバータ装置は、前記入力電流に係る物理量に基づいて前記入力電流の電流値を特定する入力電流特定部、を備え、前記入力電流取得部は、前記入力電流特定部が特定した前記電流値を取得するものであってもよい。 According to a ninth aspect of the present invention, the converter device according to any one of the first to eighth aspects further comprises an input current that specifies a current value of the input current based on a physical quantity related to the input current. An input current obtaining unit configured to obtain the current value specified by the input current specifying unit.
　本発明の第１０の態様によれば、制御信号特定方法は、交流電源から入力される入力電流の電流値を取得することと、前記入力電流の電流値が所定の電流値以下であるか否かを判定することと、前記入力電流の電流値が所定の電流値以下であると判定した場合、前記交流電源から出力される交流電圧の半周期について、当該電流値の入力電流が流れると予想した一定の期間である第１期間を特定することと、前記第１期間に基づいて、スイッチング素子をオン状態にする制御信号を特定することと、を含む。 According to a tenth aspect of the present invention, a control signal specifying method includes obtaining a current value of an input current input from an AC power supply, and determining whether the current value of the input current is equal to or less than a predetermined current value. And determining that the current value of the input current is equal to or less than a predetermined current value, it is expected that the input current of the current value flows for a half cycle of the AC voltage output from the AC power supply. Specifying a first period, which is a predetermined period, and specifying a control signal for turning on the switching element based on the first period.
　本発明の第１１の態様によれば、プログラムは、コンピュータに、交流電源から入力される入力電流の電流値を取得することと、前記入力電流の電流値が所定の電流値以下であるか否かを判定することと、前記入力電流の電流値が所定の電流値以下であると判定した場合、前記交流電源から出力される交流電圧の半周期について、当該電流値の入力電流が流れると予想した一定の期間である第１期間を特定することと、前記第１期間に基づいて、スイッチング素子をオン状態にする制御信号を特定することと、を実行させる。 According to an eleventh aspect of the present invention, the program obtains a current value of an input current input from an AC power supply, and determines whether the current value of the input current is equal to or less than a predetermined current value. And determining that the current value of the input current is equal to or less than a predetermined current value, it is expected that the input current of the current value flows for a half cycle of the AC voltage output from the AC power supply. Specifying a first period, which is a predetermined period, and specifying a control signal for turning on the switching element based on the first period.
　本発明の実施形態によるコンバータ装置、制御信号特定方法及びプログラムによれば、コンバータ装置において同期整流制御を行う場合、コンバータ装置の入力電流の大きさに関わらず効率を向上させることができる。 According to the converter device, the control signal specifying method, and the program according to the embodiment of the present invention, when performing synchronous rectification control in the converter device, efficiency can be improved regardless of the magnitude of the input current of the converter device.
本発明の一実施形態によるモータ駆動装置の構成を示す図である。FIG. 1 is a diagram illustrating a configuration of a motor drive device according to an embodiment of the present invention. 本発明の一実施形態における電源電圧、入力電流、制御信号の一例を示す図である。FIG. 3 is a diagram illustrating an example of a power supply voltage, an input current, and a control signal according to an embodiment of the present invention. 本発明の一実施形態によるコンバータ制御部の構成を示す図である。FIG. 3 is a diagram illustrating a configuration of a converter control unit according to an embodiment of the present invention. 本発明の一実施形態におけるスイッチング素子をオン状態にする期間を説明するための図である。FIG. 4 is a diagram for explaining a period during which a switching element is turned on in one embodiment of the present invention. 本発明の一実施形態による制御信号生成部の構成の一例を示す図である。FIG. 3 is a diagram illustrating an example of a configuration of a control signal generation unit according to an embodiment of the present invention. 本発明の一実施形態によるコンバータ制御部の処理フローを示す図である。FIG. 4 is a diagram illustrating a processing flow of a converter control unit according to an embodiment of the present invention. 本発明の別の実施形態における電源電圧、入力電流、制御信号の一例を示す図である。FIG. 9 is a diagram illustrating an example of a power supply voltage, an input current, and a control signal according to another embodiment of the present invention. 少なくとも１つの実施形態に係るコンピュータの構成を示す概略ブロック図である。FIG. 2 is a schematic block diagram illustrating a configuration of a computer according to at least one embodiment.
＜実施形態＞
　以下、図面を参照しながら実施形態について詳しく説明する。
　本発明の一実施形態によるモータ駆動装置について説明する。
　図１は、本発明の一実施形態によるモータ駆動装置１の構成を示す図である。モータ駆動装置１は、図１に示すように、コンバータ装置２、インバータ装置３、を備える。
　コンバータ装置２の第１端子は、交流電源４の第１端子に接続される。コンバータ装置２の第２端子は、交流電源４の第２端子に接続される。コンバータ装置２の第３端子は、インバータ装置３の第１端子に接続される。コンバータ装置２の第４端子は、インバータ装置３の第２端子に接続される。インバータ装置３の第３端子は、モータ５の第１端子に接続される。インバータ装置３の第４端子は、モータ５の第２端子に接続される。インバータ装置３の第５端子は、モータ５の第３端子に接続される。モータ駆動装置１は、交流電源４からの交流電力をコンバータ装置２によって直流電力に変換し、その直流電力をインバータ装置３によって三相交流電力に変換してモータ５に出力する装置である。 <Embodiment>
Hereinafter, embodiments will be described in detail with reference to the drawings.
A motor driving device according to an embodiment of the present invention will be described.
FIG. 1 is a diagram showing a configuration of a motor drive device 1 according to one embodiment of the present invention. The motor drive device 1 includes a converter device 2 and an inverter device 3, as shown in FIG.
A first terminal of converter device 2 is connected to a first terminal of AC power supply 4. A second terminal of converter device 2 is connected to a second terminal of AC power supply 4. The third terminal of converter device 2 is connected to the first terminal of inverter device 3. The fourth terminal of converter device 2 is connected to the second terminal of inverter device 3. The third terminal of the inverter device 3 is connected to the first terminal of the motor 5. The fourth terminal of the inverter device 3 is connected to the second terminal of the motor 5. The fifth terminal of the inverter device 3 is connected to the third terminal of the motor 5. The motor driving device 1 is a device that converts AC power from an AC power supply 4 into DC power by a converter device 2, converts the DC power into three-phase AC power by an inverter device 3, and outputs the three-phase AC power to a motor 5.
　交流電源４は、単相の交流電力をコンバータ装置２に供給する。交流電源４は、例えば、図２において電源電圧と記載されている電圧と、図２において入力電流と記載されている電流とをコンバータ装置２に供給する。
　モータ５は、インバータ装置３から供給される三相交流電力に応じて回転する。モータ５は、例えば、空気調和機に用いられる圧縮機モータである。 The AC power supply 4 supplies single-phase AC power to the converter device 2. The AC power supply 4 supplies, for example, a voltage described as a power supply voltage in FIG. 2 and a current described as an input current in FIG.
The motor 5 rotates according to the three-phase AC power supplied from the inverter device 3. The motor 5 is, for example, a compressor motor used in an air conditioner.
　コンバータ装置２は、図１に示すように、整流回路２１、入力電流特定部２２、ゼロクロス検出部２３、コンバータ制御部２４を備える。整流回路２１は、図１に示すように、ブリッジ回路２００、リアクタ２１１、コンデンサ２１６を備える。ブリッジ回路２００は、ダイオード２１２ａ、２１３ａ、コンデンサ２１２ｂ、２１３ｂ、抵抗２１２ｃ、２１３ｃ、スイッチング素子２１４、２１５を備える。
　コンバータ装置２は、交流電源４から供給される入力電流が所定の電流値以下である場合にその入力電流が流れると予想した期間の少なくとも一部を含む一定の第１期間にスイッチング素子２１４または２１５に電流を流し、入力電流が所定の電流値と超える場合にその入力電流の流れる第２期間と、その第２期間の直前及び直後の少なくとも一方へ延びた期間との総和である第３期間において、スイッチング素子２１４または２１５に電流を流すこと（すなわち、同期整流制御を行うこと）により、交流電源４からの交流電力を効率よく直流電力に変換する装置である。コンバータ装置２は、その直流電力をインバータ装置３に出力する。 The converter device 2 includes a rectifier circuit 21, an input current identification unit 22, a zero-cross detection unit 23, and a converter control unit 24, as shown in FIG. The rectifier circuit 21 includes a bridge circuit 200, a reactor 211, and a capacitor 216, as shown in FIG. The bridge circuit 200 includes diodes 212a and 213a, capacitors 212b and 213b, resistors 212c and 213c, and switching elements 214 and 215.
Converter device 2 performs switching element 214 or 215 during a certain first period including at least a part of a period in which the input current is expected to flow when the input current supplied from AC power supply 4 is equal to or less than a predetermined current value. And when the input current exceeds a predetermined current value, in a third period which is the sum of a second period in which the input current flows and a period extending to at least one of immediately before and immediately after the second period. This is a device that efficiently converts AC power from the AC power supply 4 to DC power by flowing a current through the switching element 214 or 215 (that is, performing synchronous rectification control). Converter device 2 outputs the DC power to inverter device 3.
　整流回路２１において、リアクタ２１１の第１端子は、ダイオード２１２ａのアノード、抵抗２１２ｃの第１端子、スイッチング素子２１４の第１端子それぞれに接続される。ダイオード２１２ａのカソードは、コンデンサ２１２ｂの第１端子、ダイオード２１３ａのカソード、コンデンサ２１３ｂの第１端子、コンデンサ２１６の第１端子それぞれに接続される。コンデンサ２１２ｂの第２端子は、抵抗２１３ｃの第２端子に接続される。ダイオード２１３ａのアノードは、抵抗２１３ｃの第１端子、スイッチング素子２１５の第１端子それぞれに接続される。スイッチング素子２１４の第２端子は、スイッチング素子２１５の第２端子、コンデンサ２１６の第２端子それぞれに接続される。リアクタ２１１の第２端子は、整流回路２１の第１端子に接続される。ダイオード２１３ａのアノードは、整流回路２１の第２端子に接続される。ダイオード２１２ａのカソードは、整流回路２１の第３端子に接続される。スイッチング素子２１４の第２端子は、整流回路２１の第４端子に接続される。スイッチング素子２１４の第３端子は、整流回路２１の第５端子に接続される。スイッチング素子２１５の第３端子は、整流回路２１の第６端子に接続される。
　なお、ダイオード２１２ａ、コンデンサ２１２ｂ、抵抗２１２ｃから成る回路を第１回路２１２と呼ぶ。また、ダイオード２１３ａ、コンデンサ２１３ｂ、抵抗２１３ｃから成る回路を第２回路２１３と呼ぶ。 In the rectifier circuit 21, the first terminal of the reactor 211 is connected to the anode of the diode 212a, the first terminal of the resistor 212c, and the first terminal of the switching element 214, respectively. The cathode of the diode 212a is connected to the first terminal of the capacitor 212b, the cathode of the diode 213a, the first terminal of the capacitor 213b, and the first terminal of the capacitor 216, respectively. A second terminal of the capacitor 212b is connected to a second terminal of the resistor 213c. The anode of the diode 213a is connected to the first terminal of the resistor 213c and the first terminal of the switching element 215, respectively. The second terminal of the switching element 214 is connected to the second terminal of the switching element 215 and the second terminal of the capacitor 216, respectively. The second terminal of the reactor 211 is connected to the first terminal of the rectifier circuit 21. The anode of the diode 213a is connected to the second terminal of the rectifier circuit 21. The cathode of the diode 212a is connected to the third terminal of the rectifier circuit 21. The second terminal of the switching element 214 is connected to the fourth terminal of the rectifier circuit 21. The third terminal of the switching element 214 is connected to the fifth terminal of the rectifier circuit 21. The third terminal of the switching element 215 is connected to the sixth terminal of the rectifier circuit 21.
Note that a circuit including the diode 212a, the capacitor 212b, and the resistor 212c is referred to as a first circuit 212. A circuit including the diode 213a, the capacitor 213b, and the resistor 213c is referred to as a second circuit 213.
　整流回路２１の第１端子は、入力電流特定部２２の第１端子、ゼロクロス検出部２３の第１端子それぞれに接続される。整流回路２１の第２端子は、ゼロクロス検出部２３の第２端子に接続される。整流回路２１の第５端子は、コンバータ制御部２４の第１端子に接続される。整流回路２１の第６端子は、コンバータ制御部２４の第２端子に接続される。入力電流特定部２２の第２端子は、コンバータ制御部２４の第３端子に接続される。ゼロクロス検出部２３の第３端子は、コンバータ制御部２４の第４端子に接続される。
　整流回路２１の第１端子は、コンバータ装置２の第１端子に接続される。整流回路２１の第２端子は、コンバータ装置２の第２端子に接続される。整流回路２１の第３端子は、コンバータ装置２の第３端子に接続される。整流回路２１の第４端子は、コンバータ装置２の第４端子に接続される。 The first terminal of the rectifier circuit 21 is connected to the first terminal of the input current specifying unit 22 and the first terminal of the zero-cross detecting unit 23, respectively. A second terminal of the rectifier circuit 21 is connected to a second terminal of the zero-cross detector 23. The fifth terminal of the rectifier circuit 21 is connected to the first terminal of the converter control unit 24. A sixth terminal of the rectifier circuit 21 is connected to a second terminal of the converter control unit 24. A second terminal of the input current specifying unit 22 is connected to a third terminal of the converter control unit 24. A third terminal of the zero-crossing detector 23 is connected to a fourth terminal of the converter controller 24.
The first terminal of the rectifier circuit 21 is connected to the first terminal of the converter device 2. The second terminal of the rectifier circuit 21 is connected to the second terminal of the converter device 2. The third terminal of the rectifier circuit 21 is connected to the third terminal of the converter device 2. The fourth terminal of the rectifier circuit 21 is connected to the fourth terminal of the converter device 2.
　リアクタ２１１は、昇圧動作を実現するために設けられるリアクタである。
　ブリッジ回路２００は、コンバータ制御部２４による制御に基づいて、交流電力を直流電力に整流する。スイッチング素子２１４、２１５それぞれは、例えば、スーパージャンクションＭＯＳＦＥＴ（Ｍｅｔａｌ－Ｏｘｉｄｅ　Ｓｅｍｉｃｏｎｄｕｃｔｏｒ　Ｆｉｅｌｄ－Ｅｆｆｅｃｔ　Ｔｒａｎｓｉｓｔｏｒ）、ＩＧＢＴ（Ｉｎｓｕｌａｔｅｄ　Ｇａｔｅ　Ｂｉｐｏｌａｒ　Ｔｒａｎｓｉｓｔｏｒ）等である。図１は、スイッチング素子２１４、２１５それぞれがスーパージャンクションＭＯＳＦＥＴである場合の例を示している。スイッチング素子２１４、２１５それぞれがスーパージャンクションＭＯＳＦＥＴである場合、スイッチング素子２１４、２１５それぞれにおいて、第１端子はドレインであり、第２端子はソースであり、第３端子はゲートである。スイッチング素子２１４は、図１に示すように、トランジスタ部２１４ａ、ソース－ドレイン間の寄生ダイオード２１４ｂを有する。また、スイッチング素子２１５は、図１に示すように、トランジスタ部２１５ａ、ソース－ドレイン間の寄生ダイオード２１５ｂを有する。 Reactor 211 is a reactor provided to realize a boost operation.
The bridge circuit 200 rectifies AC power to DC power based on the control of the converter control unit 24. Each of the switching elements 214 and 215 is, for example, a super-junction MOSFET (Metal-Oxide Semiconductor Field-Effect Transistor), an IGBT (Insulated Gate Bipolar Transistor), or the like. FIG. 1 shows an example in which each of the switching elements 214 and 215 is a super junction MOSFET. When each of the switching elements 214 and 215 is a super junction MOSFET, in each of the switching elements 214 and 215, the first terminal is a drain, the second terminal is a source, and the third terminal is a gate. As shown in FIG. 1, the switching element 214 has a transistor part 214a and a parasitic diode 214b between the source and the drain. Further, as shown in FIG. 1, the switching element 215 has a transistor portion 215a and a parasitic diode 215b between the source and the drain.
　コンデンサ２１６は、ブリッジ回路２００の出力する直流電力を平滑化するコンデンサである。コンデンサ２１６によって、電圧値の変動の少ない直流電圧がコンバータ装置２からインバータ装置３へ供給される。コンデンサ２１６は、例えば、電解コンデンサである。 The capacitor 216 is a capacitor for smoothing the DC power output from the bridge circuit 200. By the capacitor 216, a DC voltage with a small fluctuation in the voltage value is supplied from the converter device 2 to the inverter device 3. The capacitor 216 is, for example, an electrolytic capacitor.
　入力電流特定部２２は、交流電源４からコンバータ装置２へ供給される入力電流の電流値を、交流電源４が出力する交流電圧の周期よりも充分に短い周期ごとに特定する。例えば、入力電流特定部２２は、交流電源４とコンバータ装置２との間に設けられた電流センサを含み、その電流センサの読み取った入力電流の電流値（入力電流に係る物理量の一例）を特定する。また、例えば、入力電流特定部２２は、交流電源４とコンバータ装置２との間に設けられたシャント抵抗を含み、そのシャント抵抗の両端の電位差（入力電流に係る物理量の一例）を抵抗値で除算して電流値を特定するものであってもよい。
　入力電流特定部２２は、検出した入力電流の電流値をコンバータ制御部２４に与える。 The input current specifying unit 22 specifies the current value of the input current supplied from the AC power supply 4 to the converter device 2 for each cycle sufficiently shorter than the cycle of the AC voltage output from the AC power supply 4. For example, the input current specifying unit 22 includes a current sensor provided between the AC power supply 4 and the converter device 2, and specifies a current value (an example of a physical quantity related to the input current) of the input current read by the current sensor. I do. In addition, for example, the input current specifying unit 22 includes a shunt resistor provided between the AC power supply 4 and the converter device 2, and the potential difference between both ends of the shunt resistor (an example of a physical quantity related to the input current) is represented by a resistance value. The current value may be specified by division.
The input current specifying unit 22 gives the current value of the detected input current to the converter control unit 24.
　ゼロクロス検出部２３は、交流電源４が出力する電圧のゼロクロス点を検出する。ゼロクロス点は、交流電源４が出力する電圧がゼロボルトを交差するタイミングを示し、そのタイミングがモータ駆動装置１の処理において基準のタイミングとなる。ゼロクロス検出部２３は、ゼロクロス点の情報を含むゼロクロス信号を生成する。ゼロクロス検出部２３は、ゼロクロス信号をコンバータ制御部２４に出力する。 The zero-crossing detector 23 detects the zero-crossing point of the voltage output from the AC power supply 4. The zero-cross point indicates a timing at which the voltage output from the AC power supply 4 crosses zero volts, and the timing becomes a reference timing in the processing of the motor driving device 1. The zero-cross detection unit 23 generates a zero-cross signal including information on a zero-cross point. The zero-cross detector 23 outputs a zero-cross signal to the converter controller 24.
　コンバータ制御部２４は、入力電流特定部２２から入力電流の情報を受ける。コンバータ制御部２４は、スイッチング素子２１４、２１５それぞれのオン状態となる期間とオフ状態となる期間とを制御する。
　コンバータ制御部２４は、スイッチング素子２１４、２１５の両方を同時にオン状態にすることはなく、スイッチング素子２１４、２１５の両方をオフ状態にし、または、スイッチング素子２１４をオフ状態かつスイッチング素子２１５をオン状態にする。また、コンバータ制御部２４は、交流電源４の第１端子の電位が第２端子の電位よりも低い場合、スイッチング素子２１４、２１５の両方を同時にオン状態にすることはなく、スイッチング素子２１４、２１５の両方をオフ状態にし、または、スイッチング素子２１４をオン状態かつスイッチング素子２１５をオフ状態にする。 Converter control unit 24 receives input current information from input current specifying unit 22. The converter control unit 24 controls a period during which each of the switching elements 214 and 215 is turned on and a period during which the switching elements 214 and 215 are turned off.
The converter control unit 24 does not turn on both the switching elements 214 and 215 at the same time, turns off both the switching elements 214 and 215, or turns off the switching element 214 and turns on the switching element 215. To When the potential of the first terminal of the AC power supply 4 is lower than the potential of the second terminal, the converter control unit 24 does not turn on both of the switching elements 214 and 215 at the same time. Are turned off, or the switching element 214 is turned on and the switching element 215 is turned off.
　例えば、スイッチング素子２１４、２１５それぞれがスーパージャンクションＭＯＳＦＥＴであり、交流電源４の第１端子の電位が第２端子の電位よりも高く、コンバータ制御部２４がスイッチング素子２１４、２１５の両方をオフ状態にした場合（条件１の場合）、交流電源４の第１端子からリアクタ２１１、第１回路２１２、コンデンサ２１６、寄生ダイオード２１５ｂ、交流電源４の第２端子へと電流が流れて、コンデンサ２１６が充電される。
　また、例えば、スイッチング素子２１４、２１５それぞれがスーパージャンクションＭＯＳＦＥＴであり、交流電源４の第１端子の電位が第２端子の電位よりも高く、スイッチング素子２１４がオフ状態かつスイッチング素子２１５がオン状態である場合（条件２の場合）、交流電源４の第１端子からリアクタ２１１、第１回路２１２、コンデンサ２１６、トランジスタ部２１５ａ、交流電源４の第２端子へと電流が流れて、コンデンサ２１６が充電される。
　なお、条件２の場合においてトランジスタ部２１５ａのソース－ドレイン間電圧はほぼゼロであるのに対して、条件１の場合における寄生ダイオード２１５ｂでは順方向電圧分の電圧降下が生じる。そのため、コンバータ制御部２４は、交流電源４の第１端子からコンバータ装置２に電流を供給する場合には、スイッチング素子２１５をオフ状態にして寄生ダイオード２１５ｂに電流を流すよりも、スイッチング素子２１５をオン状態にしてトランジスタ部２１５ａに電流を流した方が寄生ダイオード２１５ｂによる順方向電圧の分だけ効率をよくすることができる。 For example, each of the switching elements 214 and 215 is a super junction MOSFET, the potential of the first terminal of the AC power supply 4 is higher than the potential of the second terminal, and the converter control unit 24 turns off both the switching elements 214 and 215. In this case (condition 1), current flows from the first terminal of the AC power supply 4 to the reactor 211, the first circuit 212, the capacitor 216, the parasitic diode 215b, and the second terminal of the AC power supply 4, and the capacitor 216 is charged. Is done.
Further, for example, each of the switching elements 214 and 215 is a super junction MOSFET, the potential of the first terminal of the AC power supply 4 is higher than the potential of the second terminal, and the switching element 214 is off and the switching element 215 is on. In some cases (condition 2), current flows from the first terminal of the AC power supply 4 to the reactor 211, the first circuit 212, the capacitor 216, the transistor unit 215a, and the second terminal of the AC power supply 4, and the capacitor 216 is charged. Is done.
In the case of the condition 2, the voltage between the source and the drain of the transistor portion 215a is almost zero, whereas in the case of the condition 1, a voltage drop of a forward voltage occurs in the parasitic diode 215b. Therefore, when supplying current to converter device 2 from the first terminal of AC power supply 4, converter control unit 24 sets switching element 215 to a lower state than switching switching element 215 to an off state and flowing current to parasitic diode 215 b. When the transistor is turned on and a current flows through the transistor portion 215a, the efficiency can be improved by the amount of the forward voltage generated by the parasitic diode 215b.
　また、スイッチング素子２１４、２１５それぞれがスーパージャンクションＭＯＳＦＥＴであり、交流電源４の第１端子の電位が第２端子の電位よりも低く、コンバータ制御部２４がスイッチング素子２１４、２１５の両方をオフ状態にした場合（条件３の場合）、交流電源４の第２端子から第２回路２１３、コンデンサ２１６、寄生ダイオード２１４ｂ、リアクタ２１１、交流電源４の第１端子へと電流が流れて、コンデンサ２１６が充電される。
　また、スイッチング素子２１４、２１５それぞれがスーパージャンクションＭＯＳＦＥＴであり、交流電源４の第１端子の電位が第２端子の電位よりも低く、スイッチング素子２１４がオン状態かつスイッチング素子２１５がオフ状態である場合（条件４の場合）、交流電源４の第２端子から第２回路２１３、コンデンサ２１６、トランジスタ部２１４ａ、リアクタ２１１、交流電源４の第１端子へと電流が流れて、コンデンサ２１６が充電される。
　なお、条件４の場合においてトランジスタ部２１４ａのソース－ドレイン間電圧はほぼゼロであるのに対して、条件３の場合における寄生ダイオード２１４ｂでは順方向電圧分の電圧降下が生じる。そのため、コンバータ制御部２４は、交流電源４の第２端子からコンバータ装置２に電流を供給する場合には、スイッチング素子２１４をオフ状態にして寄生ダイオード２１４ｂに電流を流すよりも、スイッチング素子２１４をオン状態にしてトランジスタ部２１４ａに電流を流した方が寄生ダイオード２１４ｂによる順方向電圧の分だけ効率をよくすることができる。 Further, each of the switching elements 214 and 215 is a super junction MOSFET, the potential of the first terminal of the AC power supply 4 is lower than the potential of the second terminal, and the converter control unit 24 turns off both the switching elements 214 and 215. In this case (condition 3), current flows from the second terminal of the AC power supply 4 to the second circuit 213, the capacitor 216, the parasitic diode 214b, the reactor 211, and the first terminal of the AC power supply 4, and the capacitor 216 is charged. Is done.
When the switching elements 214 and 215 are each a super junction MOSFET, the potential of the first terminal of the AC power supply 4 is lower than the potential of the second terminal, and the switching element 214 is on and the switching element 215 is off. (In the case of condition 4), current flows from the second terminal of the AC power supply 4 to the second circuit 213, the capacitor 216, the transistor unit 214a, the reactor 211, and the first terminal of the AC power supply 4, and the capacitor 216 is charged. .
In the case of the condition 4, the voltage between the source and the drain of the transistor unit 214a is almost zero, whereas in the case of the condition 3, a voltage drop of the forward voltage occurs in the parasitic diode 214b. Therefore, when a current is supplied from the second terminal of the AC power supply 4 to the converter device 2, the converter control unit 24 sets the switching element 214 to be OFF rather than flowing the current to the parasitic diode 214 b by turning off the switching element 214. When the current is supplied to the transistor portion 214a in the ON state, the efficiency can be improved by the forward voltage generated by the parasitic diode 214b.
　すなわち、本発明の一実施形態によるコンバータ制御部２４は、交流電源４の第１端子からコンバータ装置２に電流を供給する場合に、スイッチング素子２１５をオフ状態にして寄生ダイオード２１５ｂに電流を流すのではなく、スイッチング素子２１５をオン状態にしてトランジスタ部２１５ａに電流を流すことによって効率をよくする制御部である。また、本発明の一実施形態によるコンバータ制御部２４は、交流電源４の第２端子からコンバータ装置２に電流を供給する場合に、スイッチング素子２１４をオフ状態にして寄生ダイオード２１４ｂに電流を流すのではなく、スイッチング素子２１４をオン状態にしてトランジスタ部２１４ａに電流を流すことによって効率をよくする制御部である。 That is, the converter control unit 24 according to the embodiment of the present invention turns off the switching element 215 to flow the current to the parasitic diode 215b when supplying the current from the first terminal of the AC power supply 4 to the converter device 2. Rather, it is a control unit that improves the efficiency by turning on the switching element 215 and causing a current to flow through the transistor unit 215a. Further, the converter control unit 24 according to the embodiment of the present invention turns off the switching element 214 to flow the current to the parasitic diode 214b when supplying the current to the converter device 2 from the second terminal of the AC power supply 4. Rather, it is a control unit that improves efficiency by turning on the switching element 214 and flowing current to the transistor unit 214a.
　コンバータ制御部２４は、図３に示すように、基準特定部２４１、入力電流取得部２４２、制御信号生成部２４３、記憶部２４４を備える。
　基準特定部２４１は、基準となるタイミングを特定する。例えば、基準特定部２４１は、ゼロクロス検出部２３からゼロクロス信号を取得する。基準特定部２４１は、取得したゼロクロス信号の示す基準のタイミングを特定する。基準特定部２４１は、特定した基準のタイミングを制御信号生成部２４３に出力する。 The converter control unit 24 includes a reference specifying unit 241, an input current acquisition unit 242, a control signal generation unit 243, and a storage unit 244, as shown in FIG.
The reference specifying unit 241 specifies a reference timing. For example, the reference specifying unit 241 acquires a zero cross signal from the zero cross detection unit 23. The reference specifying unit 241 specifies a reference timing indicated by the acquired zero-cross signal. The reference specifying unit 241 outputs the specified reference timing to the control signal generation unit 243.
　入力電流取得部２４２は、入力電流特定部２２から入力電流の電流値（すなわち、交流電源４からコンバータ装置２へ入力される入力電流の電流値）を、入力電流特定部２２の入力電流の検出タイミングごとに取得する。入力電流取得部２４２は、取得した電流値を制御信号生成部２４３に出力する。 The input current obtaining unit 242 detects the current value of the input current from the input current specifying unit 22 (that is, the current value of the input current input from the AC power supply 4 to the converter device 2) and detects the input current of the input current specifying unit 22. Acquire at each timing. The input current acquisition unit 242 outputs the acquired current value to the control signal generation unit 243.
　制御信号生成部２４３は、基準特定部２４１から基準のタイミングを取得する。また、制御信号生成部２４３は、入力電流取得部２４２から入力電流の電流値を取得する。制御信号生成部２４３は、基準特定部２４１から取得した基準のタイミングにおける位相を位相θの基準０度とする。そして、制御信号生成部２４３は、位相θの基準に基づいて、入力電流の実効値を算出する。
　例えば、制御信号生成部２４３は、位相θの基準からの位相に応じて、入力電流取得部２４２から取得した入力電流の電流値の積算値を二乗平均して、入力電流の実効値を算出する。
　また、例えば、入力電流特定部２２が電流センサ（例えば、カレントトランス）を備える場合には、入力電流は、カレントトランスを介して、ブリッジ回路２００で全波整流され、コンデンサ２１６を充電する。制御信号生成部２４３は、このコンデンサ２１６によって平滑された状態の電圧レベルを読み取る。そして、制御信号生成部２４３は、読み取った電圧値をその電圧値に一対一で関連付けられた電流値に変換することで、入力電流の実効値を算出すればよい。なお、電圧値から電流値へ変換する場合には、電圧値と電流値との対応関係を示す変換テーブルを予め作成して記憶部２４４に記憶させ、制御信号生成部２４３が、その変換テーブルを用いて読み取った電圧値を電流の実効値に変換すればよい。 The control signal generation unit 243 acquires the reference timing from the reference identification unit 241. Further, the control signal generation unit 243 acquires the current value of the input current from the input current acquisition unit 242. The control signal generation unit 243 sets the phase at the reference timing acquired from the reference identification unit 241 as the reference 0 degree of the phase θ. Then, the control signal generator 243 calculates the effective value of the input current based on the reference of the phase θ.
For example, the control signal generation unit 243 calculates the effective value of the input current by averaging the integrated value of the current values of the input current acquired from the input current acquisition unit 242 according to the phase of the phase θ from the reference. .
For example, when the input current specifying unit 22 includes a current sensor (for example, a current transformer), the input current is full-wave rectified by the bridge circuit 200 via the current transformer, and charges the capacitor 216. The control signal generator 243 reads the voltage level in a state smoothed by the capacitor 216. Then, the control signal generator 243 may calculate the effective value of the input current by converting the read voltage value into a current value that is associated with the voltage value on a one-to-one basis. When converting from a voltage value to a current value, a conversion table indicating the correspondence between the voltage value and the current value is created in advance and stored in the storage unit 244, and the control signal generation unit 243 reads the conversion table. Then, the read voltage value may be converted into the effective value of the current.
　制御信号生成部２４３は、算出した入力電流の実効値と、データテーブルＴＢＬ１における入力電流の実効値とを比較する。制御信号生成部２４３は、比較結果に基づいて、算出した入力電流の実効値に最も近い入力電流の実効値を、データテーブルＴＢＬ１において特定する。制御信号生成部２４３は、データテーブルＴＢＬ１において、特定した入力電流に関連付けられている位相の調整量を特定する。
　制御信号生成部２４３は、電源電圧の位相を基準に（すなわち、ゼロクロス点を基準に）特定した位相の調整量だけ位相を調整する。
　そして、制御信号生成部２４３は、位相を調整した制御信号をスイッチング素子２１４、２１５それぞれに出力する。 The control signal generator 243 compares the calculated effective value of the input current with the effective value of the input current in the data table TBL1. The control signal generation unit 243 specifies the effective value of the input current closest to the calculated effective value of the input current in the data table TBL1 based on the comparison result. The control signal generation unit 243 specifies the adjustment amount of the phase associated with the specified input current in the data table TBL1.
The control signal generation unit 243 adjusts the phase by the amount of phase adjustment specified based on the phase of the power supply voltage (that is, based on the zero-cross point).
Then, the control signal generation unit 243 outputs the control signal whose phase has been adjusted to each of the switching elements 214 and 215.
　制御信号生成部２４３は、交流電源４から供給される入力電流が所定の電流値以下である場合に、その入力電流が流れると予想した期間の少なくとも一部を含む一定の第１期間にスイッチング素子をオン状態にする信号を特定する。また、制御信号生成部２４３は、入力電流が所定の電流値を超える場合に、位相０度から１８０度までの間オフ状態に制御されているスイッチング素子（スイッチング素子２１４または２１５）を、位相０度から１８０度までの間に入力電流特定部２２が入力電流を検出した第２期間（第２期間において入力電流が流れ始めるタイミングが第１タイミングの一例であり、第２期間において入力電流が流れなくなるタイミングが第２タイミングの一例である）と、その期間の直前及び直後の少なくとも一方に延長した期間との総和である第３期間に、オン状態にする信号を特定する。
　例えば、制御信号生成部２４３は、入力電流の電流値がゼロである場合のノイズを入力電流として誤検出しないように、ノイズよりも大きい値の電流しきい値（例えば、図４に示す電流しきい値３アンペア）を予め設定する。制御信号生成部２４３は、入力電流特定部２２から入力電流の電流値を取得する度に、取得した入力電流の電流値とその電流しきい値とを比較する。
　制御信号生成部２４３は、比較結果に基づいて、入力電流の電流値が電流しきい値を超えている期間（例えば、図４に示す期間β１）を特定する。入力電流の電流値が電流しきい値を超えている期間β１の値（期間β１の始まりの位相と終わりの位相との位相差）ごとに、入力電流が流れ始めてから流れ終わるまでの期間（例えば、図４に示す期間β２）、すなわち第２期間を特定するための位相の補正値であるθ１、θ２を関連付けて、例えば、記憶部２４４が予め記憶する。補正値θ１は、期間を直前へ延長する補正値である。補正値θ２は、期間を直後へ延長する補正値である。制御信号生成部２４３は、比較結果に基づいて、入力電流の電流値が電流しきい値を超えている期間β１があると判定した場合、その期間β１を直前へθ１延長し直後へθ２延長した期間β２に対して、さらに、直前及び直後の少なくとも一方へαだけ延長した期間（図４に示す例では、期間β２に対して、直前及び直後の両方にそれぞれαを延長した期間）である第３期間を、スイッチング素子をオン状態にする期間と特定する。また、制御信号生成部２４３は、比較結果に基づいて、入力電流の電流値が電流しきい値を超えている期間β１がないと判定した場合、一定の第１期間（例えば、図４に示す期間β３）を、スイッチング素子をオン状態にする期間と特定する。そして、制御信号生成部２４３は、特定した期間にスイッチング素子をオン状態にする信号を特定する。
　制御信号生成部２４３は、特定した信号の位相を１８０度遅延させて、次の半周期（制御信号を適用する半周期の一例）の制御信号である第１制御信号としてスイッチング素子（スイッチング素子２１４または２１５）に出力する。また、制御信号生成部２４３は、位相０度から１８０度までの間にオン状態に制御されたスイッチング素子を次の半周期の間オフ状態にする第２制御信号を、その位相０度から１８０度までの間に特定する。そして、制御信号生成部２４３は、次の半周期に特定した第２制御信号を、第１制御信号を出力するスイッチング素子とは別のスイッチング素子（スイッチング素子２１５または２１４）に出力する。
　なお、入力電流の検出された第２期間を含む第３期間への延長は、その半周期の期間の始まりが限界となる。また、入力電流の検出された第２期間を含む第３期間への延長は、その半周期の期間の終わりが限界となる。 When the input current supplied from the AC power supply 4 is equal to or less than a predetermined current value, the control signal generation unit 243 switches the switching element during a certain first period including at least a part of a period in which the input current is expected to flow. A signal for turning on the switch is specified. In addition, when the input current exceeds a predetermined current value, the control signal generation unit 243 causes the switching element (the switching element 214 or 215) that is controlled to be in the off state from the phase 0 degree to 180 degrees to the phase 0 level. (The timing when the input current starts to flow in the second period is an example of the first timing, and the input current flows in the second period). The signal to be turned on is specified in a third period which is the sum of a period in which the period disappears is an example of a second timing) and a period extended to at least one of immediately before and after the period.
For example, the control signal generation unit 243 may set a current threshold value larger than the noise (for example, the current threshold value shown in FIG. 4) so that the noise when the current value of the input current is zero is not erroneously detected as the input current. (Threshold value 3 amps) is set in advance. Each time the control signal generation unit 243 obtains the current value of the input current from the input current identification unit 22, it compares the obtained current value of the input current with the current threshold value.
The control signal generation unit 243 specifies a period in which the current value of the input current exceeds the current threshold (for example, a period β1 shown in FIG. 4) based on the comparison result. For each value of the period β1 during which the current value of the input current exceeds the current threshold value (the phase difference between the start phase and the end phase of the period β1), the period from when the input current starts flowing until when the input current ends (for example, For example, the storage unit 244 stores in advance a period β2 shown in FIG. 4), that is, θ1 and θ2, which are phase correction values for specifying the second period, in association with each other. The correction value θ1 is a correction value for extending the period immediately before. The correction value θ2 is a correction value for extending the period immediately after. When the control signal generation unit 243 determines that there is a period β1 in which the current value of the input current exceeds the current threshold based on the comparison result, the control unit 243 extends the period β1 by θ1 immediately before and θ2 by immediately after. In the example shown in FIG. 4, the period β2 is a period in which α is extended both immediately before and immediately after the period β2 by at least one of α and the period β2. The three periods are specified as periods during which the switching elements are turned on. In addition, when the control signal generation unit 243 determines that there is no period β1 in which the current value of the input current exceeds the current threshold based on the comparison result, the control signal generation unit 243 performs a certain first period (see, for example, FIG. The period β3) is specified as a period during which the switching element is turned on. Then, the control signal generation unit 243 specifies a signal for turning on the switching element during the specified period.
The control signal generation unit 243 delays the phase of the specified signal by 180 degrees, and uses the switching element (switching element 214) as a first control signal that is a control signal of the next half cycle (an example of a half cycle in which the control signal is applied). Or 215). In addition, the control signal generation unit 243 outputs a second control signal for turning the switching element, which has been controlled to the on state during the phase of 0 to 180 degrees, to the off state for the next half cycle from the phase of 0 to 180 degrees. Identify between degrees. Then, the control signal generation unit 243 outputs the second control signal specified in the next half cycle to a switching element (switching element 215 or 214) different from the switching element that outputs the first control signal.
Note that the extension to the third period including the second period in which the input current is detected is limited at the beginning of the half period. Further, the extension to the third period including the second period in which the input current is detected is limited at the end of the half period.
　例えば、位相０度から１８０度までの間に制御信号生成部２４３がスイッチング素子２１５をオン状態にする制御を行い、入力電流特定部２２が図２に示す入力電流を検出した場合、制御信号生成部２４３は、図２に示す入力電流が正の電流値である期間から前後それぞれに位相α分だけ期間を延ばした信号を特定する。そして、制御信号生成部２４３は、生成した信号の位相に対して位相１８０度を加える。すなわち、制御信号生成部２４３は、特定した信号を次の半周期（位相１８０度から３６０度までの期間）におけるスイッチング素子２１４の制御信号とする。制御信号生成部２４３は、位相１８０度から３６０度までの期間にその制御信号をスイッチング素子２１４に出力する。また、制御信号生成部２４３は、スイッチング素子２１５を、位相１８０度から３６０度までの期間オフ状態にする制御信号を特定する。制御信号生成部２４３は、特定した制御信号を位相１８０度から３６０度までの期間にスイッチング素子２１５に出力する。それ以降、制御信号生成部２４３は、図２に示す入力電流が負の電流値である期間についても上記処理と同様の処理を行うことで、半周期ごとに第３期間に基づいて次の半周期の制御信号を特定し、特定した制御信号をスイッチング素子２１４、２１５それぞれに出力する。
　制御信号生成部２４３は、入力電流判定部の一例、第１期間特定部の一例、第２期間特定部の一例、第３期間特定部の一例、制御信号特定部の一例、制御信号出力部の一例である。すなわち、制御信号生成部２４３は、図５に示すように、入力電流判定部、第１期間特定部、第２期間特定部、第３期間特定部、制御信号特定部、制御信号出力部を含む。 For example, when the control signal generation unit 243 performs control to turn on the switching element 215 during the phase from 0 degrees to 180 degrees, and the input current identification unit 22 detects the input current shown in FIG. The unit 243 specifies a signal whose period has been extended by the phase α before and after the period in which the input current shown in FIG. 2 has a positive current value. Then, the control signal generator 243 adds a phase of 180 degrees to the phase of the generated signal. That is, the control signal generation unit 243 sets the specified signal as a control signal for the switching element 214 in the next half cycle (a period from a phase of 180 degrees to a phase of 360 degrees). The control signal generator 243 outputs the control signal to the switching element 214 during a period from 180 degrees to 360 degrees in phase. In addition, the control signal generation unit 243 specifies a control signal that turns off the switching element 215 during a period from 180 degrees to 360 degrees in phase. The control signal generation unit 243 outputs the specified control signal to the switching element 215 during a period from 180 degrees to 360 degrees in phase. Thereafter, the control signal generation unit 243 performs the same process as the above process also during the period in which the input current shown in FIG. 2 is a negative current value, so that the next half cycle is performed based on the third period every half cycle. The control signal of the cycle is specified, and the specified control signal is output to each of the switching elements 214 and 215.
The control signal generation unit 243 includes an example of an input current determination unit, an example of a first period identification unit, an example of a second period identification unit, an example of a third period identification unit, an example of a control signal identification unit, and an example of a control signal output unit. This is an example. That is, as shown in FIG. 5, the control signal generation unit 243 includes an input current determination unit, a first period identification unit, a second period identification unit, a third period identification unit, a control signal identification unit, and a control signal output unit. .
　入力電流判定部は、入力電流の電流値が所定の電流値以下であるか否かを判定する。
　第１期間特定部は、入力電流判定部が入力電流の電流値が所定の電流値以下であると判定した場合、交流電源４から出力される交流電圧の半周期について、当該電流値の入力電流が流れると予想した一定の期間である第１期間を特定する。
　制御信号特定部は、第１期間に基づいて、スイッチング素子をオン状態にする制御信号を特定する。
　第２期間特定部は、入力電流判定部が入力電流の電流値が所定の電流値を超えると判定した場合、入力電流の電流値に基づいて、交流電源４から出力される交流電圧の半周期について、入力電流が流れ始める第１タイミングから流れなくなる第２タイミングまでの第２期間を特定する。
　第３期間特定部は、第１タイミングの直前または第２タイミングの直後の少なくとも一方に延長したときの延長した期間と、第２期間との総和である第３期間を特定する。
　制御信号出力部は、制御信号を適用する交流電圧の半周期において、２つのスイッチング素子の一方へ制御信号を出力する。
　なお、制御信号特定部は、第１期間または第３期間に基づいて、スイッチング素子をオン状態にする制御信号を特定するものであってもよい。 The input current determination unit determines whether the current value of the input current is equal to or less than a predetermined current value.
When the input current determination unit determines that the current value of the input current is equal to or less than the predetermined current value, the first period identification unit determines the input current of the current value for a half cycle of the AC voltage output from the AC power supply 4 Is specified as a first period, which is a certain period in which is expected to flow.
The control signal specifying unit specifies a control signal for turning on the switching element based on the first period.
When the input current determination unit determines that the current value of the input current exceeds a predetermined current value, the second period identification unit determines a half cycle of the AC voltage output from the AC power supply 4 based on the current value of the input current. Regarding the above, the second period from the first timing at which the input current starts flowing to the second timing at which the input current stops flowing is specified.
The third period specifying unit specifies a third period that is a sum of the extended period when extending to at least one of immediately before the first timing or immediately after the second timing and the second period.
The control signal output unit outputs the control signal to one of the two switching elements in a half cycle of the AC voltage to which the control signal is applied.
The control signal specifying section may specify a control signal for turning on the switching element based on the first period or the third period.
　記憶部２４４は、コンバータ制御部２４が行う処理に必要な種々の情報を記憶する。例えば、記憶部２４４は、入力電流の電流値が電流しきい値を超えている期間β１の値ごとに、入力電流が流れ始めてから流れ終わるまでの期間（例えば、図４に示す期間β２）、すなわち第２期間を特定するための位相の補正値であるθ１、θ２を関連付けて予め記憶する。 (4) The storage unit 244 stores various information necessary for the processing performed by the converter control unit 24. For example, the storage unit 244 stores, for each value of the period β1 in which the current value of the input current exceeds the current threshold, a period from the start of the input current to the end of the flow (for example, a period β2 illustrated in FIG. 4), That is, θ1 and θ2, which are the phase correction values for specifying the second period, are stored in advance in association with each other.
　インバータ装置３は、ＩＰＭ（Ｉｎｔｅｌｌｉｇｅｎｔ　Ｐｏｗｅｒ　Ｍｏｄｕｌｅ）３１、インバータ制御部３２を備える。
　ＩＰＭ３１は、インバータ制御部３２による制御に基づいて、直流電力から三相交流電力を生成する。ＩＰＭ３１は、生成した三相交流電力をモータに供給する。ＩＰＭ３１は、例えば、６つのスイッチング素子から成るブリッジ回路である。 The inverter device 3 includes an IPM (Intelligent Power Module) 31 and an inverter control unit 32.
The IPM 31 generates three-phase AC power from DC power based on control by the inverter control unit 32. The IPM 31 supplies the generated three-phase AC power to the motor. The IPM 31 is, for example, a bridge circuit including six switching elements.
　インバータ制御部３２は、ＩＰＭ３１を制御する。具体的には、インバータ制御部３２は、ＩＰＭ３１に直流電力から三相交流電力を生成させる。例えば、ＩＰＭ３１が６つのスイッチング素子から成るブリッジ回路である場合、インバータ制御部３２は、６つのスイッチング素子それぞれのオン状態となる期間とオフ状態となる期間とを切り替えることによって、６つのスイッチング素子それぞれに流れる電流を制御することで、ＩＰＭ３１に直流電力から三相交流電力を生成させる。 (4) The inverter control unit 32 controls the IPM 31. Specifically, inverter control unit 32 causes IPM 31 to generate three-phase AC power from DC power. For example, when the IPM 31 is a bridge circuit including six switching elements, the inverter control unit 32 switches between a period in which each of the six switching elements is turned on and a period in which the six switching elements are turned off. , The IPM 31 generates three-phase AC power from DC power.
　次に、本発明の一実施形態によるコンバータ制御部２４の処理について説明する。
　ここでは、図６に示すコンバータ制御部２４の処理について説明する。
　入力電流特定部２２は、交流電源４からコンバータ装置２へ供給される入力電流を、交流電源４が出力する交流電圧の周期よりも充分に短い周期ごとに検出する。入力電流特定部２２は、検出した入力電流の電流値をコンバータ制御部２４に与える。 Next, processing of the converter control unit 24 according to the embodiment of the present invention will be described.
Here, the process of converter control unit 24 shown in FIG. 6 will be described.
The input current specifying unit 22 detects an input current supplied from the AC power supply 4 to the converter device 2 at every cycle that is sufficiently shorter than the cycle of the AC voltage output from the AC power supply 4. The input current specifying unit 22 gives the current value of the detected input current to the converter control unit 24.
　ゼロクロス検出部２３は、交流電源４が出力する電圧のゼロクロス点を検出する。ゼロクロス検出部２３は、ゼロクロス点の情報を含むゼロクロス信号を生成する。ゼロクロス検出部２３は、ゼロクロス信号をコンバータ制御部２４に出力する。 The zero-crossing detector 23 detects the zero-crossing point of the voltage output from the AC power supply 4. The zero-cross detection unit 23 generates a zero-cross signal including information on a zero-cross point. The zero-cross detector 23 outputs a zero-cross signal to the converter controller 24.
　基準特定部２４１は、ゼロクロス検出部２３からゼロクロス信号を取得する（ステップＳ１）。基準特定部２４１は、取得したゼロクロス信号の示す基準のタイミングを特定する（ステップＳ２）。基準特定部２４１は、特定した基準のタイミングを制御信号生成部２４３に出力する。 (4) The reference specifying unit 241 acquires a zero-cross signal from the zero-cross detection unit 23 (Step S1). The reference specifying unit 241 specifies a reference timing indicated by the acquired zero-cross signal (Step S2). The reference specifying unit 241 outputs the specified reference timing to the control signal generation unit 243.
　入力電流取得部２４２は、入力電流特定部２２から入力電流の電流値を、入力電流特定部２２の入力電流の検出タイミングごとに取得する（ステップＳ３）。入力電流取得部２４２は、取得した電流値を制御信号生成部２４３に出力する。 (4) The input current acquisition unit 242 acquires the current value of the input current from the input current identification unit 22 for each input current detection timing of the input current identification unit 22 (step S3). The input current acquisition unit 242 outputs the acquired current value to the control signal generation unit 243.
　制御信号生成部２４３は、基準特定部２４１から基準のタイミングを取得する。また、制御信号生成部２４３は、入力電流取得部２４２から入力電流の電流値を取得する。制御信号生成部２４３は、基準特定部２４１から取得した基準のタイミングにおける位相を位相θの基準０度とする（ステップＳ４）。制御信号生成部２４３は、位相０度から１８０度までの間オフ状態に制御されているスイッチング素子（スイッチング素子２１４または２１５）を、位相０度から１８０度までの間に第３期間に、オン状態にする第１制御信号を特定する（ステップＳ５）。 The control signal generation unit 243 acquires the reference timing from the reference identification unit 241. Further, the control signal generation unit 243 acquires the current value of the input current from the input current acquisition unit 242. The control signal generation unit 243 sets the phase at the reference timing acquired from the reference identification unit 241 as the reference 0 degree of the phase θ (Step S4). The control signal generation unit 243 turns on the switching element (the switching element 214 or 215) that is controlled to be in the off state from the phase 0 to 180 degrees in the third period from the phase 0 to 180 degrees. The first control signal to be set is specified (Step S5).
　具体的には、制御信号生成部２４３は、入力電流の電流値がゼロである場合のノイズを入力電流として誤検出しないように、ノイズよりも大きい値の電流しきい値（例えば、図４に示す電流しきい値３アンペア）を予め設定する。制御信号生成部２４３は、位相０度を基準に半周期を１つの期間として、各半周期において、入力電流特定部２２から入力電流の電流値を取得する度に、取得した入力電流の電流値とその電流しきい値とを比較する（ステップＳ５ａ）。制御信号生成部２４３は、入力電流の電流値が電流しきい値を超えているか否かを判定する（ステップＳ５ｂ）。 Specifically, the control signal generation unit 243 sets a current threshold value larger than the noise (for example, as shown in FIG. 4) so that the noise when the current value of the input current is zero is not erroneously detected as the input current. The current threshold value shown is 3 amps). The control signal generation unit 243 sets the current value of the acquired input current every time the current value of the input current is acquired from the input current identification unit 22 in each half cycle, with the half cycle as one period based on the phase 0 degree. And its current threshold value (Step S5a). The control signal generator 243 determines whether the current value of the input current exceeds the current threshold (Step S5b).
　制御信号生成部２４３は、入力電流の電流値が電流しきい値以下であると判定した場合（ステップＳ５ｂにおいてＮＯ）、対象とする半周期が終了したか否かを判定する（ステップＳ５ｃ）。
　制御信号生成部２４３は、対象とする半周期が終了していないと判定した場合（ステップＳ５ｃにおいてＮＯ）、ステップＳ５ａの処理に戻す。
　また、制御信号生成部２４３は、対象とする半周期が終了したと判定した場合（ステップＳ５ｃにおいてＹＥＳ）、一定の第１期間（例えば、図４に示す期間β３）を、スイッチング素子をオン状態にする第１期間とし、その第１期間にスイッチング素子をオン状態にする第１制御信号を特定する（ステップＳ５ｄ）。 When determining that the current value of the input current is equal to or smaller than the current threshold value (NO in step S5b), the control signal generation unit 243 determines whether the target half cycle has ended (step S5c).
When determining that the target half cycle has not ended (NO in step S5c), the control signal generation unit 243 returns to the process of step S5a.
When determining that the target half cycle has ended (YES in step S5c), the control signal generation unit 243 sets the switching element to the ON state for a certain first period (for example, period β3 shown in FIG. 4). The first control signal for turning on the switching element during the first period is specified (step S5d).
　また、制御信号生成部２４３は、入力電流の電流値が電流しきい値を超えたと判定した場合（ステップＳ５ｂにおいてＹＥＳ）、そのときの位相を期間β１の始まりを示す位相と特定する（ステップＳ５ｅ）する。制御信号生成部２４３は、次の入力電流の電流値と電流しきい値とを比較する（ステップＳ５ｆ）。制御信号生成部２４３は、比較結果において入力電流の電流値が電流しきい値以下であるか否かを判定する（ステップＳ５ｇ）。
　制御信号生成部２４３は、入力電流の電流値が第１電流しきい値以下でないと判定した場合（ステップＳ５ｇにおいてＮＯ）、ステップＳ５ｆの処理に戻す。
　また、制御信号生成部２４３は、入力電流の電流値が電流しきい値以下であると判定した場合（ステップＳ５ｇにおいてＹＥＳ）、そのときの位相を期間β１の終わりを示す位相と特定する（ステップＳ５ｈ）。すなわち、制御信号生成部２４３は、期間β１の値を特定する。制御信号生成部２４３は、記憶部２４４において、特定した期間β１の値に関連付けられている位相の補正値θ１、θ２を特定する（ステップＳ５ｉ）。制御信号生成部２４３は、期間β１を、直前へ位相θ１だけ延ばし、直後へ位相θ２だけ延ばす。すなわち、制御信号生成部２４３は、期間β２を特定する（ステップＳ５ｊ）。制御信号生成部２４３は、期間β２を、直前と直後それぞれへ位相αだけ延ばし（ステップＳ５ｋ）、その延ばした期間をスイッチング素子をオン状態にする第３期間とし、その第３期間にスイッチング素子をオン状態にする第１制御信号を特定する（ステップＳ５ｌ）。 When determining that the current value of the input current has exceeded the current threshold value (YES in step S5b), control signal generating section 243 specifies the phase at that time as the phase indicating the start of period β1 (step S5e). ). The control signal generator 243 compares the current value of the next input current with the current threshold (step S5f). The control signal generation unit 243 determines whether or not the current value of the input current is equal to or smaller than the current threshold in the comparison result (Step S5g).
When the control signal generation unit 243 determines that the current value of the input current is not equal to or smaller than the first current threshold value (NO in step S5g), the process returns to step S5f.
When determining that the current value of the input current is equal to or smaller than the current threshold value (YES in step S5g), control signal generation section 243 specifies the phase at that time as the phase indicating the end of period β1 (step S5g). S5h). That is, the control signal generation unit 243 specifies the value of the period β1. The control signal generation unit 243 specifies the correction values θ1 and θ2 of the phase associated with the value of the specified period β1 in the storage unit 244 (Step S5i). The control signal generation unit 243 extends the period β1 by the phase θ1 immediately before and by the phase θ2 immediately after. That is, the control signal generation unit 243 specifies the period β2 (Step S5j). The control signal generator 243 extends the period β2 by the phase α immediately before and immediately after (step S5k), sets the extended period as a third period in which the switching element is turned on, and sets the switching element in the third period. The first control signal to be turned on is specified (step S51).
　制御信号生成部２４３は、ステップＳ５ｄまたはステップＳ５ｌの処理によって特定した第１制御信号の位相を１８０度遅延させて、その第１制御信号を次の半周期にスイッチング素子（スイッチング素子２１４または２１５）に出力する（ステップＳ６）。また、制御信号生成部２４３は、位相０度から１８０度までの間にオン状態に制御されたスイッチング素子を次の半周期の間オフ状態にする第２制御信号を、位相０度から１８０度までの間に特定する（ステップＳ７）。制御信号生成部２４３は、特定した第２制御信号の位相を１８０度遅延させて、その第２制御信号を次の半周期の間にスイッチング素子（スイッチング素子２１５または２１４）に出力する（ステップＳ８）。制御信号生成部２４３は、ステップＳ１に処理を戻す。 The control signal generation unit 243 delays the phase of the first control signal specified by the processing of step S5d or step S51 by 180 degrees, and switches the first control signal to the switching element (switching element 214 or 215) in the next half cycle. (Step S6). Further, the control signal generation unit 243 converts the second control signal that turns the switching element, which has been controlled to the on state during the phase of 0 to 180 degrees, to the off state for the next half cycle, from the phase of 0 to 180 degrees (Step S7). The control signal generator 243 delays the phase of the specified second control signal by 180 degrees, and outputs the second control signal to the switching element (switching element 215 or 214) during the next half cycle (step S8). ). The control signal generator 243 returns the process to step S1.
　以上、本発明の一実施形態によるモータ駆動装置１について説明した。
　本発明の一実施形態によるコンバータ装置２において、入力電流取得部２４２は、交流電源４から入力される入力電流の電流値を取得する。制御信号生成部２４３（入力電流判定部の一例）は、入力電流の電流値が所定の電流値以下であるか否かを判定する。制御信号生成部２４３（第１期間特定部の一例）は、入力電流の電流値が所定の電流値以下であると判定した場合、交流電源４から出力される交流電圧の半周期について、当該電流値の入力電流が流れると予想した一定の期間である第１期間を特定する。制御信号生成部２４３（制御信号特定部の一例）は、第１期間に基づいて、スイッチング素子をオン状態にする制御信号を特定する。
　こうすることで、モータ駆動装置１のコンバータ装置２は、入力電流が所定の電流値以下である比較的小さい電流値の期間にも同期整流を行うことができる。所定の電流値は、ノイズを誤検出しない範囲で任意の電流値に設定できる。そして、コンバータ装置２は、入力電流が所定の電流値以下であると判定した場合に同期整流を行わない整流回路に比べてダイオードの順方向電圧による電圧降下の分だけ確実に効率をよくすることができる。そのため、コンバータ装置２において同期整流制御を行う場合、コンバータ装置２の入力電流の大きさに関わらず、入力電流の大きさが比較的小さい場合であっても効率を向上させることができる。 The motor drive device 1 according to one embodiment of the present invention has been described above.
In converter device 2 according to one embodiment of the present invention, input current obtaining section 242 obtains a current value of an input current input from AC power supply 4. The control signal generation unit 243 (an example of an input current determination unit) determines whether the current value of the input current is equal to or less than a predetermined current value. When determining that the current value of the input current is equal to or less than the predetermined current value, the control signal generation unit 243 (an example of a first period specifying unit) determines the current value for a half cycle of the AC voltage output from the AC power supply 4. A first period, which is a fixed period in which the input current having a value is expected to flow, is specified. The control signal generating unit 243 (an example of a control signal specifying unit) specifies a control signal for turning on the switching element based on the first period.
By doing so, the converter device 2 of the motor drive device 1 can perform synchronous rectification even during a period in which the input current is a relatively small current value equal to or less than the predetermined current value. The predetermined current value can be set to an arbitrary current value as long as noise is not erroneously detected. When the input current is determined to be equal to or less than the predetermined current value, the converter device 2 reliably improves the efficiency by the voltage drop due to the forward voltage of the diode as compared with a rectifier circuit that does not perform synchronous rectification. Can be. Therefore, when synchronous rectification control is performed in converter device 2, regardless of the magnitude of the input current of converter device 2, efficiency can be improved even when the magnitude of the input current is relatively small.
　なお、本発明の一実施形態では、制御信号生成部２４３は、基準のタイミングから半周期ごとにスイッチング素子２１４または２１５をオフ状態に制御するものとして説明した。しかしながら、本発明の別の実施形態では、制御信号生成部２４３は、基準のタイミングから半周期ごとにスイッチング素子２１４または２１５をオフ状態に制御する代わりに、入力電流を、交流電源４の出力する交流電圧の周期に近づけるとともに、正弦波に近づけるように（すなわち、高調波歪みを所望の歪み率以下にするように）、例えば、図７に示すようなＰＡＭ（Ｐｕｌｓｅ　Ａｍｐｌｉｔｕｄｅ　Ｍｏｄｕｌａｔｉｏｎ）制御信号を用いたＰＡＭ制御を行うものであってもよい。なお、この場合、制御信号生成部２４３は、入力電流に応じてＰＡＭ制御信号を生成するＰＷＭ（Ｐｕｌｓｅ　Ｗｉｄｔｈ　Ｍｏｄｕｌａｔｉｏｎ）生成技術を用いればよい。制御信号生成部２４３がＰＡＭ制御を行った場合には、入力電流は、図７において実線によって示される波形から例えば図７において破線によって示される波形になる。その結果、歪み率は改善される。なお、入力電流の検出された第２期間の直前への延長による第３期間への延長は、その半周期の期間の始まりが限界となる。また、入力電流の検出された第２期間の直後への延長による第３期間への延長は、その半周期の期間の終わりが限界となる。そのため、ＰＡＭ制御によって入力電流波形が交流電源４の出力する交流電圧の周期と同様の周期まで改善された場合には、制御信号生成部２４３は、入力電流の検出された第２期間から第３期間への延長を行わない。 In the embodiment of the present invention, the control signal generator 243 controls the switching element 214 or 215 to be turned off every half cycle from the reference timing. However, in another embodiment of the present invention, instead of controlling the switching element 214 or 215 to be in the OFF state every half cycle from the reference timing, the control signal generation unit 243 outputs the input current from the AC power supply 4. For example, a PAM (Pulse Amplitude Modulation) control signal as shown in FIG. 7 is used so as to approach the cycle of the AC voltage and approximate a sine wave (that is, to reduce the harmonic distortion to a desired distortion rate or less). The PAM control may be performed. In this case, the control signal generation unit 243 may use a PWM (Pulse Width Modulation) generation technique of generating a PAM control signal according to the input current. When the control signal generator 243 performs the PAM control, the input current changes from the waveform shown by the solid line in FIG. 7 to, for example, the waveform shown by the broken line in FIG. As a result, the distortion rate is improved. Note that the extension of the input current to the third period immediately before the detected second period is limited to the beginning of the half period. The extension of the input current to the third period immediately after the detected second period is limited to the end of the half cycle. Therefore, when the input current waveform is improved to the same cycle as the cycle of the AC voltage output from the AC power supply 4 by the PAM control, the control signal generation unit 243 switches from the second period in which the input current is detected to the third cycle. Do not extend the period.
　なお、本発明の一実施形態では、ブリッジ回路２００は、ダイオード２１２ａを含む第１回路２１２と、ダイオード２１３ａを含む第２回路２１３とを含むものとして説明した。しかしながら、本発明の別の実施形態では、第１回路２１２、第２回路２１３は、スイッチング素子であってもよい。第１回路２１２、第２回路２１３が、スイッチング素子である場合、第１回路２１２、第２回路２１３における電圧降下が改善され、さらに効率が向上する。なお、一般的に、スイッチング素子よりもダイオード、抵抗、コンデンサの方が安価であるという理由により、本発明の一実施形態におけるブリッジ回路２００は、第１回路２１２、第２回路２１３がスイッチング素子である別の実施形態に比べて安価に実現できるという効果が期待できる。 In the embodiment of the present invention, the bridge circuit 200 has been described as including the first circuit 212 including the diode 212a and the second circuit 213 including the diode 213a. However, in another embodiment of the present invention, the first circuit 212 and the second circuit 213 may be switching elements. When the first circuit 212 and the second circuit 213 are switching elements, the voltage drop in the first circuit 212 and the second circuit 213 is improved, and the efficiency is further improved. In general, the bridge circuit 200 according to the embodiment of the present invention includes the first circuit 212 and the second circuit 213 which are switching elements because diodes, resistors, and capacitors are generally cheaper than switching elements. An effect that it can be realized at lower cost than in another embodiment can be expected.
　なお、本発明の上記各実施形態では、制御信号生成部２４３は、次の半周期の制御信号を直前の半周期における入力電流に基づいて特定するものとして説明した。しかしながら、本発明の別の実施形態では、制御信号生成部２４３は、直前の半周期の代わりに、直前の半周期より前の半周期（ただし、急激な入力電流の変化がない、すなわち、制御信号を適用するときの入力電流と同様の入力電流であった過去の期間における任意の半周期）における入力電流に基づいて、制御信号を特定するものであってもよい。なお、過去の期間における任意の半周期は、予め実験などを行って入力電流の波形が所定の違いの範囲内となる過去の期間を決定し、決定した期間内の任意の半周期とすればよい。
　また、本発明の別の実施形態では、制御信号生成部２４３は、過去の複数の半周期における入力電流の平均電流値に基づいて、制御信号を特定するものであってもよい。 In the above embodiments of the present invention, the control signal generation unit 243 has been described as specifying the control signal of the next half cycle based on the input current in the immediately preceding half cycle. However, in another embodiment of the present invention, the control signal generation unit 243 replaces the immediately preceding half cycle with a half cycle before the immediately preceding half cycle (however, there is no sharp change in the input current, that is, the control signal The control signal may be specified based on the input current in an arbitrary half cycle in the past period that was the same as the input current when applying the signal. Note that an arbitrary half cycle in the past period is determined by performing an experiment or the like in advance and determining a past period in which the waveform of the input current is within a predetermined difference range, and as an arbitrary half cycle in the determined period. Good.
In another embodiment of the present invention, the control signal generator 243 may specify the control signal based on the average current value of the input current in a plurality of past half cycles.
　なお、本発明の各実施形態における記憶部、その他の記憶装置等は、適切な情報の送受信が行われる範囲においてどこに備えられていてもよい。また、記憶部、その他の記憶装置等は、適切な情報の送受信が行われる範囲において複数存在しデータを分散して記憶していてもよい。 Note that the storage unit and other storage devices in each embodiment of the present invention may be provided anywhere as long as appropriate information is transmitted and received. A plurality of storage units and other storage devices may exist in a range where appropriate information is transmitted and received, and may store data in a distributed manner.
　なお、本発明の実施形態における処理は、適切な処理が行われる範囲において、処理の順番が入れ替わってもよい。 In the process according to the embodiment of the present invention, the order of the processes may be changed within a range where an appropriate process is performed.
　本発明の実施形態について説明したが、上述のコンバータ制御部２４、インバータ制御部３２、その他の制御装置は内部に、コンピュータシステムを有していてもよい。そして、上述した処理の過程は、プログラムの形式でコンピュータ読み取り可能な記録媒体に記憶されており、このプログラムをコンピュータが読み出して実行することによって、上記処理が行われる。コンピュータの具体例を以下に示す。
　図８は、少なくとも１つの実施形態に係るコンピュータの構成を示す概略ブロック図である。
　コンピュータ５０は、図８に示すように、ＣＰＵ６０、メインメモリ７０、ストレージ８０、インターフェース９０を備える。
　例えば、上述のコンバータ制御部２４、インバータ制御部３２、その他の制御装置のそれぞれは、コンピュータ５０に実装される。そして、上述した各処理部の動作は、プログラムの形式でストレージ８０に記憶されている。ＣＰＵ６０は、プログラムをストレージ８０から読み出してメインメモリ７０に展開し、当該プログラムに従って上記処理を実行する。また、ＣＰＵ６０は、プログラムに従って、上述した各記憶部に対応する記憶領域をメインメモリ７０に確保する。 Although the embodiment of the present invention has been described, the above-described converter control unit 24, inverter control unit 32, and other control devices may include a computer system therein. The above-described process is stored in a computer-readable recording medium in the form of a program, and the program is read and executed by the computer to perform the process. Specific examples of the computer are shown below.
FIG. 8 is a schematic block diagram illustrating a configuration of a computer according to at least one embodiment.
As shown in FIG. 8, the computer 50 includes a CPU 60, a main memory 70, a storage 80, and an interface 90.
For example, each of the above-described converter control unit 24, inverter control unit 32, and other control devices is implemented in a computer 50. The operation of each processing unit described above is stored in the storage 80 in the form of a program. The CPU 60 reads the program from the storage 80, expands the program in the main memory 70, and executes the above-described processing according to the program. Further, the CPU 60 secures a storage area corresponding to each of the above-described storage units in the main memory 70 according to a program.
　ストレージ８０の例としては、ＨＤＤ（Ｈａｒｄ　Ｄｉｓｋ　Ｄｒｉｖｅ）、ＳＳＤ（Ｓｏｌｉｄ　Ｓｔａｔｅ　Ｄｒｉｖｅ）、磁気ディスク、光磁気ディスク、ＣＤ－ＲＯＭ（Ｃｏｍｐａｃｔ　Ｄｉｓｃ　Ｒｅａｄ　Ｏｎｌｙ　Ｍｅｍｏｒｙ）、ＤＶＤ－ＲＯＭ（Ｄｉｇｉｔａｌ　Ｖｅｒｓａｔｉｌｅ　Ｄｉｓｃ　Ｒｅａｄ　Ｏｎｌｙ　Ｍｅｍｏｒｙ）、半導体メモリ等が挙げられる。ストレージ８０は、コンピュータ５０のバスに直接接続された内部メディアであってもよいし、インターフェース９０または通信回線を介してコンピュータ５０に接続される外部メディアであってもよい。また、このプログラムが通信回線によってコンピュータ５０に配信される場合、配信を受けたコンピュータ５０が当該プログラムをメインメモリ７０に展開し、上記処理を実行してもよい。少なくとも１つの実施形態において、ストレージ８０は、一時的でない有形の記憶媒体である。 Examples of the storage 80 include a hard disk drive (HDD), a solid state drive (SSD), a magnetic disk, a magneto-optical disk, a CD-ROM (Compact Disc Read Only Memory), and a DVD-ROM (Digital Documentary Discrete Memory). And a semiconductor memory. The storage 80 may be an internal medium directly connected to the bus of the computer 50, or may be an external medium connected to the computer 50 via the interface 90 or a communication line. When the program is distributed to the computer 50 via a communication line, the computer 50 that has received the program may load the program into the main memory 70 and execute the above-described processing. In at least one embodiment, storage 80 is a non-transitory tangible storage medium.
　また、上記プログラムは、前述した機能の一部を実現してもよい。さらに、上記プログラムは、前述した機能をコンピュータシステムにすでに記録されているプログラムとの組み合わせで実現できるファイル、いわゆる差分ファイル（差分プログラム）であってもよい。 The program may implement a part of the functions described above. Further, the program may be a file that can realize the above-described functions in combination with a program already recorded in the computer system, that is, a so-called difference file (difference program).
　本発明のいくつかの実施形態を説明したが、これらの実施形態は、例であり、発明の範囲を限定しない。これらの実施形態は、発明の要旨を逸脱しない範囲で、種々の追加、種々の省略、種々の置き換え、種々の変更を行ってよい。 Although some embodiments of the present invention have been described, these embodiments are examples and do not limit the scope of the invention. In these embodiments, various additions, various omissions, various substitutions, and various modifications may be made without departing from the spirit of the invention.
　本発明の実施形態によるコンバータ装置、制御信号特定方法及びプログラムによれば、コンバータ装置において同期整流制御を行う場合、コンバータ装置の入力電流の大きさに関わらず効率を向上させることができる。 According to the converter device, the control signal specifying method, and the program according to the embodiment of the present invention, when performing synchronous rectification control in the converter device, efficiency can be improved regardless of the magnitude of the input current of the converter device.
１・・・モータ駆動装置
２・・・コンバータ装置
３・・・インバータ装置
４・・・交流電源
５・・・モータ
２１・・・整流回路
２２・・・入力電流特定部
２３・・・ゼロクロス検出部
２４・・・コンバータ制御部
３１・・・ＩＰＭ
３２・・・インバータ制御部
５０・・・コンピュータ
６０・・・ＣＰＵ
７０・・・メインメモリ
８０・・・ストレージ
９０・・・インターフェース
２００・・・ブリッジ回路
２１１・・・リアクタ
２１２・・・第１回路
２１２ａ、２１３ａ・・・ダイオード
２１２ｂ、２１３ｂ、２１６・・・コンデンサ
２１２ｃ、２１３ｃ・・・抵抗
２１３・・・第２回路
２１４、２１５・・・スイッチング素子
２４１・・・基準特定部
２４２・・・入力電流取得部
２４３・・・制御信号生成部 DESCRIPTION OF SYMBOLS 1 ... Motor drive device 2 ... Converter device 3 ... Inverter device 4 ... AC power supply 5 ... Motor 21 ... Rectifier circuit 22 ... Input current specifying part 23 ... Zero cross detection Unit 24: Converter control unit 31: IPM
32 ... Inverter control unit 50 ... Computer 60 ... CPU
70 main memory 80 storage 90 interface 200 bridge circuit 211 reactor 212 first circuits 212a and 213a diodes 212b, 213b and 216 capacitors 212c, 213c ... resistor 213 ... second circuit 214, 215 ... switching element 241 ... reference identification unit 242 ... input current acquisition unit 243 ... control signal generation unit

Claims (11)

  1. 　交流電源から入力される入力電流の電流値を取得する入力電流取得部と、
    　前記入力電流の電流値が所定の電流値以下であるか否かを判定する入力電流判定部と、
    　前記入力電流判定部が前記入力電流の電流値が所定の電流値以下であると判定した場合、前記交流電源から出力される交流電圧の半周期について、当該電流値の入力電流が流れると予想した一定の期間である第１期間を特定する第１期間特定部と、
    　前記第１期間に基づいて、スイッチング素子をオン状態にする制御信号を特定する制御信号特定部と、
    　を備えるコンバータ装置。     An input current acquisition unit that acquires a current value of an input current input from the AC power supply,
    An input current determination unit that determines whether the current value of the input current is equal to or less than a predetermined current value,
    When the input current determination unit determines that the current value of the input current is equal to or less than a predetermined current value, it is expected that the input current having the current value flows for a half cycle of the AC voltage output from the AC power supply. A first period specifying unit that specifies a first period that is a certain period;
    A control signal specifying unit that specifies a control signal for turning on the switching element based on the first period;
    A converter device comprising:
  2. 　前記入力電流判定部が前記入力電流の電流値が所定の電流値を超えると判定した場合、前記入力電流の電流値に基づいて、前記交流電源から出力される交流電圧の半周期について、前記入力電流が流れ始める第１タイミングから流れなくなる第２タイミングまでの第２期間を特定する第２期間特定部と、
    　前記第１タイミングの直前または前記第２タイミングの直後の少なくとも一方に延長したときの延長した期間と、前記第２期間との総和である第３期間を特定する第３期間特定部と、
    　を備え、
    　前記制御信号特定部は、
    　前記第１期間または前記第３期間に基づいて、スイッチング素子をオン状態にする制御信号を特定する、
    　請求項１に記載のコンバータ装置。     When the input current determination unit determines that the current value of the input current exceeds a predetermined current value, based on the current value of the input current, for the half cycle of the AC voltage output from the AC power supply, A second period specifying unit that specifies a second period from a first timing at which a current starts flowing to a second timing at which the current stops flowing;
    A third period specifying unit that specifies a third period that is a sum of an extended period when extending to at least one of immediately before the first timing or immediately after the second timing, and a third period that is a sum of the second period and
    With
    The control signal identification unit,
    A control signal for turning on a switching element is specified based on the first period or the third period,
    The converter device according to claim 1.
  3. 　前記第３期間は、
    　前記半周期内にある、
    　請求項２に記載のコンバータ装置。     In the third period,
    Within the half cycle,
    The converter device according to claim 2.
  4. 　２つのスイッチング素子を有し、前記交流電源の出力する電力を整流するブリッジ回路と、
    　前記制御信号を適用する前記半周期において、前記２つのスイッチング素子の一方へ前記制御信号を出力する制御信号出力部と、
    　を備える請求項１から請求項３の何れか一項に記載のコンバータ装置。     A bridge circuit having two switching elements and rectifying power output from the AC power supply;
    A control signal output unit that outputs the control signal to one of the two switching elements in the half cycle in which the control signal is applied;
    The converter device according to any one of claims 1 to 3, further comprising:
  5. 　前記入力電流の電流値は、
    　前記制御信号が適用される半周期より前の半周期における入力電流の電流値である、
    　請求項１から請求項４の何れか一項に記載のコンバータ装置。     The current value of the input current is
    The current value of the input current in a half cycle before the half cycle to which the control signal is applied,
    The converter device according to any one of claims 1 to 4.
  6. 　前記入力電流の電流値は、
    　前記制御信号が適用される半周期の直前の半周期における入力電流の電流値である、
    　請求項５に記載のコンバータ装置。     The current value of the input current is
    The current value of the input current in a half cycle immediately before the half cycle to which the control signal is applied,
    The converter device according to claim 5.
  7. 　前記入力電流の電流値は、
    　過去の複数の半周期における入力電流の電流値の平均値である、
    　請求項１から請求項４の何れか一項に記載のコンバータ装置。     The current value of the input current is
    The average value of the current values of the input current in a plurality of past half cycles,
    The converter device according to any one of claims 1 to 4.
  8. 　前記交流電圧のゼロクロス点を検出するゼロクロス検出部と、
    　前記ゼロクロス点に基づいて前記半周期の基準となるタイミングを特定する基準特定部と、
    　を備える請求項１から請求項７の何れか一項に記載のコンバータ装置。     A zero-cross detection unit that detects a zero-cross point of the AC voltage,
    A reference specifying unit that specifies a reference timing of the half cycle based on the zero cross point,
    The converter device according to any one of claims 1 to 7, further comprising:
  9. 　前記入力電流に係る物理量に基づいて前記入力電流の電流値を特定する入力電流特定部、
    　を備え、
    　前記入力電流取得部は、
    　前記入力電流特定部が特定した前記電流値を取得する、
    　請求項１から請求項８の何れか一項に記載のコンバータ装置。     An input current specifying unit that specifies a current value of the input current based on a physical quantity related to the input current;
    With
    The input current acquisition unit,
    Acquiring the current value specified by the input current specifying unit,
    The converter device according to any one of claims 1 to 8.
  10. 　交流電源から入力される入力電流の電流値を取得することと、
    　前記入力電流の電流値が所定の電流値以下であるか否かを判定することと、
    　前記入力電流の電流値が所定の電流値以下であると判定した場合、前記交流電源から出力される交流電圧の半周期について、当該電流値の入力電流が流れると予想した一定の期間である第１期間を特定することと、
    　前記第１期間に基づいて、スイッチング素子をオン状態にする制御信号を特定することと、
    　を含む制御信号特定方法。     Obtaining the current value of the input current input from the AC power supply;
    Determining whether the current value of the input current is equal to or less than a predetermined current value;
    When it is determined that the current value of the input current is equal to or less than a predetermined current value, a half period of the AC voltage output from the AC power supply is a certain period in which the input current of the current value is expected to flow. Specifying one period,
    Specifying a control signal for turning on the switching element based on the first period;
    And a control signal specifying method.
  11. 　コンピュータに、
    　交流電源から入力される入力電流の電流値を取得することと、
    　前記入力電流の電流値が所定の電流値以下であるか否かを判定することと、
    　前記入力電流の電流値が所定の電流値以下であると判定した場合、前記交流電源から出力される交流電圧の半周期について、当該電流値の入力電流が流れると予想した一定の期間である第１期間を特定することと、
    　前記第１期間に基づいて、スイッチング素子をオン状態にする制御信号を特定することと、
    　を実行させるプログラム。     On the computer,
    Obtaining the current value of the input current input from the AC power supply;
    Determining whether the current value of the input current is equal to or less than a predetermined current value;
    When it is determined that the current value of the input current is equal to or less than a predetermined current value, a half period of the AC voltage output from the AC power supply is a certain period in which the input current of the current value is expected to flow. Specifying one period,
    Specifying a control signal for turning on the switching element based on the first period;
    A program that executes
PCT/JP2019/021030 2018-07-13 2019-05-28 Converter device, control signal specifying method and program WO2020012802A1 (en)

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