WO2019117241A1 - Alimentation électrique à découpage isolée - Google Patents

Alimentation électrique à découpage isolée Download PDF

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Publication number
WO2019117241A1
WO2019117241A1 PCT/JP2018/045851 JP2018045851W WO2019117241A1 WO 2019117241 A1 WO2019117241 A1 WO 2019117241A1 JP 2018045851 W JP2018045851 W JP 2018045851W WO 2019117241 A1 WO2019117241 A1 WO 2019117241A1
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WO
WIPO (PCT)
Prior art keywords
transformer
secondary coil
current
primary coil
coil
Prior art date
Application number
PCT/JP2018/045851
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English (en)
Japanese (ja)
Inventor
羽田　正二
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Ntn株式会社
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Ntn株式会社 filed Critical Ntn株式会社
Priority to KR1020207016745A priority Critical patent/KR102640341B1/ko
Publication of WO2019117241A1 publication Critical patent/WO2019117241A1/fr

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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0003—Details of control, feedback or regulation circuits
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac

Definitions

  • the present invention relates to a flyback-type isolated switching power supply capable of suppressing a surge voltage.
  • the high back electromotive force in the present specification, “electromotive force” and “back electromotive force” are used in the sense of voltage) in the primary coil of the transformer at the moment when the switching element is turned off A surge voltage is generated and applied to the switching element. For this reason, it has been necessary to use a high withstand voltage switching element or to provide a snubber circuit or the like for processing a back electromotive force.
  • the first aspect of the isolated switching power supply of the present invention which achieves the above object is as follows.
  • A a first transformer comprising a primary coil and a secondary coil;
  • B a switching element connected in series with the primary coil of the first transformer and on / off controlled by a control signal;
  • C A second transformer comprising a primary coil and a secondary coil, wherein the secondary coil of the first transformer and the primary coil of the second transformer are connected at a first connection point and a second connection point The second transformer connected in parallel, the second connection point being one end of the secondary coil of the second transformer and also the first output end;
  • D a first rectifying element connected so as to conduct current flowing from the second output end to the first connection point in the parallel connection and block current flowing in the opposite direction;
  • E a second rectifying element connected to conduct a current flowing from the second output end to the other end of the secondary coil of the second transformer and to block a current in the opposite direction;
  • the second aspect of the isolated switching power supply of the present invention is as
  • A a first transformer comprising a primary coil and a secondary coil
  • B a switching element connected in series with the primary coil of the first transformer and on / off controlled by a control signal
  • C A second transformer comprising a primary coil and a secondary coil, wherein the secondary coil of the first transformer and the primary coil of the second transformer are connected at a first connection point and a second connection point Connected in parallel by the second transformer, the second connection point being a first output end
  • D an inductor connected between one end of the secondary coil of the second transformer and the first output end
  • E a first rectifying element connected so as to conduct current flowing from the second output end to the first connection point in the parallel connection and block current flowing in the opposite direction
  • F a second rectifying element connected so as to conduct current flowing from the second output end to the other end of the secondary coil of the second transformer and block current flowing in the opposite direction
  • G having a third rectifying element connected to conduct current flowing from the second output end to one end of the secondary coil of the second
  • the present invention in an isolated switching power supply, it is possible to suppress the back electromotive force generated in the primary coil of the transformer when the switching element is off, that is, the surge voltage, and reduce the withstand voltage required for the switching element.
  • FIG. 1 is a diagram schematically showing a circuit configuration example of a first embodiment of the isolated switching power supply of the present invention.
  • FIGS. 2 (a) and 2 (b) schematically show the flow of current in the on period and the off period in the circuit of FIG. 1, respectively.
  • 3 (a) and 3 (b) are diagrams schematically showing an example of the potential relationship on the transformer secondary side of the on period and the off period in the circuit of FIG. 1, respectively.
  • FIG. 4 is a view schematically showing a circuit configuration example of a second embodiment of the isolated switching power supply of the present invention.
  • 5 (a) and 5 (b) are diagrams schematically showing the flow of current in the on period and the off period in the circuit of FIG. 4, respectively.
  • 6 (a) and 6 (b) are diagrams schematically showing an example of the potential relationship on the transformer secondary side of the on period and the off period in the circuit of FIG. 4, respectively.
  • the isolated switching power supply of the present invention will be described by way of an example of a DC / DC converter to which a DC voltage is input.
  • the isolated switching power supply according to the present invention functions similarly even if a voltage of any waveform is inputted, such as a pulsating current or a rectangular wave whose voltage fluctuates, or an alternating current other than a direct current having a constant voltage. It is a power converter capable of outputting a voltage.
  • FIG. 1 is a view schematically showing a circuit configuration example of a first embodiment of the isolated switching power supply of the present invention. is there.
  • This circuit is an isolated switching power supply in which the input side and the output side are electrically isolated by a transformer, and is based on a flyback method.
  • This switching power supply has a first transformer T1 and a second transformer T2.
  • the primary side and the secondary side are isolated by the transformer T1.
  • the transformer T1 includes a primary coil 1Np and a secondary coil 1Ns.
  • the transformer T2 includes a primary coil 2Np and a secondary coil 2Ns.
  • the polarities of the primary coil and the secondary coil are opposite to each other, and are the same as a general flyback type transformer. It is preferable that both the transformer T1 and the transformer T2 have the coupling degree as high as possible, that is, the primary coil and the secondary coil be closely coupled.
  • the winding start end of each coil is shown by a black circle.
  • the coil corresponds to the “roll start end” and the “roll end”
  • the coil end corresponds to the "roll end” and the “roll start end”, respectively.
  • the winding start end is referred to as one end, and the winding end is referred to as the other end.
  • An input voltage is applied between a pair of terminals consisting of a first input 1 and a second input 2.
  • One end of the primary coil 1 Np of the transformer T 1 is connected to the input end 1.
  • the input end 2 is the input side reference potential end.
  • the switching element Q is connected in series to the primary coil 1Np of the transformer T1.
  • the switching element Q is connected between the primary coil 1 Np and the input terminal 2.
  • the switching element Q has a control end, and the control end is on / off controlled to conduct or interrupt the current path including the primary coil 1Np.
  • the control end of the switching element Q is controlled by a control signal Vg.
  • the control signal Vg is, for example, a PWM signal having a pulse waveform of a predetermined frequency and a duty ratio.
  • the switching element Q is an n-channel MOSFET (hereinafter referred to as "FET Q"), one end is a drain, the other end is a source, and the control end is a gate.
  • FET Q n-channel MOSFET
  • the control signal Vg is a voltage signal.
  • an IGBT or a bipolar transistor can be used as a switching element other than the FET.
  • a positive output end p which is a first output end and a negative output end n which is a second output end are provided on the secondary side of the transformer T1.
  • a DC voltage is output between the positive electrode output end p and the negative electrode output end n.
  • the negative electrode output end n is the secondary side reference potential end.
  • An output voltage is applied to a load (not shown) connected between the positive electrode output end p and the negative electrode output end n, and an output current is supplied.
  • the primary coil 2Np of the transformer T2 is connected in parallel to the secondary coil 1Ns of the transformer T1.
  • one end of the secondary coil 1Ns of the transformer T1 and one end of the primary coil 2Np of the transformer T2 are connected at the first connection point a
  • the secondary coil of the transformer T1 is connected at the second connection point b.
  • the other end of 1 Ns is connected to the other end of the primary coil 2 Np of the transformer T2.
  • connection point b is also one end of the secondary coil 2Ns of the transformer T2, and the second connection point b is also the positive electrode output end p.
  • a first rectifying element D1 is connected between the first connection point a and the negative output end n.
  • the rectifying element D1 is connected so as to conduct the current flowing from the negative electrode output end n to the first connection point a and to cut off the current in the opposite direction. Therefore, when the rectifying element D1 is a diode, the diode D1 has an anode connected to the negative output terminal n and a cathode connected to the first connection point a.
  • a second rectifying element D2 is connected between the other end of the secondary coil 2Ns of the transformer T2 and the negative output end n.
  • the rectifying element D2 is connected so as to conduct current flowing from the negative electrode output end n to the other end of the secondary coil 2Ns and to cut off current in the opposite direction. Therefore, when the rectifying element D2 is, for example, a diode, the diode D2 has an anode connected to the negative output terminal n and a cathode connected to the other end of the secondary coil 2Ns.
  • the rectifying element such as a diode in this circuit preferably has a small forward voltage drop and operates at high speed.
  • straightening elements other than a diode the other element or circuit which has an equivalent rectification function can be used (the same may be said of each rectification
  • a smoothing capacitor C is connected between the positive electrode output end p and the negative electrode output end n.
  • control unit that generates a control signal Vg for the switching element Q.
  • the control unit detects an input voltage and / or an output voltage, determines a duty ratio of the control signal Vg based on the detected voltage, and generates a control signal Vg of a predetermined high frequency pulse based thereon.
  • a PWM IC can be used as a main part of such a control unit (the same applies to the following embodiments).
  • FIGS. 2 (a) and 2 (b) schematically show the flow of current during on and off periods, respectively (arrows indicate the direction of the current).
  • FIGS. 3A and 3B are diagrams schematically showing an example of the potential relationship between components on the secondary side of the transformer T1 in the on period and the off period, respectively.
  • the vertical direction corresponds to the level of the potential
  • the secondary side reference potential (the potential of the negative electrode output end n) is indicated by a thick line.
  • Voltages at both ends of the secondary coil 1Ns of the transformer T1, the primary coil 2Np and the secondary coil 2Ns of the transformer T2, and the capacitor C are indicated by double arrows.
  • the winding start end side is shown as a black circle (the same may be said of the electrical potential relationship figure of other embodiment).
  • the transformer T1 is excited by the flow of the current i1 through the primary coil 1Np, and predetermined magnetic energy is accumulated in the on period.
  • the voltage across the primary coil 2Np of the transformer T2 has the same magnitude as the electromotive force generated in the secondary coil 1Ns of the transformer T1.
  • the diode D2 conducts because it is forward biased, and the current i3 flows in the following path.
  • Current i3 negative electrode output terminal n ⁇ diode D2 ⁇ secondary coil 2Ns of transformer T2 ⁇ positive electrode output terminal p
  • the transformer T2 also has an effect of suppressing an inrush current to the capacitor C at the time of circuit start-up, like the external inductor in the forward system.
  • the transformer T2 is excited by the current i2 flowing through the primary coil 2Np and stores magnetic energy, and at the same time the current i3 flows through the secondary coil 2Ns by mutual induction and power is transferred.
  • the magnetic energy stored in the transformer T1 is smaller than that of the normal flyback system.
  • the reduced magnetic energy is transferred to the transformer T2.
  • the energy transferred to the transformer T2 is larger than the magnetic energy stored in the transformer T1.
  • the energy transferred to the transformer T2 becomes the magnetic energy stored in the transformer T2 and the output power (current i3) from the transformer T2.
  • this circuit is based on the flyback method, it can be said that it is similar to a forward type power supply that allows the external inductor to store magnetic energy and output power during the on period.
  • the inductance, the turns ratio, the number of turns, and the like of each of the coils of the transformers T1 and T2 it is possible to realize the transfer of larger energy by the transformer T2 during the on period.
  • the provision of the transformer T2 in this circuit reduces the amount of magnetic energy stored in the transformer T1 during the on period as compared to a normal flyback type power supply.
  • the back electromotive force or surge voltage generated in the primary coil 1Np also decreases.
  • a voltage obtained by adding an input voltage and a back electromotive force generated in the primary coil 1Np is applied to the switching element Q (between the drain and the source in the case of an FET). Therefore, in the present circuit, the withstand voltage required for the switching element Q is reduced, and the processing capacity of the snubber circuit can be reduced. Similarly, since the possibility of magnetic saturation of the transformer T1 is also reduced, the size of the transformer T1 can be reduced.
  • the magnetic energy stored in the on period in the transformer T2 is output as power in the off period. Further, when the current i5 flows, the magnetic energy accumulated in the on period in the transformer T1 is output as the power in the off period. In the preferred design, the magnetic energy stored in the transformer T1 is smaller than the magnetic energy stored in the transformer T2, so the current i5 is smaller than the current i4.
  • FIG. 4 is a diagram schematically showing a circuit configuration example of the second embodiment.
  • FIGS. 5 (a) and 5 (b) schematically show the flow of current during on and off periods, respectively.
  • two flyback transformers T1 and T2 are used.
  • the configuration of the primary side of the transformer T1 is the same as that of the first embodiment.
  • the inductor L is connected between one end of the secondary coil 2Ns of the transformer T2 and the second connection point b, that is, the positive electrode output end p.
  • a third rectifying element D3 is connected between one end of the secondary coil 2Ns of the transformer T2 and the negative output end n.
  • the rectifying element D3 is connected so as to conduct current flowing from the negative electrode output end n to one end of the secondary coil 2Ns, and to cut off current in the opposite direction. Therefore, when the rectifying element D3 is, for example, a diode, the diode D3 has an anode connected to the negative output terminal n and a cathode connected to one end of the secondary coil 2Ns.
  • FIGS. 5 (a) and 5 (b) schematically show the flow of current during on and off periods, respectively (arrows indicate the direction of the current).
  • FIGS. 6A and 6B are diagrams schematically showing an example of the potential relationship between components on the secondary side of the transformer T1 in the on period and the off period, respectively.
  • the transformer T2 in the on period is excited by the current i2 flowing through the primary coil 2Np and stores magnetic energy, and at the same time, the current i3 flows through the secondary coil 2Ns by mutual induction and the power transfer is also performed. It will be.
  • the inductor L is excited by the flow of the current i3 to accumulate magnetic energy, like the inductor in the normal forward system.
  • the inductor L also plays a role of suppressing inrush current to the capacitor C at the start of the circuit.
  • the diode D3 is cut off because it is reverse biased.
  • the other on-period operations are the same as in the first embodiment.
  • the flow of current during the on period in the second embodiment is the same as in the first embodiment. Also in the second embodiment, it is preferable to make the energy transferred to the transformer T2 and the inductor L larger than the magnetic energy stored in the transformer T1.
  • the magnetic energy stored in the on period in the transformer T2 is output as power in the off period. Further, when the current i5 flows, the magnetic energy accumulated in the on period in the transformer T1 is output as the power in the off period.
  • the diode D3 is forward biased and becomes conductive, and the current i6 flows in the following path as shown in FIG. 5 (b).
  • ⁇ Current i6 negative electrode output terminal n ⁇ diode D3 ⁇ inductor L ⁇ positive electrode output terminal p
  • the second embodiment there are more current paths during the off period than in the first embodiment. By distributing the current, the processing capacity required for each component is reduced, and as a result, the output can be increased.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Dc-Dc Converters (AREA)

Abstract

La présente invention supprime la force contre-électromotrice générée dans une bobine primaire d'un transformateur lorsqu'un élément de commutation est éteint dans une alimentation électrique à découpage isolée à transfert indirect. Cette alimentation électrique à découpage isolée comprend : un premier transformateur ; un élément de commutation qui est connecté en série à une bobine primaire du premier transformateur et mis en marche/arrêt par un signal de commande ; un second transformateur qui est pourvu d'une bobine primaire connectée en parallèle à une bobine secondaire du premier transformateur par un premier point de connexion et un second point de connexion, le second point de connexion étant une extrémité d'une bobine secondaire du second transformateur et étant une première extrémité de sortie ; un premier élément de redressement qui est connecté de manière à conduire un courant électrique circulant d'une seconde extrémité de sortie au premier point de connexion et à interrompre un courant électrique circulant dans la direction opposée ; un second élément de redressement qui est connecté de manière à conduire un courant électrique circulant de la seconde extrémité de sortie à l'autre extrémité de la bobine secondaire du second transformateur et à interrompre un courant électrique circulant dans la direction opposée ; et un condensateur entre les première et seconde extrémités de sortie.
PCT/JP2018/045851 2017-12-13 2018-12-13 Alimentation électrique à découpage isolée WO2019117241A1 (fr)

Priority Applications (1)

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JP2017238578A JP6945429B2 (ja) 2017-12-13 2017-12-13 絶縁型スイッチング電源
JP2017-238578 2017-12-13

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Citations (5)

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JPH11275860A (ja) * 1998-03-23 1999-10-08 Tdk Corp Ｄｃーｄｃコンバータ
WO2007040227A1 (fr) * 2005-10-03 2007-04-12 Sanken Electric Co., Ltd. Dispositif d'alimentation à découpage à sorties multiples
JP2010225568A (ja) * 2009-02-26 2010-10-07 Sanken Electric Co Ltd 電流均衡化装置及びその方法、ｌｅｄ照明器具、ｌｃｄｂ／ｌモジュール、ｌｃｄ表示機器
JP2015019537A (ja) * 2013-07-12 2015-01-29 株式会社東芝 スイッチング素子駆動電源回路
US20150326105A1 (en) * 2014-05-06 2015-11-12 National Tsing Hua University Pulsating Current Ripple Cancelling Circuit and Power Converting System Using the Same

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JPH0731150A (ja) 1993-07-09 1995-01-31 Shindengen Electric Mfg Co Ltd スイッチング電源装置
JP3261010B2 (ja) 1995-05-31 2002-02-25 オークマ株式会社 電力変換装置
JP2002010632A (ja) 2000-06-16 2002-01-11 Origin Electric Co Ltd Ａｃ／ｄｃコンバータ及びｄｃ−ｄｃコンバータ
JP4466089B2 (ja) 2004-01-29 2010-05-26 サンケン電気株式会社 力率改善回路
JP2007037297A (ja) 2005-07-27 2007-02-08 Sanken Electric Co Ltd 力率改善回路
CN101895211B (zh) * 2009-05-22 2012-12-19 群康科技(深圳)有限公司 可扩充交换式电源电路
JP6111970B2 (ja) * 2013-10-11 2017-04-12 株式会社デンソー 電力変換装置の制御方法
KR101589608B1 (ko) * 2014-01-06 2016-01-28 한국과학기술원 변압기 결합 재사용 스너버 회로

Patent Citations (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JPH11275860A (ja) * 1998-03-23 1999-10-08 Tdk Corp Ｄｃーｄｃコンバータ
WO2007040227A1 (fr) * 2005-10-03 2007-04-12 Sanken Electric Co., Ltd. Dispositif d'alimentation à découpage à sorties multiples
JP2010225568A (ja) * 2009-02-26 2010-10-07 Sanken Electric Co Ltd 電流均衡化装置及びその方法、ｌｅｄ照明器具、ｌｃｄｂ／ｌモジュール、ｌｃｄ表示機器
JP2015019537A (ja) * 2013-07-12 2015-01-29 株式会社東芝 スイッチング素子駆動電源回路
US20150326105A1 (en) * 2014-05-06 2015-11-12 National Tsing Hua University Pulsating Current Ripple Cancelling Circuit and Power Converting System Using the Same

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KR20200100057A (ko) 2020-08-25
JP6945429B2 (ja) 2021-10-06
KR102640341B1 (ko) 2024-02-23
JP2019106811A (ja) 2019-06-27

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