WO2018184234A1 - 主动笔、升压电路及其控制方法 - Google Patents

主动笔、升压电路及其控制方法 Download PDF

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Publication number
WO2018184234A1
WO2018184234A1 PCT/CN2017/079799 CN2017079799W WO2018184234A1 WO 2018184234 A1 WO2018184234 A1 WO 2018184234A1 CN 2017079799 W CN2017079799 W CN 2017079799W WO 2018184234 A1 WO2018184234 A1 WO 2018184234A1
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WO
WIPO (PCT)
Prior art keywords
switch
inductor
control
module
voltage
Prior art date
Application number
PCT/CN2017/079799
Other languages
English (en)
French (fr)
Inventor
李梦平
杜灿鸿
Original Assignee
深圳市汇顶科技股份有限公司
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by 深圳市汇顶科技股份有限公司 filed Critical 深圳市汇顶科技股份有限公司
Priority to CN201811575879.7A priority Critical patent/CN109634446B/zh
Priority to KR1020177034113A priority patent/KR102056530B1/ko
Priority to CN201780000367.5A priority patent/CN107438941B/zh
Priority to PCT/CN2017/079799 priority patent/WO2018184234A1/zh
Priority to EP17797041.5A priority patent/EP3404516B1/en
Priority to JP2018567835A priority patent/JP6573266B2/ja
Priority to US15/817,514 priority patent/US10261609B2/en
Publication of WO2018184234A1 publication Critical patent/WO2018184234A1/zh

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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
    • G—PHYSICS
    • G06—COMPUTING; CALCULATING OR COUNTING
    • G06F—ELECTRIC DIGITAL DATA PROCESSING
    • G06F3/00—Input arrangements for transferring data to be processed into a form capable of being handled by the computer; Output arrangements for transferring data from processing unit to output unit, e.g. interface arrangements
    • G06F3/01—Input arrangements or combined input and output arrangements for interaction between user and computer
    • G06F3/03—Arrangements for converting the position or the displacement of a member into a coded form
    • G06F3/033—Pointing devices displaced or positioned by the user, e.g. mice, trackballs, pens or joysticks; Accessories therefor
    • G06F3/0354—Pointing devices displaced or positioned by the user, e.g. mice, trackballs, pens or joysticks; Accessories therefor with detection of 2D relative movements between the device, or an operating part thereof, and a plane or surface, e.g. 2D mice, trackballs, pens or pucks
    • G06F3/03545—Pens or stylus
    • G—PHYSICS
    • G06—COMPUTING; CALCULATING OR COUNTING
    • G06F—ELECTRIC DIGITAL DATA PROCESSING
    • G06F3/00—Input arrangements for transferring data to be processed into a form capable of being handled by the computer; Output arrangements for transferring data from processing unit to output unit, e.g. interface arrangements
    • G06F3/01—Input arrangements or combined input and output arrangements for interaction between user and computer
    • G06F3/03—Arrangements for converting the position or the displacement of a member into a coded form
    • G06F3/033—Pointing devices displaced or positioned by the user, e.g. mice, trackballs, pens or joysticks; Accessories therefor
    • G06F3/038—Control and interface arrangements therefor, e.g. drivers or device-embedded control circuitry
    • G06F3/0383—Signal control means within the pointing device
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
    • H02M3/158—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load

Definitions

  • the present application relates to the field of booster circuit technology, and in particular, to an active pen, a booster circuit, and a control method thereof.
  • the pen tip 103 at the end of the pen tip 102 of the active pen 101 outputs a coded signal to realize communication between the active pen 101 and the terminal device 104 having the touch screen.
  • the coded signal output by the pen tip 103 is usually a high voltage signal to improve the active pen 101 and have The signal to noise ratio of the communication signal between the terminal devices 104 of the touch screen.
  • the scheme for realizing high voltage coding of the nib 103 is mainly LC resonance coding, and in the LC resonance circuit, the inductor and the capacitor form a series resonance circuit, and the active
  • the power supply in the pen 101 provides an energy input to the LC resonance circuit, and the LC resonance circuit outputs a high voltage coding signal to the pen tip; however, in the LC resonance circuit, when the inductance and the capacitance are selected, the circuit output high voltage frequency is fixed and unadjustable, so that The signal-to-noise ratio of the circuit cannot be fixed. At the same time, the output high-voltage amplitude is also fixed and cannot be adjusted, which can not reduce the system power consumption.
  • An object of some embodiments of the present application is to provide an active pen, a booster circuit, and a controller thereof.
  • the method by controlling the switch module, makes the output high voltage frequency of the boosting circuit adjustable, thereby improving the signal-to-noise ratio of the communication signal by using frequency hopping communication technology, and at the same time, the output high voltage amplitude of the boosting circuit is adjustable, thereby System power consumption can be reduced by adjusting the code voltage amplitude according to the application scenario.
  • the embodiment of the present application further provides an active pen, including: a pen body, a pen tip, a power supply, and the above-mentioned boosting circuit; the pen tip is disposed at one end of the pen body; the power supply and the boosting circuit are both disposed in the pen body; The other end is connected to the power supply, and the first end of the second switch is connected to the pen tip.
  • an active pen including: a pen body, a pen tip, a power supply, and the above-mentioned boosting circuit; the pen tip is disposed at one end of the pen body; the power supply and the boosting circuit are both disposed in the pen body; The other end is connected to the power supply, and the first end of the second switch is connected to the pen tip.
  • the embodiment of the present application further provides a control method of a booster circuit
  • the booster circuit includes an inductor, a switch module, a capacitor, and a control module
  • the switch module includes at least a first switch and a second switch, and the capacitor is connected in parallel with the second switch
  • the first end of the first switch is connected to one end of the inductor
  • the second end of the first switch is connected to the first end of the second switch
  • the second end of the second switch is grounded, and the other end of the inductor is used for connecting the power supply
  • the method includes: a first stage: controlling the first switch and the second switch to be in a closed state, so that the first end of the second switch outputs a low-level voltage signal; and the second stage: controlling the first switch to be in a closed state and second The switch is in an off state, causing the inductor and the capacitor to generate LC resonance and the voltage signal outputted by the first end of the second switch changes according to the change of the voltage signal of the first end of the first switch
  • the embodiment of the present application further provides a control method of a booster circuit, where the booster circuit includes an inductor, a switch module, a capacitor, and a control module; the switch module includes at least a first switch, a second switch, and a third switch, and the capacitor and the second The switch is connected in parallel; the first end of the first switch is connected to one end of the inductor, the second end of the first switch is connected to the first end of the second switch, the second end of the second switch is grounded; the other end of the inductor is used for connecting a power supply; a first end of the third switch is connected to the first end of the first switch, and a second end of the third switch is grounded; the control method comprises: a first stage: controlling the second switch and the third switch to be in a closed state, so that The first end of the second switch outputs a low-level voltage signal; wherein the first switch is in an open state or a closed state; and the second phase: controlling the second switch and the third switch to be in an open state, and
  • the switch module further includes a third switch; the first end of the third switch is connected to the first end of the first switch, and the second end of the third switch is grounded.
  • the third switch by setting the third switch, the power consumption of the circuit is reduced, and the system efficiency is improved.
  • each switch in the switch module is a field effect transistor; a control module is connected to the control terminal of each field effect transistor to control each field effect transistor.
  • This embodiment provides a composition of a switch group.
  • the first switch in the switch module is a diode
  • the other switches in the switch module are field effect transistors
  • a control module is connected to the control end of each field effect transistor to control each field effect transistor.
  • the switch module further includes a fourth switch connected to the other end of the inductor; and the other end of the inductor is connected to the power supply via the fourth switch;
  • the control method includes: before the first stage, including : an initial stage: controlling the second switch to be in a closed state, controlling the fourth switch to be in an open state, and causing the first end of the second switch to output a low-level voltage signal; wherein the first switch is in an open state or a closed state;
  • the fourth switch is also controlled to be in a closed state; in the second phase, the fourth switch is also controlled to be in a closed state; in the third phase, the fourth switch is also controlled to be in a closed state.
  • This embodiment provides a switch control method including a fourth switch.
  • FIG. 1 is a schematic diagram of an active pen control terminal device according to the prior art
  • FIG. 2 is a schematic diagram of a booster circuit according to a first embodiment of the present application.
  • FIG. 3 is a schematic waveform diagram of a normal operation of a booster circuit according to a first embodiment of the present application
  • FIG. 5 is a schematic diagram of a booster circuit according to a second embodiment of the present application.
  • FIG. 6 is a schematic diagram of a booster circuit according to a third embodiment of the present application.
  • FIG. 7 is a schematic diagram of a booster circuit according to a fourth embodiment of the present application.
  • FIG. 8 is a schematic diagram of a booster circuit including a fourth switch according to a fourth embodiment of the present application.
  • FIG. 9 is a schematic structural view of an active pen according to a fifth embodiment of the present application.
  • FIG. 10 is a flowchart of a control method of a booster circuit according to a sixth embodiment of the present application.
  • FIG. 11 is a flowchart of a control method of a booster circuit according to a seventh embodiment of the present application.
  • FIG. 12 is a flowchart of a control method of a booster circuit according to an eighth embodiment of the present application.
  • FIG. 13 is a flowchart of a control method of a booster circuit according to a ninth embodiment of the present application.
  • the first embodiment of the present application relates to a booster circuit applied to an active pen capable of outputting a high voltage coded signal to the tip of the active pen when the power supply of the active pen provides energy input.
  • the booster circuit 10 includes an inductor 1, a switch module, a capacitor 3, and a control module 4.
  • the switch module includes at least a first switch 21 and a second switch 22, and the capacitor 3 is connected in parallel with the second switch 22.
  • the first end of the first switch 21 is connected to one end of the inductor 1, and the second end of the first switch 21 is connected to the second end.
  • the first end of the second switch 22, the second end of the second switch 22 is grounded; the other end of the inductor 1 is used to connect the power supply and receive the power supply voltage.
  • the control module 4 is connected to the control end of the switch module; the control module 4 is configured to control the state of each switch in the switch module such that the first end of the second switch 22 outputs a voltage signal of a preset frequency and amplitude. It should be noted that, referring to FIG. 2, the first end of the second switch 22 outputs a voltage signal of a preset frequency and amplitude, that is, a voltage signal outputted from point A in FIG. 2, and point A is connected to the active pen tip.
  • control module 4 includes a control circuit 41 and a driving circuit 42.
  • the driving circuit 42 is connected to the control end of the switch module for driving the switch module.
  • the control circuit 41 is connected to the driving circuit 42 and is used to control the driving circuit 42.
  • the driving mode is such that the driving circuit 42 can generate a square wave of a certain duty ratio to control the switching module.
  • the driving circuit 42 and the control circuit 41 can be integrated in one chip, and the square wave is directly outputted at the IO port of the chip; however, the control circuit 41 and the driving circuit 42 can also be separately disposed through the driving circuit 42. Output square wave.
  • each switch in the switch module may be a field effect transistor, that is, the first switch 21 and the second switch 22 are both field effect transistors. Since the field effect transistor itself has a parasitic capacitance, the capacitor 3 may be a parasitic capacitance of the second switch 22 (field effect transistor) itself (this embodiment takes a field effect transistor as an example); or, the booster circuit 10 can be set.
  • a solid capacitor connected in parallel with the second switch 22, at this time, the capacitor 3 is the total capacitance of the solid capacitor connected in parallel with the parasitic capacitance of the second switch 22 (field effect transistor) itself.
  • the control module 4 is connected to the control terminal of each field effect transistor to control each field effect transistor, that is, the driving circuit 42 of the control module 4 is respectively connected to the first switch 21 (field effect transistor) and the second switch 22 (field)
  • the control terminal of the effect transistor outputs a drive signal to respectively control the first switch 21 and the second switch 22.
  • FIG. 3 the schematic diagram of the normal working waveform of the boosting circuit scheme is shown in FIG. 3, and FIG. 4 is an enlarged view of the waveform in one cycle of the normal working of the scheme.
  • the working principle of the boosting circuit scheme is described below by taking one cycle of normal operation as an example. Please refer to FIG. 4 for the switching state of each phase in a cycle, and the first phase, the second phase, and the third phase are sequentially carried out.
  • the first stage the control circuit 41 controls the driving circuit 42 to issue a driving signal, and controls both the first switch 21 and the second switch 22 to be turned on, that is, the first switch 21 and the second switch 22 are both controlled to be in a closed state; points A and B The points are grounded. At this time, the power supply charges the inductor 1, and the A point outputs a low-level voltage signal.
  • the second stage the control circuit 41 controls the driving circuit 42 to send a driving signal to control the second switch 22 to be turned off, that is, to control the first switch 21 to be in the closed state and the second switch 22 to be in the off state; at this time, the inductor 1 and the capacitor 3 constitutes the LC resonant circuit, the output voltage of point A is consistent with the voltage of point B, followed by LC resonance oscillation;
  • the third stage the control circuit 41 controls the driving circuit 42 to issue a driving signal, and controls the first switch 21 to be turned off, that is, controls the first switch 21 and the second switch 22 to be in an off state; generally, one quarter of the LC resonance is selected.
  • the first switch 21 is turned off at the time of the cycle. At this time, the LC resonance rising voltage reaches the maximum value, and due to the presence of the capacitor 3, the voltage at the point A can be maintained at the voltage value when the first switch 21 is turned off.
  • the time when the second switch 22 is turned on determines the maximum charging current of the inductor 1
  • the conduction time of the second switch 22 is The duration of the first phase to the second phase
  • the maximum value of the charging current of the inductor 1 determines the maximum value of the rising voltage of the LC resonant circuit
  • the time point at which the first switch 21 is turned off determines the final output high voltage amplitude of the point A
  • the second switch When the second switch 22 is turned on, the A point outputs a low voltage signal, and when the second switch 22 is turned off, the A point outputs a high voltage, and the switching frequency of the second switch 22 determines the frequency at which the A point outputs the high voltage; therefore, the first switch 21 is passed.
  • the control of the switching timing of the second switch 22 can realize the simultaneous regulation of the output high voltage amplitude and frequency of the A point, that is, the point A can output the voltage signal of the preset frequency
  • the present embodiment controls the switch module to make the boost circuit
  • the output high-voltage frequency is adjustable, so that the frequency-to-noise ratio of the communication signal can be improved by using frequency hopping communication technology, and the output high voltage amplitude of the boosting circuit can be adjusted, thereby reducing the system by adjusting the amplitude of the coding voltage according to the application scenario. Power consumption.
  • the second embodiment of the present application relates to a boosting circuit.
  • the present embodiment is substantially the same as the first embodiment.
  • the main difference is that in the first embodiment, the first switch 21 is a field effect transistor; In the example, the first switch 21 is a diode, please refer to FIG. 5.
  • the first switch 21 in the switch module is a diode, and the other switches are field effect transistors;
  • the control module 4 is connected to the control end of each field effect transistor to control each field effect transistor, that is, the control module.
  • the drive circuit 42 of 4 is connected to the control terminal of the second switch 22 (field effect transistor) to emit a drive signal to control the second switch 22.
  • the working principle of the boosting circuit scheme is as follows (the following table shows the switching states of each stage):
  • the first stage the control circuit 41 controls the driving circuit 42 to send a driving signal to control the second switch 22 to be turned on, that is, to control the second switch 22 to be in a closed state; the point A is grounded, and the voltage at point B is slightly higher than the voltage at point A, The first switch 21 (diode) is turned on, the power supply supplies the inductor 1 , and the A point outputs a low-level voltage signal;
  • the second stage the control circuit 41 controls the driving circuit 42 to issue a driving signal, and controls the second switch 22 to be turned off, that is, controls the second switch 22 to be in an off state;
  • the capacitor 3 when the inductor 1 and the second switch 22 are disconnected constitutes an LC
  • the voltage at point B of the first quarter cycle of the LC resonance is in a rising state, the voltage at point B is higher than the voltage at point A, the first switch 21 (diode) is in an on state, and the output voltage at point A follows the voltage at point B;
  • the third stage after the quarter cycle of the LC resonance, the voltage at point B is in a falling state, the voltage at point B is lower than the voltage at point A, the first switch 21 (diode) is turned off in the off state, and the output voltage clamp at point A is The bit is the voltage value of point B when the first switch 21 (diode) is turned off; although the point B starts to fall from the maximum value of the LC resonance rising voltage, the diode is reversely turned off, but the diode is completely turned off due to the existence of the junction capacitance. It still takes a certain time.
  • the resonant voltage at point B will drop, and the output voltage at point A will follow the voltage at point B, so that the clamp output voltage at point A is slightly lower than the maximum rise in LC resonance voltage.
  • the value, that is, the output high voltage clamp of the booster circuit is located at a value slightly lower than the maximum voltage of the LC resonant circuit.
  • the present embodiment uses a diode as the first switch, and the diode has a forward conduction and a reverse cutoff characteristic, so that it is not necessary to issue a drive signal for control.
  • the third embodiment of the present application relates to a booster circuit.
  • the present embodiment is an improvement on the basis of the second embodiment.
  • the main improvement is that, in this embodiment, referring to FIG. 6, the switch module further includes a third Switch 23.
  • the first end of the third switch 23 is connected to the first end of the first switch 21, and the second end of the third switch 23 is grounded.
  • the working principle of the boosting circuit scheme is as follows (the following table shows the switching states of each stage):
  • the first stage the control circuit 41 controls the driving circuit 42 to send a driving signal, and controls the second switch 22 and the third switch 23 to be simultaneously turned on, that is, controls the second switch 22 and the third switch 23 to be in a closed state; points A and B The points are grounded, the first switch 21 (diode) is turned off, and the point A outputs a low level voltage signal;
  • the second stage the control circuit 41 controls the driving circuit 42 to send a driving signal, and controls the second switch 22 and the third switch 23 to be simultaneously turned off, that is, the second switch 22 and the third switch 23 are both controlled to be in an off state;
  • the capacitor 3 when the second switch 22 is turned off and the capacitor 3 when the third switch 23 is turned off constitute an LC resonant circuit, the voltage of the first quarter cycle of the LC resonance is rising, and the voltage of the B point is higher than the voltage of the point A.
  • the first switch 21 (diode) is in an on state, and the output voltage of point A follows the voltage at point B;
  • the third stage after the quarter cycle of the LC resonance, the voltage at point B is in a falling state, the voltage at point B is lower than the voltage at point A, the first switch 21 (diode) is turned off in the off state, and the output voltage clamp at point A is The bit is the voltage value of point B when the first switch 21 (diode) is turned off.
  • the fourth embodiment of the present application relates to a booster circuit.
  • the present embodiment is an improvement based on the second embodiment.
  • the main improvement is that, in this embodiment, referring to FIG. 7, the switch module further includes a fourth Switch 24.
  • the other end of the inductor 1 is connected to the power supply through the fourth switch 24 to receive the power supply voltage.
  • the working principle of the boosting circuit scheme in this embodiment is as follows (the following table shows the switching states of each stage):
  • the control circuit 41 controls the driving circuit 42 to send a driving signal, controls the second switch 22 to be turned on, and the fourth switch 24 is turned off, that is, the second switch 22 is controlled to be in a closed state, and the fourth switch 24 is in an off state;
  • the power supply and the inductor 1 are disconnected, the circuit has no energy input, the point A is grounded, the point B generates a negative voltage due to the first law, the first switch 21 (diode) is turned off in the off state, and the point A outputs a low level voltage signal;
  • the first stage the control circuit 41 controls the driving circuit 42 to send a driving signal, and controls the fourth switch 24 to be turned on, that is, controls the second switch 22 and the fourth switch 24 to be in a closed state;
  • Sense 1 charging point A is grounded, point B voltage is higher than point A voltage, first switch 21 (diode) is in conduction state, point A outputs low level voltage signal;
  • the second stage the control circuit 41 controls the driving circuit 42 to issue a driving signal, and controls the second switch 22 to be turned off, that is, the second switch 22 is controlled to be in an off state, and the fourth switch 24 is in a closed state; the inductor 1 and the second switch 22 are The capacitor 3 at the time of shutdown constitutes an LC resonant circuit.
  • the voltage at point B of the first quarter cycle of the LC resonance is in a rising state, the voltage at point B is higher than the voltage at point A, and the first switch 21 (diode) is in an on state, point A.
  • the output voltage follows the voltage at point B;
  • the voltage at point B is in a falling state, the voltage at point B is lower than the voltage at point A, the first switch 21 (diode) is turned off in the off state, and the output voltage clamp at point A is The bit is the voltage value of point B when the first switch 21 (diode) is turned off.
  • the second switch 22 is used to simultaneously adjust the amplitude and frequency of the output high voltage. If the output frequency requirement is higher, the second switch 22 needs to be switched faster, correspondingly, the output voltage of the A point. The smaller the amplitude (the faster the second switch 22 switches, the shorter the on-time of the second switch 22, and the shorter the charging time for the inductor).
  • the fourth switch 24 is added. When the fourth switch 24 is turned off, the power supply and the inductor 1 are disconnected, and the circuit has no energy input; when the fourth switch 24 is turned on, the power supply and the inductor 1 are connected as a circuit. Provide energy input to charge the inductor.
  • the fourth switch 24 is added to control the maximum charging current of the inductor 1 by controlling the charging time of the inductor, thereby controlling the highest rising voltage of the LC resonant circuit to regulate the output high voltage amplitude of the point A, that is, by controlling the fourth switch 24 to regulate the output high voltage amplitude of point A.
  • this embodiment can also be used as an improvement on the basis of the third embodiment.
  • the fourth switch 24 is connected to the other end of the inductor 1, and the inductor 1 receives the power supply voltage through the fourth switch 24.
  • the working principle of the boosting circuit scheme in this embodiment is as follows (the following table shows the switching states of each stage):
  • the control circuit 41 controls the driving circuit 42 to issue a driving signal, and controls the second switch 22 and the third switch 23 to be simultaneously turned on, and the fourth switch 24 is turned off, that is, the second switch 22 and the third switch 23 are both controlled to be closed.
  • the fourth switch 24 is in the off state; the power supply and the inductor 1 are disconnected, the circuit has no energy input, the A point and the B point are both grounded, the first switch 21 (diode) is in the off state, and the A point output is low. Voltage signal
  • the first stage the control circuit 41 controls the driving circuit 42 to send a driving signal, and controls the fourth switch 24 to be turned on, that is, controls the second switch 22, the third switch 23, and the fourth switch to be in a closed state; the power supply supplies the inductor 1 , point A and point B are grounded, the first switch 21 (diode) is in the off state, and point A outputs a low level voltage signal;
  • the second stage the control circuit 41 controls the driving circuit 42 to issue a driving signal, and controls the second switch 22 and the third switch 23 to be simultaneously turned off, that is, the second switch 22 and the third switch 23 are both controlled to be in an off state and the fourth switch 24 is in a closed state;
  • the capacitor 3 when the inductor 1 and the second switch 22 are turned off and the capacitor 3 when the third switch 23 is turned off constitute an LC resonant circuit, the first quarter cycle B of the LC resonance
  • the point voltage is in a rising state, the voltage at point B is higher than the voltage at point A, the first switch 21 (diode) is in an on state, and the output voltage at point A follows the voltage at point B;
  • the voltage at point B is in a falling state, the voltage at point B is lower than the voltage at point A, the first switch 21 (diode) is turned off in the off state, and the output voltage clamp at point A is The bit is the voltage value of point B when the first switch 21 (diode) is turned off.
  • the fourth switch 24 when the fourth switch 24 is turned off, the power supply and the inductor 1 are disconnected, and the circuit has no energy input; when the fourth switch 24 is turned on, the power supply and the inductor 1 are connected to provide energy input to the circuit to charge the inductor.
  • the fourth switch 24 is added to control the maximum charging current of the inductor 1 by controlling the charging time of the inductor, thereby controlling the highest rising voltage of the LC resonant circuit to regulate the output high voltage amplitude of the point A, that is, by controlling the fourth switch 24 to regulate the output high voltage amplitude of point A.
  • the present embodiment realizes the regulation of the output high-voltage frequency by the timing control of the second switch, and controls the fourth switch timing to achieve the regulation of the output high-voltage amplitude. That is, in the present embodiment, independent control of the amplitude and frequency of the output high voltage is realized, so that the amplitude and frequency of the output high voltage can be arbitrarily adjusted as needed. It should be noted that the present embodiment can also be used as an improvement on the basis of the first embodiment, and the same technical effects can be achieved.
  • the fifth embodiment of the present application relates to an active pen for writing or inputting instructions to a terminal device having a touch screen, such as a computer screen, a mobile device, a drawing board, etc., to implement human-computer interaction.
  • the active pen 301 includes a pen body 302, a pen tip 303, a power supply 304, and the booster circuit 10 of any of the first to fourth embodiments.
  • the pen tip 303 is disposed at one end of the pen body 302; the power supply 304 and the booster circuit 10 are both disposed in the pen body 302; the other end of the inductor 1 is connected to the power supply 304, and the first end of the second switch 22 Connected to the pen tip 303 and convert the voltage signal of the preset frequency and amplitude through the pen tip 303 It is transmitted for the coding signal.
  • this embodiment provides an active pen that applies a booster circuit.
  • the sixth embodiment of the present application relates to a control method of a booster circuit, which is applied to the booster circuit 10 described above, please refer to FIG. 5.
  • FIG. 1 A specific flowchart of the control method of the booster circuit is shown in FIG.
  • Step 101 The first stage: controlling both the first switch and the second switch to be in a closed state.
  • control circuit 41 controls the driving circuit 42 to issue a driving signal to control the second switch 22 to be in a closed state; the point A is grounded, and the voltage at point B is slightly higher than the voltage at point A, and at this time, the first switch 21 (diode) is turned on.
  • the power supply charges the inductor 1 so that the first end of the second switch 22 outputs a low-level voltage signal.
  • the first switch 21 is a diode. Due to the characteristics of the diode being forward-conducting and reverse-cutting, the opening and closing state thereof changes according to the change of the opening and closing state of the second switch 22, that is, the control circuit 41 controls the second.
  • the opening and closing of the switch 22 causes a change in the opening and closing state of the first switch 21 (diode); therefore, when the first switch 21 is a component such as a diode (having a forward conduction, a reverse cutoff characteristic), the control circuit
  • the control thereof can be understood as the control circuit 41 indirectly controlling the first switch 21 by controlling the second switch 22, that is, the control circuit 41 controls it indirectly; and when the first switch 21 is a component having a control terminal, For example, when it is a field effect transistor, the control circuit 41 controls it to be directly controlled (ie, the control circuit 41 directly transmits a signal indicating the opening and closing to the control terminal of the first switch 21).
  • Step 102 the second stage: controlling the first switch to be in a closed state and the second switch to be in an open state.
  • control circuit 41 controls the driving circuit 42 to issue a driving signal to control the second switch 22 to be in an off state; at this time, the capacitor 3 when the inductor 1 is disconnected from the second switch 22 constitutes an LC resonant power.
  • the circuit generates LC resonance.
  • the voltage at point B of the first quarter cycle of the LC resonance is rising, the voltage at point B is higher than the voltage at point A, and the first switch 21 (diode) is in an on state.
  • the second switch 22 The voltage signal outputted by the first end of the first signal follows the voltage signal of the first end of the first switch (ie, point B).
  • Step 103 The third stage: controlling both the first switch and the second switch to be in an off state.
  • the control circuit 41 controls the drive circuit 42 to issue a drive signal, controls the second switch 22 to be turned off, the voltage at point B is in a falling state, and the voltage at point B is lower than the voltage at point A,
  • a switch 21 (diode) reverse cut-off is in an off state, due to the presence of the capacitor 3, the voltage signal of the first end of the first switch 21 (diode) is clamped, and the voltage signal outputted by the first end of the second switch 22
  • the voltage value at the time when the first switch 21 (diode) is turned off is maintained, that is, the first end of the second switch 22 outputs a voltage signal of a preset frequency and amplitude.
  • the time when the second switch 22 is turned on determines the maximum charging current of the inductor 1
  • the conduction time of the second switch 22 is The duration of the first phase to the second phase
  • the maximum value of the charging current of the inductor 1 determines the maximum value of the rising voltage of the LC resonant circuit
  • the time point at which the first switch 21 is turned off determines the final output high voltage amplitude of the point A
  • the second switch When the second switch 22 is turned on, the A point outputs a low voltage signal, and when the second switch 22 is turned off, the A point outputs a high voltage, and the switching frequency of the second switch 22 determines the frequency at which the A point outputs the high voltage; therefore, the first switch 21 is passed.
  • the control of the switching timing of the second switch 22 can realize the simultaneous regulation of the output high voltage amplitude and frequency of the A point, that is, the point A can output the voltage signal of the preset frequency
  • the embodiment is a method embodiment corresponding to the first embodiment and the second embodiment, and the embodiment can be implemented in cooperation with the first embodiment and the second embodiment.
  • the related technical details mentioned in the first embodiment and the second embodiment are still effective in this embodiment, and are not described herein again in order to reduce repetition.
  • the related technical details mentioned in this embodiment can also be applied to the first embodiment and the second embodiment. In the example.
  • the present embodiment controls the switching module to make the output high voltage frequency of the boosting circuit adjustable, thereby improving the signal-to-noise ratio of the communication signal by using frequency hopping communication technology, and simultaneously making the boosting
  • the output high voltage amplitude of the circuit is adjustable, which can reduce the system power consumption by adjusting the coding voltage amplitude according to the application scenario.
  • the seventh embodiment of the present application relates to a control method of a booster circuit.
  • the present embodiment is an improvement based on the sixth embodiment.
  • the main improvement is that when the switch module is added with the fourth switch, the Four-switch control.
  • the switch module further includes a fourth switch 24; the fourth switch 24 is connected to the other end of the inductor 1, and the other end of the inductor 1 is connected to the power supply through the fourth switch 24.
  • FIG. 1 A specific flowchart of the control method of the booster circuit is shown in FIG.
  • Step 201 Initial stage: controlling the second switch to be in a closed state, and controlling the fourth switch to be in an open state; wherein the first switch is in an open or closed state.
  • control circuit 41 controls the drive circuit 42 to issue a drive signal, controls the second switch 22 to be in a closed state, and the fourth switch 24 is in an open state.
  • the circuit has no energy input, the A point is grounded, and the B point is due to the time.
  • the law generates a negative voltage, the first switch 21 (diode) is reversely turned off in an off state, and the first end of the second switch 22 outputs a low level voltage signal.
  • the first switch 21 is a field effect transistor, it may be in an open or closed state.
  • the first switch 21 is in an off state, which can reduce power consumption of the circuit.
  • Step 202 The first stage: controlling the first switch, the second switch and the fourth switch to be in a closed state.
  • control circuit 41 controls the drive circuit 42 to issue a drive signal to control the second switch.
  • the off 22 and the fourth switch 24 are both in a closed state; the power supply charges the inductor 1 , the point A is grounded, the voltage at point B is higher than the voltage at point A, the first switch 21 (diode) is in an on state, and the second switch 22 is One end outputs a low level voltage signal.
  • Step 203 The second stage: controlling the first switch and the fourth switch to be in a closed state and the second switch to be in an open state.
  • control circuit 41 controls the driving circuit 42 to issue a driving signal, and controls the fourth switch 24 to be in a closed state and the second switch 22 to be in an open state; the capacitor 3 when the inductor 1 and the second switch 22 are turned off constitute an LC resonant circuit.
  • the voltage of point B of the first quarter cycle of the LC resonance is rising, the voltage of point B is higher than the voltage of point A, the first switch 21 (diode) is in an on state, and the output voltage of the first end of the second switch 22 follows B.
  • Step 204 The third stage: controlling the first switch and the second switch to be in an off state and the fourth switch to be in a closed state.
  • the control circuit 41 controls the drive circuit 42 to issue a drive signal, controls the second switch 22 to be in an open state, and the fourth switch 24 is in a closed state, and the voltage at point B is in a falling state.
  • the voltage at point B is lower than the voltage at point A, and the first switch 21 (diode) is turned off in the off state.
  • the output voltage signal of the first end of the second switch 22 is clamped to the voltage when the first switch 21 is turned off.
  • the value, that is, the first end of the second switch 22 outputs a voltage signal of a predetermined frequency and amplitude.
  • the fourth switch 24 is added. When the fourth switch 24 is turned off, the power supply and the inductor 1 are disconnected, and the circuit has no energy input; when the fourth switch 24 is turned on, the power supply and the inductor 1 are connected to provide energy for the circuit. Input to charge the inductor.
  • the fourth switch 24 is added to control the maximum charging current of the inductor 1 by controlling the charging time of the inductor, thereby controlling the highest value of the rising voltage of the LC resonant circuit, The output high voltage amplitude of point A is adjusted, that is, the output high voltage amplitude of point A is controlled by controlling the fourth switch 24.
  • the present embodiment can be implemented in cooperation with the fourth embodiment.
  • the technical details mentioned in the fourth embodiment are still effective in this embodiment.
  • the technical effects that can be achieved in the fourth embodiment can also be implemented in the embodiment. To reduce the repetition, details are not described herein again. Accordingly, the related art details mentioned in the embodiment can also be applied to the fourth embodiment.
  • the present embodiment realizes independent regulation of the output high-voltage frequency by timing control of the second switch, and achieves independent regulation of the output high-voltage amplitude by controlling the fourth switch timing.
  • the eighth embodiment of the present application relates to a control method of a booster circuit, which is applied to the booster circuit 10 described above, please refer to FIG. 6.
  • FIG. 1 A specific flowchart of the control method of the booster circuit is shown in FIG.
  • Step 301 the first stage: controlling the second switch and the third switch to be in a closed state; wherein the first switch is in an open or closed state.
  • control circuit 41 controls the driving circuit 42 to issue a driving signal, and controls the second switch 22 and the third switch 23 to be in a closed state; at this time, both points A and B are grounded, and the first switch 21 (diode) is turned off.
  • the first end of the second switch 22 outputs a low level voltage signal.
  • the first switch 21 when the first switch 21 is a field effect transistor, the first switch 21 may be in an open or closed state. Preferably, the first switch 21 is in an off state, which can reduce power consumption of the circuit.
  • the control circuit 41 controls it to be directly controlled (ie, the control circuit 41 directly transmits a signal indicating the opening and closing) To the control terminal of the first switch 21; and when the first switch 21 is a diode, due to the characteristics of the diode being forward-conducting and reverse-cutting, the opening and closing state thereof is opened and closed with the second switch 22 and the third switch 23.
  • the change of the state changes that is, the control circuit 41 controls the opening and closing of the second switch 22 and the third switch 23 to cause a change in the opening and closing state of the first switch 21 (diode); therefore, when the first switch 21 is, for example, a diode
  • the control of the control circuit 41 can be understood as the control circuit 41 indirectly controlling the first switch 21 by controlling the second switch 22 and the third switch 23, that is, the control The control of the first switch 21 by the circuit 41 is an indirect control.
  • Step 302 The second stage: controlling the second switch and the third switch to be in an off state, and the first switch is in a closed state.
  • control circuit 41 controls the driving circuit 42 to emit a driving signal, and controls the second switch 22 and the third switch 23 to be in an off state; the capacitor 3 when the inductor 1 is disconnected from the second switch 22 and the third switch 23 constitutes an LC.
  • the voltage at point B is higher than the voltage at point A.
  • the first switch 21 (diode) is in an on state, and the output voltage signal of the first end of the second switch 22 rises with resonance in the first quarter cycle of the LC resonance. That is, the voltage signal outputted by the first end of the second switch 22 rises following the rise of the voltage signal of the first end of the first switch 21.
  • Step 303 the third stage: controlling the first switch, the second switch and the third switch to be in an off state.
  • the control circuit 41 controls the driving circuit 42 to issue a driving signal, and controls the second switch 22 and the third switch 23 to be in an off state; at this time, the voltage at point B is lower than A.
  • Point voltage the first switch 21 (diode) reverse cutoff is in an off state, the voltage of the first end of the first switch 21 (diode) is clamped, and the output voltage signal of the first end of the second switch 22 is clamped to a voltage value when the switch 21 is turned off, that is, the first end of the second switch 22 outputs a preset frequency and amplitude Degree of voltage signal.
  • the time when the second switch 22 is turned on determines the maximum charging current of the inductor 1
  • the conduction time of the second switch 22 is The duration of the first phase to the second phase
  • the maximum value of the charging current of the inductor 1 determines the maximum value of the rising voltage of the LC resonant circuit
  • the time point at which the first switch 21 is turned off determines the final output high voltage amplitude of the point A
  • the second switch When the second switch 22 is turned on, the A point outputs a low voltage signal, and when the second switch 22 is turned off, the A point outputs a high voltage, and the switching frequency of the second switch 22 determines the frequency at which the A point outputs the high voltage; therefore, the first switch 21 is passed.
  • the control of the switching timing of the second switch 22 can realize the simultaneous regulation of the output high voltage amplitude and frequency of the A point, that is, the point A can output the voltage signal of the preset frequency
  • the present embodiment can be implemented in cooperation with the third embodiment.
  • the technical details mentioned in the third embodiment are still effective in this embodiment, and the technical effects that can be achieved in the third embodiment can also be implemented in this embodiment. To reduce repetition, details are not described herein again. Accordingly, the related art details mentioned in the embodiment can also be applied to the third embodiment.
  • the present embodiment provides a control method when the third switch is added, which reduces the power consumption of the circuit and improves the system efficiency.
  • the ninth embodiment of the present application relates to a control method of a booster circuit.
  • the present embodiment is an improvement on the basis of the eighth embodiment.
  • the main improvement is that when the fourth switch is added to the switch module, the Four-switch control.
  • the switch module further includes a fourth switch 24 connected to the other end of the inductor 1 ; the inductor 1 receives the power supply voltage through the fourth switch 24 .
  • FIG. 1 A specific flowchart of the control method of the booster circuit is shown in FIG.
  • Step 401 an initial stage: controlling the fourth switch to be in an off state and the second switch and the third switch are in a closed state; wherein the first switch 21 is in an open or closed state.
  • control circuit 41 controls the driving circuit 42 to issue a driving signal, and controls the fourth switch 24 to be in an off state and the second switch 22 and the third switch 23 are both in a closed state; at this time, the circuit has no energy input, point A and Point B is grounded, the first switch 21 (diode) is in an off state, and the first end of the second switch 22 outputs a low level voltage signal.
  • the first switch 21 when the first switch 21 is a field effect transistor, the first switch 21 may be in an open or closed state. Preferably, the first switch 21 is in an off state, which can reduce power consumption of the circuit.
  • Step 402 The first stage: controlling the second switch, the third switch and the fourth switch to be in a closed state; wherein the first switch is in an open or closed state.
  • the control circuit 41 controls the driving circuit 42 to issue a driving signal, and controls the second switch 22, the third switch 23, and the fourth switch 24 to be in a closed state; the power supply source charges the inductor 1, and both the A point and the B point are grounded.
  • the first switch 21 (diode) is in an off state, at which time the first end of the second switch 22 outputs a low level voltage signal. It should be noted that when the first switch 21 is a field effect transistor, the first switch 21 may be in an open or closed state. Preferably, the first switch 21 is in an off state, which can reduce power consumption of the circuit.
  • Step 403 The second stage: controlling the second switch and the third switch to be in an off state, and controlling the first switch and the fourth switch to be in a closed state.
  • control circuit 41 controls the driving circuit 42 to issue a driving signal, and controls the second switch 22 and the third switch 23 to be in an off state, and controls the fourth switch 24 to be in a closed state; the inductor 1 and the second switch 22 and the third
  • the capacitor 3 when the switch 23 is turned off constitutes an LC resonance circuit, the voltage of the first quarter cycle of the LC resonance is rising, the voltage of the B point is higher than the voltage of the point A, the first switch 21 (diode) is in an on state, at this time, the first terminal output voltage signal of the second switch 22 rises with resonance, that is, the voltage signal outputted by the first end of the second switch 22 follows the first switch 21 The voltage signal at the terminal rises and rises.
  • Step 404 The third stage: controlling the first switch, the second switch, and the third switch to be in an off state, and the fourth switch is in a closed state.
  • the control circuit 41 controls the drive circuit 42 to issue a drive signal, and controls the second switch 22 and the third switch 23 to be in an open state, and the fourth switch 24 is in a closed state;
  • the voltage at point B is in a falling state, the voltage at point B is lower than the voltage at point A, the first switch 21 (diode) is turned off in the off state, and the voltage at the first end of the first switch 21 (diode) is clamped.
  • the first end output voltage signal of the second switch 22 is clamped to a voltage value when the first switch 21 is turned off, that is, the first end of the second switch 22 outputs a voltage signal of a preset frequency and amplitude.
  • the fourth switch 24 when the fourth switch 24 is turned off, the power supply and the inductor 1 are disconnected, and the circuit has no energy input; when the fourth switch 24 is turned on, the power supply and the inductor 1 are connected to provide energy input to the circuit to charge the inductor.
  • the fourth switch 24 is added to control the maximum charging current of the inductor 1 by controlling the charging time of the inductor, thereby controlling the highest rising voltage of the LC resonant circuit to regulate the output high voltage amplitude of the point A, that is, by controlling the fourth switch 24 to regulate the output high voltage amplitude of point A.
  • the present embodiment can be implemented in cooperation with the fourth embodiment.
  • the technical details mentioned in the fourth embodiment are still effective in this embodiment.
  • the technical effects that can be achieved in the fourth embodiment can also be implemented in the embodiment. To reduce the repetition, details are not described herein again. Accordingly, the related art details mentioned in the embodiment can also be applied to the fourth embodiment.
  • the embodiment achieves the pair by controlling the timing of the second switch. Independent regulation of the output high-voltage frequency, through the control of the fourth switch timing, to achieve independent control of the output high-voltage amplitude.

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Abstract

一种主动笔、升压电路及其控制方法。升压电路（10），包括：电感（1）、开关模块、电容（3）以及控制模块（4）；所述开关模块至少包括第一开关（21）与第二开关（22），所述电容（3）与所述第二开关（22）并联连接；所述第一开关（21）的第一端连接于所述电感（1）的一端，所述第一开关（21）的第二端连接于所述第二开关（22）的第一端，所述第二开关（22）的第二端接地；所述电感（1）的另一端用于连接供电电源；所述控制模块（4）连接于所述开关模块的控制端；所述控制模块（4）用于控制所述开关模块中各开关的状态，以使得所述第二开关（22）的第一端输出预设频率和幅度的电压信号。所述控制方法可以通过使用跳频通讯技术来提高通讯信号的信噪比，同时能够通过根据应用场景调整打码电压幅度来降低系统功耗。

Description

主动笔、升压电路及其控制方法 技术领域
本申请涉及升压电路技术领域，特别涉及一种主动笔、升压电路及其控制方法。
背景技术
目前，越来越多的终端设备带有触摸屏，主动笔101可以用来书写或者输入指令到具有触摸屏的终端设备104，如电脑屏幕、移动终端设备、绘图板等，以实现人机交互，如图1所示。
主动笔101笔头102末端的笔尖103输出打码信号，以实现主动笔101与有触摸屏的终端设备104之间的通讯，笔尖103输出的打码信号通常为高压信号，以提高主动笔101与具有触摸屏的终端设备104之间的通讯信号信噪比。
发明人在实现本申请的过程中发现，现有技术中至少存在如下问题：目前笔尖103实现高压打码的方案主要是LC谐振打码，LC谐振电路中，电感和电容构成串联谐振电路，主动笔101内的电源为LC谐振电路提供能量输入，LC谐振电路输出高压打码信号至笔尖；然而，在LC谐振电路中，当电感和电容选定之后，电路输出高压频率固定不可调节，以致于电路的信噪比固定无法提高；同时电路输出高压幅度也固定不可调节，无法降低系统功耗。
发明内容
本申请部分实施例的目的在于提供一种主动笔、升压电路及其控制方 法，通过对开关模块的控制，使得升压电路的输出高压频率可调，从而可通过使用跳频通讯技术来提高通讯信号的信噪比，同时使得升压电路的输出高压幅度可调，从而可通过根据应用场景调整打码电压幅度来降低系统功耗。
本申请的一个实施例提供了一种升压电路，包括：电感、开关模块、电容以及控制模块；开关模块至少包括第一开关与第二开关，电容与第二开关并联连接；第一开关的第一端连接于电感的一端，第一开关的第二端连接于第二开关的第一端，第二开关的第二端接地；电感的另一端用于连接供电电源；控制模块连接于开关模块的控制端；控制模块用于控制开关模块中各开关的状态，以使得第二开关的第一端输出预设频率和幅度的电压信号。
本申请实施例还提供了一种主动笔，包括：笔身、笔尖、供电电源以及上述的升压电路；笔尖设置于笔身的一端；供电电源与升压电路均设置于笔身内；电感的另一端连接于供电电源，第二开关的第一端连接于笔尖。
本申请实施例还提供了一种升压电路的控制方法，升压电路包括电感、开关模块、电容以及控制模块；开关模块至少包括第一开关与第二开关，电容与第二开关并联连接；第一开关的第一端连接于电感的一端，第一开关的第二端连接于第二开关的第一端，第二开关的第二端接地；电感的另一端用于连接供电电源；控制方法包括：第一阶段：控制第一开关与第二开关均处于闭合状态，使第二开关的第一端输出低电平的电压信号；第二阶段：控制第一开关处于闭合状态且第二开关处于断开状态，使电感与电容产生LC谐振且第二开关的第一端输出的电压信号跟随第一开关的第一端的电压信号的变化而变化；第三阶段：控制第一开关与第二开关均处于断开状态，使第一开关的第一端的电压信号被钳位且第二开关的第一端输出预设频率和幅度的电压信号；其中，第 一阶段、第二阶段、第三阶段依次被执行。
本申请实施例还提供了一种升压电路的控制方法，升压电路包括电感、开关模块、电容以及控制模块；开关模块至少包括第一开关、第二开关以及第三开关，电容与第二开关并联连接；第一开关的第一端连接于电感的一端，第一开关的第二端连接于第二开关的第一端，第二开关的第二端接地；电感的另一端用于连接供电电源；第三开关的第一端连接于第一开关的第一端，第三开关的第二端接地；控制方法包括：第一阶段：控制第二开关与第三开关处于闭合状态，使第二开关的第一端输出低电平的电压信号；其中，第一开关为断开状态或者闭合状态；第二阶段：控制第二开关与第三开关均处于断开状态，控制第一开关处于闭合状态，使电感与电容产生LC谐振且第二开关的第一端输出的电压信号跟随第一开关的第一端的电压信号的变化而变化；第三阶段：控制第一开关、第二开关以及第三开关均为断开状态，使第一开关的第一端的电压被钳位且第二开关的第一端输出预设频率和幅度的电压信号；其中，所述第一阶段、所述第二阶段、所述第三阶段依次被执行。
本申请实施例相对于现有技术而言，通过对开关模块的控制，使得升压电路的输出高压频率可调，从而可通过使用跳频通讯技术来提高通讯信号的信噪比，同时使得升压电路的输出高压幅度可调，从而可通过根据应用场景调整打码电压幅度来降低系统功耗。
另外，开关模块还包括第三开关；第三开关的第一端连接于第一开关的第一端，第三开关的第二端接地。本实施例中，通过设置第三开关，减少电路功耗，提升系统效率。
另外，开关模块还包括第四开关，连接于电感的另一端，电感的另一端 通过第四开关连接至供电电源。本实施例通过对第二开关和第四开关时序的控制，以实现对升压电路的输出高压幅度和频率的独立调控。
另外，开关模块中的各开关均为场效应晶体管；控制模块连接于每个场效应晶体管的控制端，以控制每个场效应晶体管。本实施例提供了一种开关组的组成方式。
另外，开关模块中的第一开关为二极管，开关模块中的其它开关均为场效应晶体管；控制模块连接于每个场效应晶体管的控制端，以控制每个场效应晶体管。本实施例提供了另一种开关组的组成方式，利用二极管作为第一开关使用，而二极管具有正向导通、反向截止特性，从而不需要发出驱动信号进行控制。
另外，控制模块包括用于驱动开关模块的驱动电路，以及用于控制驱动电路的驱动方式的控制电路。本实施例提供了控制模块的组成方式。
另外，驱动电路与控制电路集成在一个芯片中。
另外，在升压电路的控制方法中，开关模块还包括第四开关，连接于电感的另一端；电感的另一端通过第四开关连接供电电源；控制方法包括：在第一阶段之前，还包括：初始阶段：控制第二开关处于闭合状态，控制第四开关处于断开状态，使第二开关的第一端输出低电平的电压信号；其中，第一开关为断开状态或者闭合状态；在第一阶段中，还控制第四开关处于闭合状态；在第二阶段中，还控制第四开关处于闭合状态；在第三阶段中，还控制第四开关处于闭合状态。本实施例提供了包含第四开关的开关控制方法。
另外，在升压电路的控制方法中，开关模块还包括第四开关，连接于电感的另一端；电感的另一通过第四开关连接供电电压；在第一阶段之前，还包 括：初始阶段：控制第四开关处于断开状态，控制第二开关与第三开关处于闭合状态，使第二开关的第一端输出低电平的电压信号；其中，第一开关为断开状态或者闭合状态；在第一阶段中，还控制第四开关处于闭合状态；在第二阶段中，还控制第四开关处于闭合状态；在第三阶段中，还控制第四开关处于闭合状态。本实施例提供了包含第四开关的开关控制方法。
附图说明
一个或多个实施例通过与之对应的附图中的图片进行示例性说明，这些示例性说明并不构成对实施例的限定，附图中具有相同参考数字标号的元件表示为类似的元件，除非有特别申明，附图中的图不构成比例限制。
图1是根据现有技术的主动笔控制终端设备的示意图；
图2是根据本申请第一实施例的升压电路的示意图；
图3是根据本申请第一实施例的升压电路正常工作的波形示意图；
图4是根据本申请第一实施例的升压电路正常工作时的一个周期内的波形示意图；
图5是根据本申请第二实施例的升压电路的示意图；
图6是根据本申请第三实施例的升压电路的示意图；
图7是根据本申请第四实施例的升压电路的示意图；
图8是根据本申请第四实施例的包括第四开关的升压电路的示意图；
图9是根据本申请第五实施例的主动笔的结构示意图；
图10是根据本申请第六实施例的升压电路的控制方法的流程图；
图11是根据本申请第七实施例的升压电路的控制方法的流程图；
图12是根据本申请第八实施例的升压电路的控制方法的流程图；
图13是根据本申请第九实施例的升压电路的控制方法的流程图。
具体实施例
为了使本申请的目的、技术方案及优点更加清楚明白，以下结合附图及实施例，对本申请部分实施例进行进一步详细说明。应当理解，此处所描述的具体实施例仅仅用以解释本申请，并不用于限定本申请。
本申请的第一实施例涉及一种升压电路，应用于主动笔，能够在主动笔的供电电源提供能量输入时，输出高压打码信号到主动笔的笔尖。请参考图2，升压电路10包括电感1、开关模块、电容3以及控制模块4。
开关模块至少包括第一开关21与第二开关22，电容3与第二开关22并联连接；第一开关21的第一端连接于电感1的一端，第一开关21的第二端连接于第二开关22的第一端，第二开关22的第二端接地；电感1的另一端用于连接供电电源，接收供电电源电压。
控制模块4连接于开关模块的控制端；控制模块4用于控制开关模块中各开关的状态，以使得第二开关22的第一端输出预设频率和幅度的电压信号。需要说明的是，请参考图2，第二开关22的第一端输出预设频率和幅度的电压信号，即为图2中A点输出的电压信号，A点与主动笔笔尖连接。
本实施例中，控制模块4包括控制电路41和驱动电路42；驱动电路42连接于开关模块的控制端，用于驱动开关模块；控制电路41连接于驱动电路42，且用于控制驱动电路42的驱动方式，使得驱动电路42可以产生一定占空比的方波来控制开关模块。
在一个例子中，驱动电路42与控制电路41可以集成在一个芯片中，直接在芯片的IO口输出方波；然不限于此，控制电路41与驱动电路42也可以分开设置，通过驱动电路42输出方波。
本实施例中，开关模块中的各开关可以为场效应晶体管，即，第一开关21与第二开关22均为场效应晶体管。由于场效应晶体管自身带有寄生电容，因此，电容3可以是第二开关22(场效应晶体管)自身的寄生电容(本实施例以场效应晶体管为例)；或者，升压电路10中可以设置一个与第二开关22并联连接的实体电容，此时，电容3是指该实体电容与第二开关22(场效应晶体管)自身的寄生电容并联连接后的总电容。
控制模块4连接于每个场效应晶体管的控制端，以控制每个场效应晶体管，即，控制模块4的驱动电路42分别连接于第一开关21(场效应晶体管)与第二开关22(场效应晶体管)的控制端，以发出驱动信号来分别控制第一开关21与第二开关22。
本实施例中，升压电路方案的正常工作波形示意图如图3所示，图4为该方案正常工作时一个周期内的波形放大图。
下面以正常工作时的一个周期为例对升压电路方案的工作原理进行说明，请参考图4下表为一个周期中各个阶段的开关状态且第一阶段、第二阶段、第三阶段依次被执行。
Figure PCTCN2017079799-appb-000001
Figure PCTCN2017079799-appb-000002
第一阶段：控制电路41控制驱动电路42发出驱动信号，控制第一开关21和第二开关22均导通，即，控制第一开关21和第二开关22均处于闭合状态；A点和B点均接地，此时，供电电源对电感1充电，A点输出低电平电压信号；
第二阶段：控制电路41控制驱动电路42发出驱动信号，控制第二开关22断开，即，控制第一开关21处于闭合状态且第二开关22处于断开状态；此时，电感1和电容3构成LC谐振电路，A点输出电压与B点电压保持一致跟随LC谐振震荡；
第三阶段：控制电路41控制驱动电路42发出驱动信号，控制第一开关21断开，即，控制第一开关21、第二开关22均处于断开状态；一般选择LC谐振的四分之一周期时断开第一开关21，此时，LC谐振上升电压达到最大值，而由于电容3的存在，A点电压可以维持在第一开关21断开时的电压值。
本实施例的升压电路方案中，在电感1不出现磁饱和现象的情况下，第二开关22导通的时间决定了电感1的充电电流最大值，第二开关22的导通时间即为第一阶段至第二阶段的时长；电感1的充电电流最大值决定了LC谐振电路的上升电压最大值，第一开关21断开的时间点决定了A点的最终输出高压幅度；第二开关22导通时A点输出低电平电压信号，第二开关22断开时A点输出高电压，第二开关22的开关频率决定了A点输出高压的频率；因此，通过对第一开关21和第二开关22开关时序的控制可以实现对A点输出高压幅度和频率的同时调控，即使得A点能够输出预设频率和幅度的电压信号。
本实施例相对于现有技术而言，通过对开关模块的控制，使得升压电路 的输出高压频率可调，从而可通过使用跳频通讯技术来提高通讯信号的信噪比，同时使得升压电路的输出高压幅度可调，从而可通过根据应用场景调整打码电压幅度来降低系统功耗。
本申请第二实施例涉及一种升压电路，本实施例与第一实施例大致相同，主要区别之处在于：在第一实施例中，第一开关21为场效应晶体管；而在本实施例中，第一开关21为二极管，请参考图5。
本实施例中，开关模块中的第一开关21为二极管，其它开关均为场效应晶体管；控制模块4连接于每个场效应晶体管的控制端，以控制每个场效应晶体管，即，控制模块4的驱动电路42连接于第二开关22(场效应晶体管)的控制端，以发出驱动信号来控制第二开关22。
本实施例中，请参考图4，升压电路方案的工作原理如下(下表为各个阶段的开关状态)：
Figure PCTCN2017079799-appb-000003
第一阶段：控制电路41控制驱动电路42发出驱动信号，控制第二开关22导通，即，控制第二开关22处于闭合状态；A点接地，B点电压略高于A点电压，此时，第一开关21(二极管)导通，供电电源对电感1充电，A点输出低电平电压信号；
第二阶段：控制电路41控制驱动电路42发出驱动信号，控制第二开关22断开，即，控制第二开关22处于断开状态；电感1与第二开关22断开时的电容3构成LC谐振电路，LC谐振的前四分之一周期B点电压处于上升状态，B点电压高于A点电压，第一开关21(二极管)处于导通状态，A点输出电压跟随B点电压上升；
第三阶段：LC谐振的四分之一周期后，B点电压处于下降状态，B点电压低于A点电压，第一开关21(二极管)反向截止处于关断状态，A点输出电压钳位为第一开关21(二极管)关断时的B点电压值；虽然B点从LC谐振上升电压最大值处开始下降时，二极管便反向截止，但二极管由于结电容的存在，彻底关断仍需要一定的时间，因此，在二极管彻底关断的时间内，B点的谐振电压会下降，A点输出电压跟随B点电压，从而A点的钳位输出高压略低于LC谐振上升电压最大值，即，将升压电路的输出高压钳位于略低于LC谐振电路上升电压的最大值处。
本实施例相对于第一实施例而言，利用二极管作为第一开关使用，而二极管具有正向导通、反向截止特性，从而不需要发出驱动信号进行控制。
本申请的第三实施例涉及一种升压电路，本实施例是在第二实施例基础上的改进，主要改进之处在于：本实施例中，请参考图6，开关模块还包括第三开关23。
本实施例中，第三开关23的第一端连接于第一开关21的第一端，第三开关23的第二端接地。
本实施例中，请参考图4，升压电路方案的工作原理如下(下表为各个阶段的开关状态)：
Figure PCTCN2017079799-appb-000004
第一阶段：控制电路41控制驱动电路42发出驱动信号，控制第二开关22和第三开关23同时导通，即，控制第二开关22、第三开关23均处于闭合状态；A点和B点均接地，第一开关21(二极管)关断，A点输出低电平电压信号；
第二阶段：控制电路41控制驱动电路42发出驱动信号，控制第二开关22和第三开关23同时断开，即，控制第二开关22、第三开关23均处于断开状态；电感1与第二开关22断开时的电容3以及第三开关23断开时的电容3构成LC谐振电路，LC谐振的前四分之一周期B点电压处于上升状态，B点电压高于A点电压，此时第一开关21(二极管)处于导通状态，A点输出电压跟随B点电压上升；
第三阶段：LC谐振的四分之一周期后，B点电压处于下降状态，B点电压低于A点电压，第一开关21(二极管)反向截止处于关断状态，A点输出电压钳位为第一开关21(二极管)关断时的B点电压值。
本实施例相对于第二实施例而言，增加第三开关后，第一阶段中，由于第二开关和第三开关同时导通，A点和B点均接地，第一开关(二极管)处于关断状态，从而降低了电路功耗，提高了系统效率。值得一提的是，本实施例 也可以作为在第一实施例基础上的改进，可以达到相同技术效果。
本申请的第四实施例涉及一种升压电路，本实施例是在第二实施例基础上的改进，主要改进之处在于：本实施例中，请参考图7，开关模块还包括第四开关24。
本实施例中，电感1的另一端通过第四开关24连接至供电电源，接收供电电源电压。
本实施例中的升压电路方案的工作原理如下(下表为各个阶段的开关状态)：
Figure PCTCN2017079799-appb-000005
初始阶段：控制电路41控制驱动电路42发出驱动信号，控制第二开关22导通、第四开关24关断，即，控制第二开关22处于闭合状态，第四开关24处于断开状态；供电电源与电感1断开，电路无能量输入，A点接地，B点由于楞次定律产生负压，第一开关21(二极管)反向截止处于关断状态，A点输出低电平电压信号；
第一阶段：控制电路41控制驱动电路42发出驱动信号，控制第四开关24导通，即，控制第二开关22、第四开关24均处于闭合状态；供电电源对电 感1充电，A点接地，B点电压高于A点电压，第一开关21(二极管)处于导通状态，A点输出低电平电压信号；
第二阶段：控制电路41控制驱动电路42发出驱动信号，控制第二开关22关断，即，控制第二开关22处于断开状态，第四开关24处于闭合状态；电感1与第二开关22关断时的电容3构成LC谐振电路，LC谐振的前四分之一周期B点电压处于上升状态，B点电压高于A点电压，第一开关21(二极管)处于导通状态，A点输出电压跟随B点电压上升；
第三阶段，LC谐振的四分之一周期后，B点电压处于下降状态，B点电压低于A点电压，第一开关21(二极管)反向截止处于关断状态，A点输出电压钳位为第一开关21(二极管)关断时的B点电压值。
其中，在第二实施例中，第二开关22用于同时对输出高压的幅度与频率进行调节，若输出频率要求越高，则需要第二开关22切换越快，对应的，A点输出电压的幅度越小(第二开关22切换越快，则第二开关22导通时间越短，从而对电感的充电时间越短)。而在本实施例中，增加第四开关24，第四开关24关断时，供电电源与电感1断开，电路无能量输入；第四开关24导通时，供电电源与电感1连接为电路提供能量输入，对电感充电。增加第四开关24，通过对电感充电时间的调控，控制电感1的充电电流最大值，从而控制LC谐振电路的上升电压最高值，以调控A点的输出高压幅度，即，通过控制第四开关24来调控A点的输出高压幅度。
另外，请参考图8，本实施例也可以作为在第三实施例基础上的改进。
本实施例中，第四开关24连接于电感1的另一端，电感1通过第四开关24接收供电电源电压。
本实施例中的升压电路方案的工作原理如下(下表为各个阶段的开关状态)：
Figure PCTCN2017079799-appb-000006
初始阶段：控制电路41控制驱动电路42发出驱动信号，控制第二开关22和第三开关23同时导通、第四开关24关断，即，控制第二开关22和第三开关23均处于闭合状态且第四开关24处于断开状态；供电电源与电感1断开，电路无能量输入，A点和B点均接地，第一开关21(二极管)处于关断状态，A点输出低电平电压信号；
第一阶段：控制电路41控制驱动电路42发出驱动信号，控制第四开关24导通，即，控制第二开关22、第三开关23以及第四开关均处于闭合状态；供电电源对电感1充电，A点和B点均接地，第一开关21(二极管)处于关断状态，A点输出低电平电压信号；
第二阶段：控制电路41控制驱动电路42发出驱动信号，控制第二开关22和第三开关23同时关断，即，控制第二开关22和第三开关23均处于断开状态且第四开关24处于闭合状态；电感1与第二开关22关断时的电容3以及第三开关23关断时的电容3构成LC谐振电路，LC谐振的前四分之一周期B 点电压处于上升状态，B点电压高于A点电压，第一开关21(二极管)处于导通状态，A点输出电压跟随B点电压上升；
第三阶段，LC谐振的四分之一周期后，B点电压处于下降状态，B点电压低于A点电压，第一开关21(二极管)反向截止处于关断状态，A点输出电压钳位为第一开关21(二极管)关断时的B点电压值。
本实施例中，第四开关24关断时，供电电源与电感1断开，电路无能量输入；第四开关24导通时，供电电源与电感1连接为电路提供能量输入，对电感充电。增加第四开关24，通过对电感充电时间的调控，控制电感1的充电电流最大值，从而控制LC谐振电路的上升电压最高值，以调控A点的输出高压幅度，即，通过控制第四开关24来调控A点的输出高压幅度。
本实施例相对于第二实施例而言，通过对第二开关的时序控制实现对输出高压频率的调控，通过对第四开关时序的控制，以实现对输出高压幅度的调控。即，本实施例中实现了对输出高压的幅度与频率的独立控制，使得可以根据需要任意调节输出高压的幅度与频率。需要说明的是，本实施例也可以作为在第一实施例基础上的改进，可以达到相同技术效果。
本申请第五实施例涉及一种主动笔，应用于书写或输入指令到具有触摸屏的终端设备，如电脑屏幕、移动设备、绘图板等，以实现人机交互。请参考图9，主动笔301包括笔身302、笔尖303、供电电源304以及第一实施例至第四实施例中任一项的升压电路10。
本实施例中，笔尖303设置于笔身302的一端；供电电源304与升压电路10均设置于笔身302内；电感1的另一端连接于供电电源304，第二开关22的第一端连接于笔尖303，并通过笔尖303将预设频率和幅度的电压信号转换 为打码信号发射出去。
本实施例相对于现有技术而言，提供了一种应用升压电路的主动笔。
本申请第六实施例涉及一种升压电路的控制方法，应用于上述升压电路10，请参考图5。
升压电路的控制方法的具体流程图如图10所示。
步骤101，第一阶段：控制第一开关与第二开关均处于闭合状态。
具体而言，控制电路41控制驱动电路42发出驱动信号，控制第二开关22处于闭合状态；A点接地，B点电压略高于A点电压，此时，第一开关21(二极管)导通，供电电源对电感1充电，使第二开关22的第一端输出低电平的电压信号。
本实施例中，第一开关21为二极管，由于二极管正向导通、反向截止的特性，其开合状态会随着第二开关22开合状态的变化而变化，即控制电路41控制第二开关22的开合会导致第一开关21(二极管)的开合状态产生变化；因此，当第一开关21为例如二极管这类元器件(具有正向导通、反向截止特性)时，控制电路41对其的控制可以理解为控制电路41通过控制第二开关22来间接控制第一开关21，即控制电路41对其的控制是间接控制；而当第一开关21为具有控制端的元器件，例如为场效应晶体管时，控制电路41对其的控制为直接控制(即控制电路41直接发送表征开合的信号至第一开关21的控制端)。
步骤102，第二阶段：控制第一开关处于闭合状态且第二开关处于断开状态。
具体而言，控制电路41控制驱动电路42发出驱动信号，控制第二开关22处于断开状态；此时，电感1与第二开关22断开时的电容3构成LC谐振电 路，产生LC谐振，LC谐振的前四分之一周期B点电压处于上升状态，B点电压高于A点电压，第一开关21(二极管)处于导通状态，此时，第二开关22的第一端输出的电压信号跟随第一开关的第一端(即B点)的电压信号上升。
步骤103，第三阶段：控制第一开关与第二开关均处于断开状态。
具体而言，LC谐振的四分之一周期后，控制电路41控制驱动电路42发出驱动信号，控制第二开关22断开，B点电压处于下降状态，B点电压低于A点电压，第一开关21(二极管)反向截止处于关断状态，由于电容3的存在，第一开关21(二极管)的第一端的电压信号被钳位，第二开关22的第一端输出的电压信号维持在第一开关21(二极管)断开时的电压值，即，第二开关22的第一端输出预设频率和幅度的电压信号。
本实施例的升压电路方案中，在电感1不出现磁饱和现象的情况下，第二开关22导通的时间决定了电感1的充电电流最大值，第二开关22的导通时间即为第一阶段至第二阶段的时长；电感1的充电电流最大值决定了LC谐振电路的上升电压最大值，第一开关21断开的时间点决定了A点的最终输出高压幅度；第二开关22导通时A点输出低电平电压信号，第二开关22断开时A点输出高电压，第二开关22的开关频率决定了A点输出高压的频率；因此，通过对第一开关21和第二开关22开关时序的控制可以实现对A点输出高压幅度和频率的同时调控，即使得A点能够输出预设频率和幅度的电压信号。
不难发现，本实施例为与第一实施例、第二实施例相对应的方法实施例，本实施例可与第一实施例、第二实施例互相配合实施。第一实施例、第二实施例中提到的相关技术细节在本实施例中依然有效，为了减少重复，这里不再赘述。相应地，本实施例中提到的相关技术细节也可应用在第一实施例、第二实 施例中。
本实施例相对于现有技术而言，通过对开关模块的控制，使得升压电路的输出高压频率可调，从而可通过使用跳频通讯技术来提高通讯信号的信噪比，同时使得升压电路的输出高压幅度可调，从而可通过根据应用场景调整打码电压幅度来降低系统功耗。
本申请第七实施例涉及一种升压电路的控制方法，本实施例是在第六实施例基础上的改进，主要改进之处在于：在开关模块增加了第四开关时，增加了对第四开关的控制。
本实施例中，请参考图7，开关模块还包括第四开关24；第四开关24连接于电感1的另一端，电感1的另一端通过第四开关24连接供电电源。
升压电路的控制方法的具体流程图如图11所示。
步骤201，初始阶段：控制第二开关处于闭合状态，控制第四开关处于断开状态；其中，第一开关处于断开或者闭合状态。
具体而言，控制电路41控制驱动电路42发出驱动信号，控制第二开关22处于闭合状态、第四开关24处于断开状态，此时，电路无能量输入，A点接地，B点由于楞次定律产生负压，第一开关21(二极管)反向截止处于关断状态，第二开关22的第一端输出低电平的电压信号。需要说明的是，当第一开关21为场效应晶体管时，其处于断开或者闭合状态均可，较佳的，第一开关21处于断开状态，可以减少电路的功耗。
步骤202，第一阶段：控制第一开关、第二开关与第四开关均处于闭合状态。
具体而言，控制电路41控制驱动电路42发出驱动信号，控制第二开 关22与第四开关24均处于闭合状态；供电电源对电感1充电，A点接地，B点电压高于A点电压，第一开关21(二极管)处于导通状态，第二开关22的第一端输出低电平电压信号。
步骤203，第二阶段：控制第一开关、第四开关处于闭合状态且第二开关处于断开状态。
具体而言，控制电路41控制驱动电路42发出驱动信号，控制第四开关24处于闭合状态且第二开关22处于断开状态；电感1与第二开关22关断时的电容3构成LC谐振电路，LC谐振的前四分之一周期B点电压处于上升状态，B点电压高于A点电压，第一开关21(二极管)处于导通状态，第二开关22的第一端输出电压跟随B点电压上升。
步骤204，第三阶段：控制第一开关、第二开关均处于断开状态且第四开关处于闭合状态。
具体而言，LC谐振的四分之一周期后，控制电路41控制驱动电路42发出驱动信号，控制第二开关22处于断开状态且第四开关24处于闭合状态，B点电压处于下降状态，B点电压低于A点电压，第一开关21(二极管)反向截止处于关断状态，此时，第二开关22的第一端输出电压信号钳位为第一开关21断开时的电压值，即，第二开关22的第一端输出预设频率和幅度的电压信号。
本实施例中，增加第四开关24，第四开关24关断时，供电电源与电感1断开，电路无能量输入；第四开关24导通时，供电电源与电感1连接为电路提供能量输入，对电感充电。增加第四开关24，通过对电感充电时间的调控，控制电感1的充电电流最大值，从而控制LC谐振电路的上升电压最高值，以 调控A点的输出高压幅度，即，通过控制第四开关24来调控A点的输出高压幅度。
由于第四实施例与本实施例相互对应，因此本实施例可与第四实施例互相配合实施。第四实施例中提到的相关技术细节在本实施例中依然有效，在第四实施例中所能达到的技术效果在本实施例中也同样可以实现，为了减少重复，这里不再赘述。相应地，本实施例中提到的相关技术细节也可应用在第四实施例中。
本实施例相对于第六实施例而言，通过对第二开关的时序控制实现对输出高压频率的独立调控，通过对第四开关时序的控制，以实现对输出高压幅度的独立调控。
本申请第八实施例涉及一种升压电路的控制方法，应用于上述升压电路10，请参考图6。
升压电路的控制方法的具体流程图如图12所示。
步骤301，第一阶段：控制第二开关与第三开关均处于闭合状态；其中，第一开关处于断开或者闭合状态。
具体而言，控制电路41控制驱动电路42发出驱动信号，控制第二开关22与第三开关23均处于闭合状态；此时，A点和B点均接地，第一开关21(二极管)关断，第二开关22的第一端输出低电平的电压信号。需要说明的是，当第一开关21为场效应晶体管时，第一开关21处于断开或者闭合状态均可，较佳的，第一开关21处于断开状态，可以减少电路的功耗。
其中，当第一开关21为具有控制端的元器件，例如为场效应晶体管时，控制电路41对其的控制为直接控制(即控制电路41直接发送表征开合的信号 至第一开关21的控制端)；而当第一开关21为二极管时，由于二极管正向导通、反向截止的特性，其开合状态会随着第二开关22、第三开关23开合状态的变化而变化，即控制电路41控制第二开关22、第三开关23的开合会导致第一开关21(二极管)的开合状态产生变化；因此，当第一开关21为例如二极管这类元器件(具有正向导通、反向截止特性)时，控制电路41对其的控制可以理解为控制电路41通过控制第二开关22、第三开关23来间接控制第一开关21，即控制电路41对第一开关21的控制是间接控制。
步骤302，第二阶段：控制第二开关与第三开关处于断开状态，第一开关处于闭合状态。
具体而言，控制电路41控制驱动电路42发出驱动信号，控制第二开关22与第三开关23处于断开状态；电感1与第二开关22以及第三开关23断开时的电容3构成LC谐振电路，B点电压高于A点电压，此时第一开关21(二极管)处于导通状态，LC谐振的前四分之一周期第二开关22的第一端输出电压信号随着谐振上升，即，第二开关22的第一端输出的电压信号跟随第一开关21的第一端的电压信号的上升而上升。
步骤303，第三阶段：控制第一开关、第二开关与第三开关均处于断开状态。
具体而言，LC谐振的四分之一周期后，控制电路41控制驱动电路42发出驱动信号，控制第二开关22与第三开关23均处于断开状态；此时，B点电压低于A点电压，第一开关21(二极管)反向截止处于关断状态，第一开关21(二极管)的第一端的电压被钳位，第二开关22的第一端输出电压信号钳位为第一开关21断开时的电压值，即，第二开关22的第一端输出预设频率和幅 度的电压信号。
本实施例的升压电路方案中，在电感1不出现磁饱和现象的情况下，第二开关22导通的时间决定了电感1的充电电流最大值，第二开关22的导通时间即为第一阶段至第二阶段的时长；电感1的充电电流最大值决定了LC谐振电路的上升电压最大值，第一开关21断开的时间点决定了A点的最终输出高压幅度；第二开关22导通时A点输出低电平电压信号，第二开关22断开时A点输出高电压，第二开关22的开关频率决定了A点输出高压的频率；因此，通过对第一开关21和第二开关22开关时序的控制可以实现对A点输出高压幅度和频率的同时调控，即使得A点能够输出预设频率和幅度的电压信号。
由于第三实施例与本实施例相互对应，因此本实施例可与第三实施例互相配合实施。第三实施例中提到的相关技术细节在本实施例中依然有效，在第三实施例中所能达到的技术效果在本实施例中也同样可以实现，为了减少重复，这里不再赘述。相应地，本实施例中提到的相关技术细节也可应用在第三实施例中。
本实施例相对于现有技术而言，提供了增加第三开关时的控制方法，降低了电路功耗，提高了系统效率。
本申请第九实施例涉及一种升压电路的控制方法，本实施例是在第八实施例基础上的改进，主要改进之处在于：在开关模块中增加第四开关时，增加了对第四开关的控制。
本实施例中，请参考图8，开关模块还包括第四开关24，连接于电感1的另一端；电感1通过第四开关24接收供电电源电压。
升压电路的控制方法的具体流程图如图13所示。
步骤401，初始阶段：控制第四开关处于断开状态且第二开关、第三开关处于闭合状态；其中，第一开关21处于断开或者闭合状态。
具体而言，控制电路41控制驱动电路42发出驱动信号，控制第四开关24处于断开状态且第二开关22、第三开关23均处于闭合状态；此时，电路无能量输入，A点和B点均接地，第一开关21(二极管)处于关断状态，第二开关22的第一端输出低电平的电压信号。需要说明的是，当第一开关21为场效应晶体管时，第一开关21处于断开或者闭合状态均可，较佳的，第一开关21处于断开状态，可以减少电路的功耗。
步骤402，第一阶段：控制第二开关、第三开关与第四开关处于闭合状态；其中，第一开关处于断开或者闭合状态。
具体而言，控制电路41控制驱动电路42发出驱动信号，控制第二开关22、第三开关23与第四开关24均处于闭合状态；供电电源对电感1充电，A点和B点均接地，第一开关21(二极管)处于关断状态，此时，第二开关22的第一端输出低电平的电压信号。需要说明的是，当第一开关21为场效应晶体管时，第一开关21处于断开或者闭合状态均可，较佳的，第一开关21处于断开状态，可以减少电路的功耗。
步骤403，第二阶段：控制第二开关与第三开关均处于断开状态，控制第一开关、第四开关处于闭合状态。
具体而言，控制电路41控制驱动电路42发出驱动信号，控制第二开关22与第三开关23均处于断开状态，控制第四开关24处于闭合状态；电感1与第二开关22以及第三开关23关断开时的电容3构成LC谐振电路，LC谐振的前四分之一周期B点电压处于上升状态，B点电压高于A点电压，第一开关 21(二极管)处于导通状态，此时，第二开关22的第一端输出电压信号随着谐振上升，即，第二开关22的第一端输出的电压信号跟随第一开关21的第一端的电压信号的上升而上升。
步骤404，第三阶段：控制第一开关、第二开关以及第三开关均为断开状态，第四开关处于闭合状态。
具体而言，LC谐振的四分之一周期后，控制电路41控制驱动电路42发出驱动信号，控制第二开关22以及第三开关23均为断开状态，第四开关24处于闭合状态；此时，B点电压处于下降状态，B点电压低于A点电压，第一开关21(二极管)反向截止处于关断状态，第一开关21(二极管)的第一端的电压被钳位，第二开关22的第一端输出电压信号钳位为第一开关21断开时的电压值，即，第二开关22的第一端输出预设频率和幅度的电压信号。
本实施例中，第四开关24关断时，供电电源与电感1断开，电路无能量输入；第四开关24导通时，供电电源与电感1连接为电路提供能量输入，对电感充电。增加第四开关24，通过对电感充电时间的调控，控制电感1的充电电流最大值，从而控制LC谐振电路的上升电压最高值，以调控A点的输出高压幅度，即，通过控制第四开关24来调控A点的输出高压幅度。
由于第四实施例与本实施例相互对应，因此本实施例可与第四实施例互相配合实施。第四实施例中提到的相关技术细节在本实施例中依然有效，在第四实施例中所能达到的技术效果在本实施例中也同样可以实现，为了减少重复，这里不再赘述。相应地，本实施例中提到的相关技术细节也可应用在第四实施例中。
本实施例相对于第八实施例而言，通过对第二开关的时序控制实现对 输出高压频率的独立调控，通过对第四开关时序的控制，以实现对输出高压幅度的独立调控。
上面各种方法的步骤划分，只是为了描述清楚，实现时可以合并为一个步骤或者对某些步骤进行拆分，分解为多个步骤，只要包括相同的逻辑关系，都在本专利的保护范围内；对算法中或者流程中添加无关紧要的修改或者引入无关紧要的设计，但不改变其算法和流程的核心设计都在该专利的保护范围内。
本领域的普通技术人员可以理解，上述各实施例是实现本申请的具体实施例，而在实际应用中，可以在形式上和细节上对其作各种改变，而不偏离本申请的精神和范围。

Claims (12)

  1. 一种升压电路，包括：电感、开关模块、电容以及控制模块；
    所述开关模块至少包括第一开关与第二开关，所述电容与所述第二开关并联连接；
    所述第一开关的第一端连接于所述电感的一端，所述第一开关的第二端连接于所述第二开关的第一端，所述第二开关的第二端接地；所述电感的另一端用于连接供电电源；
    所述控制模块连接于所述开关模块的控制端；所述控制模块用于控制所述开关模块中各开关的状态，以使得所述第二开关的第一端输出预设频率和幅度的电压信号。
  2. 如权利要求1所述的升压电路，其中，所述开关模块还包括第三开关；
    所述第三开关的第一端连接于所述第一开关的第一端，所述第三开关的第二端接地。
  3. 如权利要求1或2所述的升压电路，其中，所述开关模块还包括第四开关，所述电感的另一端通过所述第四开关连接至所述供电电源。
  4. 如权利要求1至3中任一项所述的升压电路，其中，所述开关模块中的各开关均为场效应晶体管；
    所述控制模块连接于每个所述场效应晶体管的控制端，以控制每个所述场效应晶体管。
  5. 如权利要求1至3中任一项所述的升压电路，其中，所述开关模块中的所述第一开关为二极管，所述开关模块中的其它开关均为场效应晶体管；
    所述控制模块连接于每个所述场效应晶体管的控制端，以控制每个所述场效应晶体管。
  6. 如权利要求1至3中任一项所述的升压电路，其中，所述控制模块包括用于驱动所述开关模块的驱动电路，以及用于控制所述驱动电路的驱动方式的控制电路。
  7. 如权利要求6所述的升压电路，其中，所述驱动电路与所述控制电路集成在一个芯片中。
  8. 一种主动笔，包括：笔身、笔尖、供电电源以及权利要求1至7中任一项所述的升压电路；
    所述笔尖设置于所述笔身的一端；
    所述供电电源与所述升压电路均设置于所述笔身内；
    所述电感的另一端连接于所述供电电源，所述第二开关的第一端连接于所述笔尖。
  9. 一种升压电路的控制方法，所述升压电路包括电感、开关模块、电容以 及控制模块；所述开关模块至少包括第一开关与第二开关，所述电容与所述第二开关并联连接；所述第一开关的第一端连接于所述电感的一端，所述第一开关的第二端连接于所述第二开关的第一端，所述第二开关的第二端接地；所述电感的另一端用于连接供电电源；所述控制方法包括：
    第一阶段：控制所述第一开关与所述第二开关均处于闭合状态，使所述第二开关的第一端输出低电平的电压信号；
    第二阶段：控制所述第一开关处于闭合状态且所述第二开关处于断开状态，使所述电感与所述电容产生LC谐振且所述第二开关的第一端输出的电压信号跟随所述第一开关的第一端的电压信号的变化而变化；
    第三阶段：控制所述第一开关与所述第二开关均处于断开状态，使所述第一开关的第一端的电压信号被钳位且所述第二开关的第一端输出预设频率和幅度的电压信号；
    其中，所述第一阶段、所述第二阶段、所述第三阶段依次被执行。
  10. 如权利要求9所述的控制方法，其中，所述开关模块还包括第四开关，连接于所述电感的另一端；所述电感的另一端通过所述第四开关连接所述供电电源；所述控制方法包括：
    在所述第一阶段之前，还包括：
    初始阶段：控制所述第二开关处于闭合状态，控制所述第四开关处于断开状态，使所述第二开关的第一端输出低电平的电压信号；其中，所述第一开关 为断开状态或者闭合状态；
    在所述第一阶段中，还控制所述第四开关处于闭合状态；
    在所述第二阶段中，还控制所述第四开关处于闭合状态；
    在所述第三阶段中，还控制所述第四开关处于闭合状态。
  11. 一种升压电路的控制方法，所述升压电路包括电感、开关模块、电容以及控制模块；所述开关模块至少包括第一开关、第二开关以及第三开关，所述电容与所述第二开关并联连接；所述第一开关的第一端连接于所述电感的一端，所述第一开关的第二端连接于所述第二开关的第一端，所述第二开关的第二端接地；所述电感的另一端用于连接供电电源；所述第三开关的第一端连接于所述第一开关的第一端，所述第三开关的第二端接地；所述控制方法包括：
    第一阶段：控制所述第二开关与所述第三开关处于闭合状态，使所述第二开关的第一端输出低电平的电压信号；其中，所述第一开关为断开状态或者闭合状态；
    第二阶段：控制所述第二开关与所述第三开关均处于断开状态，控制所述第一开关处于闭合状态，使所述电感与所述电容产生LC谐振且所述第二开关的第一端输出的电压信号跟随所述第一开关的第一端的电压信号的变化而变化；
    第三阶段：控制所述第一开关、所述第二开关以及所述第三开关均为断开状态，使所述第一开关的第一端的电压被钳位且所述第二开关的第一端输出预 设频率和幅度的电压信号；
    其中，所述第一阶段、所述第二阶段、所述第三阶段依次被执行。
  12. 如权利要求11所述的控制方法，其中，所述开关模块还包括第四开关，连接于所述电感的另一端；所述电感的另一通过所述第四开关连接所述供电电压；
    在所述第一阶段之前，还包括：
    初始阶段：控制所述第四开关处于断开状态，控制所述第二开关与所述第三开关处于闭合状态，使所述第二开关的第一端输出低电平的电压信号；其中，所述第一开关为断开状态或者闭合状态；
    在所述第一阶段中，还控制所述第四开关处于闭合状态；
    在所述第二阶段中，还控制所述第四开关处于闭合状态；
    在所述第三阶段中，还控制所述第四开关处于闭合状态。
PCT/CN2017/079799 2017-04-07 2017-04-07 主动笔、升压电路及其控制方法 WO2018184234A1 (zh)

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