WO2018129831A1 - 一种修正波逆变器智能型短路保护开关电路 - Google Patents

一种修正波逆变器智能型短路保护开关电路 Download PDF

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Publication number
WO2018129831A1
WO2018129831A1 PCT/CN2017/081780 CN2017081780W WO2018129831A1 WO 2018129831 A1 WO2018129831 A1 WO 2018129831A1 CN 2017081780 W CN2017081780 W CN 2017081780W WO 2018129831 A1 WO2018129831 A1 WO 2018129831A1
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tube
unit
resistor
npn
short
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PCT/CN2017/081780
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English (en)
French (fr)
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侯涛
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广东百事泰电子商务股份有限公司
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Publication of WO2018129831A1 publication Critical patent/WO2018129831A1/zh

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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02H—EMERGENCY PROTECTIVE CIRCUIT ARRANGEMENTS
    • H02H7/00—Emergency protective circuit arrangements specially adapted for specific types of electric machines or apparatus or for sectionalised protection of cable or line systems, and effecting automatic switching in the event of an undesired change from normal working conditions
    • H02H7/10—Emergency protective circuit arrangements specially adapted for specific types of electric machines or apparatus or for sectionalised protection of cable or line systems, and effecting automatic switching in the event of an undesired change from normal working conditions for converters; for rectifiers
    • H02H7/12—Emergency protective circuit arrangements specially adapted for specific types of electric machines or apparatus or for sectionalised protection of cable or line systems, and effecting automatic switching in the event of an undesired change from normal working conditions for converters; for rectifiers for static converters or rectifiers
    • H02H7/122—Emergency protective circuit arrangements specially adapted for specific types of electric machines or apparatus or for sectionalised protection of cable or line systems, and effecting automatic switching in the event of an undesired change from normal working conditions for converters; for rectifiers for static converters or rectifiers for inverters, i.e. dc/ac converters
    • H02H7/1227—Emergency protective circuit arrangements specially adapted for specific types of electric machines or apparatus or for sectionalised protection of cable or line systems, and effecting automatic switching in the event of an undesired change from normal working conditions for converters; for rectifiers for static converters or rectifiers for inverters, i.e. dc/ac converters responsive to abnormalities in the output circuit, e.g. short circuit

Definitions

  • the invention relates to a protection circuit of an inverter, in particular to an intelligent short circuit protection switch circuit of a modified wave inverter.
  • the common correction wave inverter and the AC to AC correction wave inverter are directly boosted and then sent to the inverter circuit, and there is no buffer circuit in the middle, when the output end of the inverter circuit is non-pure.
  • a peak current exceeding tens of times of the normal load will be generated on the switching tube of the inverter circuit, which usually causes the inverter to not bear the non-capacitive load and cause the false shutdown.
  • the inverters in the prior art are subjected to the impact of current by the performance of the inverter switching device itself, so that it is easy to cause an accidental shutdown or damage to the switch tube, so that the damage rate and cost of the open-tube device are greatly increased.
  • the technical problem to be solved by the present invention is to provide a timely protection under the condition that a peak current is generated in the inverter part, thereby improving the capacitive load capacity of the inverter and avoiding the inverter error.
  • the present invention adopts the following technical solutions.
  • An intelligent short circuit protection switch circuit for a modified wave inverter comprising: a PFC boosting unit for boosting conversion of an input voltage thereof; and a shorting switch unit having an input end connected to the PFC boosting unit The output terminal, the short-circuiting switch unit is configured to drive the input end and the output end to be turned on or off according to an electrical signal received by the control terminal thereof; and an inverter unit whose input end is connected to the output end of the short-circuiting switch unit.
  • the inverter unit is configured to invert the voltage outputted by the short-circuit switch unit into alternating current; a current sampling circuit is configured to collect the current signal of the inverter unit bus; and an intelligent identification unit is connected to the output end of the current sampling circuit, The intelligent identification unit is configured to receive a current signal collected by the current sampling circuit, and: when the current signal does not exceed a preset value, send a conduction signal to the control end of the short-circuiting switch unit, so that the short-circuiting switch unit drives the input end thereof and The output end is turned on; when the current signal is higher than the preset value, a disconnection electric signal is sent to the control end of the short-circuiting switch unit to drive the short-circuiting switch unit An input terminal and an output terminal is disconnected.
  • the PFC boosting unit includes a boosting inductor, a first switching transistor, a first diode, and a first electrolytic capacitor, and a front end of the boosting inductor is used to connect a DC voltage, and the boosting inductor
  • the back end is connected to the drain of the first switch tube, the source of the first switch tube is grounded, and the gate of the first switch tube is used to access a PWM control signal.
  • the drain of the first switch tube is connected to the anode of the first diode, the cathode of the first diode is used as the output end of the PFC boost unit, and the cathode of the first diode is connected to the first electrolytic capacitor
  • the positive electrode, the negative electrode of the first electrolytic capacitor is grounded.
  • the short-circuiting switch unit includes a second switching tube, a first NPN tube, a PNP tube, an optocoupler and a second electrolytic capacitor, and a drain of the second switching tube serves as an input end of the short-circuiting switch unit, a source of the second switch tube serves as an output end of the short-circuit switch unit, a collector of the first NPN tube is connected to a high potential, and a base of the first NPN tube is connected to a high potential through a first resistor, the first The emitter of the NPN tube is connected to the emitter of the PNP tube, the collector of the first NPN tube is connected to the source of the second switch tube, and the electrical signal of the emitter of the first NPN tube is transmitted to the second switch tube a gate of the second electrolytic capacitor connected to a source of the second switching transistor, a cathode of the second electrolytic capacitor being grounded, the photocoupler comprising a transmitting tube and a receiving tube, the first NPN tube a base,
  • the emitter of the first NPN transistor is connected to the gate of the second switching transistor through a second resistor.
  • the collector of the first NPN tube is connected to a high potential through a third resistor.
  • the smart identification unit includes a first comparator, a second NPN tube, a second diode, and a first capacitor, and an anode of the second diode is used to connect a high potential, the second The cathode of the pole tube is grounded through a first capacitor, the base of the second NPN tube is used to access a current signal output by the current sampling circuit, the emitter of the second NPN tube is grounded, and the set of the second NPN tube
  • the electrode is connected to the cathode of the second diode, and the electrical signal of the second diode cathode is transmitted to the inverting end of the first comparator, and the non-inverting end of the first comparator is used to access the first reference
  • the voltage, the output of the first comparator is connected to the anode of the transmitting tube as an output of the smart identification unit.
  • the method further includes a second comparator and a third NPN tube, wherein the electrical signal of the second diode is transmitted to the inverting end of the second comparator, and the non-inverting end of the second comparator is used for Entering a second reference voltage, the electrical signal of the output of the second comparator is transmitted to the base of the third NPN tube, and the collector of the third NPN tube is connected to the inverting end of the first comparator, the third The emitter of the NPN tube is grounded.
  • a fourth NPN tube is further included, the electrical signal of the output of the second comparator is transmitted to the base of the fourth NPN tube, and the collector of the fourth NPN tube is connected to the inverting end of the second comparator. The emitter of the fourth NPN tube is grounded.
  • the inverter unit includes an inverter bridge composed of a third switch tube, a fourth switch tube, a fifth switch tube, and a sixth switch tube, and the gate of the third switch tube and the fourth switch tube a gate, a gate of the fifth switch, and a gate of the sixth switch are respectively used for accessing a PWM driving signal, and the third switch, the fourth switch, and the fifth switch are controlled by the PWM drive signal And an on state of the sixth switch tube, so that the inverter unit outputs an alternating current.
  • the current sampling circuit includes a fourth resistor, a fifth resistor, and a sixth resistor connected in parallel with each other, and a front end of the fourth resistor, the fifth resistor, and the sixth resistor is connected to a cathode of the DC bus of the inverter unit.
  • the rear ends of the fourth resistor, the fifth resistor, and the sixth resistor are grounded, and the front ends of the fourth resistor, the fifth resistor, and the sixth resistor serve as outputs of the current sampling circuit.
  • the intelligent short circuit protection switch circuit of the modified wave inverter when the inverter unit does not generate a spike current, the intelligent identification unit controls the input end and the output end of the short circuit switch unit to be turned on, so that the output of the PFC boost unit is turned on.
  • the signal is transmitted to the inverter unit through the short-circuit switch unit, so that the load is normally powered; when the inverter unit generates a peak current due to the non-resistive load, the peak current is transmitted to the intelligent identification unit, and the intelligent identification unit controls the short-circuit switch unit to The input and output are disconnected, which in turn disconnects the PFC boost unit from the inverter unit.
  • the invention realizes timely protection under the condition that a peak current or a load short circuit occurs in the inverter part, thereby improving the capacity load capacity of the inverter, and at the same time avoiding accidental shutdown or accidental damage of the inverter, Reduced circuit cost.
  • FIG. 1 is a circuit schematic diagram of a PFC boost unit, a short circuit switch unit, and an intelligent identification unit.
  • FIG. 2 is a circuit schematic diagram of an inverter unit.
  • the invention discloses an intelligent short circuit protection switch circuit for a modified wave inverter, which is combined with FIG. 1 and FIG. 2 and includes:
  • a PFC boosting unit 10 for boosting conversion of its input voltage
  • a short-circuiting switch unit 20 having an input terminal connected to an output end of the PFC boosting unit 10, wherein the short-circuiting switch unit 20 is configured to drive its input end and output end to be turned on or off according to an electrical signal received by its control terminal;
  • An inverter unit 30 having an input end connected to an output end of the short-circuiting switch unit 20, wherein the inverter unit 30 is configured to invert a voltage output by the short-circuiting switch unit 20 into an alternating current;
  • a current sampling circuit 50 for collecting a current signal of the busbar of the inverter unit 30;
  • An intelligent identification unit 40 is connected to the output of the current sampling circuit 50, and the smart identification unit 40 is configured to receive the current signal collected by the current sampling circuit 50, and:
  • a disconnection electric signal is sent to the control end of the short-circuiting switch unit 20 to make the short-circuit switch Unit 20 drives its input and output disconnected.
  • the smart identification unit 40 controls the input terminal and the output terminal of the short-circuit switch unit 20 to be turned on, so that the output signal of the PFC boosting unit 10 is transmitted to the reverse through the short-circuit switch unit 20.
  • the unit 30 is changed to make the load power on normally; when the inverter unit 30 generates a peak current due to the non-resistive load, the peak current is transmitted to the smart identification unit 40, and the smart identification unit 40 controls the short-circuit switch unit 20 to input the input end thereof. Disconnected from the output, thereby disconnecting the PFC boost unit 10 and the inverter unit 30.
  • the invention realizes timely protection under the condition that a peak current or a load short circuit occurs in the inverter part, thereby improving the capacity load capacity of the inverter, and at the same time avoiding accidental shutdown or accidental damage of the inverter, Reduced circuit cost.
  • the PFC boosting unit 10 includes a boosting inductor L2, a first switching transistor Q5, a first diode D1, and a first electrolytic capacitor C2, and a front end of the boosting inductor L2 is used for accessing a DC voltage, a rear end of the boosting inductor L2 is connected to a drain of the first switching transistor Q5, a source of the first switching transistor Q5 is grounded, and a gate of the first switching transistor Q5 is used for accessing a circuit a PWM control signal, a drain of the first switching transistor Q5 is connected to an anode of the first diode D1, a cathode of the first diode D1 is an output end of the PFC boosting unit 10, and the first diode The cathode of the tube D1 is connected to the anode of the first electrolytic capacitor C2, and the cathode of the first electrolytic capacitor C2 is grounded.
  • the filter capacitor C1 performs high-frequency filtering on the obtained DC pulse power source or pure DC to the first switching transistor Q5 and the boosting inductor L2 for boosting.
  • the boosting principle is as follows: the first switching transistor Q5 When conducting, the current on the filter capacitor C1 is looped through the boost inductor L2, the first switch transistor Q5 to GND, and the boost inductor L2 stores energy. At this time, the voltage polarity of the boost inductor L2 is positive and negative; When the first switching transistor Q5 is turned off, an induced electromotive force is formed on the boosting inductor that is much higher than the input voltage.
  • the polarity of the voltage on the boosting inductor L2 is positive and negative, and the induced electromotive force passes through the first diode.
  • D1 is rectified, a unidirectional voltage is formed and then sent to the first electrolytic capacitor C2 for filtering.
  • the first electrolytic capacitor C2 is a large-capacity electrolytic capacitor, and the voltage filtered by the first electrolytic capacitor C2 is a pure DC voltage.
  • the short-circuiting switch unit 20 includes a second switching transistor Q6, a first NPN transistor Q9, a PNP transistor Q10, an optocoupler and a second electrolytic capacitor C3, and the drain of the second switching transistor Q6 serves as The input end of the short switch unit 20, the source of the second switch tube Q6 serves as the output end of the short switch unit 20, the collector of the first NPN tube Q9 is connected to a high potential, and the base of the first NPN tube Q9 The pole is connected to the high potential through the first resistor R21, the emitter of the first NPN transistor Q9 is connected to the emitter of the PNP transistor Q10, and the collector of the first NPN transistor Q9 is connected to the source of the second switching transistor Q6.
  • the optocoupler includes a transmitting tube U5A and a receiving tube U5B.
  • the base of the first NPN tube Q9, the base of the PNP tube Q10, and the input end of the receiving tube U5B are connected to each other.
  • the output of the tube U5B is connected to the second switch
  • the source of the tube Q6, the anode of the transmitting tube U5A serves as the control end of the short-circuiting switch unit 20, and the cathode of the transmitting tube U5A is grounded.
  • the emitter of the first NPN transistor Q9 is connected to the gate of the second switching transistor Q6 through the second resistor R1.
  • the collector of the first NPN transistor Q9 is connected to a high potential through a third resistor R20.
  • VCC1 passes through the third resistor R20, the first resistor R21, the first NPN tube Q9, the PNP tube Q10, and the second resistor R1.
  • the driving circuit is composed of the GEAT pole of the second switching transistor Q6, and the second switching transistor Q6 is turned on to charge the second electrolytic capacitor C3.
  • the capacity of the second electrolytic capacitor C3 is much less than that of the first electrolytic capacitor C2.
  • the variable circuit works normally to output the corrected wave voltage to the load. When the connected load is abnormal, the inverter circuit generates an abnormal current, and the current sampling circuit is sent to the intelligent identification circuit.
  • the receiving tube U5B is turned on, and the base of the first NPN tube Q9 is pulled low, first.
  • the NPN tube Q9 is turned off, the PNP tube Q10 is turned on, the GEAT pole voltage of the second switch tube Q6 is pulled to the low level by the PNP tube Q10, the second switch tube Q6 is turned off, and the voltage stored on the second electrolytic capacitor C3 is reversed.
  • the receiving tube U5B will be turned off, and the second switching tube Q6 will continue to be turned on, and the second electrolytic capacitor C3 will have a continuous voltage supply to the inverter circuit.
  • the voltage of the second electrolytic capacitor C3 is turned to zero after the second switching transistor Q6 is turned off, the abnormal current generated by the inverter circuit is still not eliminated, and the receiving tube U5B is permanently turned on and the second switching transistor Q6 is turned off, thereby The power supply of the inverter circuit is broken, and the purpose of protecting the device and the user's personal safety is achieved.
  • the smart identification unit 40 includes a first comparator U9A, a second NPN tube Q12, a second diode D2, and a first capacitor C4, and an anode of the second diode D2 is used for Connected to a high potential, the cathode of the second diode D2 is grounded through a first capacitor C4, and the base of the second NPN transistor Q12 is used to access a current signal output by the current sampling circuit 50, the second NPN tube The emitter of Q12 is grounded, the collector of the second NPN transistor Q12 is connected to the cathode of the second diode D2, and the electrical signal of the cathode of the second diode D2 is transmitted to the opposite phase of the first comparator U9A.
  • the non-inverting terminal of the first comparator U9A is used to access the first reference voltage VF1, and the output end of the first comparator U9A is connected to the anode of the transmitting tube U5A as an output end of the smart identification unit 40. .
  • the smart identification unit 40 further includes a second comparator U9B and a third NPN tube Q11, and an electrical signal of the cathode of the second diode D2 is transmitted to an inverting end of the second comparator U9B,
  • the non-inverting terminal of the second comparator U9B is used to access the second reference voltage VF2
  • the electrical signal of the output of the second comparator U9B is transmitted to the base of the third NPN transistor Q11
  • the collector of the third NPN transistor Q11 Connected to the inverting terminal of the first comparator U9A, the emitter of the third NPN transistor Q11 is grounded.
  • the smart identification unit 40 further includes a fourth NPN tube Q13, the electrical signal of the output of the second comparator U9B is transmitted to the base of the fourth NPN tube Q13, and the collector connection of the fourth NPN tube Q13. Second ratio The emitter of the fourth NPN transistor Q13 is grounded at the inverting terminal of the comparator U9B.
  • the seventh resistor R36, the eighth resistor R37, the second diode D2, the first capacitor C4, and the second NPN transistor Q12 form a timing circuit
  • a ninth resistor R44, a tenth resistor R35, and a second Capacitor C5 is connected to the current sampling circuit.
  • the seventh resistor R36 and the eighth resistor R37 form a voltage dividing circuit
  • the second diode D2 charges the divided capacitor to the first capacitor C4
  • the second diode D2 prevents the first capacitor C4 from discharging to the eighth resistor R37. Since the first comparator U9A and the second comparator U9B are composed of comparators, the input resistance is large, and the first capacitor C4 is fully charged without a discharge loop.
  • the voltage flowing through the current sampling circuit forms a voltage drop insufficient to turn on the second NPN transistor Q12, and the voltage on the first capacitor C4 is higher than VF1 and VF2, the first comparator The 1 pin of U9A and the 7 pin of the second comparator U9B respectively output a low level, the transmitting tube U5A is not turned on, and the second switching tube Q6 operates normally.
  • the voltage is divided by R38 and the ninth resistor R44, and then the second capacitor C5 filters out the interference signal and sends it to the base of the second NPN tube Q12.
  • the NPN tube Q12 will be turned on, and the voltage on the first capacitor C4 of the timing circuit will be released.
  • the first comparator U9A will output a high level.
  • the transmitting tube U5A is turned on, the receiving tube U5A controls the receiving tube U5B, the receiving tube U5B is also turned on, the receiving tube U5B turns off the second switching tube Q6, and the voltage stored by the inverter circuit by the second electrolytic capacitor C3 Power supply, if the voltage of the second electrolytic capacitor C3 is not discharged, but the high voltage generated by the large current on the sampling circuit has disappeared, the seventh resistor R36 charges the first capacitor C4 when the voltage on the first capacitor C4 is high.
  • the first comparator U9A will output a low level, and the second switch Q6 will continue to work.
  • the user should access the interference peak current generated by the capacitive or inductive load, and the circuit can work. of.
  • the high voltage generated by the large current on the sampling resistor is still sufficient for the second NPN transistor Q12 to continue to conduct, and the voltage on the first capacitor C4 passes through the second NPN tube.
  • the second comparator U9B When Q12 is released below the VF2 voltage, the second comparator U9B will output a high level, and the third NPN tube Q11 and the fourth NPN tube Q13 are turned on, respectively, and the first comparator U9A and the second comparator U9B are respectively connected to the second leg. And the 6-pin level is pulled low to zero. At this time, the first comparator U9A is locked by the second comparator U9B, and the transmitting tube U5A will be permanently turned on, thereby permanently turning off the second switching transistor Q6.
  • the capacity of the second electrolytic capacitor C3 is less than that of the first electrolytic capacitor C2, and when the second switching transistor Q6 is turned off, the energy stored in the second electrolytic capacitor C3 cannot be sufficient to damage the switch of the inverter circuit.
  • the voltage on the second electrolytic capacitor C3 is discharged, the voltage on the first capacitor C4 of the timer circuit falls below VF2, but the voltage on the first capacitor C4 cannot be released to zero.
  • the inverter unit 30 includes an inverter bridge composed of a third switch tube Q1, a fourth switch tube Q2, a fifth switch tube Q3, and a sixth switch tube Q4.
  • the gate of the three-switching transistor Q1, the gate of the fourth switching transistor Q2, the gate of the fifth switching transistor Q3, and the gate of the sixth switching transistor Q4 are respectively used to access the PWM driving signal.
  • the conduction state of the third switching transistor Q1, the fourth switching transistor Q2, the fifth switching transistor Q3, and the sixth switching transistor Q4 is controlled by the PWM driving signal to cause the inverter unit 30 to output an alternating current.
  • the third switching transistor Q1, the sixth switching transistor Q4, the fourth switching transistor Q2, and the fifth switching transistor Q3 are alternately turned on, and a correction wave AC voltage is formed on the OUT_L and OUT_N to the load, and F1 is formed. It is a safety insurance tube.
  • the current sampling circuit 50 includes a fourth resistor R3, a fifth resistor R4, and a sixth resistor R5 connected in parallel with each other, and the front ends of the fourth resistor R3, the fifth resistor R4, and the sixth resistor R5. Connected to the negative pole of the DC bus of the inverter unit 30, the rear ends of the fourth resistor R3, the fifth resistor R4 and the sixth resistor R5 are grounded, and the fourth resistor R3, the fifth resistor R4 and the sixth resistor R5 The front end serves as the output of the current sampling circuit 50.
  • the intelligent short circuit protection switch circuit of the modified wave inverter disclosed by the invention has the function of intelligently identifying whether the load is short-circuited, and can timely respond to the inrush current of the capacitive or inductive load, and under the action of the above circuit, the modified wave inversion can be made
  • the device's capacitive or inductive load capacity is enhanced, and the device is not easily damaged, the safety is greatly improved, and the cost of the inverter circuit can be reduced.

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Abstract

一种修正波逆变器智能型短路保护开关电路，包括：PFC升压单元　(10)，用于对其输入电压进行升压转换；短路开关单元　(20)，其输入端连接于PFC升压单元　(10)　的输出端，短路开关单元　(20)　用于根据其控制端接收的电信号而驱动其输入端和输出端导通或断开；逆变单元　(30),其输入端连接于短路开关单元　(20)　的输出端，逆变单元　(30)　用于将短路开关单元　(20)　输出的电压逆变为交流电；电流采样电路　(50)，用于采集逆变单元　(30)　母线的电流信号；智能识别单元　(40)，连接于电流采样电路(50)的输出端，智能识别单元　(40)　用于接收电流采样电路　(50)　采集的电流信号，以及：当电流信号未超过预设值时向短路开关单元　(20)　的控制端发出导通电信号，以令短路开关单元(20)驱动其输入端和输出端导通；当电流信号高于预设值时向短路开关单元　(20)　的控制端发出断开电信号，以令短路开关单元　(20)　驱动其输入端和输出端断开。该短路保护开关电路能提高逆变器的带容性负载能力，可避免逆变器误关机或误损坏。

Description

一种修正波逆变器智能型短路保护开关电路
技术领域
本发明涉及逆变器的保护电路，尤其涉及一种修正波逆变器智能型短路保护开关电路。
背景技术
现有技术中，常见的修正波逆变器及AC转AC修正波逆变器，都是直接升压滤波后再送给逆变电路，中间没有缓冲电路，当逆变电路的输出端带非纯阻性负载时，会在逆变电路的开关管上产生超过正常带载时几十倍的尖峰电流，通常会造成逆变器带不起非容性负载而导致误关机。而且现有技术中的逆变器，都是靠逆变开关器件本身的性能而承受电流的冲击，因此容易造成误关机或损坏开关管，使得开管器件的损坏率和成本大大增加。
发明内容
本发明要解决的技术问题在于，针对现有技术的不足，提供一种能够在逆变部分产生尖峰电流的情况下及时保护，进而提高逆变器的带容性负载能力、避免逆变器误关机或误损坏的修正波逆变器智能型短路保护开关电路。
为解决上述技术问题，本发明采用如下技术方案。
一种修正波逆变器智能型短路保护开关电路，其包括有：一PFC升压单元，用于对其输入电压进行升压转换；一短路开关单元，其输入端连接于PFC升压单元的输出端，所述短路开关单元用于根据其控制端接收的电信号而驱动其输入端和输出端导通或断开；一逆变单元，其输入端连接于短路开关单元的输出端，所述逆变单元用于将短路开关单元输出的电压逆变为交流电；一电流采样电路，用于采集逆变单元母线的电流信号；一智能识别单元，连接于电流采样电路的输出端，所述智能识别单元用于接收电流采样电路采集的电流信号，以及：当所述电流信号未超过预设值时向短路开关单元的控制端发出导通电信号，以令短路开关单元驱动其输入端和输出端导通；当所述电流信号高于预设值时向短路开关单元的控制端发出断开电信号，以令短路开关单元驱动其输入端和输出端断开。
优选地，所述PFC升压单元包括有升压电感、第一开关管、第一二极管和第一电解电容，所述升压电感的前端用于接入直流电压，所述升压电感的后端连接于第一开关管的漏极，所述第一开关管的源极接地，所述第一开关管的栅极用于接入一路PWM控制信号，所 述第一开关管的漏极连接第一二极管的阳极，所述第一二极管的阴极作为PFC升压单元的输出端，且该第一二极管的阴极连接第一电解电容的正极，所述第一电解电容的负极接地。
优选地，所述短路开关单元包括有第二开关管、第一NPN管、PNP管、光耦和第二电解电容，所述第二开关管的漏极作为短路开关单元的输入端，所述第二开关管的源极作为短路开关单元的输出端，所述第一NPN管的集电极连接高电位，所述第一NPN管的基极通过第一电阻连接于高电位，所述第一NPN管的发射极与PNP管的发射极相连接，所述第一NPN管的集电极连接于第二开关管的源极，所述第一NPN管发射极的电信号传输至第二开关管的栅极，所述第二电解电容的正极连接于第二开关管的源极，所述第二电解电容的负极接地，所述光耦包括有发射管和接收管，所述第一NPN管的基极、PNP管的基极和接收管的输入端相互连接，所述接收管的输出端连接于第二开关管的源极，所述发射管的阳极作为短路开关单元的控制端，所述发射管的阴极接地。
优选地，所述第一NPN管的发射极通过第二电阻连接于第二开关管的栅极。
优选地，所述第一NPN管的集电极通过第三电阻连接于高电位。
优选地，所述智能识别单元包括有第一比较器、第二NPN管、第二二极管和第一电容，所述第二二极管的阳极用于连接高电位，所述第二二极管的阴极通过第一电容接地，所述第二NPN管的基极用于接入电流采样电路输出的电流信号，所述第二NPN管的发射极接地，所述第二NPN管的集电极连接于第二二极管的阴极，且所述第二二极管阴极的电信号传输至第一比较器的反相端，所述第一比较器的同相端用于接入第一基准电压，所述第一比较器的输出端作为智能识别单元的输出端而连接于所述发射管的阳极。
优选地，还包括有第二比较器和第三NPN管，所述第二二极管阴极的电信号传输至第二比较器的反相端，所述第二比较器的同相端用于接入第二基准电压，所述第二比较器输出端的电信号传输至第三NPN管的基极，所述第三NPN管的集电极连接于第一比较器的反相端，所述第三NPN管的发射极接地。
优选地，还包括有第四NPN管，所述第二比较器输出端的电信号传输至第四NPN管的基极，所述第四NPN管的集电极连接于第二比较器的反相端，所述第四NPN管的发射极接地。
优选地，所述逆变单元包括由第三开关管、第四开关管、第五开关管和第六开关管组成的逆变桥，所述第三开关管的栅极、第四开关管的栅极、第五开关管的栅极和第六开关管的栅极分别用于接入PWM驱动信号，藉由所述PWM驱动信号而控制第三开关管、第四开关管、第五开关管和第六开关管的导通状态，以令所述逆变单元输出交流电。
优选地，所述电流采样电路包括有相互并联的第四电阻、第五电阻和第六电阻，所述第四电阻、第五电阻和第六电阻的前端连接于逆变单元的直流母线的负极，所述第四电阻、第五电阻和第六电阻的后端接地，且所述第四电阻、第五电阻和第六电阻的前端作为电流采样电路的输出端。
本发明公开的修正波逆变器智能型短路保护开关电路中，当逆变单元未产生尖峰电流时，智能识别单元控制短路开关单元的输入端和输出端导通，使得PFC升压单元的输出信号通过短路开关单元传输至逆变单元，使得负载正常上电；当逆变单元因带非阻性负载而产生尖峰电流时，该尖峰电流传输至智能识别单元，智能识别单元控制短路开关单元将其输入端和输出端断开，进而将PFC升压单元和逆变单元之间断开。基于上述结构，本发明实现了在逆变部分产生尖峰电流或者负载短路等情况下及时进行保护，从而提高逆变器的带容性负载能力，同时可避免逆变器误关机或误损坏，大大降低了电路成本。
附图说明
图1为PFC升压单元、短路开关单元和智能识别单元的电路原理图。
图2为逆变单元的电路原理图。
具体实施方式
下面结合附图和实施例对本发明作更加详细的描述。
本发明公开了一种修正波逆变器智能型短路保护开关电路，结合图1和图2所示，其包括有：
一PFC升压单元10，用于对其输入电压进行升压转换；
一短路开关单元20，其输入端连接于PFC升压单元10的输出端，所述短路开关单元20用于根据其控制端接收的电信号而驱动其输入端和输出端导通或断开；
一逆变单元30，其输入端连接于短路开关单元20的输出端，所述逆变单元30用于将短路开关单元20输出的电压逆变为交流电；
一电流采样电路50，用于采集逆变单元30母线的电流信号；
一智能识别单元40，连接于电流采样电路50的输出端，所述智能识别单元40用于接收电流采样电路50采集的电流信号，以及：
当所述电流信号未超过预设值时向短路开关单元20的控制端发出导通电信号，以令短路开关单元20驱动其输入端和输出端导通；
当所述电流信号高于预设值时向短路开关单元20的控制端发出断开电信号，以令短路开关 单元20驱动其输入端和输出端断开。
上述电路中，当逆变单元30未产生尖峰电流时，智能识别单元40控制短路开关单元20的输入端和输出端导通，使得PFC升压单元10的输出信号通过短路开关单元20传输至逆变单元30，使得负载正常上电；当逆变单元30因带非阻性负载而产生尖峰电流时，该尖峰电流传输至智能识别单元40，智能识别单元40控制短路开关单元20将其输入端和输出端断开，进而将PFC升压单元10和逆变单元30之间断开。基于上述结构，本发明实现了在逆变部分产生尖峰电流或者负载短路等情况下及时进行保护，从而提高逆变器的带容性负载能力，同时可避免逆变器误关机或误损坏，大大降低了电路成本。
关于升压部分，所述PFC升压单元10包括有升压电感L2、第一开关管Q5、第一二极管D1和第一电解电容C2，所述升压电感L2的前端用于接入直流电压，所述升压电感L2的后端连接于第一开关管Q5的漏极，所述第一开关管Q5的源极接地，所述第一开关管Q5的栅极用于接入一路PWM控制信号，所述第一开关管Q5的漏极连接第一二极管D1的阳极，所述第一二极管D1的阴极作为PFC升压单元10的输出端，且该第一二极管D1的阴极连接第一电解电容C2的正极，所述第一电解电容C2的负极接地。
上述PFC升压单元10中，滤波电容C1将获得的直流脉动电源或纯直流进行高频滤波送给第一开关管Q5、升压电感L2进行升压，升压原理如下：第一开关管Q5导通时，滤波电容C1上的电流经升压电感L2、第一开关管Q5到GND形成回路，升压电感L2储存能量，这时升压电感L2的电压极性为前正后负；当第一开关管Q5关断时，升压电感上会形成比输入电压高得多的感应电动势，这时升压电感L2上的电压极性为前负后正，感应电动势经第一二极管D1进行整流后形成单向电压再送给第一电解电容C2滤波，第一电解电容C2为大容量的电解电容，经过第一电解电容C2滤波后的电压为纯直流电压。
作为一种优选方式，所述短路开关单元20包括有第二开关管Q6、第一NPN管Q9、PNP管Q10、光耦和第二电解电容C3，所述第二开关管Q6的漏极作为短路开关单元20的输入端，所述第二开关管Q6的源极作为短路开关单元20的输出端，所述第一NPN管Q9的集电极连接高电位，所述第一NPN管Q9的基极通过第一电阻R21连接于高电位，所述第一NPN管Q9的发射极与PNP管Q10的发射极相连接，所述第一NPN管Q9的集电极连接于第二开关管Q6的源极，所述第一NPN管Q9发射极的电信号传输至第二开关管Q6的栅极，所述第二电解电容C3的正极连接于第二开关管Q6的源极，所述第二电解电容C3的负极接地，所述光耦包括有发射管U5A和接收管U5B，所述第一NPN管Q9的基极、PNP管Q10的基极和接收管U5B的输入端相互连接，所述接收管U5B的输出端连接于第二开关 管Q6的源极，所述发射管U5A的阳极作为短路开关单元20的控制端，所述发射管U5A的阴极接地。
进一步地，所述第一NPN管Q9的发射极通过第二电阻R1连接于第二开关管Q6的栅极。所述第一NPN管Q9的集电极通过第三电阻R20连接于高电位。
上述短路开关单元20中，当电源开通时由于没有异常信号接收管U5B没有导通，这时VCC1通过第三电阻R20、第一电阻R21、第一NPN管Q9、PNP管Q10、第二电阻R1组成的驱动电路给第二开关管Q6的GEAT极，第二开关管Q6导通，对第二电解电容C3充电，第二电解电容C3的容量要比第一电解电容C2少很多，这时逆变电路正常工作输出修正波电压给负载。当接入的负载发生异常时，逆变电路会产生异常电流，通电流采样电路送给智能识别电路，这时接收管U5B会导通，将第一NPN管Q9的基极拉低，第一NPN管Q9关闭，PNP管Q10导通，第二开关管Q6的GEAT极电压被PNP管Q10拉到低电平为零，第二开关管Q6关闭，第二电解电容C3上储存的电压供给逆变电路，当异常信号消除后，接收管U5B会关掉，同时第二开关管Q6会继续导通，第二电解电容C3上将有持续的电压供给逆变电路。如果第二开关管Q6关闭后，第二电解电容C3的电压放到零时，逆变电路产生的异常电流仍没有消除，这时接收管U5B会永久导通关掉第二开关管Q6，从而断掉逆变电路的供电，达到保护设备和用户人身安全的目的。
作为一种优选方式，所述智能识别单元40包括有第一比较器U9A、第二NPN管Q12、第二二极管D2和第一电容C4，所述第二二极管D2的阳极用于连接高电位，所述第二二极管D2的阴极通过第一电容C4接地，所述第二NPN管Q12的基极用于接入电流采样电路50输出的电流信号，所述第二NPN管Q12的发射极接地，所述第二NPN管Q12的集电极连接于第二二极管D2的阴极，且所述第二二极管D2阴极的电信号传输至第一比较器U9A的反相端，所述第一比较器U9A的同相端用于接入第一基准电压VF1，所述第一比较器U9A的输出端作为智能识别单元40的输出端而连接于所述发射管U5A的阳极。
进一步地，所述智能识别单元40还包括有第二比较器U9B和第三NPN管Q11，所述第二二极管D2阴极的电信号传输至第二比较器U9B的反相端，所述第二比较器U9B的同相端用于接入第二基准电压VF2，所述第二比较器U9B输出端的电信号传输至第三NPN管Q11的基极，所述第三NPN管Q11的集电极连接于第一比较器U9A的反相端，所述第三NPN管Q11的发射极接地。
此外，所述智能识别单元40还包括有第四NPN管Q13，所述第二比较器U9B输出端的电信号传输至第四NPN管Q13的基极，所述第四NPN管Q13的集电极连接于第二比 较器U9B的反相端，所述第四NPN管Q13的发射极接地。
上述智能识别单元40中，第七电阻R36、第八电阻R37、第二二极管D2、第一电容C4、第二NPN管Q12组成定时电路，第九电阻R44、第十电阻R35、第二电容C5与电流采样电路相连。第七电阻R36、第八电阻R37组成分压电路，第二二极管D2将分得的电压给第一电容C4充电，第二二极管D2防止第一电容C4向第八电阻R37放电，由于第一比较器U9A和第二比较器U9B是由比较器组成，所以输入电阻很大，第一电容C4充满电后没有放电回路。当负载在逆变电路的承受范围内，电流采样电路上流过的电流形成的压降不足以当第二NPN管Q12导通，第一电容C4上的电压高过VF1和VF2，第一比较器U9A的1脚与第二比较器U9B的7脚分别输出低电平，发射管U5A不导通，第二开关管Q6正常工作。当电流采样电路上有大电流形成的高电压后，通过分压R38、第九电阻R44，分压后再经第二电容C5滤除干扰信号送到第二NPN管Q12的基极，第二NPN管Q12会导通，这时会将定时电路第一电容C4上的电压释放，当电容第一电容C4的电压释放到比VF1低时，第一比较器U9A的1脚会输出高电平，同时发射管U5A导通，由发射管U5A去控制接收管U5B，接收管U5B也导通，接收管U5B关断第二开关管Q6，这时逆变电路靠第二电解电容C3储存的电压供电，如果第二电解电容C3的电压没有放完，但是采样电路上的大电流产生的高电压已消失，那么第七电阻R36会对第一电容C4充电，当第一电容C4上的电压高于VF1时，第一比较器U9A的1脚会输出低电平，第二开关管Q6继续工作，这时应该是用户接入了容性或感性负载所产生的干扰尖峰电流，电路是可以工作的。但如果第二电解电容C3上的电压已放完，采样电阻上由大电流产生的高电压仍然足以让第二NPN管Q12继续导通，这时第一电容C4上的电压通过第二NPN管Q12释放到低于VF2电压时，第二比较器U9B将输出高电平，第三NPN管Q11、第四NPN管Q13导通，分别将第一比较器U9A与第二比较器U9B的2脚和6脚电平拉低到零，这时第一比较器U9A被第二比较器U9B锁死，发射管U5A将永久导通，从而将第二开关管Q6永久关闭。
作为一种优选方式，第二电解电容C3的容量要少于第一电解电容C2，并且当第二开关管Q6断开时，第二电解电容C3上储存的能量不能足以损坏逆变电路的开关管，同时第二电解电容C3上的电压放完后，定时器电路第一电容C4上的电压要降到VF2以下，但第一电容C4上的电压不能释放到零。
关于逆变部分，请参照图2，所述逆变单元30包括由第三开关管Q1、第四开关管Q2、第五开关管Q3和第六开关管Q4组成的逆变桥，所述第三开关管Q1的栅极、第四开关管Q2的栅极、第五开关管Q3的栅极和第六开关管Q4的栅极分别用于接入PWM驱动信 号，藉由所述PWM驱动信号而控制第三开关管Q1、第四开关管Q2、第五开关管Q3和第六开关管Q4的导通状态，以令所述逆变单元30输出交流电。
上述逆变单元30中，第三开关管Q1、第六开关管Q4与第四开关管Q2、第五开关管Q3交替导通，会在OUT_L、OUT_N上形成修正波交流电压送给负载，F1是安全保险管。
作为一种优选方式，所述电流采样电路50包括有相互并联的第四电阻R3、第五电阻R4和第六电阻R5，所述第四电阻R3、第五电阻R4和第六电阻R5的前端连接于逆变单元30的直流母线的负极，所述第四电阻R3、第五电阻R4和第六电阻R5的后端接地，且所述第四电阻R3、第五电阻R4和第六电阻R5的前端作为电流采样电路50的输出端。
上述电流采样电路50中，当逆变电路工作时，会在第四电阻R3、第五电阻R4和第六电阻R5上流过电流从而产生压降，当负载短路时或超过逆变电路所承受的功率时第四电阻R3、第五电阻R4和第六电阻R5上会产生很大的压降，从而让智能识别电路去识别负载是否短路。
本发明公开的修正波逆变器智能型短路保护开关电路，其具有智能识别负载是否短路，并能及时应对容性或感性负载的冲击电流，在上述电路的作用下，可使得修正波逆变器的带容性或感性载能力增强，同时不容易损坏设备，安全性大大提高，此外还可以减少逆变电路的成本。
以上所述只是本发明较佳的实施例，并不用于限制本发明，凡在本发明的技术范围内所做的修改、等同替换或者改进等，均应包含在本发明所保护的范围内。

Claims (10)

  1. 一种修正波逆变器智能型短路保护开关电路，其特征在于，包括有：
    一PFC升压单元(10)，用于对其输入电压进行升压转换；
    一短路开关单元(20)，其输入端连接于PFC升压单元(10)的输出端，所述短路开关单元(20)用于根据其控制端接收的电信号而驱动其输入端和输出端导通或断开；
    一逆变单元(30)，其输入端连接于短路开关单元(20)的输出端，所述逆变单元(30)用于将短路开关单元(20)输出的电压逆变为交流电；
    一电流采样电路(50)，用于采集逆变单元(30)母线的电流信号；
    一智能识别单元(40)，连接于电流采样电路(50)的输出端，所述智能识别单元(40)用于接收电流采样电路(50)采集的电流信号，以及：
    当所述电流信号未超过预设值时向短路开关单元(20)的控制端发出导通电信号，以令短路开关单元(20)驱动其输入端和输出端导通；
    当所述电流信号高于预设值时向短路开关单元(20)的控制端发出断开电信号，以令短路开关单元(20)驱动其输入端和输出端断开。
  2. 如权利要求1所述的修正波逆变器智能型短路保护开关电路，其特征在于，所述PFC升压单元(10)包括有升压电感(L2)、第一开关管(Q5)、第一二极管(D1)和第一电解电容(C2)，所述升压电感(L2)的前端用于接入直流电压，所述升压电感(L2)的后端连接于第一开关管(Q5)的漏极，所述第一开关管(Q5)的源极接地，所述第一开关管(Q5)的栅极用于接入一路PWM控制信号，所述第一开关管(Q5)的漏极连接第一二极管(D1)的阳极，所述第一二极管(D1)的阴极作为PFC升压单元(10)的输出端，且该第一二极管(D1)的阴极连接第一电解电容(C2)的正极，所述第一电解电容(C2)的负极接地。
  3. 如权利要求1所述的修正波逆变器智能型短路保护开关电路，其特征在于，所述短路开关单元(20)包括有第二开关管(Q6)、第一NPN管(Q9)、PNP管(Q10)、光耦和第二电解电容(C3)，所述第二开关管(Q6)的漏极作为短路开关单元(20)的输入端，所述第二开关管(Q6)的源极作为短路开关单元(20)的输出端，所述第一NPN管(Q9)的集电极连接高电位，所述第一NPN管(Q9)的基极通过第一电阻(R21)连接于高电位，所述第一NPN管(Q9)的发射极与PNP管(Q10)的发射极相连接，所述第一NPN管(Q9)的集电极连接于第二开关管(Q6)的源极，所述第一NPN管(Q9)发射极的电信号传输至第二开关管(Q6)的栅极，所述第二电解电容(C3)的正极连接于第二开关管(Q6)的源极，所述第二电解电容(C3)的负极接地，所述光耦包括有发射管(U5A)和接收管 (U5B)，所述第一NPN管(Q9)的基极、PNP管(Q10)的基极和接收管(U5B)的输入端相互连接，所述接收管(U5B)的输出端连接于第二开关管(Q6)的源极，所述发射管(U5A)的阳极作为短路开关单元(20)的控制端，所述发射管(U5A)的阴极接地。
  4. 如权利要求3所述的修正波逆变器智能型短路保护开关电路，其特征在于，所述第一NPN管(Q9)的发射极通过第二电阻(R1)连接于第二开关管(Q6)的栅极。
  5. 如权利要求3所述的修正波逆变器智能型短路保护开关电路，其特征在于，所述第一NPN管(Q9)的集电极通过第三电阻(R20)连接于高电位。
  6. 如权利要求3所述的修正波逆变器智能型短路保护开关电路，其特征在于，所述智能识别单元(40)包括有第一比较器(U9A)、第二NPN管(Q12)、第二二极管(D2)和第一电容(C4)，所述第二二极管(D2)的阳极用于连接高电位，所述第二二极管(D2)的阴极通过第一电容(C4)接地，所述第二NPN管(Q12)的基极用于接入电流采样电路(50)输出的电流信号，所述第二NPN管(Q12)的发射极接地，所述第二NPN管(Q12)的集电极连接于第二二极管(D2)的阴极，且所述第二二极管(D2)阴极的电信号传输至第一比较器(U9A)的反相端，所述第一比较器(U9A)的同相端用于接入第一基准电压(VF1)，所述第一比较器(U9A)的输出端作为智能识别单元(40)的输出端而连接于所述发射管(U5A)的阳极。
  7. 如权利要求6所述的修正波逆变器智能型短路保护开关电路，其特征在于，还包括有第二比较器(U9B)和第三NPN管(Q11)，所述第二二极管(D2)阴极的电信号传输至第二比较器(U9B)的反相端，所述第二比较器(U9B)的同相端用于接入第二基准电压(VF2)，所述第二比较器(U9B)输出端的电信号传输至第三NPN管(Q11)的基极，所述第三NPN管(Q11)的集电极连接于第一比较器(U9A)的反相端，所述第三NPN管(Q11)的发射极接地。
  8. 如权利要求7所述的修正波逆变器智能型短路保护开关电路，其特征在于，还包括有第四NPN管(Q13)，所述第二比较器(U9B)输出端的电信号传输至第四NPN管(Q13)的基极，所述第四NPN管(Q13)的集电极连接于第二比较器(U9B)的反相端，所述第四NPN管(Q13)的发射极接地。
  9. 如权利要求1所述的修正波逆变器智能型短路保护开关电路，其特征在于，所述逆变单元(30)包括由第三开关管(Q1)、第四开关管(Q2)、第五开关管(Q3)和第六开关管(Q4)组成的逆变桥，所述第三开关管(Q1)的栅极、第四开关管(Q2)的栅极、第五开关管(Q3)的栅极和第六开关管(Q4)的栅极分别用于接入PWM驱动信号，藉由所述 PWM驱动信号而控制第三开关管(Q1)、第四开关管(Q2)、第五开关管(Q3)和第六开关管(Q4)的导通状态，以令所述逆变单元(30)输出交流电。
  10. 如权利要求9所述的修正波逆变器智能型短路保护开关电路，其特征在于，所述电流采样电路(50)包括有相互并联的第四电阻(R3)、第五电阻(R4)和第六电阻(R5)，所述第四电阻(R3)、第五电阻(R4)和第六电阻(R5)的前端连接于逆变单元(30)的直流母线的负极，所述第四电阻(R3)、第五电阻(R4)和第六电阻(R5)的后端接地，且所述第四电阻(R3)、第五电阻(R4)和第六电阻(R5)的前端作为电流采样电路(50)的输出端。
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* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN109802373A (zh) * 2018-12-29 2019-05-24 惠州三华工业有限公司 提高区分度的短路保护电路及短路保护系统
CN110416978A (zh) * 2019-07-18 2019-11-05 珠海格力电器股份有限公司 一种直流母线保护电路、电路系统及空调外机
CN110504824A (zh) * 2019-09-05 2019-11-26 厦门厦华科技有限公司 一种双开关管驱动的均流电路
CN110611292A (zh) * 2019-10-26 2019-12-24 广州睿圣电子科技有限公司 一种pfc电路及其保护电路
CN110988575A (zh) * 2019-12-30 2020-04-10 国家电网有限公司 电力终端电量采集告警系统
CN111856125A (zh) * 2020-08-06 2020-10-30 汉纳森（厦门）数据股份有限公司 车辆以及车辆的大电流控制电路
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CN115808582A (zh) * 2022-11-21 2023-03-17 深圳市索源科技有限公司 一种逆变器负载检测电路
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Families Citing this family (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JP6340463B1 (ja) * 2017-09-26 2018-06-06 高周波熱錬株式会社 電源装置
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Citations (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN202840489U (zh) * 2012-09-05 2013-03-27 成都科方电源技术有限公司 逆变器输出短路保护和输出过载保护装置
TWI519052B (zh) * 2014-03-12 2016-01-21 旭隼科技股份有限公司 具短路保護的橋式電路及其方法
CN205195247U (zh) * 2015-12-12 2016-04-27 上海奉天电子股份有限公司 一种具有双重短路保护的逆变器
CN106300277A (zh) * 2016-08-31 2017-01-04 苏州迈力电器有限公司 高频逆变器短路保护控制电路

Family Cites Families (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US5726845A (en) * 1996-02-28 1998-03-10 Astec International Limited Short circuit protection for power factor correction circuit
CN202167837U (zh) * 2011-08-11 2012-03-14 海信（山东）空调有限公司 一种pfc过流保护电路及应用该电路的空调器
CN106329699B (zh) * 2015-06-24 2019-03-05 维谛技术有限公司 一种不间断电源及其控制方法、控制装置
CN206506287U (zh) * 2017-01-16 2017-09-19 广东百事泰电子商务股份有限公司 一种修正波逆变器智能型短路保护开关电路

Patent Citations (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN202840489U (zh) * 2012-09-05 2013-03-27 成都科方电源技术有限公司 逆变器输出短路保护和输出过载保护装置
TWI519052B (zh) * 2014-03-12 2016-01-21 旭隼科技股份有限公司 具短路保護的橋式電路及其方法
CN205195247U (zh) * 2015-12-12 2016-04-27 上海奉天电子股份有限公司 一种具有双重短路保护的逆变器
CN106300277A (zh) * 2016-08-31 2017-01-04 苏州迈力电器有限公司 高频逆变器短路保护控制电路

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* Cited by examiner, † Cited by third party
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