WO2018096731A1 - Filtre à guide d'ondes diélectrique, circuit frontal haute fréquence, dispositif de communication, système mimo massif, et procédé d'ajustement pour filtre à guide d'ondes diélectrique - Google Patents

Filtre à guide d'ondes diélectrique, circuit frontal haute fréquence, dispositif de communication, système mimo massif, et procédé d'ajustement pour filtre à guide d'ondes diélectrique Download PDF

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Publication number
WO2018096731A1
WO2018096731A1 PCT/JP2017/028152 JP2017028152W WO2018096731A1 WO 2018096731 A1 WO2018096731 A1 WO 2018096731A1 JP 2017028152 W JP2017028152 W JP 2017028152W WO 2018096731 A1 WO2018096731 A1 WO 2018096731A1
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WIPO (PCT)
Prior art keywords
dielectric
waveguide filter
resonance
dielectric waveguide
coupling
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Application number
PCT/JP2017/028152
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English (en)
Japanese (ja)
Inventor
多田　斉
実 松平
克人 黒田
小島　洋
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株式会社村田製作所
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Publication of WO2018096731A1 publication Critical patent/WO2018096731A1/fr

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    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
    • H01P1/00—Auxiliary devices
    • H01P1/20—Frequency-selective devices, e.g. filters
    • H01P1/207—Hollow waveguide filters
    • H01P1/208—Cascaded cavities; Cascaded resonators inside a hollow waveguide structure
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
    • H01P3/00—Waveguides; Transmission lines of the waveguide type
    • H01P3/12—Hollow waveguides
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q3/00—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system
    • H01Q3/26—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system varying the relative phase or relative amplitude of energisation between two or more active radiating elements; varying the distribution of energy across a radiating aperture
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
    • H04B1/38—Transceivers, i.e. devices in which transmitter and receiver form a structural unit and in which at least one part is used for functions of transmitting and receiving
    • H04B1/40—Circuits
    • H04B1/44—Transmit/receive switching
    • H04B1/48—Transmit/receive switching in circuits for connecting transmitter and receiver to a common transmission path, e.g. by energy of transmitter

Definitions

  • the present invention relates to a dielectric waveguide filter, a high-frequency front-end circuit, a communication device, a Massive MIMO system, and a method for adjusting a dielectric waveguide filter.
  • Patent Document 1 discloses a waveguide filter in which a plurality of resonance portions are formed in a dielectric block by a plurality of slits (grooves).
  • the slit shape for example, width and depth
  • the electrical coupling and bandwidth of the waveguide filter can be controlled, so that the performance characteristics of the waveguide filter can be controlled. Is described.
  • the present invention provides a dielectric waveguide filter whose pass bandwidth can be easily adjusted even after the dielectric waveguide filter is manufactured, and a high-frequency front-end circuit using the dielectric waveguide filter , A communication device, a Massive MIMO system, and a method for adjusting a dielectric waveguide filter.
  • a dielectric waveguide filter is a dielectric waveguide filter including a dielectric block having an electrode formed on a surface thereof, wherein the dielectric
  • the block includes a plurality of resonating parts in which electromagnetic field resonance occurs, and a coupling part that is located between at least one pair of adjacent resonating parts among the plurality of resonating parts and that couples the adjacent resonating parts.
  • TE Transverse Electric
  • different resonance modes occur depending on the frequency of the propagated signal.
  • an EVEN mode in which an in-phase electric field is excited in an adjacent resonance unit and an ODD mode in which an anti-phase electric field is excited are examples of different resonance modes.
  • the pass bandwidth of the dielectric waveguide filter is obtained by combining a plurality of different resonance modes.
  • a dielectric exposed portion is provided on the surface of the coupling portion of the dielectric block.
  • the adjustment can be performed by simply peeling off a part of the electrode formed on the surface of the coupling portion of the dielectric block, and it is not essential to change the shape of the dielectric block. As a result, a dielectric waveguide filter whose pass bandwidth can be easily adjusted is obtained.
  • the dielectric exposed portion includes a top surface facing a mounting surface on which the dielectric waveguide filter is mounted on a mounting substrate, and a side surface intersecting the top surface, of the surface of the coupling portion. It may be formed in the connection region.
  • the dielectric exposed portion is formed in a portion where the current density related to coupling in the EVEN mode becomes dominant in the EVEN mode and the ODD mode, the frequency of the EVEN mode is lowered.
  • the frequency of the ODD mode can be maintained.
  • the difference between the frequency of the EVEN mode and the frequency of the ODD mode is increased, and the bandwidth of the dielectric waveguide filter is increased (in other words, coupling is performed). Can be strengthened).
  • the dielectric exposed portion may have a long shape extending substantially parallel to the direction in which the resonance portions are arranged.
  • the frequency of the EVEN mode can be lowered more reliably.
  • the dielectric exposed portion may be formed in a central region of the top surface facing the mounting surface on which the dielectric waveguide filter is mounted on the mounting substrate, of the surface of the coupling portion.
  • the dielectric exposed portion is formed in a portion where the current density related to coupling in the ODD mode becomes dominant in the EVEN mode and the ODD mode described above, so that the frequency of the ODD mode is lowered.
  • the frequency of the EVEN mode can be maintained.
  • the difference between the frequency of the EVEN mode and the frequency of the ODD mode is reduced, and the bandwidth of the dielectric waveguide filter is reduced (in other words, coupling is performed). Can be weakened).
  • the dielectric exposed portion may have a long shape extending substantially perpendicular to the direction in which the resonance portions are arranged.
  • the frequency of the ODD mode can be more reliably lowered.
  • the dielectric block has at least one of a groove, a through hole, and a coupling window, and the groove, the through hole, among a plurality of portions that divide the dielectric block in a signal propagation direction, And the part which does not have any of the coupling window is the resonance part, and the cross section through which a signal can pass is narrowed compared with the resonance part by at least one of the groove, the through hole, and the coupling window.
  • the formed portion may be the coupling portion.
  • the resonance portion and the coupling portion can be provided in the dielectric block by the groove, the through hole, and the coupling window.
  • the coupling portion has a side surface intersecting a mounting surface on which the dielectric waveguide filter is mounted on a mounting substrate, and each of the plurality of resonance portions is a TE mode resonator, And the dielectric exposed portion includes the side surface of the coupling portion and the opposite side surface of the resonance portion. May be provided in at least one of them.
  • the resonance frequency of the ODD mode can be maintained while lowering the resonance frequency of the EVEN mode.
  • the resonance frequency of the EVEN mode is lower than the resonance frequency of the ODD mode, the difference between the resonance frequency of the EVEN mode and the resonance frequency of the ODD mode is increased, and the bandwidth of the dielectric waveguide filter is increased. Can do.
  • the dielectric exposed portion may be provided on the side surface of the coupling portion.
  • the dielectric exposed portion is formed on the side surface of the coupling portion where the inductive coupling becomes strong, the resonance frequency of the EVEN mode can be more reliably lowered.
  • the dielectric exposed portion may be provided on both the side surface of the coupling portion and the opposite side surface of the resonance portion.
  • the resonance frequency of the EVEN mode can be more reliably lowered.
  • the dielectric block is provided with a groove having a depth in a direction perpendicular to both the arrangement direction of the resonance parts and the vertical direction of the mounting surface, and the dielectric block is divided into signal propagation directions.
  • a portion not having the groove is the resonance portion, and a portion in which a cross section through which a signal can pass is narrowed by the groove compared with the resonance portion is the coupling portion
  • the bottom surface may be the side surface of the coupling portion, and the side surface of the groove may be the opposite side surface of the resonance portion.
  • the groove can be provided with the opposite side surface of the resonance portion and the side surface of the coupling portion in the dielectric block.
  • the bottom surface of the groove may have a roundness when the groove is viewed in cross section.
  • the dielectric exposed portion may be provided on all of the bottom surface of the groove.
  • the dielectric exposed portion is formed on the entire side surface of the coupling portion where inductive coupling is strong, the resonance frequency of the EVEN mode can be lowered more reliably.
  • the dielectric block includes four or more resonating portions, and the grooves in which the dielectric exposed portions are formed are provided between the adjacent resonating portions, and the four or more continuous resonating portions are provided.
  • the exposed area of the dielectric exposed part of the groove provided between the resonance part at the outermost end and the resonance part adjacent to the resonance part at the outermost end is the resonance at the outermost end. It may be larger than the exposed area of the dielectric exposed portion of the groove provided between the adjacent resonance portions inside the portion.
  • the inductive coupling between the outermost resonance part and the resonance part adjacent to the outermost resonance part is inductive coupling between the resonance parts adjacent to each other inside the outermost resonance part.
  • a stronger dielectric waveguide filter can be provided.
  • Each of the plurality of resonating parts is a TE mode resonator composed of individual dielectric blocks, and the coupling part has a joint surface between the surfaces that maximize the electric field of the pair of adjacent resonating parts.
  • the dielectric exposed portion may be provided at a joint of the dielectric block on the surface of the dielectric waveguide filter.
  • the dielectric exposed portion where the electrode is not formed is provided at the end of the joint surface of the TE mode resonator.
  • the plurality of resonance units are arranged on the first resonance unit group in a vertical direction perpendicular to the first resonance unit group including a plurality of first resonance units arranged along a predetermined plane.
  • a second resonance part group including one or more second resonance parts, and the first resonance part and the second resonance part arranged in the vertical direction are a joint surface between surfaces where the electric field is maximum.
  • the dielectric exposed portion may be provided on the surface of the coupling portion between the first resonance portion and the second resonance portion.
  • the coupling can be adjusted after manufacturing, and a compact dielectric having a plurality of resonance parts arranged in a small area by arranging a plurality of resonance parts in a direction along a predetermined plane and in a direction perpendicular thereto.
  • a waveguide filter is obtained.
  • the joint surface may be provided substantially parallel to the mounting surface of the dielectric waveguide filter.
  • the joint surface may be provided substantially perpendicular to the mounting surface of the dielectric waveguide filter.
  • the surface of the dielectric block may be recessed at the dielectric exposed portion.
  • the coupling by the magnetic field between the adjacent resonating parts is further strengthened through the hollow hollow space, and the coupling adjustment amount can be further increased.
  • a high-frequency front-end circuit includes the above-described dielectric waveguide filter connected to an antenna element, a transmission amplifier circuit that amplifies a high-frequency transmission signal transmitted to the antenna element, and the antenna element
  • a reception amplifying circuit for amplifying the high-frequency received signal received in step 1 a transmission amplifying circuit, the receiving amplifying circuit, and a switch circuit for switching connection between the dielectric waveguide filter.
  • a high-frequency front-end circuit includes a transmission amplifier circuit that amplifies a high-frequency transmission signal output from an RF signal processing circuit, and a reception amplifier circuit that amplifies a high-frequency reception signal and outputs the amplified signal to the RF signal processing circuit And the above-described dielectric waveguide filter disposed between the RF signal processing circuit and the transmission amplifier circuit or between the RF signal processing circuit and the reception amplifier circuit.
  • a communication apparatus includes an antenna element, the above-described high-frequency front-end circuit, which is connected to the antenna element and amplifies a high-frequency signal transmitted and received by the antenna element, and the high-frequency front-end circuit
  • An RF signal processing circuit that performs signal processing including frequency conversion between the high-frequency signal and the baseband signal, and a baseband signal processing that is connected to the RF signal processing circuit and processes the baseband signal A circuit.
  • a Massive MIMO system includes an antenna including a plurality of patch antennas arranged in a matrix, and the above-described dielectric waveguide filter for each patch antenna.
  • a method for adjusting a dielectric waveguide filter according to an aspect of the present invention includes a dielectric block having electrodes formed on a surface thereof, and the dielectric block includes a plurality of resonance units in which electromagnetic field resonance occurs. And a dielectric waveguide filter having a coupling part that is located between adjacent resonance parts and that couples adjacent resonance parts, a part of the electrode formed on the surface of the coupling part is removed. To do.
  • the dielectric waveguide filter whose pass bandwidth is easy to adjust, and the high frequency front end circuit using the said dielectric waveguide filter , A communication device, a Massive MIMO system, and a method for adjusting the dielectric waveguide filter.
  • FIG. 1 is a perspective view showing an example of the structure of a dielectric waveguide filter according to a comparative example of the first embodiment.
  • FIG. 2 is an exploded perspective view showing an example of the structure of the high-frequency module according to the comparative example of the first embodiment.
  • FIG. 3 is a graph showing an example of frequency characteristics of the dielectric waveguide filter according to the comparative example of the first embodiment.
  • FIG. 4 is a conceptual diagram illustrating the EVEN mode of the dielectric waveguide filter according to the comparative example of the first embodiment.
  • FIG. 5 is a diagram showing a simulation result of current distribution in the EVEN mode of the dielectric waveguide filter according to the comparative example of the first embodiment.
  • FIG. 1 is a perspective view showing an example of the structure of a dielectric waveguide filter according to a comparative example of the first embodiment.
  • FIG. 2 is an exploded perspective view showing an example of the structure of the high-frequency module according to the comparative example of the first embodiment.
  • FIG. 3 is
  • FIG. 6 is a conceptual diagram illustrating the ODD mode of the dielectric waveguide filter according to the comparative example of the first embodiment.
  • FIG. 7 is a diagram showing a simulation result of current distribution in the ODD mode of the dielectric waveguide filter according to the comparative example of the first embodiment.
  • FIG. 8 is a perspective view showing an example of the structure of the dielectric waveguide filter according to the first embodiment.
  • FIG. 9 is a perspective view showing a construction example of the dielectric exposed portion according to the first embodiment.
  • FIG. 10 is a graph showing an example of frequency characteristics of the dielectric waveguide filter according to the first exemplary embodiment.
  • FIG. 11 is a perspective view showing an example of the structure of the dielectric waveguide filter according to the first embodiment.
  • FIG. 12 is a perspective view showing a construction example of the dielectric exposed portion according to the first embodiment.
  • FIG. 13 is a graph showing an example of frequency characteristics of the dielectric waveguide filter according to the first exemplary embodiment.
  • FIG. 14 is a perspective view showing an example of the structure of a dielectric waveguide filter according to a comparative example of the second embodiment.
  • FIG. 15 is an exploded perspective view showing an example of the structure of a high-frequency module according to a comparative example of the second embodiment.
  • FIG. 16 is a conceptual diagram illustrating an EVEN mode of a dielectric waveguide filter according to a comparative example of the second embodiment.
  • FIG. 17 is a diagram illustrating a simulation result of current distribution in the EVEN mode of the dielectric waveguide filter according to the comparative example of the second embodiment.
  • FIG. 18 is a conceptual diagram illustrating an ODD mode of a dielectric waveguide filter according to a comparative example of the second embodiment.
  • FIG. 19 is a diagram illustrating a simulation result of current distribution in the ODD mode of the dielectric waveguide filter according to the comparative example of the second embodiment.
  • FIG. 20 is a perspective view showing an example of the structure of the dielectric waveguide filter according to the second embodiment.
  • FIG. 21 is a perspective view showing an example of the structure of the dielectric waveguide filter according to the second embodiment.
  • FIG. 22 is a perspective view showing an example of the structure of the dielectric waveguide filter according to the third embodiment.
  • FIG. 23 is a perspective view showing an example of the structure of a dielectric waveguide filter according to a comparative example of the fourth embodiment.
  • FIG. 24 is an exploded perspective view showing an example of the structure of a high-frequency module according to a comparative example of the fourth embodiment.
  • FIG. 25 is a graph showing an example of frequency characteristics of a dielectric waveguide filter according to a comparative example of the fourth embodiment.
  • FIG. 26 is a conceptual diagram illustrating the EVEN mode of the dielectric waveguide filter according to the comparative example of the fourth embodiment.
  • FIG. 27A is a perspective view illustrating a simulation result of a magnetic field in the EVEN mode of the dielectric waveguide filter according to the comparative example of the fourth embodiment.
  • FIG. 27B is a plan view showing a simulation result of a magnetic field in the EVEN mode of the dielectric waveguide filter according to the comparative example of the fourth embodiment.
  • FIG. 28 is a conceptual diagram illustrating an ODD mode of a dielectric waveguide filter according to a comparative example of the fourth embodiment.
  • FIG. 29A is a perspective view showing a simulation result of a magnetic field in the ODD mode of the dielectric waveguide filter according to the comparative example of the fourth embodiment.
  • FIG. 29B is a plan view showing a simulation result of the magnetic field in the ODD mode of the dielectric waveguide filter according to the comparative example of the fourth embodiment.
  • FIG. 30 is a perspective view showing an example of the structure of the dielectric waveguide filter according to the fourth embodiment.
  • FIG. 31A is a plan view of a dielectric waveguide filter according to Embodiment 4.
  • FIG. 31B is a side view of the dielectric waveguide filter according to the fourth exemplary embodiment.
  • FIG. 32 is a plan view showing a simulation result of a magnetic field in the EVEN mode of the dielectric waveguide filter according to the fourth embodiment.
  • FIG. 33A is a plan view of a dielectric waveguide filter according to Modification 1 of Embodiment 4.
  • FIG. FIG. 33B is a side view of a dielectric waveguide filter according to Modification 1 of Embodiment 4.
  • FIG. 34 is a plan view showing a simulation result of a magnetic field in the EVEN mode of the dielectric waveguide filter according to the first modification of the sixth embodiment.
  • FIG. 35A is a plan view of a dielectric waveguide filter according to Modification 2 of Embodiment 4.
  • FIG. FIG. 35B is a side view of the dielectric waveguide filter according to the second modification of the fourth embodiment.
  • FIG. 36 is a plan view showing a simulation result of a magnetic field in the EVEN mode of the dielectric waveguide filter according to the second modification of the fourth embodiment.
  • FIG. 37 is a diagram illustrating an example of the structure of a dielectric waveguide filter according to a third modification of the fourth embodiment.
  • FIG. 38 is a perspective view showing an example of the structure of the dielectric waveguide filter according to the fifth embodiment.
  • FIG. 39 is a perspective view showing a simulation result of the magnetic field of the resonating unit according to the fifth embodiment.
  • FIG. 40 is an enlarged perspective view showing an example of the structure of the dielectric waveguide filter according to the fifth embodiment.
  • FIG. 41 is a perspective view showing an example of the structure of the dielectric waveguide filter according to the fifth embodiment.
  • FIG. 42 is a perspective view showing an example of the structure of a dielectric waveguide filter according to a modification of the fifth embodiment.
  • FIG. 43 is an exploded perspective view showing an example of the structure of a dielectric waveguide filter according to a modification of the fifth embodiment.
  • FIG. 44A is a circuit diagram showing a high-frequency front-end circuit and a communication device according to Embodiment 6.
  • FIG. 44B is a circuit diagram showing a high-frequency front end circuit according to Modification 1 of Embodiment 6.
  • FIG. 44A is a circuit diagram showing a high-frequency front-end circuit and a communication device according to Embodiment 6.
  • FIG. 44B is a circuit diagram showing a high-frequency front end circuit according to Modification 1 of Embodiment 6.
  • FIG. 44C is a circuit diagram showing a high-frequency front end circuit according to the second modification of the sixth embodiment.
  • FIG. 45A is a circuit diagram showing a Massive MIMO system according to Embodiment 7.
  • FIG. 45B is a plan view of the antenna device of the Massive MIMO system according to Embodiment 7.
  • FIG. 1 is a perspective view showing an example of the structure of a dielectric waveguide filter according to a comparative example of the first embodiment, and shows a general dielectric waveguide filter as viewed from below the mounting surface. Yes.
  • the dielectric waveguide filter 1 is composed of a dielectric block 40 having an electrode 50 formed on the surface, and the dielectric block 40 has a groove 40a in a direction crossing the signal propagation direction. Is formed.
  • the dielectric block 40 is made of a dielectric material such as crystal or ceramic, and the groove 40a is provided by machining with a wire saw or the like, for example.
  • the electrode 50 is formed by, for example, applying and baking a conductive paste containing silver or copper. In FIG. 1, the electrode 50 is disposed in a hatched area on the surface of the dielectric block 40 and is not disposed in a white area.
  • the portions not including the groove 40 a are the resonance portions 11 and 12. Further, a portion including the groove 40 a and having a cross section through which a signal can pass is narrower than the resonance portions 11 and 12 is the coupling portion 17.
  • the resonating units 11 and 12 generate electromagnetic field resonance inside and function as dielectric resonators.
  • the coupling unit 17 couples the resonance units 11 and 12.
  • the coupling part 17 is an example of a coupling part constituted by grooves.
  • the coupling portion is a portion having a narrow cross section through which a signal can pass as compared with the resonance portion, and is not necessarily constituted by a groove.
  • the coupling portion may be configured by a through-hole, a coupling window, or the like, which will be described later.
  • the resonance units 11 and 12 are respectively provided with input / output units 21 and 22 for converting a signal propagation mode between a TE (Transverse Electric) mode and a TEM (Transverse ElectroMagnetic) mode.
  • the TE mode and the TEM mode are signal propagation modes inside and outside the dielectric waveguide filter 1, respectively.
  • the input / output units 21 and 22 are configured by electrodes 50 arranged in a specific shape on the mounting surface of the dielectric waveguide filter 1.
  • FIG. 2 is an exploded perspective view showing an example of the structure of the high-frequency module according to the comparative example of the first embodiment.
  • the high-frequency module 8 is formed by mounting the dielectric waveguide filter 1 on a substrate 80.
  • a broken line on the substrate 80 represents a mounting position of the dielectric waveguide filter 1.
  • a conductive foil 81 is laid on the substrate 80.
  • the substrate 80 is made of, for example, a resin such as epoxy or phenol, and the conductor foil 81 is made of, for example, a copper foil.
  • the conductor foil 81 is disposed in a region indicated by oblique lines on the surface of the substrate 80 and is not disposed in a white region.
  • the conductive foil 81 mainly forms a ground plane, and forms coplanar lines 82 and 83 at positions corresponding to the input / output portions 21 and 22 of the dielectric waveguide filter 1.
  • the high-frequency module 8 is configured by joining the conductive foil 81 of the substrate 80 and the electrode 50 on the mounting surface of the dielectric waveguide filter 1 with a conductive bonding material such as solder.
  • An application circuit using the high frequency module 8 inputs and outputs signals to and from the dielectric waveguide filter 1 via the coplanar lines 82 and 83 of the substrate 80.
  • FIG. 3 is a graph showing an example of frequency characteristics of the dielectric waveguide filter 1.
  • FIG. 3 shows the simulation results of the reflection characteristics at the input / output unit 21 and the pass characteristics when the input / output unit 21 is viewed from the input / output unit 21.
  • the frequency characteristics of the dielectric waveguide filter 1 have notches in the reflection characteristics and peaks in the pass characteristics at the two frequencies f1 and f2. Thereby, the dielectric waveguide filter 1 functions as a bandpass filter having a pass band corresponding to the frequencies f1 and f2.
  • the present inventor has found that the respective signals of the frequencies f1 and f2 are coupled by the following different resonance modes. It was.
  • FIG. 4 is a diagram for explaining a resonance mode of the dielectric waveguide filter 1 with respect to a signal having a frequency f1.
  • the signal of the frequency f1 applied to the input / output unit 21 propagates in the dielectric waveguide filter 1 by exciting the in-phase AC electric fields E1 and E2 in the resonance units 11 and 12. And output from the input / output unit 22.
  • a resonance mode in which an in-phase AC electric field is generated between adjacent resonance parts is referred to as an EVEN mode.
  • in-phase AC electric fields E1 and E2 are indicated by arrows in the same direction.
  • FIG. 5 is a diagram showing a simulation result of current distribution in the EVEN mode of the dielectric waveguide filter 1.
  • the EVEN mode current flowing on the surface of the coupling portion 17 becomes dominant in the direction substantially perpendicular to the arrangement direction of the resonance portions 11 and 12 from the side surface to the top surface.
  • the top surface is a surface facing the mounting surface on which the dielectric waveguide filter 1 is mounted on the mounting substrate, and the side surface is a surface intersecting the top surface.
  • the current I EVEN that becomes dominant in the EVEN mode on the surface of the coupling portion 17 is represented by a thick arrow.
  • the current I EVEN is considered to be involved in the coupling of the resonance units 11 and 12.
  • FIG. 6 is a diagram for explaining a resonance mode of the dielectric waveguide filter 1 with respect to a signal having a frequency f2.
  • the signal having the frequency f2 applied to the input / output unit 21 excites the AC electric fields E1 and E3 having opposite phases to the resonance units 11 and 12, and passes through the dielectric waveguide filter 1. Propagated and output from the input / output unit 22.
  • a resonance mode in which an AC electric field having a reverse phase is generated between adjacent resonance parts is referred to as an ODD mode.
  • AC electric fields E1 and E3 having opposite phases are represented by arrows pointing in the reverse direction.
  • FIG. 7 is a diagram showing a simulation result of current distribution in the ODD mode of the dielectric waveguide filter 1.
  • the ODD mode current flowing on the surface of the coupling portion 17 becomes predominant in the direction substantially parallel to the arrangement direction of the resonance portions 11 and 12 near the center of the top surface.
  • the current I ODD that prevails in the ODD mode on the surface of the coupling portion 17 is represented by a thick arrow.
  • the current I ODD is considered to be involved in the coupling of the resonance units 11 and 12.
  • the inventor Based on the analysis result of the current distribution in the dielectric waveguide filter 1 described above, the inventor provides a dielectric exposed portion where the electrode 50 is not formed on a specific portion of the surface of the coupling portion 17, thereby A technique for adjusting the passband width of a body waveguide filter has been devised.
  • the dielectric exposed portion is provided on the surface of the coupling portion 17 in a portion where the current density is dominant in any one of the plurality of resonance modes.
  • FIG. 8 is a perspective view showing an example of the structure of the dielectric waveguide filter according to the first embodiment.
  • the dielectric waveguide filter 1a of FIG. 8 is different from the dielectric waveguide filter 1 of FIG. 1 in that there is a dielectric exposed portion 61 where the electrode 50 is not formed on the surface of the coupling portion 17. .
  • the dielectric exposed portion 61 is provided at a position where the current I EVEN in FIG. 4 becomes more dominant than the current I ODD in FIG.
  • the dielectric exposed portion 61 is provided in a connection region between the top surface and the side surface of the coupling portion 17.
  • the connection region between the top surface and the side surface is a region near the boundary between the top surface and the side surface.
  • the top surface is divided into three parts in the direction substantially orthogonal to the signal propagation direction and It may be a region composed of the whole.
  • FIG. 9 is a perspective view showing a construction example of the dielectric exposed portion 61.
  • the dielectric exposed portion 61 a is formed by cutting the boundary between the top surface and the side surface of the coupling portion 17 with a drill and removing the electrode 50 together with a part of the dielectric block 40. Thus, when forming the dielectric exposure part 61, a part of dielectric block 40 may be shaved.
  • the dielectric exposed portion 61 is not limited to drilling, and may be formed by removing only the electrode 50 by laser processing, for example.
  • FIG. 10 is a graph showing an example of frequency characteristics of the dielectric waveguide filter 1a.
  • FIG. 10 shows simulation results based on the arrangement of the electrodes 50 in FIG. 8 as adjusted reflection characteristics and adjusted pass characteristics. For comparison, the reflection characteristics and transmission characteristics of the dielectric waveguide filter 1 are shown again.
  • the frequency of the EVEN mode decreases from f1 to f1a as compared to the frequency characteristic of the dielectric waveguide filter 1, whereas the ODD The mode frequency f2 is generally maintained. Therefore, in the dielectric waveguide filter 1a, the difference between the frequency f1a of the EVEN mode and the frequency f2 of the ODD mode is larger than that of the dielectric waveguide filter 1, and the passband width is expanded (in other words, resonance The coupling between the parts 11 and 12 is strengthened).
  • the dielectric exposed portion 61 Since the dielectric exposed portion 61 is provided at a position where the current I EVEN becomes dominant, the dielectric exposed portion 61 strongly inhibits the current I EVEN while not significantly affecting the current I ODD . As a result, it is considered that the current I EVEN must go through a long path, the frequency f1a in the EVEN mode is lowered, and the frequency f2 in the ODD mode is generally maintained.
  • the dielectric exposed portion 61 may have a long shape extending substantially parallel to the direction in which the resonance portions 11 and 12 are arranged. As a result, the dielectric exposed portion 61 that is long in the direction intersecting the current I EVEN in FIG. 4 is formed, so that the current I EVEN can be more reliably inhibited and the frequency of the EVEN mode can be more reliably lowered.
  • the dielectric exposure portion 61 can selectively adjust the frequency of the EVEN mode to widen the passband width.
  • the pass bandwidth can be narrowed with the same concept.
  • FIG. 11 is a perspective view showing another example of the structure of the dielectric waveguide filter according to the first embodiment.
  • the dielectric waveguide filter 1b of FIG. 11 differs from the dielectric waveguide filter 1a of FIG. 8 in the arrangement of the dielectric exposed portions 62.
  • the dielectric exposed portion 62 is provided at a position where the current I ODD in FIG. 5 becomes more dominant than the current I EVEN in FIG.
  • the dielectric exposed portion 62 is provided in the central region of the top surface of the coupling portion 17.
  • the central region of the top surface may be, for example, a central region obtained by dividing the top surface into three in a direction substantially orthogonal to the signal propagation direction.
  • FIG. 12 is a perspective view showing a construction example of the dielectric exposed portion 62.
  • the dielectric exposed portion 62 a is formed by cutting the center of the top surface of the coupling portion 17 with a drill and removing the electrode 50 together with a part of the dielectric block 40. As described above, when the dielectric exposed portion 62 is formed, a part of the dielectric block 40 may be removed.
  • the dielectric exposed portion 62 is not limited to drilling, and may be formed, for example, by removing only the electrode 50 by laser processing.
  • FIG. 13 is a graph showing an example of frequency characteristics of the dielectric waveguide filter 1b.
  • FIG. 13 shows simulation results based on the arrangement of the electrodes 50 in FIG. 11 as adjusted reflection characteristics and adjusted pass characteristics. For comparison, the reflection characteristics and transmission characteristics of the dielectric waveguide filter 1 are shown again.
  • the frequency of the ODD mode decreases from f2 to f2a as compared with the frequency characteristic of the dielectric waveguide filter 1, whereas EVEN The mode frequency f1 is generally maintained. Therefore, in the dielectric waveguide filter 1b, compared with the dielectric waveguide filter 1, the difference between the frequency f1 of the EVEN mode and the frequency f2a of the ODD mode is reduced, and the passband width is narrowed (in other words, resonance The coupling between the parts 11 and 12 is weakened).
  • the dielectric exposed portion 62 Since the dielectric exposed portion 62 is provided at a position where the current I ODD becomes dominant, the dielectric exposed portion 62 strongly inhibits the current I ODD, but does not significantly affect the current I EVEN . As a result, the current I ODD has to go through a long path, the frequency f2a in the ODD mode is lowered, and the frequency f1 in the EVEN mode is generally maintained.
  • the dielectric exposed portion 62 may have a long shape extending substantially perpendicular to the direction in which the resonance portions 11 and 12 are arranged. As a result, the dielectric exposed portion 62 that is long in the direction crossing the current I ODD in FIG. 6 is formed, so that the current I ODD can be more reliably inhibited and the frequency of the ODD mode can be lowered more reliably.
  • the dielectric exposed portion 62 can selectively adjust the frequency of the ODD mode to narrow the passband width.
  • the pass bandwidth of the dielectric waveguide filter is adjusted by adjusting the frequency of a specific resonance mode.
  • the adjustment can be performed by simply peeling off a part of the electrode 50 formed on the surface of the coupling portion 17, and it is not essential to change the shape of the dielectric block 40.
  • a dielectric waveguide filter can be obtained.
  • FIG. 14 is a perspective view showing an example of the structure of a dielectric waveguide filter according to a comparative example of the second embodiment, and shows a general dielectric waveguide filter as viewed from below the mounting surface. Yes.
  • the dielectric waveguide filter 2 includes a dielectric block 40 having an electrode 50 formed on the surface, and a through hole 40 b is formed in the dielectric block 40.
  • the electrode 50 is arranged in a region indicated by oblique lines on the surface of the dielectric block 40 and is not arranged in a white region. In the dielectric waveguide filter 2, the electrode 50 is also disposed on the inner wall of the through hole 40b.
  • the portions not including the through hole 40b are the resonance portions 11 and 12, respectively.
  • a portion including the through hole 40 b and having a cross section through which a signal can pass is narrower than the resonance portions 11 and 12 is the coupling portion 18.
  • the resonating units 11 and 12 function as a dielectric resonator, and the coupling unit 18 couples the resonating units 11 and 12.
  • the coupling portion 18 is an example of a coupling portion configured by a through hole.
  • FIG. 15 is an exploded perspective view showing an example of the structure of the high-frequency module according to the comparative example of the second embodiment.
  • the high-frequency module 9 is formed by mounting the dielectric waveguide filter 2 on a substrate 80.
  • a broken line on the substrate 80 represents a mounting position of the dielectric waveguide filter 2.
  • FIG. 16 is a diagram for explaining the EVEN mode of the dielectric waveguide filter 2. Similar to the EVEN mode of the dielectric waveguide filter 1 described with reference to FIG. 4, the signal applied to the input / output unit 21 excites the in-phase AC electric fields E1 and E2 to the resonance units 11 and 12, thereby causing dielectric conduction. It propagates through the wave tube filter 2 and is output from the input / output unit 22.
  • FIG. 17 is a diagram showing a simulation result of current distribution in the EVEN mode of the dielectric waveguide filter 2.
  • the current in the EVEN mode flowing through the surface of the coupling portion 18 flows from the side surface to the top surface as seen in the portion surrounded by the dotted line in FIG. 17. In the meantime, it becomes dominant in the direction substantially perpendicular to the direction in which the resonance parts 11 and 12 are arranged.
  • the current I EVEN that becomes dominant in the EVEN mode on the surface of the coupling portion 18 is represented by a thick arrow.
  • FIG. 18 is a diagram for explaining the ODD mode of the dielectric waveguide filter 2. Similar to the ODD mode of the dielectric waveguide filter 1 described with reference to FIG. 6, the signal applied to the input / output unit 21 excites the AC electric fields E 1 and E 3 having opposite phases to the resonance units 11 and 12, It propagates through the waveguide filter 2 and is output from the input / output unit 22.
  • FIG. 19 is a diagram showing a simulation result of current distribution in the ODD mode of the dielectric waveguide filter 2.
  • the current in the ODD mode flowing through the surface of the coupling portion 18 passes through the top surface as seen in the portion surrounded by the dotted line in FIG. On both sides of the mouth of the hole 40b, it becomes dominant in a direction substantially parallel to the direction in which the resonance parts 11 and 12 are arranged.
  • the current I ODD that is dominant in the ODD mode on the surface of the coupling portion 18 is represented by a thick arrow.
  • a dielectric exposed portion where the electrode 50 is not formed is provided on a specific portion of the surface of the coupling portion 18.
  • the pass bandwidth of the dielectric waveguide filter 2 can be adjusted.
  • FIG. 20 is a perspective view showing an example of the structure of the dielectric waveguide filter according to the second embodiment.
  • the dielectric waveguide filter 2a in FIG. 20 is different from the dielectric waveguide filter 2 in FIG. 14 in that there is a dielectric exposed portion 61 in which the electrode 50 is not formed on the surface of the coupling portion 18. .
  • the dielectric exposed portion 61 is provided at a position where the current I EVEN in FIG. 16 becomes more dominant than the current I ODD in FIG.
  • the dielectric exposed portion 61 is provided in a connection region between the top surface and the side surface of the coupling portion 18.
  • the connection region between the top surface and the side surface is a region near the boundary between the top surface and the side surface.
  • the top surface is divided into three parts in the direction substantially orthogonal to the signal propagation direction and It may be a region composed of the whole.
  • the dielectric exposed portion 61 is provided at a position where the current I EVEN dominates, it is considered that the frequency of the EVEN mode is lowered and the frequency of the ODD mode is maintained similarly to the dielectric exposed portion 61.
  • the dielectric exposed portion 61 may have a long shape extending substantially parallel to the direction in which the resonance portions 11 and 12 are arranged. Thereby, the long dielectric exposed portion 61 is formed in the direction intersecting with the current I EVEN in FIG. 16, so that the current I EVEN can be more reliably inhibited and the frequency of the EVEN mode can be more reliably lowered.
  • the dielectric exposure part 61 can selectively adjust the frequency of the EVEN mode to widen the passband width.
  • FIG. 21 is a perspective view showing another example of the structure of the dielectric waveguide filter according to the second embodiment.
  • the dielectric waveguide filter 2b shown in FIG. 21 is different from the dielectric waveguide filter 2a shown in FIG.
  • the dielectric exposed portion 62 is provided at a position where the current I ODD in FIG. 18 becomes more dominant than the current I EVEN in FIG.
  • the dielectric exposed portion 62 is provided in the central region of the top surface of the coupling portion 18.
  • the central region of the top surface may be, for example, a region obtained by removing the mouth portion of the through hole 40b from a central region obtained by dividing the top surface into three in a direction substantially orthogonal to the signal propagation direction.
  • the dielectric exposed portion 62 is provided at a position where the current I ODD becomes dominant, it is considered that the frequency of the ODD mode is lowered and the frequency of the EVEN mode is maintained, similarly to the dielectric exposed portion 62.
  • the dielectric exposed portion 62 may have a long shape extending substantially perpendicular to the direction in which the resonance portions 11 and 12 are arranged. As a result, the dielectric exposed portion 62 that is long in the direction intersecting with the current I ODD in FIG. 18 is formed, so that the current I ODD can be more reliably inhibited and the frequency of the ODD mode can be lowered more reliably.
  • the dielectric exposed portion 62 can selectively adjust the frequency of the ODD mode to narrow the passband width.
  • the pass bandwidth of the dielectric waveguide filter is adjusted by adjusting the frequency of a specific resonance mode.
  • the adjustment can be performed by simply peeling off a part of the electrode 50 formed on the surface of the coupling portion 18, and it is not essential to change the shape of the dielectric block 40.
  • FIG. 22 is a perspective view showing an example of the structure of the dielectric waveguide filter according to the third embodiment.
  • the dielectric waveguide filter 3 is configured by bonding dielectric waveguide filters 3 a and 3 b provided separately.
  • the dielectric waveguide filter 3a is composed of a dielectric block 41 having an electrode 51 formed on the surface thereof, and a groove 41a is formed in the dielectric block 41 in a direction crossing the signal propagation direction (Y direction). Yes.
  • the portions not including the groove 41a are the resonance portions 13a, 13b, and 13c.
  • the coupling portion 17 is a portion including the groove 41a and having a cross section (XZ plane) through which a signal can pass that is narrower than the XZ cross section of the resonance portions 13a, 13b, and 13c.
  • the resonance units 13a, 13b, and 13c function as dielectric resonators, and the coupling unit 17 couples the resonance units 13a and 13b and the resonance units 13b and 13c, respectively.
  • the dielectric waveguide filter 3b is composed of a dielectric block 42 having an electrode 52 formed on the surface thereof, and a groove 42a is formed in the dielectric block 42 in a direction crossing the signal propagation direction (Y direction). Yes.
  • the portions not including the groove 42a are the resonance portions 13d, 13e, and 13f.
  • the coupling portion 17 includes the groove 42a and a cross section (XZ plane) through which a signal can pass is narrower than the XZ cross section of the resonance portions 13d, 13e, and 13f.
  • the resonance units 13d, 13e, and 13f function as dielectric resonators, and the coupling unit 17 couples the resonance units 13d and 13e and the resonance units 13e and 13f, respectively.
  • a coupling window 53 for coupling the resonating parts 13c and 13d is provided on the joint surface (YZ surface) of the resonating parts 13c and 13d.
  • the coupling window 53 is formed by providing portions where the electrodes 51 and 52 are not disposed on the surfaces of the dielectric blocks 41 and 42 facing each other and bonding the portions. Between the resonating parts 13c and 13d, the signal propagates in the X direction, and the coupling window 53 is narrower than the YZ cross section of the resonating parts 13c and 13d.
  • a portion not including the coupling window 53 among the plurality of portions obtained by dividing the portions in the signal propagation direction (X direction) is the resonance portion. 13c and 13d. Further, a portion including the coupling window 53 and having a cross section (YZ plane) through which a signal can pass is narrower than the YZ cross section of the resonance portions 13 c and 13 d is the coupling portion 19.
  • the coupling portion 19 is an example of a coupling portion configured by a coupling window.
  • Dielectric waveguide filters 3a and 3b are bonded to each other with an adhesive, for example, so that dielectric waveguide filter 3 in which resonance portions 13a to 13f are connected in this order is configured.
  • FIG. 22 shows an example of the arrangement of the dielectric exposed portions 61 and 62 in each of the coupling portions 17 and 19.
  • the dielectric exposed portion 61 is provided in a connection region between the top surface and the side surface of each of the coupling portions 17 and 19.
  • the dielectric exposed portion 61 may have an elongated shape that extends substantially parallel to the direction in which adjacent resonance portions are arranged. In FIG. 22, for the sake of simplicity, the dielectric exposed portion 61 is shown only on the top surface of each of the coupling portions 17 and 19.
  • the dielectric exposed portion 62 is provided in the central region of the top surface of each of the coupling portions 17 and 19.
  • the dielectric exposed portion 62 may have a long shape extending substantially perpendicular to the direction in which the adjacent resonance portions are arranged.
  • the pass bandwidth described in the first embodiment can be adjusted by providing any one of the dielectric exposed portions 61 and 62 in each of the coupling portions 17 and 19. it can.
  • the passband width is widened (in other words, coupling between adjacent resonance portions is strengthened).
  • the dielectric exposed portion 62 is provided, the passband width is narrowed (in other words, the coupling between the adjacent resonance portions is weakened).
  • the frequency of the EVEN mode or the ODD mode is selectively adjusted by providing one of the dielectric exposed portions 61 and 62 in each of the coupling portions 17 and 19.
  • the pass bandwidth can be adjusted.
  • the dielectric exposed portions 61 and 62 provided in the dielectric waveguide filter 3 are confirmed as, for example, drilling marks shown in FIGS. 9 and 12 or laser processing marks (not shown).
  • the pass bandwidth of the dielectric waveguide filter is adjusted by adjusting the frequency of a specific resonance mode for each pair of adjacent resonance portions.
  • the adjustment can be performed by simply peeling off a part of the electrodes 51 and 52 formed on the surfaces of the coupling portions 17 and 19, and it is not essential to change the shapes of the dielectric blocks 41 and 42.
  • FIG. 23 is a perspective view showing an example of the structure of a dielectric waveguide filter according to a comparative example, and shows a general dielectric waveguide filter when the mounting surface 71 is viewed from below.
  • the dielectric waveguide filter 6 includes a dielectric block 43 having an electrode 50 formed on the surface thereof.
  • the dielectric block 43 has a groove 43a in a direction crossing the signal propagation direction. Is formed.
  • the dielectric block 43 is made of, for example, a dielectric material such as crystal or ceramic, and the groove 43a is provided by machining using, for example, a wire saw.
  • the electrode 50 is formed by, for example, applying and baking a conductive paste containing silver or copper. In FIG. 23, the electrode 50 is disposed in a region indicated by hatching on the surface of the dielectric block 43 and is not disposed in a white region.
  • the portions not including the groove 43 a are the resonance portions 11 and 12. Further, a portion including the groove 43 a and having a cross section through which a signal can pass is narrower than the resonance portions 11 and 12 is the coupling portion 17.
  • the resonating units 11 and 12 generate electromagnetic field resonance inside and function as a dielectric resonator in a TE (Transverse Electric) mode.
  • the coupling unit 17 couples the resonance units 11 and 12.
  • the coupling part 17 is an example of a coupling part constituted by the grooves 43a.
  • the resonance units 11 and 12 are provided with input / output units 21 and 22 for converting a signal propagation mode between a TE mode and a TEM (Transverse ElectroMagnetic) mode, respectively.
  • the input / output units 21 and 22 are configured by electrodes 50 arranged in a specific shape on the mounting surface 71 of the dielectric waveguide filter 6.
  • FIG. 24 is an exploded perspective view showing an example of the structure of the high-frequency module according to the comparative example.
  • the high-frequency module 8 is formed by mounting a dielectric waveguide filter 6 on a substrate 80.
  • a broken line on the substrate 80 represents a mounting position of the dielectric waveguide filter 6.
  • a conductive foil 81 is laid on the substrate 80.
  • the substrate 80 is made of, for example, a resin such as epoxy or phenol, and the conductor foil 81 is made of, for example, a copper foil.
  • the conductor foil 81 is disposed in a region indicated by oblique lines on the surface of the substrate 80 and is not disposed in a white region.
  • the conductive foil 81 mainly constitutes a ground plane, and coplanar lines 82 and 83 are constituted at positions corresponding to the input / output portions 21 and 22 of the dielectric waveguide filter 6.
  • the high-frequency module 8 is configured by bonding the conductive foil 81 of the substrate 80 and the electrode 50 on the mounting surface 71 of the dielectric waveguide filter 6 with a conductive bonding material such as solder.
  • An application circuit that uses the high-frequency module 8 inputs and outputs signals to and from the dielectric waveguide filter 6 via the coplanar lines 82 and 83 of the substrate 80.
  • FIG. 25 is a graph showing an example of frequency characteristics of the dielectric waveguide filter 6.
  • FIG. 25 shows respective simulation results of the reflection characteristics at the input / output unit 21 and the transmission characteristics when the input / output unit 22 is viewed from the input / output unit 21.
  • the frequency characteristics of the dielectric waveguide filter 6 have notches in the reflection characteristics and peaks in the transmission characteristics at the two resonance frequencies f1 and f2.
  • the dielectric waveguide filter 6 functions as a band-pass filter having a pass band corresponding to the resonance frequencies f1 and f2.
  • the present inventor has found that the respective resonance frequency f1 and f2 signals are coupled in the following different resonance modes. I found it.
  • FIG. 26 is a diagram for explaining a resonance mode of the dielectric waveguide filter 6 with respect to a signal having a resonance frequency f1.
  • the signal having the resonance frequency f1 applied to the input / output unit 21 excites the in-phase AC electric fields E1 and E2 in the resonance units 11 and 12, and passes through the dielectric waveguide filter 6. Propagated and output from the input / output unit 22.
  • a resonance mode in which an in-phase AC electric field is generated between adjacent resonance parts is referred to as an EVEN mode.
  • in-phase AC electric fields E1 and E2 are indicated by arrows in the same direction.
  • FIG. 27A is a perspective view showing a simulation result of a magnetic field in the EVEN mode of the dielectric waveguide filter 6.
  • FIG. 27B is a plan view showing a simulation result of the magnetic field in the EVEN mode of the dielectric waveguide filter 6, and is a cross section when the dielectric waveguide filter 6 is viewed in plan.
  • the EVEN mode magnetic field vector generated in the dielectric waveguide filter 6 appears inside each of the resonance part 11 and the resonance part 12, and in particular, the resonance part. It appears strongly along the side surface 73 of the coupling part 17 that connects 11 and 12.
  • the side surface 73 of the coupling portion 17 is a surface that intersects the mounting surface 71 on which the dielectric waveguide filter 6 is mounted on the mounting substrate.
  • the magnetic field vector Mv that becomes strong in the EVEN mode of the dielectric waveguide filter 6 is represented by a thick arrow. In the EVEN mode of the dielectric waveguide filter 6, it is considered that the magnetic field vector Mv is involved in the coupling of the resonance units 11 and 12.
  • FIG. 28 is a diagram for explaining a resonance mode of the dielectric waveguide filter 6 with respect to a signal having a resonance frequency f2.
  • the signal of the resonance frequency f2 applied to the input / output unit 21 excites the AC electric fields E1 and E3 having opposite phases to the resonance units 11 and 12, and the dielectric waveguide filter 6 Is output from the input / output unit 22.
  • a resonance mode in which an alternating-phase AC electric field is generated between adjacent resonance parts is referred to as an ODD mode.
  • AC electric fields E1 and E3 having opposite phases are represented by arrows pointing in the opposite direction.
  • FIG. 29A is a perspective view showing a simulation result of a magnetic field in the ODD mode of the dielectric waveguide filter 6.
  • FIG. 29B is a plan view showing a simulation result of the magnetic field in the ODD mode of the dielectric waveguide filter 6, and is a cross section when the dielectric waveguide filter 6 is viewed in plan.
  • the ODD mode magnetic field vector generated in the dielectric waveguide filter 6 appears so as to circulate in the opposite directions inside the resonating unit 11 and the resonating unit 12, respectively.
  • the magnetic field vector in the ODD mode in the coupling portion 17 appears in a direction substantially perpendicular to the direction in which the resonance portions 11 and 12 are arranged. In the ODD mode of the dielectric waveguide filter 6, it is considered that the magnetic field vector is less likely to be involved in the coupling of the resonance units 11 and 12.
  • the present inventor provides a dielectric exposed portion in which the electrode 50 is not formed in a specific portion of the dielectric waveguide filter 6 based on the analysis result of the magnetic field in the dielectric waveguide filter 6 described above.
  • a technique for adjusting the passband width of a dielectric waveguide filter has been devised.
  • the dielectric exposed portion is provided in a portion where the magnetic field vector strongly appears in the EVEN mode in the dielectric waveguide filter 6.
  • FIG. 30 is a perspective view showing an example of the structure of the dielectric waveguide filter 6a according to the sixth embodiment.
  • FIG. 31A is a plan view of the dielectric waveguide filter 6a, and is a cross section when the dielectric waveguide filter 6a is viewed in plan.
  • FIG. 31B is a side view of the dielectric waveguide filter 6a.
  • FIG. 32 is a plan view showing a simulation result of the magnetic field of the dielectric waveguide filter 6a.
  • the dielectric waveguide filter 6a of the present embodiment has a dielectric exposed portion 63 where the electrode 50 is not formed on the side surface 73 of the coupling portion 17. It is different in point.
  • the dielectric block 43 of the dielectric waveguide filter 6a is provided with a pair of grooves 43a.
  • the groove 43 a is provided in the dielectric block 43 so as to have a depth in a direction perpendicular to both the arrangement direction of the resonance parts 11 and 12 and the vertical direction of the mounting surface 71.
  • the groove 43 a is provided along a direction perpendicular to the mounting surface 71 and penetrates the dielectric block 43.
  • the dielectric exposed portion 63 is provided on the side surface 73 of the coupling portion 17 that is the same surface as the bottom surface of the groove 43a. As described above, the side surface 73 of the coupling portion 17 is a place where the EVEN mode magnetic field vector Mv appears strongly. In the present embodiment, the dielectric exposed portion 63 is provided on the entire side surface 73.
  • the dielectric exposed portion 63 is formed by cutting the side surface 73 of the coupling portion 17 with a drill and removing the electrode 50 together with a part of the dielectric block 43. As described above, when the dielectric exposed portion 63 is formed, a part of the dielectric block 43 may be removed.
  • the dielectric exposed portion 63 is not limited to drilling, and may be formed by removing only the electrode 50 by laser processing, for example.
  • the magnetic field vector Mv is limited by the electrode 50 provided on the side surface 73 of the coupling portion 17.
  • the dielectric exposed portion 63 is provided on the side surface 73 of the coupling portion 17, and as shown in FIG. Is alleviated. Therefore, inductive coupling in the EVEN mode can be strengthened.
  • the resonance frequency f1 of the EVEN mode is lower than that of the dielectric waveguide filter 6 of the comparative example. Further, the resonance frequency f2 of the ODD mode is generally maintained. Therefore, in the dielectric waveguide filter 6a, compared to the dielectric waveguide filter 6, the difference (f2-f1) in the resonance frequency between the EVEN mode and the ODD mode is increased, and the passband width is widened.
  • the passband width of the dielectric waveguide filter 6a can be adjusted by providing the dielectric exposed portion 63 on the side surface 73 of the coupling portion 17. It can.
  • the adjustment can be performed by simply peeling off a part of the electrode 50 formed on the side surface 73 of the coupling portion 17, and it is not essential to change the shape of the dielectric block 43.
  • it is practically possible to individually adjust the pass bandwidth of many dielectric waveguide filters after the electrodes are formed on the surface in the mass production process.
  • a dielectric waveguide filter can be obtained.
  • FIG. 33A is a plan view of a dielectric waveguide filter 6b according to Modification 1 of Embodiment 4, and is a cross section when the dielectric waveguide filter 6b is viewed in plan.
  • FIG. 33B is a side view of the dielectric waveguide filter 6b.
  • FIG. 34 is a plan view showing a simulation result of the magnetic field in the EVEN mode of the dielectric waveguide filter 6b.
  • the bottom surface of the groove 43a (side surface 73 of the coupling portion 17) is curved. Specifically, when the groove 43a is viewed in cross section, the bottom surface of the groove 43a is rounded.
  • the dielectric exposed portion 63 is provided on the entire bottom surface having the roundness. In other words, when the groove 43 a is viewed in cross section, the dielectric exposed portion 63 is rounded, and a space is formed between both ends of the dielectric exposed portion 63.
  • the passband width of the dielectric waveguide filter 6b can be adjusted by providing the dielectric exposed portion 63 on the bottom surface of the groove 43a. Further, since the dielectric exposed portion 63 is rounded, as shown in FIG. 34, a magnetic field vector that penetrates the space from one end portion of both ends of the dielectric exposed portion 63 and reaches the other end portion is obtained. Will occur and inductive coupling can be increased. With this structure, in the dielectric waveguide filter 6b, the passband width can be largely adjusted as compared with the dielectric waveguide filter 6a of the fourth embodiment.
  • FIG. 35A is a plan view of a dielectric waveguide filter 6c according to Modification 2 of Embodiment 4, and is a cross section when the dielectric waveguide filter 6c is viewed in plan.
  • FIG. 35B is a side view of the dielectric waveguide filter 6c.
  • FIG. 36 is a plan view showing a simulation result of a magnetic field in the EVEN mode of the dielectric waveguide filter 6c.
  • the dielectric exposed portion 63 is provided not only on the bottom surface of the groove 43a but also on the side surface of the groove 43a. Specifically, the dielectric exposed portion 63 is provided on the opposite side surface 75 of the resonance portions 11 and 12 that is the side surface of the groove 43a.
  • the opposing side surface 75 is a surface that intersects the mounting surface 71 and the side surface 73 and faces between the pair of adjacent resonance portions 11 and 12.
  • the dielectric exposed portion 63 is U-shaped, and a space is formed between both ends of the dielectric exposed portion 63.
  • the passband width of the dielectric waveguide filter 6c is adjusted by providing the dielectric exposed portion 63 on the side surface of the groove 43a (opposite side surface 75 of the resonance portions 11 and 12). can do. Further, since the dielectric exposed portion 63 is provided on the side surface of the groove 43a, as shown in FIG. 36, the dielectric exposed portion 63 penetrates the space from one end portion of the both ends of the dielectric exposed portion 63 to reach the other end portion. A magnetic field vector is generated, and inductive coupling can be increased. With this structure, the passband width of the dielectric waveguide filter 6c can be adjusted larger than that of the dielectric waveguide filter 6a of the fourth embodiment.
  • FIG. 37 is a diagram illustrating an example of the structure of the dielectric waveguide filter 6d according to the third modification of the fourth embodiment, and is a cross section when the dielectric waveguide filter 6d is viewed in plan.
  • FIG. 37A is an overall view of the dielectric waveguide filter 6d
  • FIG. 37B is a partially enlarged view of FIG.
  • the dielectric waveguide filter 6d of Modification 3 has four or more continuous resonance portions, and the exposed areas of the dielectric exposure portions 63 provided between adjacent resonance portions are different.
  • the dielectric waveguide filter 6d has nine resonating portions 11a, 11b, 11c, 11d, 11e, 11f, 11g, 11h, and 11i.
  • the dielectric waveguide filter 6d is composed of a dielectric block 43 having an electrode 50 formed on the surface thereof, and a groove 43a is formed in the dielectric block 43 in a direction crossing the signal propagation direction.
  • the portions not including the groove 43a are the resonance portions 11a to 11i.
  • a portion including the groove 43a and having a cross section through which a signal can pass is narrower than the resonance portions 11a to 11i is the coupling portion 17.
  • the resonating units 11a to 11i cause electromagnetic field resonance inside and function as TE mode dielectric resonators.
  • the coupling unit 17 couples the adjacent resonance units 11a to 11i.
  • the groove 43a is provided between the adjacent resonance parts 11a to 11i, and the dielectric exposed part 63 is formed in the groove 43a.
  • the resonating unit 11a and the resonating unit 11i are provided with input / output units 21 and 22 for converting the signal propagation mode between the TE mode and the TEM mode, respectively.
  • the input / output units 21 and 22 are configured by electrodes 50 arranged in a specific shape on the mounting surface 71 of the dielectric waveguide filter 6d.
  • the exposed area of the dielectric exposed portion 63 provided on the side surface of the groove 43a differs between adjacent resonators. Specifically, in the arrangement direction of the resonance parts 11a to 11i, the exposed area gradually decreases from one outermost resonance part 11a toward the center resonance part 11e. Further, the exposed area gradually increases from the central resonance portion 11e toward the other outermost resonance portion 11i. For example, as shown in FIG. 37B, the depth of the dielectric exposed portion 63 in the groove 43a between the resonance portions 11a and 11b is d1, and the dielectric exposed portion in the groove 43a between the resonance portions 11b and 11c.
  • the depth of the dielectric exposed portion 63 in the groove 43a between the resonance portions 11c and 11d is d3, and the depth of the dielectric exposed portion 63 in the groove 43a between the resonance portions 11d and 11e is d4.
  • the exposed area of the dielectric exposed portion 63 of the groove 43a provided between the outermost resonance portion 11a and the resonance portion 11b adjacent to the outermost resonance portion 11a is the outermost resonance portion 11a. Is larger than the exposed area of the dielectric exposed portion 63 of the groove 43a provided between the adjacent resonance portions 11b and 11c. Further, the exposed area of the dielectric exposed portion 63 of the groove 43a provided between the outermost resonance portion 11i and the resonance portion 11h adjacent to the outermost resonance portion 11i is the outermost resonance portion 11i. Is larger than the exposed area of the dielectric exposed portion 63 of the groove 43a provided between the adjacent resonance portions 11h and 11g.
  • inductive coupling between the outermost resonance part 11a and the resonance part 11b adjacent to the outermost resonance part 11a is adjacent to the inner side of the outermost resonance part 11a.
  • a dielectric waveguide filter 6d having a structure stronger than the inductive coupling between the resonating portions 11b and 11c can be provided.
  • the dielectric exposed portion is provided in the portion where the magnetic field of the dielectric waveguide filter strongly appears to adjust the coupling between the adjacent resonance portions.
  • the portion where the dielectric exposed portion is provided It is not limited to examples.
  • the coupling between the adjacent resonance portions may be adjusted by providing a dielectric exposure portion in a portion where the electric field of the dielectric waveguide filter strongly appears.
  • a dielectric waveguide filter in which a plurality of TE mode resonators configured by individual dielectric blocks are coupled, at least one pair of adjacent TE mode resonators has a surface (hereinafter referred to as a maximum electric field).
  • a maximum electric field A configuration in which a dielectric exposed portion is provided at the joint of the dielectric block on the surface of the dielectric waveguide filter in the case where they are bonded at a joint surface between them (referred to as E plane).
  • FIG. 38 is a perspective view showing an example of the structure of the dielectric waveguide filter according to the fourth embodiment.
  • the dielectric waveguide filter 7a is configured by bonding the resonating portions 14a and 14b provided separately.
  • the resonating portions 14a and 14b are TE mode resonators configured by dielectric blocks 44a and 44b having electrodes formed on the surfaces, respectively.
  • the following magnetic field vectors are generated inside the TE mode resonator, that is, the resonance portions 14a and 14b.
  • FIG. 39 is a perspective view showing a simulation result of the magnetic field of the TE mode resonator.
  • a magnetic field in the direction along the XY plane appears strongly, so that the electric field becomes maximum on the XY plane.
  • the resonating portions 14a and 14b are coupled at the joint surface between the E surfaces where the electric field is maximum.
  • the coupling portion that couples the resonating portions 14a and 14b includes a joint surface between the E surfaces that maximizes the electric field.
  • a coupling window 54a that couples the resonating portions 14a and 14b is provided at the periphery of the joint surface (XY surface) of the resonating portions 14a and 14b.
  • a dielectric exposed portion 64 is provided at the joint 76 of the dielectric blocks 44a and 44b on the surface of the dielectric waveguide filter 7a.
  • FIG. 40 is an enlarged perspective view showing an example of a detailed shape of the dielectric exposed portion 64.
  • the dielectric exposed portion 64 is formed by, for example, cutting the joint 76 on the surface of the dielectric waveguide filter 7a with a drill and removing the electrodes together with a part of the dielectric blocks 44a and 44b. Is formed by.
  • a part of dielectric block 44a, 44b may be shaved. That is, the surfaces of the dielectric blocks 44 a and 44 b may be recessed in the dielectric exposed portion 64.
  • the dielectric exposed portion 64 is not limited to drilling, and may be formed by removing only the electrodes by laser processing, for example.
  • the position of the coupling window in the dielectric waveguide filter is not limited to the example of FIG.
  • FIG. 41 is a perspective view showing an example of the structure of a dielectric waveguide filter in which the installation position of the coupling window is different.
  • the dielectric waveguide filter 7b of FIG. 41 is different from the dielectric waveguide filter 7a in that the coupling window 54b is provided at the center of the joint surface (XY plane) of the resonance portions 14a and 14b. Is different.
  • the shape of the dielectric exposed portion 64 is the same in the dielectric waveguide filters 7a and 7b.
  • the coupling between the resonance parts 14a and 14b in the dielectric waveguide filter 7a is inductive, and the coupling between the resonance parts 14a and 14b in the dielectric waveguide filter 7b is It is capacitive.
  • the resonance portion Coupling due to a magnetic field newly occurs between 14a and 14b.
  • the main coupling between the resonance parts 14a and 14b is an inductive coupling (for example, the dielectric waveguide filter 7a in FIG. 38)
  • the inductive coupling can be strengthened by a newly generated magnetic field.
  • the main coupling between the resonating portions 14a and 14b is capacitive coupling (for example, the dielectric waveguide filter 7b in FIG. 41)
  • the capacitive coupling can be weakened by a newly generated magnetic field.
  • the amount of coupling between the resonance parts can be adjusted after bonding the resonance parts, that is, after manufacturing.
  • the coupling by the magnetic field between the resonance portions 14a and 14b is further strengthened through the hollow space, and the coupling adjustment amount is further increased. be able to.
  • the mounting direction of the dielectric waveguide filters 7a and 7b to the mounting substrate is not particularly limited.
  • the mounting surfaces of the dielectric waveguide filters 7a and 7b may be provided on the XY plane substantially parallel to the joint surfaces of the resonance portions 14a and 14b.
  • the resonance portions 14a and 14b are stacked on the mounting substrate, and the bonding surfaces of the resonance portions 14a and 14b are disposed in a direction substantially parallel to the mounting substrate.
  • the mounting surfaces of the dielectric waveguide filters 7a and 7b may be provided on the YZ surface or the XZ surface substantially perpendicular to the joint surfaces of the resonance portions 14a and 14b.
  • the resonance parts 14a and 14b are arranged in a plane on the mounting board, and the joint surfaces of the resonance parts 14a and 14b are arranged in a direction substantially perpendicular to the mounting board.
  • the degree of freedom in mounting and arranging the dielectric waveguide filters 7a and 7b is high.
  • the dielectric exposed portion 64 may be provided on the facing surface of the mounting surface of the dielectric waveguide filters 7a and 7b. Thereby, even after the dielectric waveguide filters 7a and 7b are attached to the mounting substrate, the coupling amount between the resonance parts can be easily adjusted.
  • FIG. 42 is a perspective view showing an example of the structure of the dielectric waveguide filter according to the first modification of the fifth embodiment.
  • FIG. 43 is an exploded perspective view showing an example of the structure of the dielectric waveguide filter according to the first modification of the fifth embodiment.
  • the dielectric waveguide filter 7c includes a plurality of resonance units 15a to 15h and input / output units 23a and 23b provided in the resonance units 15a and 15h, respectively.
  • the resonance parts 15a, 15b, 15g, and 15h are disposed along the XY plane, and the resonance parts 15d, 15c, 15f, and 15e are respectively disposed on the resonance parts 15a, 15b, 15g, and 15h in the Z direction.
  • the XY plane is an example of a predetermined plane
  • the Z direction is an example of the vertical direction perpendicular to the predetermined plane.
  • the resonating portions 15a and 15b are constituted by a dielectric block 45a and are coupled by a coupling portion constituted by a groove.
  • the resonating parts 15c and 15d are constituted by a dielectric block 45b and are coupled by a coupling part constituted by a groove.
  • the resonating parts 15e and 15f are constituted by a dielectric block 45c and are coupled by a coupling part constituted by a groove.
  • the resonating portions 15g and 15h are constituted by a dielectric block 45d and are coupled by a coupling portion constituted by a groove.
  • the resonating parts 15b and 15c are coupled by a coupling part constituted by a coupling window 55a provided in the dielectric blocks 45a and 45b.
  • the resonating portions 15d and 15e are coupled by a coupling portion constituted by a coupling window 55b provided in the dielectric blocks 45b and 45c.
  • the resonating parts 15f and 15g are coupled by a coupling part constituted by a coupling window 55c provided in the dielectric blocks 45c and 45d.
  • the dielectric exposed portions 65a and 65b are provided on the surface of the coupling portion of the resonance portions 15b and 15c, that is, the joint 77 of the dielectric blocks 45a and 45b.
  • the dielectric waveguide filter 7c configured as described above, coupling adjustment after manufacture is possible, and a plurality of resonance portions are arranged in the direction along the XY plane and the Z direction perpendicular to the XY plane.
  • a compact dielectric waveguide filter in which a large number of resonance parts are arranged in a small area can be obtained.
  • FIG. 44A is a circuit diagram showing the high-frequency front-end circuit 110 and its peripheral circuit (communication device) according to the sixth embodiment.
  • a high-frequency front-end circuit 110 an antenna element 150, an RF signal processing circuit 191 and a baseband signal processing circuit 192 are shown.
  • the high-frequency front end circuit 110 includes filters 161, 162, and 163, a switch circuit 170, a power amplifier circuit 181, and a low noise amplifier circuit 182.
  • the power amplifier circuit 181 is a transmission amplification circuit that amplifies the high-frequency transmission signal output from the RF signal processing circuit 191 and outputs the amplified signal to the antenna element 150 via the switch circuit 170 and the filter 161.
  • the low noise amplifier circuit 182 is a reception amplification circuit that amplifies a high-frequency signal that has passed through the antenna element 150, the filter 161, and the switch circuit 170 and outputs the amplified signal to the RF signal processing circuit 191.
  • the filter 161 is an antenna filter that is connected to the antenna element 150 and selectively allows high-frequency signals in the transmission band and the reception band to pass therethrough, for example.
  • the filter 162 is an interstage filter that is disposed between the power amplifier circuit 181 and the RF signal processing circuit 191 and selectively passes a high-frequency signal in the transmission band.
  • the filter 163 is an interstage filter that is disposed between the low noise amplifier circuit 182 and the RF signal processing circuit 191 and selectively passes a high frequency signal in the reception band.
  • the switch circuit 170 is a switch that switches connection between the antenna element 150 and the transmission signal path and the reception signal path.
  • the RF signal processing circuit 191 processes the high-frequency reception signal input from the antenna element 150 via the reception signal path by down-conversion or the like, and the baseband signal processing circuit 192 generates the reception signal generated by the signal processing. Output to.
  • the RF signal processing circuit 191 is, for example, an RFIC (Radio Frequency Integrated Circuit). Further, the RF signal processing circuit 191 performs signal processing on the transmission signal input from the baseband signal processing circuit 192 by up-conversion or the like, and outputs the high-frequency transmission signal generated by the signal processing to the power amplifier circuit 181.
  • the signal processed by the baseband signal processing circuit 192 is used, for example, for displaying an image as an image signal or for calling as an audio signal.
  • the high-frequency front end circuit 110 may include other circuit elements between the filters 161, 162, and 163, the switch circuit 170, the power amplifier circuit 181, and the low noise amplifier circuit 182.
  • the dielectric waveguide filters according to the first to fifth embodiments can be used as the filters 161, 162, and 163.
  • the pass bandwidths of the filters 161, 162, and 163 can be easily adjusted, so that it is possible to realize a high-frequency front-end circuit that reduces the variation in high-frequency characteristics while reducing the manufacturing cost. .
  • FIG. 44B is a circuit diagram showing the high-frequency front-end circuit 110B according to the first modification of the sixth embodiment.
  • the high frequency front end circuit 110 ⁇ / b> B includes filters 161, 162 and 163, a power amplifier circuit 181, a low noise amplifier circuit 182, a circulator 171, and a switch circuit 172.
  • the high-frequency front end circuit 110B according to this modification is different from the high-frequency front end circuit 110 in the configuration for switching between the transmission signal path and the reception signal path.
  • the description of the same configuration as that of the high-frequency front end circuit 110 will be omitted, and a description will be given focusing on different configurations.
  • the circulator 171 has an antenna-side terminal, a transmission-side terminal, and a reception-side terminal. During reception, the circulator 171 selectively propagates a reception signal from the antenna element 150 to the reception signal path, and at the time of transmission, the antenna element 150 is transmitted from the transmission signal path. This is a circuit element that selectively propagates a transmission signal to.
  • the switch circuit 172 is a switch for switching the connection between the circulator 171 and the reception signal path.
  • the receiving side terminal of the circulator 171 is terminated with a terminating resistor (50 ⁇ ).
  • the reception side terminal of the circulator 171 is connected to the low noise amplifier circuit 182.
  • the high-frequency front end circuit 110B is applied as a time division duplex front-end circuit.
  • the dielectric waveguide filters according to the first to fifth embodiments can be used as the filters 161, 162, and 163.
  • FIG. 44C is a circuit diagram showing a high-frequency front-end circuit 110C according to the second modification of the sixth embodiment.
  • the high frequency front end circuit 110 ⁇ / b> C includes a duplexer 164, filters 162 and 163, a power amplifier circuit 181, a low noise amplifier circuit 182, and an isolator 173.
  • the high-frequency front end circuit 110C according to this modification is different from the high-frequency front end circuit 110 in the configuration for switching between the transmission signal path and the reception signal path.
  • the description of the same configuration as that of the high-frequency front end circuit 110 will be omitted, and a description will be given focusing on different configurations.
  • the duplexer 164 has an antenna terminal, a transmission side terminal, and a reception side terminal, has a transmission filter between the antenna terminal and the transmission side terminal, and has a reception filter between the antenna terminal and the reception side terminal. Have.
  • the isolator 173 is a circuit element that is disposed between the transmission-side terminal of the duplexer 164 and the power amplifier circuit 181 and propagates a transmission signal in one direction from the power amplifier circuit 181 to the duplexer 164.
  • the isolator 173 can be realized, for example, by terminating one terminal among the three terminals of the circulator by 50 ⁇ .
  • the high frequency front end circuit 110C is applied as a front end circuit of a frequency division duplex system.
  • the dielectric waveguide filter according to the first to fifth embodiments is used as the transmission-side filter and the reception-side filter of the duplexer 164 and the filters 162 and 163. it can.
  • the phantom cell is a network configuration that separates a control signal for ensuring communication stability between a macro cell in a low frequency band and a small cell in a high frequency band and a data signal that is a target of high-speed data communication.
  • Each phantom cell is provided with a Massive MIMO antenna device.
  • the Massive MIMO system is a technique for improving transmission quality in a millimeter wave band or the like, and controls the directivity of the antenna element by controlling a signal transmitted from each antenna element.
  • the Massive MIMO system uses a large number of antenna elements, and therefore can generate a sharp directional beam.
  • By increasing the directivity of the beam it is possible to fly radio waves to some extent even in a high frequency band, and it is possible to reduce the interference between cells and increase the frequency utilization efficiency.
  • FIG. 45A is a circuit diagram showing a Massive MIMO system according to Embodiment 7.
  • FIG. 45B is a plan view of the antenna device of the Massive MIMO system according to Embodiment 7.
  • the antenna device 111 shown in FIG. 45B is used in the Massive MIMO system shown in FIG. 45A.
  • the antenna device 111 includes a plurality of patch antennas 112 arranged in a matrix.
  • FIG. 45A is a diagram illustrating a configuration of a high-frequency front-end circuit 110A including the antenna device 111.
  • This high-frequency front end circuit 110A is a Massive MIMO system according to the present embodiment.
  • the patch antenna 112 is connected with band-pass filters 161a, 161b and 161c.
  • a switch circuit 170a is connected between the filter 161a, the power amplifier circuit 181a, and the low noise amplifier circuit 182a.
  • a switch circuit 170b is connected between the filter 161b, the power amplifier circuit 181b, and the low noise amplifier circuit 182b.
  • a switch circuit 170c is connected between the filter 161c, the power amplifier circuit 181c, and the low noise amplifier circuit 182c.
  • the low noise amplifier circuits 182a, 182b, and 182c are connected to the baseband signal processing circuit 192.
  • a band pass filter 162a and a mixer 194a are connected between the baseband signal processing circuit 192 and the power amplifier circuit 181a.
  • a band-pass filter 162b and a mixer 194b are connected between the baseband signal processing circuit 192 and the power amplifier circuit 181b.
  • a band-pass filter 162c and a mixer 194c are connected between the baseband signal processing circuit 192 and the power amplifier circuit 181c.
  • a local oscillator 193 is connected to the mixers 194a, 194b and 194c. The local oscillator 193 outputs, to the mixers 194a to 194c, a reference frequency for up-conversion to a high frequency and down-conversion to a low frequency in the mixers 194a to 194c.
  • Filters 161a to 161c pass the transmission / reception frequency band and remove other frequency components.
  • the switch circuits 170a to 170c switch between a transmission signal and a reception signal.
  • the filters 162a to 162c pass the frequency band of the transmission signal and remove other frequency components.
  • the dielectric waveguide filters according to the first to fifth embodiments can be used as the filters 161a to 161c and 162a to 162c.
  • the filters 161a to 161c connected to the patch antenna 112 may be arranged on the back surface of the substrate on which the patch antenna 112 is formed. Good. Thereby, the antenna device 111 including the patch antenna 112 with the filters 161a to 161c is configured.
  • the pass bandwidths of the filters 161a to 161c and 162a to 162c can be easily adjusted, so that the variation in high-frequency characteristics is reduced while reducing the manufacturing cost.
  • a MIMO system can be realized.
  • the dielectric waveguide filter, the high-frequency front end circuit, the communication device, and the Massive MIMO system according to the embodiments of the present invention have been described.
  • the present invention is not limited to individual embodiments. Unless it deviates from the gist of the present invention, the embodiment in which various modifications conceived by those skilled in the art have been made in the present embodiment, and forms constructed by combining components in different embodiments are also applicable to one or more of the present invention. It may be included within the scope of the embodiments.
  • the present invention can be widely used in communication devices such as a millimeter-wave mobile communication system and a Massive MIMO system as a dielectric waveguide filter whose passband width can be easily adjusted.
  • Dielectric waveguide filter 8 9 High frequency module 11, 11a to 11i, 12, 13a to 13f, 14a, 14b, 15a to 15h Resonance unit 17 to 19 Coupling unit 21, 22, 23a, 23b Input / output unit 40 to 43, 44a, 44b, 45a to 45d Dielectric block 40a to 43a Groove 40b Through Hole 50 to 52 Electrode 53, 54a, 54b, 55a to 55c Coupling window 61, 61a, 62, 62a, 63, 64, 65a, 65b Dielectric exposed portion 71 Mounting surface 73 Side surface of coupling portion (bottom surface of groove) 75 Opposite side of the resonance part (side of groove) 76, 77 Seam of dielectric block 80 Substrate 81 Conductive foil 82, 83 Coplanar line 110, 110A to 110C High frequency

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  • Computer Networks & Wireless Communication (AREA)
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Abstract

L'invention concerne un filtre de guide d'ondes diélectrique (1a) qui est configuré à partir d'un bloc diélectrique (40) sur la surface duquel une électrode (50) est formée, le bloc diélectrique (40) comprenant une pluralité de parties de résonance (11, 12) dans lesquelles se produit une résonance de champ électromagnétique, et une partie de couplage (17) qui est située entre les parties de résonance (11, 12) et couple les parties de résonance (11, 12), et une section d'exposition diélectrique (61) sur laquelle l'électrode (50) n'est pas formée est présente sur la surface de la partie de couplage (17). Les parties de résonance (11, 12) peuvent chacune être un résonateur en mode TE qui produit une résonance dans un mode EVEN ou ODD, et la partie d'exposition diélectrique (61) est fournie dans une partie impliquée dans le couplage dans n'importe quel mode de résonance de la partie de couplage (17).
PCT/JP2017/028152 2016-11-22 2017-08-02 Filtre à guide d'ondes diélectrique, circuit frontal haute fréquence, dispositif de communication, système mimo massif, et procédé d'ajustement pour filtre à guide d'ondes diélectrique WO2018096731A1 (fr)

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CN109560355A (zh) * 2018-12-28 2019-04-02 重庆思睿创瓷电科技有限公司 用于5g通信的介质体、介质波导滤波器、射频模块及基站
CN109616725A (zh) * 2018-12-29 2019-04-12 扬州江嘉科技有限公司 一种新型介质波导滤波器
JP2019153928A (ja) * 2018-03-02 2019-09-12 宇部興産株式会社 誘電体導波管型共振部品およびその特性調整方法
CN110336102A (zh) * 2019-07-09 2019-10-15 重庆思睿创瓷电科技有限公司 一种改善谐波性能的介质波导滤波器、射频模块及基站
CN110416669A (zh) * 2019-08-20 2019-11-05 京信通信技术(广州)有限公司 介质滤波器、信号收发装置及基站
CN110661066A (zh) * 2019-10-30 2020-01-07 京信通信技术(广州)有限公司 通信装置、介质波导滤波器及其容性耦合带宽调节方法
CN111384490A (zh) * 2018-12-29 2020-07-07 深圳市大富科技股份有限公司 一种介质滤波器及通信设备
CN113690560A (zh) * 2020-05-18 2021-11-23 大富科技(安徽)股份有限公司 一种介质滤波器、介质谐振器及通信设备
CN117393984A (zh) * 2023-11-21 2024-01-12 南通大学 一种正交双脊介质波导谐振器及包含该谐振器的滤波器

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Publication number Priority date Publication date Assignee Title
JP2019153928A (ja) * 2018-03-02 2019-09-12 宇部興産株式会社 誘電体導波管型共振部品およびその特性調整方法
CN109560355A (zh) * 2018-12-28 2019-04-02 重庆思睿创瓷电科技有限公司 用于5g通信的介质体、介质波导滤波器、射频模块及基站
CN109560355B (zh) * 2018-12-28 2024-05-14 重庆思睿创瓷电科技有限公司 用于5g通信的介质体、介质波导滤波器、射频模块及基站
CN109616725A (zh) * 2018-12-29 2019-04-12 扬州江嘉科技有限公司 一种新型介质波导滤波器
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CN110416669A (zh) * 2019-08-20 2019-11-05 京信通信技术(广州)有限公司 介质滤波器、信号收发装置及基站
CN110416669B (zh) * 2019-08-20 2024-06-25 京信通信技术(广州)有限公司 介质滤波器、信号收发装置及基站
CN110661066A (zh) * 2019-10-30 2020-01-07 京信通信技术(广州)有限公司 通信装置、介质波导滤波器及其容性耦合带宽调节方法
CN110661066B (zh) * 2019-10-30 2024-03-26 京信通信技术(广州)有限公司 通信装置、介质波导滤波器及其容性耦合带宽调节方法
CN113690560A (zh) * 2020-05-18 2021-11-23 大富科技(安徽)股份有限公司 一种介质滤波器、介质谐振器及通信设备
CN117393984A (zh) * 2023-11-21 2024-01-12 南通大学 一种正交双脊介质波导谐振器及包含该谐振器的滤波器

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