WO2013175903A1 - Dispositif d'antenne et dispositif sans fil mimo - Google Patents

Dispositif d'antenne et dispositif sans fil mimo Download PDF

Info

Publication number
WO2013175903A1
WO2013175903A1 PCT/JP2013/061379 JP2013061379W WO2013175903A1 WO 2013175903 A1 WO2013175903 A1 WO 2013175903A1 JP 2013061379 W JP2013061379 W JP 2013061379W WO 2013175903 A1 WO2013175903 A1 WO 2013175903A1
Authority
WO
WIPO (PCT)
Prior art keywords
radiating element
terminal
radiating
series reactance
input port
Prior art date
Application number
PCT/JP2013/061379
Other languages
English (en)
Japanese (ja)
Inventor
宏弥 田中
Original Assignee
株式会社村田製作所
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by 株式会社村田製作所 filed Critical 株式会社村田製作所
Publication of WO2013175903A1 publication Critical patent/WO2013175903A1/fr

Links

Images

Classifications

    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/12—Supports; Mounting means
    • H01Q1/22—Supports; Mounting means by structural association with other equipment or articles
    • H01Q1/24—Supports; Mounting means by structural association with other equipment or articles with receiving set
    • H01Q1/241—Supports; Mounting means by structural association with other equipment or articles with receiving set used in mobile communications, e.g. GSM
    • H01Q1/242—Supports; Mounting means by structural association with other equipment or articles with receiving set used in mobile communications, e.g. GSM specially adapted for hand-held use
    • H01Q1/243—Supports; Mounting means by structural association with other equipment or articles with receiving set used in mobile communications, e.g. GSM specially adapted for hand-held use with built-in antennas
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/52—Means for reducing coupling between antennas; Means for reducing coupling between an antenna and another structure
    • H01Q1/521—Means for reducing coupling between antennas; Means for reducing coupling between an antenna and another structure reducing the coupling between adjacent antennas
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q21/00—Antenna arrays or systems
    • H01Q21/28—Combinations of substantially independent non-interacting antenna units or systems
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q21/00—Antenna arrays or systems
    • H01Q21/30—Combinations of separate antenna units operating in different wavebands and connected to a common feeder system

Definitions

  • the present invention relates to an antenna apparatus having a plurality of radiating elements and a MIMO radio apparatus.
  • High-speed and large-capacity wireless communication can be performed by MIMO (Multi-Input Multi-Output) technology that performs spatial multiplexing by installing a plurality of radiating elements on both the transmitting side and the receiving side.
  • a MIMO antenna is required to have low coupling and low correlation between a plurality of radiating elements.
  • Patent Document 1 discloses a MIMO antenna that achieves low correlation by changing the directions of dipole axes of two radiating elements.
  • Patent Document 2 and Non-Patent Documents 1 to 3 disclose a technique for reducing coupling between antenna elements by connecting two antenna elements with a connection element.
  • the operating bandwidth of the antenna device becomes narrow. For example, it is difficult to ensure the bandwidth of the band 13 in which the LTE standard is used.
  • the radiation characteristics of the radiating element are affected by the components around the antenna and the shape of the mobile terminal. For this reason, if the components arranged around the antenna or the shape of the mobile terminal change, the radiation characteristics also change.
  • the radiating elements since the radiating elements are connected by a decoupling element, the radiating element itself must be tuned according to a change in the radiation characteristics.
  • a decoupling element that reduces mutual coupling between When the second terminal of the first series reactance element is used as a first input port and the fourth terminal of the second series reactance element is used as a second input port, the first radiation is supplied.
  • An antenna device is provided in which the resonance frequency of the element and the resonance frequency of the second radiating element are different from each other.
  • the characteristic of one of the radiating elements becomes relatively wide due to decoupling, and the characteristic of the other radiating element is relatively Narrow band.
  • the broadband radiating element covers both downlink and uplink frequency bands for MIMO communication.
  • the narrowband radiating element covers the downlink frequency band for MIMO communication.
  • the decoupling element can reduce the correlation coefficient between the two radiating elements. This makes it possible to increase downlink throughput.
  • a resonance frequency of the first radiating element is lower than a resonance frequency of the second radiating element, and the decoupling is performed.
  • the element may be configured by an inductor, and the bandwidth of the first radiating element may be wider than the bandwidth of the second radiating element.
  • the decoupling circuit may be configured with a capacitor, and the bandwidth of the first radiating element may be wider than the bandwidth of the second radiating element.
  • the electrical length of the first radiating element and the electrical length of the second radiating element may be different from each other.
  • the resonance frequencies of the two radiating elements can be made different.
  • a second transmission / reception circuit that performs transmission / reception in a frequency band different from that of the first transmission / reception circuit;
  • a signal inserted between the first radiating element and the first series reactance element and received by the first radiating element is transmitted to any of the first transmitting / receiving circuit and the second transmitting / receiving circuit.
  • communication can be performed in a frequency band different from the frequency band of MIMO communication.
  • a decoupling element that reduces mutual coupling between A portable terminal housing containing the first radiating element, the second radiating element, the first series reactance element, the second series reactance element, and the decoupling element;
  • a transmission / reception circuit for processing signals received by the first radiating element and the second radiating element and supplying a signal to be transmitted to the first radiating element;
  • the characteristic of one of the radiating elements becomes relatively wide due to decoupling, and the characteristic of the other radiating element is relatively Narrow band.
  • the broadband radiating element covers both downlink and uplink frequency bands for MIMO communication.
  • the narrowband radiating element covers the downlink frequency band for MIMO communication.
  • the decoupling element can reduce the correlation coefficient between the two radiating elements. This makes it possible to increase downlink throughput.
  • a resonance frequency of the first radiating element is lower than a resonance frequency of the second radiating element, and the decoupling is performed.
  • the ring element may be composed of an inductor, and the bandwidth of the first radiating element may be wider than the bandwidth of the second radiating element.
  • the decoupling circuit when power is supplied from the first input port and the second input port, a resonance frequency of the first radiating element is higher than a resonance frequency of the second radiating element,
  • the decoupling circuit may be configured by a capacitor, and the bandwidth of the first radiating element may be wider than the bandwidth of the second radiating element.
  • the electrical length of the first radiating element and the electrical length of the second radiating element may be different from each other.
  • the resonance frequencies of the two radiating elements can be made different.
  • the characteristic of one of the radiating elements becomes relatively wide due to decoupling, and the characteristic of the other radiating element is relatively Narrow band.
  • the broadband radiating element covers both downlink and uplink frequency bands for MIMO communication.
  • the narrowband radiating element covers the downlink frequency band for MIMO communication.
  • the decoupling element can reduce the correlation coefficient between the two radiating elements. This makes it possible to increase downlink throughput.
  • FIG. 1 is an equivalent circuit diagram of the antenna device according to the first embodiment.
  • FIG. 2 is a schematic perspective view of the antenna device according to the first embodiment.
  • FIG. 3 is a graph showing the frequency characteristics of the return loss of the two radiating elements in the state before the decoupling of the antenna device according to the first embodiment.
  • FIG. 4 is a graph showing frequency characteristics of return loss of two radiating elements in a state before decoupling of the antenna device according to Comparative Example 1.
  • FIG. 5 shows the frequency characteristics of the return loss S11 of the first radiating element in the state after decoupling of the antenna device according to Example 1 and Comparative Example 1, and the first characteristic of the antenna device according to Comparative Example 2 that is not decoupled.
  • FIG. 6 shows the mutual coupling S21 between the first radiating element and the second radiating element in the state after the decoupling of the antenna apparatus according to the first embodiment and the comparative example 1, and the antenna apparatus according to the comparative example 2 that is not decoupled. It is a graph which shows the frequency characteristic of mutual coupling S21 of the 1st radiation element of this, and a 2nd radiation element.
  • FIG. 7 shows the frequency characteristics of the return loss S22 of the second radiating element in the state after the decoupling of the antenna device according to Example 1 and Comparative Example 1, and the second characteristic of the antenna device according to Comparative Example 2 that is not decoupled.
  • FIG. 8A is a graph showing the frequency characteristics of the antenna efficiency in the state after decoupling of the antenna device according to Example 1, and the frequency characteristics of the antenna efficiency of the antenna device according to Comparative Example 2 that is not decoupled.
  • 5 is a graph showing frequency characteristics of antenna efficiency in a state after decoupling of the antenna devices according to Example 1 and Comparative Example 1.
  • FIG. 9 shows the frequency characteristic of the correlation coefficient between the first radiating element and the second radiating element in the state before the decoupling of the antenna device according to Example 1 and Comparative Example 1, and Comparative Example 2 in which the decoupling is not performed.
  • FIG. 5 is a graph showing the frequency characteristics of the correlation coefficient between the first radiating element and the second radiating element of the antenna device according to FIG.
  • FIG. 10 is a block diagram of a transmission / reception circuit mounted on the antenna device according to the first embodiment.
  • FIG. 11 is a plan view of an antenna device in which a simulation is performed on the relationship between the difference between the resonance frequencies of two radiating elements and the bandwidth.
  • FIG. 12 is a chart showing reactances of the first series reactance element and the second series reactance element of a plurality of samples to be simulated.
  • FIG. 2 to No. 6 is a graph showing the frequency characteristics of the return loss S11 of the first radiating element in a state after decoupling of the 6 samples.
  • FIG. 17 is an equivalent circuit diagram of the antenna device according to the second embodiment.
  • FIG. 18 is a graph showing the frequency characteristics of the return loss and antenna efficiency of the antenna device according to the second embodiment.
  • FIG. 1 shows an equivalent circuit diagram of the antenna device according to the first embodiment.
  • One end (first terminal) T 1 of the first series reactance element 22 is connected to the first radiating element 20, and the other end (second terminal) T 2 is transmitted / received via the first matching circuit 27.
  • the circuit 29 is connected.
  • One end (third terminal) T 3 of the second series reactance element 23 is connected to the second radiating element 21, and the other end (fourth terminal) T 4 is transmitted and received via the second matching circuit 28.
  • the circuit 29 is connected.
  • An inductor or a capacitor is used for the first series reactance element 22 and the second series reactance element 23.
  • the decoupling element 26 connects the second terminal T2 of the first series reactance element 22 and the fourth terminal T4 of the second series reactance element 23 to each other.
  • the resonance frequency of the first radiating element 20 and the second radiating element are used.
  • the resonance frequency of the element 21 is different.
  • This shift in the resonance frequency is realized by adjusting the electrical lengths of the first radiating element 20 and the second radiating element 21 and the reactances of the first series reactance element 22 and the second series reactance element 23.
  • the electrical lengths of the first radiating element 20 and the second radiating element 21 may be different from each other, and the reactances of the first series reactance element 22 and the second series reactance element 23 may be mutually different. It may be different.
  • both the electrical length and the reactance may be different from each other.
  • the decoupling element 26 reduces the mutual coupling between the first radiating element 20 and the second radiating element 21.
  • the decoupling element 26 for example, an inductor, a capacitor, or a transmission line is used. Specifically, the point P1 closer to the transmission / reception circuit 29 than the interconnection point between the first series reactance element 22 and the decoupling element 26 is used as the first input port, and the second series reactance element 23 and the decoupling element are connected.
  • the value of the S parameter element S12 (hereinafter referred to as mutual coupling S12) in the operating frequency band of the antenna device
  • the second terminal T2 and the fourth terminal T4 are smaller than the mutual coupling S12 when the first input port and the second input port are used as the first input port and the second input port, respectively.
  • FIG. 2 is a perspective view of the antenna device according to the first embodiment.
  • a dielectric substrate 30 is stored in a housing 35 of the portable terminal.
  • a ground plate 31 is formed on the back surface of the dielectric substrate 30.
  • FR4 is used for the dielectric substrate 30.
  • the planar shape of the dielectric substrate 30 is, for example, a rectangle having long and short sides of 100 mm and 50 mm, respectively. This dimension is determined based on the dimension of the casing 35 of the portable terminal in which the dielectric substrate 30 is accommodated.
  • a rectangular antenna region 32 having a width of about 12 mm is defined on the surface of the dielectric substrate 30 from one short side to the inside.
  • the ground plate 31 is disposed in almost the entire area other than the antenna region 32.
  • the first radiation element 20 and the second radiation element 21 are formed on the surface of the carrier 33.
  • the carrier 33 is mounted on the antenna region 32 of the dielectric substrate 30.
  • ABS resin is used for the carrier 33.
  • Both the first radiating element 20 and the second radiating element 21 have a meander shape.
  • a first series reactance element 22, a second series reactance element 23, a decoupling element 26, a first matching circuit 27, a second matching circuit 28, and a transmission / reception circuit 29 are mounted on the surface of the dielectric substrate 30. ing.
  • the first radiating element 20 and the first series reactance element 22, the second radiating element 21 and the second series reactance element 23, and these elements are connected by a microstrip line. Alternatively, direct connection may be made without going through a transmission line.
  • one antenna region 32 is secured in the vicinity of one short side of the dielectric substrate 30, but the antenna region 32 may be secured at another position.
  • one antenna region may be secured in the vicinity of two short sides.
  • the first radiating element 20 is disposed in one antenna region
  • the second radiating element 21 is disposed in the other antenna region.
  • an antenna region may be secured in the vicinity of the long side of the dielectric substrate 30.
  • FIG. 3 shows S parameter elements S11 and S22 (hereinafter referred to as return losses S11 and S22) when the second terminal T2 and the fourth terminal T4 in FIG. 1 are the first input port and the second input port, respectively.
  • the results of the frequency characteristics obtained by simulation are obtained by simulation. That is, the return losses S11 and S22 shown in FIG. 3 correspond to the return loss in the state before decoupling.
  • the horizontal axis represents the frequency in the unit “GHz”, and the vertical axis represents the return losses S11 and S22 in the unit “dB”.
  • the resonance frequency of the first radiating element 20 is about 0.79 GHz
  • the resonance frequency of the second radiating element 21 is about 0.85 GHz.
  • the antenna devices according to Comparative Example 1 and Comparative Example 2 were also simulated.
  • the antenna device according to Comparative Example 1 when the second terminal T2 and the fourth terminal T4 in FIG. 1 are the first input port and the second input port, respectively, the first radiating element 20 and the second terminal T4 are used.
  • the resonance frequency with the radiating element 21 is substantially the same.
  • the antenna device according to the comparative example 2 has a configuration in which the decoupling element 26 (FIG. 1) is removed from the antenna device according to the first embodiment.
  • an inductor was used as the decoupling element 26.
  • FIG. 4 shows the result of the simulation of the frequency characteristics of the return losses S11 and S22 from the first radiating element 20 and the second radiating element 21 of the antenna device according to Comparative Example 1.
  • the second terminal T2 and the fourth terminal T4 in FIG. 1 are a first input port and a second input port, respectively. That is, the return losses S11 and S22 shown in FIG. 4 correspond to the return loss in the state before decoupling.
  • the horizontal axis represents frequency in the unit “GHz”, and the vertical axis represents return loss in the unit “dB”.
  • the resonance frequencies of the first radiating element 20 and the second radiating element 21 are both about 0.745 GHz.
  • FIGS. 5 to 7 show the simulation results of the S parameters of the antenna devices according to Example 1, Comparative Example 1, and Comparative Example 2.
  • FIG. 5 to 7 respectively show the interconnection point Q1 between the first matching circuit 27 and the transmission / reception circuit 29 and the interconnection point Q2 between the second matching circuit 28 and the transmission / reception circuit 29 shown in FIG.
  • a return loss S11, a mutual coupling S12, and a return loss S22 when the input port is 1 and the second input port are shown. That is, the return loss S11, the mutual coupling S12, and the return loss S22 of the antenna devices according to Example 1 and Comparative Example 1 shown in FIGS. 5 to 7 correspond to values in a state after decoupling.
  • the thick solid line indicates the S parameter of the antenna device according to the first embodiment.
  • a broken line and a thin solid line indicate S parameters of the antenna devices according to Comparative Example 1 and Comparative Example 2, respectively.
  • the downlink frequency band 746 MHz to 756 MHz of the band 13 is indicated by Bd
  • the uplink frequency band 777 MHz to 787 MHz is indicated by Bu.
  • the return loss S11 of the antenna device according to Comparative Example 1 (same resonance frequency) is smaller than the return loss S11 of the antenna device according to Example 1 and Comparative Example 2.
  • the return loss S11 of the antenna device according to the first comparative example is larger than the return loss S11 of the antenna device according to the first and second comparative examples.
  • the bandwidth of the first radiating element 20 of the antenna device according to the comparative example 1 is not sufficient.
  • the downlink frequency band Bd and the uplink frequency band Bu In both cases, the return loss of the first radiating element 20 is reduced to some extent.
  • the mutual coupling S21 between the radiating elements of the antenna device according to the comparative example 2 is the radiating element of the antenna device according to the first embodiment and the comparative example 1. It is larger than the mutual coupling S21. This is because no decoupling element is inserted.
  • the antenna device having a large mutual coupling S21 is not suitable for use as a MIMO antenna because the antenna gain (Gain) is reduced.
  • the return loss S22 of the antenna device according to Example 1 is larger than the return loss S22 of the antenna device according to Comparative Example 1 and Comparative Example 2.
  • the return loss S22 of the antenna device according to the first embodiment is also small enough to withstand practical use.
  • FIG. 8A shows frequency characteristics of antenna efficiency of the antenna devices according to Example 1 and Comparative Example 2.
  • the horizontal axis represents frequency in the unit “GHz”, and the vertical axis represents antenna efficiency in the unit “dB”.
  • the thick solid line and the thin solid line in FIG. 8A indicate the antenna efficiencies of the first radiating element 20 and the second radiating element 21 of the antenna device according to the first embodiment, respectively, and the thick broken line and the thin broken line are according to Comparative Example 2, respectively.
  • the antenna efficiencies of the first radiating element 20 and the second radiating element 21 of the antenna apparatus are shown.
  • the antenna efficiency of the first radiating element 20 of the antenna apparatus according to the first embodiment is highest in both the downlink frequency band Bd and the uplink frequency band Bu.
  • the antenna efficiency of the second radiating element 21 of the antenna device according to the first embodiment is lower than the antenna efficiency of the second radiating element 21 of the antenna device according to the comparative example 2.
  • the antenna efficiency of the second radiating element 21 of the antenna device according to Example 1 is the antenna efficiency of the first and second radiating elements 20 and 21 of the antenna device according to Comparative Example 2. It is about the same.
  • FIG. 8B shows frequency characteristics of antenna efficiency of the antenna devices according to Example 1 and Comparative Example 1.
  • the horizontal axis represents frequency in the unit “GHz”, and the vertical axis represents antenna efficiency in the unit “dB”.
  • the thick solid line and the thin solid line in FIG. 8B indicate the antenna efficiencies of the first radiating element 20 and the second radiating element 21 of the antenna device according to the first embodiment, respectively, and the thick broken line and the thin broken line are according to Comparative Example 1, respectively.
  • the antenna efficiencies of the first radiating element 20 and the second radiating element 21 of the antenna apparatus are shown.
  • the antenna efficiency of the first radiating element 20 of the antenna apparatus according to the first embodiment is highest in both the downlink frequency band Bd and the uplink frequency band Bu.
  • the antenna efficiency of the second radiating element 21 of the antenna apparatus according to the first embodiment is the same as that of the second radiating element 21 of the antenna apparatus according to the first comparative example in both the downlink frequency band Bd and the uplink frequency band Bu. Lower than efficiency.
  • the antenna efficiency of the second radiating element 21 of the antenna device according to the first embodiment is also large enough to withstand practical use.
  • FIG. 9 shows a simulation result of the frequency characteristics of the correlation coefficient (correlation) between the first radiating element 20 and the second radiating element 21 of the antenna device according to Example 1, Comparative Example 1, and Comparative Example 2.
  • the horizontal axis represents the frequency in the unit “GHz”, and the vertical axis represents the correlation coefficient.
  • the correlation coefficient is preferably 0.7 or less in terms of electric field value.
  • a sufficiently small correlation coefficient is obtained in the downlink frequency band Bd as compared with the antenna device according to the comparative example 2 in which the decoupling element 26 is not inserted.
  • the antenna device according to Example 1 shows a smaller correlation coefficient than that of Comparative Example 1 in which the decoupling element 26 is inserted.
  • the resonance frequency between the first radiating element 20 and the second radiating element 21 is obtained. This is an effect of setting the reactances of the first series reactance element 22 and the second series reactance element 23 so that are different from each other.
  • the first radiating element 20 (FIG. 1) of the antenna device according to the first embodiment is suitable for use in both the downlink and uplink frequency bands Bd and Bu.
  • the second radiating element 21 (FIG. 1) of the antenna device according to the first embodiment is not suitable for use in the uplink frequency band Bu, but is suitable for use in the downlink frequency band Bd. I understand. That is, in the downlink frequency band Bd, both the first radiating element 20 and the second radiating element 21 can be used. In the uplink frequency band Bu, the first radiating element 20 can be used.
  • the first embodiment as shown in FIG. 9, since the correlation coefficient is low in the downlink frequency band Bd, when the antenna device according to the first embodiment is applied to a MIMO antenna for a mobile terminal, a high throughput is achieved. It becomes possible to obtain.
  • the resonance of the first radiating element 20 is achieved.
  • the reactances of the first series reactance element 22 and the second series reactance element 23 are selected so that the frequency and the resonance frequency of the second radiating element 21 are equal.
  • This configuration is equivalent to a configuration in which two radiating elements having the same electrical length are arranged. In a state where the two radiating elements are connected to each other by the decoupling element 26, that is, in a decoupled state, the amplitudes of the current distribution on the two radiating elements are equal, and the phase difference is 180 °.
  • the resonance of the first radiating element 20 is achieved.
  • the reactances of the first series reactance element 22 and the second series reactance element 23 are selected so that the frequency and the resonance frequency of the second radiating element 21 are different. As a result, the balance of the current distribution on the two radiating elements is lost, and the electromagnetic field near the radiating elements changes.
  • Example 1 an inductor was used as the decoupling element 26.
  • the bandwidth of the first radiating element 20 having a low resonance frequency in the configuration before decoupling is wider than the bandwidth of the other second radiating element 21.
  • a relatively narrowband radiating element, ie, a second radiating element 21 covers the downlink frequency band Bd, and a relatively wideband first radiating element 20 includes both downlink and uplink frequencies.
  • the frequency band is set so as to cover the bands Bd and Bu.
  • the bandwidth of the second radiating element 21 having the higher resonance frequency in the configuration before decoupling becomes wide, and the band of the first radiating element 20 having the lower resonance frequency.
  • the width becomes narrower.
  • the second radiating element 21 covers both the downlink and uplink frequency bands Bd, Bu, and the first radiating element 20 covers the downlink frequency band Bd. That's fine.
  • One of the two radiating elements has a relatively wide bandwidth and the other has a relatively narrow bandwidth because the electromagnetic field distribution near the radiating element after the decoupling element 26 is inserted is This is because the first series reactance element 22 and the second series reactance element 23 are changed.
  • the first series reactance element 22 and the second series reactance element 23 have a role of changing the electromagnetic field distribution in the vicinity of the radiating element.
  • the resonance frequency of the first radiating element 20 and the second radiating element 21 is adjusted by adjusting the reactance of the first series reactance element 22 and the second series reactance element 23.
  • By adjusting the reactance of the series reactance element 23 desired antenna characteristics can be realized.
  • the first series reactance element 22 and the second series reactance element 23 have a role of making the resonance frequencies of the first radiating element 20 and the second radiating element 21 different, and a transmission line is arranged between the radiating elements. Without functioning, it also functions as part of a decoupling circuit that connects the first radiating element 20 and the second radiating element 21.
  • FIG. 10 shows a block diagram of the transmission / reception circuit 29.
  • the baseband integrated circuit 40 performs baseband signal processing.
  • the high frequency integrated circuit 41 performs signal processing in the radio frequency band.
  • a transmission signal is input from the high frequency integrated circuit 41 to the first radiating element 20 via the power amplifier 42, the surface wave filter 43, and the diplexer 44. No transmission signal is input to the second radiating element 21.
  • the high frequency signal received by the first radiating element 20 is input to the high frequency integrated circuit 41 through the diplexer 44 and the surface wave filter 45.
  • a high frequency signal received by the second radiating element 21 is input to the high frequency integrated circuit 41 via the surface wave filter 46 and the low noise amplifier 47.
  • the broadband first radiating element 20 is used for the uplink, and both the first radiating element 20 and the second radiating element 21 are used for the downlink.
  • FIG. 11 shows a plan view of the antenna device used for the simulation.
  • the planar shape of the dielectric substrate 30 is rectangular, and its thickness is 0.8 mm.
  • the short side length (width) W of the dielectric substrate 30 is 25 mm.
  • the surface of the dielectric substrate 30 is divided into a ground region having a length L1 (45 mm) and an antenna region having a length L2 (21.8 mm) in the length direction.
  • a ground plate 31 is disposed over the entire ground region of length L1.
  • the first radiating element 20 and the second radiating element 21 are arranged in the antenna region having the length L2.
  • Each of the first radiating element 20 and the second radiating element 21 extends in parallel to the long side of the dielectric substrate 30 from the position corresponding to the edge of the ground plate 31 toward the short side of the dielectric substrate 30. .
  • the width D1 of the first radiating element 20 and the second radiating element 21 is 1.44 mm.
  • the distance D2 between the first radiating element 20 and the second radiating element 21 is 7.06 mm.
  • the feeding ends of the first radiating element 20 and the second radiating element 21 are defined as a first input port FP1 and a second input port FP2, respectively.
  • the return loss S11 of the first radiating element 20 is equal to the return loss S22 of the second radiating element 21.
  • the reactance of the first series reactance element 22 (FIG. 1) and the second series reactance element 23 (FIG. 1) is the same at a frequency of 2.45 GHz, and the first radiating element 20 and the second radiating element 21 are the same.
  • the condition where and are not coupled to each other was calculated by simulation.
  • the resonance frequency of the first radiating element 20 and the resonance frequency of the second radiating element 21 are the same, and the points P1 and P2 in FIG.
  • both the first series reactance element 22 and the second series reactance element 23 should be 0.38 nH inductors, and the decoupling element 26 should be a 1.08 pF capacitor.
  • the inductance of the first series reactance element 22 that satisfies the decoupling condition having the same resonance frequency is referred to as a reference inductance jXr.
  • the inductance jX2 of the second series reactance element 23 was calculated for five samples in which the inductance jX1 of the first series reactance element 22 was changed from the reference inductance jXr. Note that all samples satisfy the condition that the first radiating element 20 and the second radiating element 21 are not coupled to each other.
  • Fig. 12 shows the No. satisfying the decoupling condition with the same resonance frequency.
  • No. 1 and No. 1 in which jX1 is changed from the reference inductance jXr (0.38 nH). 2 to No.
  • the ratio of the inductance jX1 to the inductances jX1, jX2 and the reference inductance jXr of the six samples is shown. It can be seen that as the inductance jX1 of the first series reactance element 22 increases from the reference inductance jXr, the inductance jX2 of the second series reactance element 23 decreases in order to decouple the radiation elements.
  • FIGS. 2 to No. The result of having calculated the frequency characteristic of S parameter of 6 samples by simulation is shown.
  • the S parameters shown in FIGS. 13 to 15 are calculated using the points Q1 and Q2 in FIG. 1 as the first input port and the second input port, respectively.
  • the horizontal axis in FIGS. 13 to 15 represents the frequency in the unit “GHz”, and the vertical axis in FIGS. 13 to 15 represents the return loss S11, the mutual coupling S12, and the return loss S22 in the unit “dB”, respectively.
  • the S parameter of 6 samples is shown.
  • the frequency characteristic of the S parameter of sample 1 is No. 1.
  • the frequency characteristics of the S parameter of sample 2 are almost the same.
  • the return losses S11 and S22 show the minimum values in the vicinity of the resonance frequency.
  • the frequency band where the return loss is ⁇ 10 dB or less is called the bandwidth of the radiating element.
  • the bandwidth of the radiating element As shown in FIG. 13, as the sample number increases, that is, as the ratio of the inductance jX1 to the reference inductance jXr increases, the bandwidth of the first radiating element 20 decreases. Conversely, as shown in FIG. 15, the bandwidth of the second radiating element 21 increases as the sample number increases, that is, as the ratio of the inductance jX1 to the reference inductance jXr increases.
  • the mutual coupling S12 between the radiating elements decreases as the sample number increases, that is, as the ratio of the inductance jX1 to the reference inductance jXr increases. Further, the bandwidth of the frequency at which the size of the mutual coupling S12 is ⁇ 10 dB or less also increases as the ratio of the inductance jX1 to the reference inductance jXr increases.
  • FIG. 16 shows the relationship between the bandwidth of the frequency characteristics of the return losses S11 and S22 and the mutual coupling S21 and the ratio of the inductance jX1 to the reference inductance jXr.
  • the horizontal axis represents the ratio of the inductance jX1 to the reference inductance jXr, and the vertical axis represents the ratio of the bandwidth to the center frequency in the unit “%”.
  • the triangle symbol, square symbol, and circle symbol in the figure indicate the bandwidths of the frequency characteristics of the return loss S11, the mutual coupling S21, and the return loss S22, respectively.
  • the bandwidth of the frequency characteristic of the return loss S11 becomes narrower and the bandwidth of the frequency characteristic of the return loss S22 becomes wider.
  • the relatively wideband second radiating element 21 is used in both the downlink and the uplink, and the relatively narrowband first radiating element 20 is used only in the downlink. Use it.
  • FIG. 17 shows an equivalent circuit diagram of the antenna device according to the second embodiment.
  • differences from the antenna device according to the first embodiment illustrated in FIG. 1 will be described, and description of the same configuration will be omitted.
  • Example 1 as shown in FIG. 1, the first radiating element 20 and the first series reactance element 22 were directly connected.
  • the first radiating element 20 and the first series reactance element 22 are connected via a switching element 50.
  • the transmission / reception circuit 52 for the band 5 and the band 2 is mounted.
  • the transmission / reception circuit 52 is connected to the switching element 50 via the matching circuit 51.
  • the switching element 50 for example, a single pole double throw (SPDT) switch is used.
  • the first radiating element 20 is connected to the input port of the SPDT switch, the first series reactance element 22 is connected to one output port, and the matching circuit 51 is connected to the other output port.
  • the switching element 50 switches between a first state in which the first radiating element 20 is connected to the first series reactance element 22 and a second state in which the first radiating element 20 is connected to the matching circuit 51.
  • the antenna device according to the second embodiment can transmit and receive the radio frequency band of the band 13 in the first state, and can transmit and receive the radio frequency bands of the band 5 and the band 2 in the second state.
  • An example of a characteristic is shown.
  • the horizontal axis represents the frequency in the unit “GHz”
  • the left vertical axis represents the return loss in the unit “dB”
  • the right vertical axis represents the antenna efficiency in the unit “dB”.
  • the thin solid line in the figure indicates the return loss
  • the thick solid line indicates the antenna efficiency in the band 5 band
  • the thick broken line indicates the antenna efficiency in the band 2 band. It can be seen that the antenna device according to the second embodiment can cope with the frequency bands of band 5 and band 2.
  • the antenna device according to the second embodiment can cope with the frequency band of the band 13 in the same manner as the antenna device according to the first embodiment.
  • an SPDT switch is used as the switching element 50, but a diplexer may also be used.
  • an SPnT switch having n output ports may be used as the switching element 50.
  • a switching element may be inserted between the second radiating element 21 and the second series reactance element 23, or between the first radiating element 20 and the first series reactance element 22, and the second A switching element may be connected to both the radiation element 21 and the second series reactance element 23.
  • the insertion position of the switching element 50 is not limited to between the first radiating element 20 and the first series reactance element 22, and the switching element 50 may be inserted after the first series reactance element 22.

Landscapes

  • Engineering & Computer Science (AREA)
  • Computer Networks & Wireless Communication (AREA)
  • Support Of Aerials (AREA)

Abstract

Parmi la paire de bornes d'un premier élément de réactance en série, une borne, une première borne, est connectée à un premier élément rayonnant, et l'autre borne, une seconde borne, est connectée à un premier circuit d'émission/réception. Parmi la paire de bornes d'un second élément de réactance en série, une borne, une troisième borne, est connectée à un second élément rayonnant, et l'autre borne, une quatrième borne, est connectée au premier circuit d'émission/réception. Un élément de découplage connecte la seconde borne du premier élément de réactance en série et la quatrième borne du second élément de réactance en série l'un à l'autre, et réduit l'interconnexion entre le premier élément rayonnant et le second élément rayonnant. Quand une puissance est fournie avec la seconde borne du premier élément de réactance en série servant de premier port d'entrée et la quatrième borne du second élément de réactance en série servant de second port d'entrée, la fréquence de résonance du premier élément rayonnant et la fréquence de résonance du second élément rayonnant sont différentes l'une de l'autre.
PCT/JP2013/061379 2012-05-23 2013-04-17 Dispositif d'antenne et dispositif sans fil mimo WO2013175903A1 (fr)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
JP2012-117326 2012-05-23
JP2012117326 2012-05-23

Publications (1)

Publication Number Publication Date
WO2013175903A1 true WO2013175903A1 (fr) 2013-11-28

Family

ID=49623604

Family Applications (1)

Application Number Title Priority Date Filing Date
PCT/JP2013/061379 WO2013175903A1 (fr) 2012-05-23 2013-04-17 Dispositif d'antenne et dispositif sans fil mimo

Country Status (1)

Country Link
WO (1) WO2013175903A1 (fr)

Cited By (8)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN103618139A (zh) * 2013-12-07 2014-03-05 威海北洋电气集团股份有限公司 射频天线去耦合方法及装置
WO2018048044A2 (fr) 2016-09-07 2018-03-15 Lg Electronics Inc. Terminal mobile
US10734720B2 (en) 2015-12-29 2020-08-04 Huawei Technologies Co., Ltd. Antenna and communications device
CN112510368A (zh) * 2020-10-19 2021-03-16 西安朗普达通信科技有限公司 一种可调谐双频去耦芯片
CN113659295A (zh) * 2020-05-12 2021-11-16 西安电子科技大学 滤波器、天线装置和电子设备
WO2021227813A1 (fr) * 2020-05-12 2021-11-18 西安电子科技大学 Appareil d'antenne et dispositif électronique
CN113922050A (zh) * 2021-11-03 2022-01-11 华南理工大学 双覆层去耦合结构、双极化天线及天线阵列
WO2022126643A1 (fr) * 2020-12-18 2022-06-23 华为技术有限公司 Module d'antenne et dispositif de station de base

Citations (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JP2004096303A (ja) * 2002-08-30 2004-03-25 Kyocera Corp アンテナ構造の利得調整方法およびアンテナ構造ならびに通信装置
JP2011071597A (ja) * 2009-09-24 2011-04-07 Toshiba Corp 無線端末
WO2011102143A1 (fr) * 2010-02-19 2011-08-25 パナソニック株式会社 Dispositif d'antenne, et terminal mobile sans fil muni de celui-ci

Patent Citations (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JP2004096303A (ja) * 2002-08-30 2004-03-25 Kyocera Corp アンテナ構造の利得調整方法およびアンテナ構造ならびに通信装置
JP2011071597A (ja) * 2009-09-24 2011-04-07 Toshiba Corp 無線端末
WO2011102143A1 (fr) * 2010-02-19 2011-08-25 パナソニック株式会社 Dispositif d'antenne, et terminal mobile sans fil muni de celui-ci

Cited By (13)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN103618139B (zh) * 2013-12-07 2016-08-17 威海北洋电气集团股份有限公司 射频天线去耦合方法及装置
CN103618139A (zh) * 2013-12-07 2014-03-05 威海北洋电气集团股份有限公司 射频天线去耦合方法及装置
US10734720B2 (en) 2015-12-29 2020-08-04 Huawei Technologies Co., Ltd. Antenna and communications device
US10840582B2 (en) 2016-09-07 2020-11-17 Lg Electronics Inc. Mobile terminal
EP3510667A4 (fr) * 2016-09-07 2020-04-01 LG Electronics Inc. -1- Terminal mobile
CN109690868A (zh) * 2016-09-07 2019-04-26 Lg 电子株式会社 移动终端
WO2018048044A2 (fr) 2016-09-07 2018-03-15 Lg Electronics Inc. Terminal mobile
CN113659295A (zh) * 2020-05-12 2021-11-16 西安电子科技大学 滤波器、天线装置和电子设备
WO2021227813A1 (fr) * 2020-05-12 2021-11-18 西安电子科技大学 Appareil d'antenne et dispositif électronique
CN112510368A (zh) * 2020-10-19 2021-03-16 西安朗普达通信科技有限公司 一种可调谐双频去耦芯片
CN112510368B (zh) * 2020-10-19 2023-06-09 西安朗普达通信科技有限公司 一种可调谐双频去耦芯片
WO2022126643A1 (fr) * 2020-12-18 2022-06-23 华为技术有限公司 Module d'antenne et dispositif de station de base
CN113922050A (zh) * 2021-11-03 2022-01-11 华南理工大学 双覆层去耦合结构、双极化天线及天线阵列

Similar Documents

Publication Publication Date Title
WO2013175903A1 (fr) Dispositif d'antenne et dispositif sans fil mimo
US8854273B2 (en) Antenna and communication device thereof
EP1506594B1 (fr) Agencement d'antenne et module comprenant cet agencement
EP2660933B1 (fr) Antenne réseau de terminal mobile et procédé de mise en uvre
US7336239B2 (en) Small multi-mode antenna and RF module using the same
US6943746B2 (en) Radio device and antenna structure
US20120306718A1 (en) Antenna and wireless mobile terminal equipped with the same
CN109672019B (zh) 一种终端mimo天线装置及实现天线信号传输方法
US10622716B1 (en) Balanced antenna
US9748661B2 (en) Antenna for achieving effects of MIMO antenna
CN202759016U (zh) 可调谐耦合馈电天线系统
EP2290746B1 (fr) Antenne planaire avec rayonnement isotrope
JP2013214953A (ja) マルチバンド・マルチアンテナシステムおよびその通信装置
JP2012513731A (ja) マルチポートアンテナ構造
CN106450752B (zh) 一种用于智能手机实现高隔离度的mimo天线
JPWO2013061502A1 (ja) アンテナ装置及び無線通信装置
TW201635647A (zh) 可重組的多頻多功能天線
US9306275B2 (en) Multi-antenna and electronic device
CN110323562A (zh) 基于互补开口谐振环的可调谐超宽带mimo天线
JPWO2013051188A1 (ja) アンテナ装置及び無線通信装置
JPWO2013051187A1 (ja) アンテナ装置及び無線通信装置
CN110911842B (zh) 一种具有共辐射体天线的终端
CN113517565A (zh) 一种应用于5g移动终端的三频mimo天线
JP5714507B2 (ja) Ｍｉｍｏアンテナ装置及び無線通信装置
JP5694953B2 (ja) アンテナ装置及び無線通信装置

Legal Events

Date Code Title Description
121 Ep: the epo has been informed by wipo that ep was designated in this application

Ref document number: 13793990

Country of ref document: EP

Kind code of ref document: A1

NENP Non-entry into the national phase

Ref country code: DE

122 Ep: pct application non-entry in european phase

Ref document number: 13793990

Country of ref document: EP

Kind code of ref document: A1

NENP Non-entry into the national phase

Ref country code: JP