WO2018064835A1 - 一种喇叭天线 - Google Patents

一种喇叭天线 Download PDF

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Publication number
WO2018064835A1
WO2018064835A1 PCT/CN2016/101595 CN2016101595W WO2018064835A1 WO 2018064835 A1 WO2018064835 A1 WO 2018064835A1 CN 2016101595 W CN2016101595 W CN 2016101595W WO 2018064835 A1 WO2018064835 A1 WO 2018064835A1
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Prior art keywords
dielectric
dielectric plate
fss
horn antenna
wall
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PCT/CN2016/101595
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English (en)
French (fr)
Inventor
罗昕
陈一
吕廷海
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华为技术有限公司
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Application filed by 华为技术有限公司 filed Critical 华为技术有限公司
Priority to BR112019004151-6A priority Critical patent/BR112019004151B1/pt
Priority to EP16918168.2A priority patent/EP3419117B1/en
Priority to PCT/CN2016/101595 priority patent/WO2018064835A1/zh
Priority to JP2019529307A priority patent/JP6706722B2/ja
Priority to CN201680082894.0A priority patent/CN108701905B/zh
Publication of WO2018064835A1 publication Critical patent/WO2018064835A1/zh
Priority to US16/159,494 priority patent/US10727607B2/en

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    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q19/00—Combinations of primary active antenna elements and units with secondary devices, e.g. with quasi-optical devices, for giving the antenna a desired directional characteristic
    • H01Q19/10—Combinations of primary active antenna elements and units with secondary devices, e.g. with quasi-optical devices, for giving the antenna a desired directional characteristic using reflecting surfaces
    • H01Q19/18—Combinations of primary active antenna elements and units with secondary devices, e.g. with quasi-optical devices, for giving the antenna a desired directional characteristic using reflecting surfaces having two or more spaced reflecting surfaces
    • H01Q19/19—Combinations of primary active antenna elements and units with secondary devices, e.g. with quasi-optical devices, for giving the antenna a desired directional characteristic using reflecting surfaces having two or more spaced reflecting surfaces comprising one main concave reflecting surface associated with an auxiliary reflecting surface
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q13/00—Waveguide horns or mouths; Slot antennas; Leaky-waveguide antennas; Equivalent structures causing radiation along the transmission path of a guided wave
    • H01Q13/02—Waveguide horns
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q15/00—Devices for reflection, refraction, diffraction or polarisation of waves radiated from an antenna, e.g. quasi-optical devices
    • H01Q15/0006—Devices acting selectively as reflecting surface, as diffracting or as refracting device, e.g. frequency filtering or angular spatial filtering devices
    • H01Q15/0013—Devices acting selectively as reflecting surface, as diffracting or as refracting device, e.g. frequency filtering or angular spatial filtering devices said selective devices working as frequency-selective reflecting surfaces, e.g. FSS, dichroic plates, surfaces being partly transmissive and reflective
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q19/00—Combinations of primary active antenna elements and units with secondary devices, e.g. with quasi-optical devices, for giving the antenna a desired directional characteristic
    • H01Q19/10—Combinations of primary active antenna elements and units with secondary devices, e.g. with quasi-optical devices, for giving the antenna a desired directional characteristic using reflecting surfaces
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q19/00—Combinations of primary active antenna elements and units with secondary devices, e.g. with quasi-optical devices, for giving the antenna a desired directional characteristic
    • H01Q19/10—Combinations of primary active antenna elements and units with secondary devices, e.g. with quasi-optical devices, for giving the antenna a desired directional characteristic using reflecting surfaces
    • H01Q19/12—Combinations of primary active antenna elements and units with secondary devices, e.g. with quasi-optical devices, for giving the antenna a desired directional characteristic using reflecting surfaces wherein the surfaces are concave
    • H01Q19/13—Combinations of primary active antenna elements and units with secondary devices, e.g. with quasi-optical devices, for giving the antenna a desired directional characteristic using reflecting surfaces wherein the surfaces are concave the primary radiating source being a single radiating element, e.g. a dipole, a slot, a waveguide termination
    • H01Q19/132—Horn reflector antennas; Off-set feeding
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q19/00—Combinations of primary active antenna elements and units with secondary devices, e.g. with quasi-optical devices, for giving the antenna a desired directional characteristic
    • H01Q19/10—Combinations of primary active antenna elements and units with secondary devices, e.g. with quasi-optical devices, for giving the antenna a desired directional characteristic using reflecting surfaces
    • H01Q19/18—Combinations of primary active antenna elements and units with secondary devices, e.g. with quasi-optical devices, for giving the antenna a desired directional characteristic using reflecting surfaces having two or more spaced reflecting surfaces
    • H01Q19/19—Combinations of primary active antenna elements and units with secondary devices, e.g. with quasi-optical devices, for giving the antenna a desired directional characteristic using reflecting surfaces having two or more spaced reflecting surfaces comprising one main concave reflecting surface associated with an auxiliary reflecting surface
    • H01Q19/191—Combinations of primary active antenna elements and units with secondary devices, e.g. with quasi-optical devices, for giving the antenna a desired directional characteristic using reflecting surfaces having two or more spaced reflecting surfaces comprising one main concave reflecting surface associated with an auxiliary reflecting surface wherein the primary active element uses one or more deflecting surfaces, e.g. beam waveguide feeds

Definitions

  • the present invention relates to the field of wireless communication technologies, and in particular, to a horn antenna that can be used for a dual-frequency parabolic antenna.
  • the microwave equipment in the Eband (71-76 GHz, 81-86 GHz) frequency band plays an increasingly important role in the base station backhaul network.
  • the electromagnetic wave "rain decay" of the Eband band is particularly serious, the Eband microwave single-hop distance is usually less than 3 kilometers.
  • one solution is to use the Eband band microwave device in combination with other low-frequency microwave devices. When there is a large rainfall, the Eband microwave device cannot work normally, but the low-frequency microwave The device is still working.
  • the solution uses a dual-frequency parabolic antenna, as shown in Figure 1.
  • the dual-frequency parabolic antenna includes a primary reflective surface, a secondary reflective surface, a low frequency feed, and a high frequency feed, wherein the low frequency feed and the high frequency feed are both It is a kind of horn antenna. When applied to other antenna structures, it is usually called horn feed.
  • the two feeds share one main reflection surface.
  • the Frequency Selective Surface (FSS) is used as the sub-reflection surface.
  • the secondary reflecting surface is designed as a hyperboloid, and the virtual focus of the hyperboloid coincides with the real focus of the main reflecting surface, and the feeds of different frequencies are divided into the virtual focus and the real focus of the hyperboloid.
  • the secondary reflection is transmitted in the electromagnetic wave emitted by the low frequency feed located at the virtual focus, and is reflected by the electromagnetic wave emitted from the high frequency feed located at the real focus, thereby realizing the function of dual frequency multiplexing.
  • the low frequency horn feed and the FSS are two independent devices, and there is a problem of large assembly error, low antenna gain, and beam pointing away from the boresight direction.
  • the embodiment of the invention provides a horn antenna, which integrates the functions of a low frequency horn feed and an FSS.
  • the problem that the antenna gain is low and the beam is directed away from the boresight direction due to the large assembly error is solved in the prior art.
  • a horn antenna comprising: a frequency selective surface FSS, a connection structure and a waveguide, the connection structure comprising a first dielectric plate, a second dielectric plate and a dielectric wall, the first dielectric plate a surface having a convex surface, the second surface of the first dielectric plate being connected to the dielectric wall, wherein a distance between the two surfaces of the first dielectric plate is a thickness of the first dielectric plate
  • the dielectric wall has a cylindrical structure, a first surface of the dielectric wall is covered by the first dielectric plate, and a second surface of the dielectric wall is covered by the second dielectric plate, wherein the dielectric wall
  • the spacing between the two surfaces is the height of the dielectric wall, the area of the first surface of the dielectric wall is not less than the area of the second surface of the dielectric wall; the middle of the second dielectric plate has a hole; a first dielectric plate, the dielectric wall and the second dielectric plate together forming a hollow structure; the FSS covering
  • the horn antenna provided by the embodiment of the invention integrates the functions of the FSS and the low frequency horn feed, can greatly reduce the alignment error with the high frequency horn feed, reduce the assembly difficulty, and has high radiation efficiency.
  • the array arrangement direction of the FSS is 45 degrees or 135 degrees with the polarization direction of the incident electromagnetic wave, and the electromagnetic wave transmitted through the FSS can be reduced.
  • the thickness of the first dielectric plate is a half of a corresponding wavelength of the first frequency plate in the first dielectric plate, wherein the The first frequency point is the center frequency of the transmission band of the FSS.
  • Embodiments of the present invention can cancel the reflection of transmitted electromagnetic waves from the front and back of the first dielectric plate, and increase the transmission bandwidth of the FSS to the low frequency band.
  • another portion of the waveguide is inserted into the hollow structure.
  • the horn antenna further includes a choke slot, and the horn is located in the hollow structure Around the waveguide, the trough depth of the choke is one quarter of a corresponding wavelength of the first frequency in the air, wherein the first frequency is the center frequency of the transmission band of the FSS.
  • the energy of the electromagnetic wave can be radiated more concentratedly, and the radiation efficiency of the horn antenna is improved.
  • the number of the chute slots is more than one, and the slot spacing is a corresponding wavelength of the first frequency point in the air. 1/10.
  • the horn antenna includes a plurality of choke slots to further improve the radiation efficiency of the horn antenna.
  • the horn antenna integrates the functions of the FSS and the low-frequency horn feed, which can greatly reduce the alignment error with the high-frequency horn feed and reduce the assembly difficulty, and the horn antenna provided by the embodiment of the present invention It also has a high radiation efficiency.
  • FIG. 1 is a schematic structural view of a conventional dual-frequency parabolic antenna
  • FIG. 2 is a schematic structural view of a conventional horn antenna
  • FIG. 3 is a schematic structural diagram of a horn antenna according to an embodiment of the present invention.
  • FIG. 4 is a schematic structural diagram of a dual-frequency parabolic antenna to which an embodiment of the present invention is applied;
  • FIG. 5 is a diagram showing a relationship between an arrangement direction of an FSS array and a polarization direction of an incident electromagnetic wave in a horn antenna according to an embodiment of the present invention
  • FIG. 6 is a comparison diagram of electromagnetic wave patterns after electromagnetic waves are respectively subjected to FSS in the horn antenna provided by the present invention and the existing FSS;
  • Fig. 7 is a comparison diagram of reflection coefficients of electromagnetic waves in a low frequency band after a horn antenna adopting a hollow connection structure and a horn antenna having a solid connection structure.
  • the horn antenna is a very widely used antenna.
  • the low frequency feed and the high frequency feed in Fig. 1 are horn antennas.
  • the existing horn antenna is usually composed of a solid dielectric block and a waveguide, as shown in Fig. 2.
  • the solid dielectric block has a conical shape with a curved top, and a tip opposite to the top of the curved surface is inserted into the waveguide and connected to the waveguide to form a horn feed.
  • FSS and low-frequency horn feeds horn antennas are often referred to as horn feeds in antenna structures
  • the gain is reduced and the beam is pointing away from the boresight.
  • the embodiment of the invention provides a horn antenna 300, which integrates the functions of the FSS and the low frequency horn feed, and has the structure as shown in FIG. 3, including: FSS 310, connection structure 320 and waveguide 330,
  • the connecting structure 320 includes a first dielectric plate 321, a second dielectric plate 322 and a dielectric wall 323.
  • the first surface of the first dielectric plate 321 is a hyperbolic surface with a convex surface, and the second surface of the first dielectric plate 321 and the dielectric wall 323 is connected, wherein the distance between the two surfaces of the first dielectric plate 321 is the thickness of the first dielectric plate 321; the dielectric wall 323 has a cylindrical structure, and the first surface of the dielectric wall 323 is covered by the first dielectric plate 321, the dielectric wall The second surface is covered by the second dielectric plate 322, wherein the distance between the two surfaces of the dielectric wall 323 is the height of the dielectric wall 323, and the first surface of the dielectric wall 323 The area is not less than the area of the second surface of the dielectric wall 323; the intermediate position of the second dielectric plate 322 has a hole; the first dielectric plate 321, the dielectric wall 323 and the second dielectric plate 322 together form
  • the hole area of the second dielectric plate 322 is consistent with the cross-sectional area of the waveguide 330, and the two are closely combined to serve as a connection;
  • the dielectric wall 323 is a cylindrical structure, which may be in the shape of a cylinder or a horn;
  • the first dielectric plate 321 needs to adopt a material with less loss of transmitted electromagnetic wave, and the medium material in the existing horn antenna can be used, and the second dielectric plate and the dielectric wall mainly serve as a support, and the hard material can be used.
  • the embodiment is not limited thereto.
  • the FSS 310 in the embodiment of the present invention has a function of transmitting a low-frequency electromagnetic wave and reflecting a high-frequency electromagnetic wave. Any existing FSS having the above functions may be used, which is not limited in the embodiment of the present invention.
  • the horn antenna 300 provided by the embodiment of the present invention integrates the functions of the FSS and the low-frequency feed, and only needs to consider the horn.
  • the alignment of the antenna 300 with the high frequency horn feed serves to reduce the alignment error, and the alignment error can be controlled within ⁇ 0.2 mm.
  • the hollow structure connection structure 320 can minimize the electromagnetic wave propagation in the medium, because the transmission loss of the electromagnetic wave in the medium is always greater than the transmission loss in the air, and reducing the electromagnetic wave propagation in the medium is equivalent to reducing the unnecessary loss.
  • the horn antenna 300 provided by the embodiment of the present invention can achieve a radiation efficiency of 98%.
  • the array arrangement direction of the FSS 310 is 45 degrees or 135 degrees with the polarization direction of the incident electromagnetic wave, as shown in FIG. 4, the solid arrow indicates the polarization direction of the incident electromagnetic wave, and the dotted arrow Indicates the array arrangement direction of the FSS 310. Since the electromagnetic wave is usually a sine wave, the polarization direction is represented by two kinds of 180 degrees difference. As shown by the arrows in the solid line in FIG. 4, the array of the FSS 310 is used. The arrangement direction and the polarization direction of the incident electromagnetic wave are 45 degrees at a certain time, and may become 135 degrees at the next moment. Embodiments of the present invention propose to reduce the height of the transmitted electromagnetic wave side lobes.
  • the low-frequency electromagnetic wave emitted by the horn antenna 300 is incident on the FSS 310.
  • the incident electromagnetic wave passes through the FSS 310, an induced current is generated on the surface of the FSS 310, and an induced current is generated.
  • the generated scattered electromagnetic waves interact with the incident electromagnetic waves to form transmitted electromagnetic waves.
  • the array arrangement direction of the FSS 310 is 45 degrees or 135 degrees with the polarization direction of the incident electromagnetic wave
  • the two sides of the slit in the two directions generate an induced current
  • the scattered electromagnetic wave formed at this time is opposite to the pole of the incident electromagnetic wave.
  • the direction of the polarization is symmetrical.
  • the result of the change of the transmitted electromagnetic wave after the FSS is as shown in FIG. 5, which can greatly reduce the degree of deterioration of the transmitted electromagnetic wave beam shape, reduce the height of the transmitted electromagnetic wave side lobes, and satisfy the RPE template formulated by ETSI.
  • the energy is more concentrated, the directivity of the horn antenna 300 is improved, and the interference to the surrounding stations is reduced.
  • connection structure 320 another portion of the waveguide 330 is inserted into the connection structure 320, wherein the distance of the waveguide 330 to the first dielectric plate 321 needs to be based on the curvature of the first surface of the first dielectric plate 321 and the phase center of the horn antenna 300. decided together. This is because the FSS 310 is to be used as a secondary reflecting surface of the dual-frequency parabolic antenna.
  • the phase center of the horn antenna 300 must be coincident with the virtual focus of the FSS 310, and the FSS 310 covers the first surface of the first dielectric plate 321, the curvature and The first surface of the first dielectric plate 321 is uniform, so the virtual focus position of the FSS 310 can be determined by the curvature of the first surface of the first dielectric plate 321; and the phase center is a theoretical point, and the antenna radiates a signal outward.
  • the center of the circle is considered to be the phase center of the antenna, but since the actual antenna fabrication cannot be perfect, the phase center of the actual antenna is usually a region; in the embodiment of the invention, by adjusting the specific shape or waveguide of the dielectric wall 323 The distance from 330 to the first dielectric plate 321 or the like can change the phase center of the horn antenna 300, so that the virtual focus of the FSS 310 coincides with the phase center of the antenna.
  • the horn antenna 300 further includes a choke groove 340 located around the waveguide 330 inserted into the hollow structure, the groove depth of the choke groove 340 being the first frequency point corresponding to the wavelength in the air. 1/4, wherein the first frequency point is the center frequency of the transmission band of the FSS 310.
  • the choke groove 340 can suppress lateral propagation of surface current around the waveguide 330 inserted into the hollow structure, thereby radiating the energy of the transmitted electromagnetic wave more concentratedly, improving the radiation efficiency of the horn antenna 300.
  • the number of choke slots 340 is more than one, and the slot pitch of the plurality of choke slots 340 is 1/10 of the corresponding wavelength of the first frequency point in the air. In the present embodiment, if the horn antenna 300 includes a plurality of choke slots 340, the energy of the transmitted electromagnetic waves radiated forward can be further concentrated to improve the radiation efficiency of the horn antenna 300.
  • the number of choke slots 340 is not as large as possible.
  • the first choke slot 340 closest to the waveguide 330 is most effective, and the second to Nth choke slots 340 are further and further away from the waveguide 330, and the effect is also getting smaller and smaller, and the number of the choke slots 340 is The embodiment of the present invention does not limit this.
  • v the velocity of light in the medium.
  • the thickness of the first dielectric plate 321 is a half of a corresponding wavelength of the first frequency plate in the first dielectric plate 321, wherein the first frequency point is a center frequency point of the FSS transmission frequency band. At this time, the thickness of the first dielectric plate 321 does not change, and the curvatures of the first surface and the second surface of the first dielectric plate 321 necessarily coincide.
  • the low-frequency transmission bandwidth of the FSS 310 is related to the thickness of the first dielectric plate 321
  • the low-frequency electromagnetic wave is in the process from air to medium to air when the thickness of the first dielectric plate 321 is half of the wavelength of the medium corresponding to the first frequency point.
  • the reflections generated from the first surface and the second surface of the first dielectric plate 321 will cancel each other (both amplitudes are opposite in phase), and the low-frequency transmission bandwidth of the FSS 310 can be increased. Therefore, the thickness of the first dielectric plate 321 of the embodiment of the present invention is half of the medium wavelength corresponding to the first frequency point, and can play the role of increasing the transmission bandwidth of the low frequency band compared with other thicknesses.
  • connection structure 320 having a hollow structure without using a solid structure.
  • the electromagnetic wave loss can be reduced, the radiation efficiency of the horn antenna 300 can be improved, and the low frequency band is also used. Transmitted bandwidth related.
  • Figure 6 shows the reflection coefficient of the FSS to the low-frequency electromagnetic wave. It can be seen from the figure that when the solid medium is used, the transmission bandwidth of the FSS (the reflection coefficient is below -15 dB) is around 1 GHz, and the embodiment of the present invention is used. In the hollow structure, the transmission bandwidth of the FSS can reach about 1.85 GHz, and the transmission bandwidth of the low frequency band can be significantly improved.
  • the embodiment of the present invention integrates the low frequency horn feed and the FSS, which can greatly reduce the alignment error with the high frequency horn feed; the hollow structure connection structure 320 can minimize the electromagnetic wave propagation in the medium. , reducing the unnecessary loss, increasing the radiation efficiency of the horn antenna 300, and obtaining a larger low-band transmission bandwidth relative to the solid medium; the array arrangement direction of the FSS 310 and the polarization of the incident electromagnetic wave in the embodiment of the present invention The direction is 45 degrees or 135 degrees, which can reduce the deterioration of the transmitted electromagnetic beam shape and reduce the height of the transmitted electromagnetic wave side lobes, thereby improving the directivity of the horn antenna 300 and reducing interference to surrounding sites.

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Abstract

本发明公开一种喇叭天线，包括：频率选择表面FSS，连接结构和波导管；连接结构包括第一介质板，第二介质板和介质壁，第一介质板的第一表面为表面凸起的双曲面，第二表面与介质壁相连，其中，两个表面的间距为第一介质板的厚度；介质壁呈筒状结构，介质壁的第一表面被第一介质板覆盖，介质壁的第二表面被第二介质板覆盖，其中，这两个表面的间距为介质壁的高度；第二介质板的中间位置有孔；介质壁，第一介质板和第二介质板共同构成中空结构；FSS覆盖第一介质板的第一表面；波导管的一部分插入到第二介质板的孔中。本发明公开的喇叭天线可以降低透过FSS的光束的副瓣高度，提高天线的指向性，还具有更高的辐射效率。

Description

一种喇叭天线 技术领域
本发明涉及无线通信技术领域，尤其涉及一种可用于双频抛物面天线的喇叭天线。
背景技术
随着无线通信技术的迅速发展，微波点到点通信的传输容量不断增大，Eband(71-76GHz，81-86GHz)频段的微波设备在基站回传网络中发挥越来越重要的作用。但是，因为Eband频段的电磁波“雨衰”特别严重，所以Eband微波单跳距离通常小于3公里。为了增大Eband微波的单跳距离，降低建站成本，有一种解决方案是将Eband频段微波设备和其他低频微波设备组合使用，当出现较大降雨时，Eband微波设备虽然无法正常工作，但是低频微波设备依然可以正常工作。
该解决方案采用双频抛物面天线，结构如图1所示，该双频抛物面天线包括主反射面，副反射面，低频馈源和高频馈源，其中，低频馈源和高频馈源均为喇叭天线的一种，在应用于其他天线结构中时，通常被称为喇叭馈源，两个馈源共用一个主反射面；将频率选择表面(Frequency Selective Surface，FSS)用作副反射面，副反射面设计成双曲面，双曲面的虚焦点与主反射面的实焦点重合，将不同频率的馈源分置于双曲面的虚焦点和实焦点。副反射面对位于虚焦点的低频馈源发射的电磁波是透射的，对位于实焦点的高频馈源发射的电磁波是反射的，从而实现双频复用的功能。
在现有技术中，低频喇叭馈源和FSS是两个独立的器件，存在装配误差大，天线增益低，波束指向偏离视轴方向的问题。
发明内容
本发明实施例提供一种喇叭天线，集成了低频喇叭馈源和FSS的功能， 解决了在现有技术中，装配误差大导致的天线增益低，波束指向偏离视轴方向的问题。
第一方面，提供一种喇叭天线，包括：频率选择表面FSS，连接结构和波导管，所述连接结构，包括第一介质板，第二介质板和介质壁，所述第一介质板的第一表面为表面凸起的双曲面，所述第一介质板的第二表面与所述介质壁相连，其中，所述第一介质板的两个表面的间距为所述第一介质板的厚度；所述介质壁呈筒状结构，所述介质壁的第一表面被所述第一介质板覆盖，所述介质壁的第二表面被所述第二介质板覆盖，其中，所述介质壁的两个表面的间距为所述介质壁的高度，所述介质壁的第一表面的面积不小于所述介质壁的第二表面的面积；所述第二介质板的中间位置有孔；所述第一介质板，所述介质壁和所述第二介质板共同构成中空结构；所述FSS覆盖所述第一介质板的第一表面；所述波导管的一部分插入到所述第二介质板的孔中。
本发明实施例提供的喇叭天线集成了FSS和低频喇叭馈源的功能，可以大幅降低与高频喇叭馈源的对准误差，降低装配难度，还具有较高的辐射效率。
结合第一方面，在第一方面的第一种可能的实现方式中，所述FSS的阵列排布方向与入射电磁波的极化方向成45度或135度，可以降低透过该FSS的电磁波的副瓣高度，从而降低该电磁波波束形状的劣化程度。
结合第一方面，在第一方面的第二种可能的实现方式中，所述第一介质板的厚度为第一频点在所述第一介质板中对应的波长的一半，其中，所述第一频点为所述FSS的透射频段的中心频点。本发明实施例可以使透射电磁波从所述第一介质板正面和背面的反射相互抵消，增加FSS对低频段的透射带宽。
结合第一方面或第一方面的第一种或第二种可能的实现方式，在第一方面的第三种可能的实现方式中，所述波导管的另一部分插入到所述中空结构中。
结合第一方面的第三种可能的实现方式，在第一方面的第四种可能的实现方式中，所述喇叭天线还包括扼流槽，位于插入到中空结构中的所述 波导管的周围，所述扼流槽的槽深为第一频点在空气中对应的波长的1/4，其中，所述第一频点为所述FSS的透射频段的中心频点。本发明实施例可以使电磁波的能量更加集中地向前辐射，提高所述喇叭天线的辐射效率。
结合第一方面的第四种可能的实现方式，在第一方面的第五种可能的实现方式中，所述扼流槽的数量不止一个，槽间距为第一频点在空气中对应的波长的1/10。在本实施例中，所述喇叭天线包括多个扼流槽，进一步提高所述喇叭天线的辐射效率。
在本发明实施例提供的方案中，喇叭天线集成了FSS和低频喇叭馈源的功能，可以大幅降低与高频喇叭馈源的对准误差，降低装配难度，而且本发明实施例提供的喇叭天线还具有较高的辐射效率。
附图说明
为了更清楚地说明本发明实施例或现有技术中的技术方案，下面将对实施例或现有技术描述中所需要使用的附图作简单地介绍，显而易见地，下面描述中的附图仅仅是本发明的一些实施例，对于本领域普通技术人员来讲，在不付出创造性劳动性的前提下，还可以根据这些附图获得其他的附图。
图1为现有的双频抛物面天线的结构示意图；
图2为现有的喇叭天线的结构示意图；
图3为本发明一实施例提供的一种喇叭天线的结构示意图；
图4为应用本发明实施例的双频抛物面天线的结构示意图；
图5为本发明实施例提供的喇叭天线中FSS阵列排布方向与入射电磁波极化方向之间的关系图；
图6为电磁波分别经本发明提供的喇叭天线中的FSS与现有的FSS之后，电磁波方向图的对比图；
图7为经过采用中空连接结构的喇叭天线和采用实心连接结构的喇叭天线后，低频段电磁波的反射系数对比图。
具体实施方式
下面将结合本发明实施例中的附图，对本发明实施例中的技术方案进行清楚、完整地描述，显然，所描述的实施例是本发明的一部分实施例，而不是全部实施例。基于本发明中的实施例，本领域普通技术人员在没有做出创造性劳动的前提下所获得的所有其他实施例，都应属于本发明的保护范围。
以下描述中，为了说明而不是为了限定，提出了诸如特定系统结构、接口、技术之类的具体细节，以便透彻理解本发明。然而，本领域的技术人员应当清楚，在没有这些具体细节的其它实施例中也可以实现本发明。在其它情况中，省略对众所周知的装置、电路以及方法的详细说明，以免不必要的细节妨碍本发明的描述。
当本发明实施例提及“第一”、“第二”等序数词时，除非根据上下文其确实表达顺序之意，否则应当理解为仅仅是起区分之用。
为了便于本领域技术人员的理解，本发明通过以下实施例对本发明提供的技术方案进行说明。
众所周知，喇叭天线是一种应用非常广泛的天线，图1中的低频馈源和高频馈源均为喇叭天线，现有的喇叭天线通常由实心介质块和波导管组成，如图2所示，该实心介质块为具有曲面顶的圆锥形，与曲面顶相对的尖端插入到波导管内部，与波导管相连，形成喇叭馈源。然而，在现有双频抛物面天线中，FSS和低频喇叭馈源(喇叭天线用于天线结构中通常被称为喇叭馈源)是两个独立的器件，这会导致装配误差大，进而引起天线增益降低，波束指向偏离视轴方向的问题。
本发明实施例提供一种喇叭天线300，集成了FSS和低频喇叭馈源的功能，其结构如图3所示，包括：FSS 310，连接结构320和波导管330，
连接结构320，包括第一介质板321，第二介质板322和介质壁323，第一介质板321的第一表面为表面凸起的双曲面，第一介质板321的第二表面与介质壁323相连，其中，第一介质板321的两个表面的间距为第一介质板321的厚度；介质壁323呈筒状结构，介质壁323的第一表面被第一介质板321覆盖，介质壁的第二表面被第二介质板322覆盖，其中，介质壁323的两个表面的间距为介质壁323的高度，介质壁323的第一表面 的面积不小于介质壁323的第二表面的面积；第二介质板322的中间位置有孔；第一介质板321，介质壁323和第二介质板322共同构成中空结构；FSS 310覆盖第一介质板321的第一表面；波导管330的一部分插入到第二介质板322的孔中。
应理解，第二介质板322的孔面积与波导管330的截面积一致，两者紧密结合，起到连接作用；介质壁323为筒状结构，可以是圆筒，喇叭筒等形状；另外，第一介质板321需采用对透射电磁波损耗较小的材料，采用现有喇叭天线中的介质材料即可，而第二介质板和介质壁主要起支撑作用，采用硬质材料即可，本发明实施例对此均不作限定。
本发明实施例中的FSS 310具有透射低频段电磁波，反射高频段电磁波的功能，可以采用任意具有上述功能的现有FSS，本发明实施例对此不做限定。
图3为应用了本发明实施例提供的喇叭天线300的双频抛物面天线，从图中可以看出，本发明实施例提供的喇叭天线300集成了FSS和低频馈源的功能，只需考虑喇叭天线300与高频喇叭馈源的对准，起到降低对准误差的功能，可以将该对准误差控制在±0.2mm以内。而且，采用中空结构的连接结构320，可以尽量减少电磁波在介质中传播，因为电磁波在介质中的传输损耗总是大于在空气中的传输损耗，减少电磁波在介质中传播，就等于减少无谓的损耗，增加发射出去的功率，本发明实施例提供的喇叭天线300的辐射效率可以达到98％。
可选地，作为另一个实施例，FSS 310的阵列排布方向与入射电磁波的极化方向成45度或135度，如图4所示，实线箭头表示入射电磁波的极化方向，虚线箭头表示FSS 310的阵列排布方向，由于电磁波通常为正弦波，其极化方向表现为两种相差180度的情况，就如图4中实线两端均有箭头所示，故FSS 310的阵列排布方向与入射电磁波的极化方向在某一时刻成45度，在下一时刻就可能变成135度。本发明实施例提出可以起到降低透射电磁波副瓣高度的作用。
具体的，以喇叭天线300发射的低频电磁波入射到FSS 310为例，该入射电磁波通过FSS 310时，会在FSS 310表面产生感应电流，感应电流 产生的散射电磁波和入射电磁波相互作用，形成透射电磁波。当FSS 310的阵列排布方向与入射电磁波极化方向一致(0度)或者垂直(90度)时，和极化方向一致的缝隙的两边金属没有产生感应电流，和极化方向垂直的缝隙的两边金属会产生感应电流，这时产生的散射电磁波相对于入射电磁波极化方向是不对称的，此时，透射电磁波经FSS 310之后的方向图变化结果如图5所示，无法满足欧洲电信标准化协会(European Telecommunications Standards Institute，ETSI)制定的天线方向图(Radiation Pattern Envelope，RPE)模板。而当FSS 310的阵列排布方向与入射电磁波的极化方向呈45度或者135度时，前述两个方向的缝隙的两边金属都会产生感应电流，这时形成的散射电磁波相对于入射电磁波的极化方向是对称的，此时，透射电磁波经FSS之后的方向图变化结果如图5所示，可以大幅降低透射电磁波波束形状的劣化程度，降低透射电磁波副瓣高度，满足ETSI制定的RPE模板，而且与现有的排列方向(0度或90度)相比，能量更加集中，提高了喇叭天线300的指向性，减少了对周围站点的干扰。
可选地，波导管330的另一部分插入到连接结构320中，其中，波导管330到第一介质板321的距离需要根据第一介质板321的第一表面的曲率和喇叭天线300的相位中心共同决定。这是由于FSS 310要用作双频抛物面天线的副反射面，必须要求喇叭天线300的相位中心与FSS 310的虚焦点重合，而FSS 310覆盖了第一介质板321的第一表面，曲率与第一介质板321的第一表面一致，故FSS 310的虚焦点位置可以由第一介质板321的第一表面的曲率决定；而相位中心是一个理论上的点，天线向外辐射的信号的圆心即被认为是天线的相位中心，但是由于实际天线的制作不可能完美无缺，故实际天线的相位中心通常是一个区域；在本发明实施例中，通过调节介质壁323的具体形状或者波导管330到第一介质板321的距离等，即可改变喇叭天线300的相位中心，实现FSS 310的虚焦点与天线的相位中心重合。
另外，喇叭天线300还包括扼流槽340，位于插入到中空结构中的波导管330的周围，该扼流槽340的槽深为第一频点在空气中对应的波长的 1/4，其中，第一频点为FSS 310的透射频段的中心频点。该扼流槽340可以抑制插入到中空结构中的波导管330周围的表面电流横向传播，从而使透射电磁波的能量更加集中地向前辐射，提高喇叭天线300的辐射效率。进一步地，扼流槽340的数量不止一个，多个扼流槽340的槽间距为第一频点在空气中对应的波长的1/10。在本实施例中，如果喇叭天线300包括多个扼流槽340，可以进一步集中向前辐射的透射电磁波的能量，提高喇叭天线300的辐射效率。
需要说明的是，扼流槽340的数量并不是越多越好。最接近波导管330的第一个扼流槽340效果最明显，第二至第N个扼流槽340距离波导管330越来越远，效果也越来越小，扼流槽340的数量要由实际情况决定，本发明实施例对此不做限定。
需要说明的是，频率(f)与波长(λ)的关系为v＝f×λ，其中，v表示光在介质中的速度。在真空中，v等于光速，即3×108m/s；在介质中，与该介质的折射率有关，假设介质的折射率为n，则v＝光速/n。
可选地，作为另一个实施例，第一介质板321的厚度为第一频点在第一介质板321中对应的波长的一半，其中，第一频点为FSS透射频段的中心频点。此时，第一介质板321的厚度不变，则第一介质板321的第一表面和第二表面的曲率必然一致。
由于FSS 310的低频透射带宽与第一介质板321的厚度有关，当第一介质板321的厚度为第一频点对应的介质波长的一半时，低频电磁波在从空气到介质再到空气的过程中，从第一介质板321第一表面和第二表面产生的反射将相互抵消(两者幅度相等相位相反)，可以增大FSS 310的低频透射带宽。故本发明实施例的第一介质板321的厚度为第一频点对应的介质波长一半，与其他厚度相比，可以起到增加低频段的透射带宽的作用。
另外，本发明实施例采用具有中空结构的连接结构320，而没有采用实心结构的原因，除中空结构的连接结构320可以减少电磁波损耗，提高喇叭天线300的辐射效率之外，还与低频段的透射带宽有关。图6显示了FSS对低频段电磁波的反射系数，从图中可以看出，采用实心介质时，FSS的透射带宽(反射系数在-15dB以下)在1GHz左右，采用本发明实施例 的中空结构时，FSS的透射带宽可以达到约1.85GHz，低频段的透射带宽可以得到明显地提升。
综上所述，本发明实施例将低频喇叭馈源和FSS做成一体，可以大幅降低与高频喇叭馈源的对准误差；采用中空结构的连接结构320，可以尽量减少电磁波在介质中传播，减少无谓的损耗，增大喇叭天线300的辐射效率，且相对实心介质来说，可以得到更大的低频段透射带宽；本发明实施例的FSS 310的阵列排布方向与入射电磁波的极化方向成45度或者135度，可以起到降低透射电磁波波束形状的劣化，降低透射电磁波副瓣高度的作用，进而提高喇叭天线300的指向性，减少对周围站点的干扰。
以上所述，仅为本发明的具体实施方式，但本发明的保护范围并不局限于此，任何熟悉本技术领域的技术人员在本发明揭露的技术范围内，可轻易想到变化或替换，都应涵盖在本发明的保护范围之内。因此，本发明的保护范围应以所述权利要求的保护范围为准。

Claims (6)

  1. 一种喇叭天线，其特征在于，包括：频率选择表面FSS，连接结构和波导管，
    所述连接结构，包括第一介质板，第二介质板和介质壁，所述第一介质板的第一表面为表面凸起的双曲面，所述第一介质板的第二表面与所述介质壁相连，其中，所述第一介质板的两个表面的间距为所述第一介质板的厚度；所述介质壁呈筒状结构，所述介质壁的第一表面被所述第一介质板覆盖，所述介质壁的第二表面被所述第二介质板覆盖，其中，所述介质壁的两个表面的间距为所述介质壁的高度，所述介质壁的第一表面的面积不小于所述介质壁的第二表面的面积；所述第二介质板的中间位置有孔；所述第一介质板，所述介质壁和所述第二介质板共同构成中空结构；
    所述FSS覆盖所述第一介质板的第一表面；
    所述波导管的一部分插入到所述第二介质板的孔中。
  2. 根据权利要求1所述的喇叭天线，其特征在于，所述FSS的阵列排布方向与入射电磁波的极化方向成45度或135度。
  3. 根据权利要求1所述的喇叭天线，其特征在于，所述第一介质板的厚度为第一频点在所述第一介质板中对应的波长的一半，其中，所述第一频点为所述FSS的透射频段的中心频点。
  4. 根据权利要求1至3任一项所述的喇叭天线，其特征在于，所述波导管的另一部分插入到所述中空结构中。
  5. 根据权利要求4所述的喇叭天线，其特征在于，所述喇叭天线还包括扼流槽，位于插入到所述中空结构中的所述波导管的周围，所述扼流槽的槽深为第一频点在空气中对应的波长的1/4，其中，所述第一频点为所述FSS的透射频段的中心频点。
  6. 根据权利要求5所述的喇叭天线，其特征在于，所述扼流槽的数量不止一个，槽间距为所述第一频点在空气中对应的波长的1/10。
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* Cited by examiner, † Cited by third party
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CN108767464A (zh) * 2018-06-01 2018-11-06 航天恒星科技有限公司 一种小型化高效率的喇叭形介质光纳米天线
EP3618189A1 (fr) * 2018-08-28 2020-03-04 ArianeGroup SAS Antenne pour un satellite spatial

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* Cited by examiner, † Cited by third party
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TR201819490A2 (tr) * 2018-12-14 2019-02-21 Profen Iletisim Teknolojileri Ve Hizmetleri Sanayi Ticaret Anonim Sirketi Frekans seçi̇ci̇ yüzeyli̇ i̇ki̇nci̇l reflektör
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USD889445S1 (en) * 2019-01-28 2020-07-07 King Saud University Omnidirectional multiband antenna
USD891404S1 (en) * 2019-01-28 2020-07-28 King Saud University Omnidirectional ultra-wideband antenna
USD890145S1 (en) * 2019-01-29 2020-07-14 King Saud University Ultra-wideband unipole antenna
CN110334480B (zh) * 2019-07-26 2022-11-22 中国电子科技集团公司第五十四研究所 用于降低噪声温度的双偏置天线副面扩展曲面设计方法
AU2021333393A1 (en) * 2020-08-27 2023-06-29 Safety Connect IT Pty Ltd A vehicle, equipment and machinery control method and systems
US20220352639A1 (en) * 2021-04-30 2022-11-03 The Board Of Trustees Of The University Of Alabama Miniaturized reflector antenna
TWI832328B (zh) * 2022-07-12 2024-02-11 國立臺灣大學 整合天線裝置

Citations (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US20070109212A1 (en) * 2005-11-14 2007-05-17 Northrop Grumman Corporation High power dual band high gain antenna system and method of making the same
CN201758183U (zh) * 2010-05-19 2011-03-09 广东通宇通讯设备有限公司 一种微波天线的馈源及微波天线
US20160226151A1 (en) * 2015-01-29 2016-08-04 Harris Corporation Method for upgrading a satellite antenna assembly having a subreflector and an associated satellite antenna assembly
CN105870641A (zh) * 2016-05-11 2016-08-17 广东通宇通讯股份有限公司 双频带双反射面天线

Family Cites Families (39)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US3231892A (en) * 1962-06-26 1966-01-25 Philco Corp Antenna feed system simultaneously operable at two frequencies utilizing polarization independent frequency selective intermediate reflector
US4017865A (en) * 1975-11-10 1977-04-12 Rca Corporation Frequency selective reflector system
CA1262773A (en) * 1985-12-25 1989-11-07 Mitsuhiro Kusano Horn antenna with a choke surface-wave structure on the outer surface thereof
US5373302A (en) * 1992-06-24 1994-12-13 The United States Of America As Represented By The Administrator Of The National Aeronautics And Space Administration Double-loop frequency selective surfaces for multi frequency division multiplexing in a dual reflector antenna
JPH07226623A (ja) * 1994-02-15 1995-08-22 Mitsubishi Electric Corp 偏波共用アンテナ
US6121939A (en) * 1996-11-15 2000-09-19 Yagi Antenna Co., Ltd. Multibeam antenna
SE508356C2 (sv) * 1997-02-24 1998-09-28 Ericsson Telefon Ab L M Antennanordningar
JP3784715B2 (ja) * 2001-12-26 2006-06-14 シャープ株式会社 フィードホーン構造、その製造方法、コンバータおよび衛星通信受信用アンテナ
US6870511B2 (en) * 2002-05-15 2005-03-22 Hrl Laboratories, Llc Method and apparatus for multilayer frequency selective surfaces
US6774861B2 (en) * 2002-06-19 2004-08-10 Northrop Grumman Corporation Dual band hybrid offset reflector antenna system
JP4263166B2 (ja) * 2004-12-10 2009-05-13 シャープ株式会社 フィードホーン、電波受信用コンバータおよびアンテナ
JP2007096868A (ja) * 2005-09-29 2007-04-12 Mitsubishi Electric Corp 反射板および該反射板を備えたリフレクタアンテナ
US8212734B1 (en) * 2007-11-15 2012-07-03 Lockheed Martin Corporation Hybrid reflector with radiating subreflector
EP2234204A4 (en) * 2007-12-07 2010-12-22 Nec Corp PARABOLIC ANTENNA
US8680954B2 (en) 2008-08-29 2014-03-25 Nec Corporation Waveguide, waveguide connection structure and waveguide connection method
US8497810B2 (en) * 2009-03-18 2013-07-30 Kvh Industries, Inc. Multi-band antenna system for satellite communications
WO2011051456A1 (de) * 2009-10-29 2011-05-05 Technische Universität Dresden Antennenanordnung zur übertragung von signalen
KR100976535B1 (ko) * 2010-01-07 2010-08-17 삼성탈레스 주식회사 주파수 선택기
FR2959611B1 (fr) * 2010-04-30 2012-06-08 Thales Sa Element rayonnant compact a cavites resonantes.
WO2013003453A2 (en) * 2011-06-27 2013-01-03 Triton Systems, Inc. Insert for radomes and methods of manufacturing insert for radomes
CN102394374B (zh) * 2011-06-29 2013-08-28 西安空间无线电技术研究所 一种双频馈源
US9551820B2 (en) * 2011-08-03 2017-01-24 The United States Of America As Represented By The Secretary Of The Army Electromagnetic composite-based reflecting terahertz waveplate
JP5854888B2 (ja) * 2011-08-29 2016-02-09 三菱電機株式会社 一次放射器及びアンテナ装置
CN103036026B (zh) * 2011-09-29 2016-01-13 深圳光启高等理工研究院 一种喇叭天线
CN103036029B (zh) * 2011-09-29 2016-01-13 深圳光启高等理工研究院 一种喇叭天线
EP2590264A1 (en) * 2011-11-02 2013-05-08 Astrium Limited Dual band splashplate support for a reflector antenna
CN202487779U (zh) * 2012-03-12 2012-10-10 中国电子科技集团公司第五十四研究所 一种利用频率选择表面技术实现宽频带四频段共用天线
CN102694255B (zh) * 2012-04-27 2014-08-13 深圳光启创新技术有限公司 超材料微波天线罩和天线系统
EP2752941A1 (de) * 2013-01-03 2014-07-09 VEGA Grieshaber KG Parabolantenne mit einem im Radom integrierten Subreflektor
US20150009083A1 (en) * 2013-04-03 2015-01-08 Prime Electronics And Satellitics Incorporation Feed horn having dielectric layers and assembly of feed horn and radome
US9379457B2 (en) * 2013-04-03 2016-06-28 Prime Electronics And Satellitics Incorporation Radome for feed horn and assembly of feed horn and radome
CN104425875A (zh) * 2013-08-30 2015-03-18 深圳光启创新技术有限公司 一种超材料天线增强装置及天线、天线阵列
JP6198647B2 (ja) * 2014-03-19 2017-09-20 三菱電機株式会社 アンテナ装置
US9893417B2 (en) * 2015-01-29 2018-02-13 Speedcast International Limited Satellite communications terminal for a ship and associated methods
US9685712B2 (en) * 2015-01-29 2017-06-20 Harris Corporation Multi-band satellite antenna assembly with dual feeds in a coaxial relationship and associated methods
US9859621B2 (en) * 2015-01-29 2018-01-02 Speedcast International Ltd Multi-band satellite antenna assembly and associated methods
US10193234B2 (en) * 2015-01-29 2019-01-29 Speedcast International Limited Method for upgrading a satellite antenna assembly and an associated upgradable satellite antenna assembly
CN204632922U (zh) * 2015-04-28 2015-09-09 电子科技大学 一种基于超材料加载的高增益喇叭天线
US10658757B2 (en) * 2015-06-19 2020-05-19 Hughes Network Systems, Llc Satellite ground terminal utilizing frequency-selective surface subreflector

Patent Citations (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US20070109212A1 (en) * 2005-11-14 2007-05-17 Northrop Grumman Corporation High power dual band high gain antenna system and method of making the same
CN201758183U (zh) * 2010-05-19 2011-03-09 广东通宇通讯设备有限公司 一种微波天线的馈源及微波天线
US20160226151A1 (en) * 2015-01-29 2016-08-04 Harris Corporation Method for upgrading a satellite antenna assembly having a subreflector and an associated satellite antenna assembly
CN105870641A (zh) * 2016-05-11 2016-08-17 广东通宇通讯股份有限公司 双频带双反射面天线

Non-Patent Citations (1)

* Cited by examiner, † Cited by third party
Title
See also references of EP3419117A4 *

Cited By (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN108767464A (zh) * 2018-06-01 2018-11-06 航天恒星科技有限公司 一种小型化高效率的喇叭形介质光纳米天线
EP3618189A1 (fr) * 2018-08-28 2020-03-04 ArianeGroup SAS Antenne pour un satellite spatial
FR3085552A1 (fr) * 2018-08-28 2020-03-06 Arianegroup Sas Antenne pour un satellite spatial

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CN108701905B (zh) 2020-12-15
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BR112019004151A2 (pt) 2019-05-28
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US10727607B2 (en) 2020-07-28
US20190051990A1 (en) 2019-02-14
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CN108701905A (zh) 2018-10-23
EP3419117A4 (en) 2019-05-22

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