WO2016186000A1 - Système de communication sans fil et dispositif de réception - Google Patents

Système de communication sans fil et dispositif de réception Download PDF

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Publication number
WO2016186000A1
WO2016186000A1 PCT/JP2016/064157 JP2016064157W WO2016186000A1 WO 2016186000 A1 WO2016186000 A1 WO 2016186000A1 JP 2016064157 W JP2016064157 W JP 2016064157W WO 2016186000 A1 WO2016186000 A1 WO 2016186000A1
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unit
mutual information
calculating
transmission
information amount
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PCT/JP2016/064157
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English (en)
Japanese (ja)
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大樹 星
仲田　樹広
圭 伊藤
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株式会社日立国際電気
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Priority to JP2017519166A priority Critical patent/JP6576443B2/ja
Publication of WO2016186000A1 publication Critical patent/WO2016186000A1/fr

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    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03M—CODING; DECODING; CODE CONVERSION IN GENERAL
    • H03M13/00—Coding, decoding or code conversion, for error detection or error correction; Coding theory basic assumptions; Coding bounds; Error probability evaluation methods; Channel models; Simulation or testing of codes
    • H03M13/37—Decoding methods or techniques, not specific to the particular type of coding provided for in groups H03M13/03 - H03M13/35
    • H03M13/45—Soft decoding, i.e. using symbol reliability information
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L1/00—Arrangements for detecting or preventing errors in the information received
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems

Definitions

  • the present invention relates to a wireless communication system and a receiving apparatus.
  • the bit error rate is an index of transmission quality, and the bit error rate required for each system is different.
  • FPU Field Pickup Unit
  • the bit error rate after inner code decoding is 1 ⁇ 10 ⁇ 4 or less. It is possible to correct errors up to error-free (for example, see Non-Patent Document 1).
  • the bit error rate fluctuates every moment according to the state of the transmission path. Therefore, it is necessary to grasp how much transmission margin there is for the required bit error rate in order to perform stable transmission.
  • a transmission margin As a method of calculating a transmission margin, received power measured at the receiving side, received CNR (Carrier to Noise power Ratio), MER (Modulation Error Ratio), etc., computer simulation, The margin is calculated from the previous verification result obtained by actual measurement or the like. Since the received power and the received CNR that satisfy the required bit error rate change according to the transmission path characteristics and the influence of interference, a table storing the margin for each transmission path is prepared in advance, and the margin is set according to the transmission path. Is desirable but not realistic. Therefore, it is common to set a transmission margin based on a simulation result by a computer simulation with a predetermined transmission path model or an actual measurement value of the transmission path.
  • CNR Carrier to Noise power Ratio
  • MER Modulation Error Ratio
  • AMC Adaptive Modulation Coding
  • HSDPA High Speed Downlink Packet Access
  • LTE Long Term Evolution
  • AMC generally selects MCS (Modulation and Coding Set) that maximizes the transmission rate while satisfying the required bit error rate of the system, based on transmission path information obtained by the receiving apparatus.
  • MCS Modulation and Coding Set
  • the reception CNR or the like is used as an index of the quality of the transmission path.
  • the reception CNR threshold value for selecting the optimum MCS is set based on the bit error rate characteristics in each MCS obtained in advance based on computer simulation, actual measurement values, and the like.
  • Patent Document 1 when the number of repetitions is limited in the turbo equalization technique, a modulation method and a coding rate that can complete the decoding process of transmission data with the number of repetitions are described. A technique for selecting is disclosed.
  • ARIB STD-B57 version 2.0 “1.2 GHz / 2.3 GHz band portable OFDM digital wireless transmission system for transmitting TV broadcast program material”, Japan Radio Industry Association Error control considering terrestrial transmission line characteristics, Annual Conference of the Institute of Image Information and Television Engineers (1998)
  • transmission quality may deteriorate in an environment where the antenna correlation is high, because it becomes difficult to separate and detect received signals.
  • the transmission margin is set based on the reception power, reception CNR, etc., which are the indicators of the conventional transmission path quality, the bit error rate is high in the above high antenna correlation environment even though there is a transmission margin with a high reception CNR. There arises a problem of deterioration.
  • An object of the present invention is to improve a transmission rate by selecting an appropriate modulation method and coding rate even in a high antenna correlation environment or an environment where a narrow band interference signal is mixed.
  • a receiving apparatus of the present invention is a receiving apparatus that generates coded bits from an information bit input by error correction coding processing, and receives a modulated signal that is digitally modulated with respect to the coded bits.
  • Demodulating means for calculating a log likelihood ratio for encoded bits of correction encoding; means for calculating an average mutual information amount for log likelihood ratios for encoded bits; average mutual information amount and required bit error rate
  • the receiving apparatus of the present invention generates coded bits by performing error correction coding processing on information bit input, and performs digital modulation on the coded bits rearranged in a predetermined order by an interleaver having interleaving means.
  • a receiving unit that receives the modulated signal, a demodulating unit that calculates a log-likelihood ratio for a coded bit based on the received signal and a priori information, and data rearranged by the interleaver on the transmitting side
  • a deinterleaver unit having a deinterleaver that rearranges the order back to the original order; a mutual information calculation unit and a margin calculation unit arranged in at least one of the preceding stage or the subsequent stage of the deinterleaver unit;
  • Demodulating interleaver and interleaver output comprising decoding means for calculating frequency ratio and interleaving means for rearranging coded bits of decoding section output in predetermined order Of comprising means for inputting as a priori information, characterized in that it comprises means for calculating a logarithmic likelihood ratio or the hard decision result for the resulting information bit by the error correction decoding means.
  • the receiving apparatus of the present invention is the above-described receiving apparatus, and includes an interference detection unit and an erasure correction unit arranged at least one of the preceding stage and the subsequent stage of the demodulation unit, and the interference detection unit is arranged at the preceding stage of the demodulation unit.
  • it has means for detecting an interference component from the received signal, and when it is arranged at the latter stage of the demodulator, it has means for detecting an interference component for the coded bit output from the demodulator, and the erasure correction And means for performing erasure correction processing on the received signal based on the detection result of interference obtained by the interference detecting means for the received signal input to the demodulating section when placed in the preceding stage of the demodulating section.
  • To degree ratio Means for performing erasure correction processing means for calculating the average mutual information amount with respect to the log likelihood ratio for the coded bits after the erasure correction processing, and the average mutual information amount obtained by the average mutual information amount calculation means And means for calculating a transmission margin from the demodulator output mutual information amount or the decoding unit input mutual information amount satisfying the required bit error rate.
  • the wireless communication system of the present invention includes a base station and a mobile station, and the base station and the mobile station generate encoded bits by performing error correction encoding processing on information bit input, and digitally modulate the encoded bits.
  • a radio communication system for transmitting and receiving a modulated signal wherein a base station performs error correction coding, digital modulation, and a modulation scheme or coding rate based on a transmission margin notified from a reception processing unit.
  • a transmission processing unit having means for transmitting by changing at least one of the above, means for receiving a digitally modulated signal from the mobile station, and extracting a transmission margin generated by the mobile station from the received signal
  • a reception processing unit provided with means, and a means for notifying a transmission margin to the error correction coding control unit is provided with either a transmission processing unit or a reception processing unit.
  • Means for performing positive encoding, means for performing digital modulation, a transmission processing unit comprising means for transmitting a frame signal including feedback information, means for receiving a digitally modulated signal from a base station, and receiving A demodulating means for calculating coded bits from the signal; means for calculating an average mutual information amount with respect to a log likelihood ratio with respect to the coded bits; an average mutual information amount obtained by the average mutual information calculating means; A means for calculating a transmission margin from a decoding unit input mutual information amount or a demodulating unit output mutual information amount satisfying a bit error rate, a means for notifying the transmission processing unit of the transmission margin, and an information bit obtained by the error correction decoding unit
  • a reception processing unit having a means for calculating a log likelihood ratio and a means for calculating a determination result of the log likelihood ratio for the information bits, Characterized in that it comprises means for generating feedback information based on the margin to one of the transmission processing unit or the reception processing unit.
  • the wireless communication system of the present invention is the communication system described above, wherein at least one reception processing unit of the base station or the mobile station includes a demodulation unit, an average mutual information calculation unit, a transmission margin calculation unit, Correction decoding means, deinterleaving means, logarithm for information bits obtained by error correction decoding means, mutual information amount calculating means, margin calculating means arranged in at least one of the preceding stage and the succeeding stage of deinterleaving means Likelihood ratio or hard decision result calculation means is provided.
  • the wireless communication system of the present invention is the communication system described above, wherein at least one reception processing unit of the base station or the mobile station includes a demodulation unit, an average mutual information calculation unit, a transmission margin calculation unit, Correction decoding means, deinterleaving means, logarithm for information bits obtained by error correction decoding means, mutual information amount calculating means, margin calculating means arranged in at least one of the preceding stage and the succeeding stage of deinterleaving means A likelihood ratio or hard decision result calculating means, an interference component detecting means, an erasure correcting means, a means for calculating an average mutual information amount with respect to a log likelihood ratio for the coded bits obtained by the erasure correcting means; Demodulator output mutual information amount or decoding unit input phase satisfying average mutual information amount and required bit error rate obtained by average mutual information amount calculation means Characterized in that it comprises a means for calculating a transmission margin from the amount of information.
  • the present invention it is possible to improve the transmission rate by selecting an appropriate modulation method and coding rate even in a high antenna correlation environment or an environment where a narrow band interference signal is mixed.
  • FIG. 3 is a diagram for explaining a transmission margin calculation example from a bit error rate characteristic with respect to a decoding unit input mutual information amount in FIG. 2.
  • FIG. 1 is a first block diagram according to an embodiment of the present invention.
  • a MIMO (Multiple Input Multiple Output) transmission system composed of two transmitting antennas and two receiving antennas will be described, but the transmitting device and the receiving transmission have a single input single output (SISO) transmission. It can also be applied to SIMO (Single Input Multiple Output) transmission system in which only the system and the receiving device have two or more antennas, and MISO (Multiple Input Single Output) transmission system in which only the transmission device has two or more antennas. is there.
  • SISO Multiple Input Single Output
  • Unit 1 includes a reception system 1 and a reception system 2, and includes an antenna 101-1 for the reception system 1, an antenna 101-2 for the reception system 2, and an RF (Radio Frequency: radio) for the reception system 1.
  • Unit 102-1, RF system 102-2 for reception system 2 demodulation unit 103, deinterleaver unit 104-1 for reception system 1, deinterleaver unit 104-2 for reception system 2, MUX (Multiplexer) Unit 105, decoding unit 106, hard decision unit 107, mutual information amount calculation unit 108, and margin calculation unit 109.
  • RF Radio Frequency: radio
  • the antenna 101-1 and the antenna 101-2 receive a radio signal transmitted from the transmission device, and the RF unit 102-1 and the RF unit 102-2 receive the carrier frequency bands received by the antenna 101-1 and the antenna 101-2, respectively.
  • the received signal is down-converted from the received signal to a baseband signal, and the received signals Y 1 and Y 2 are output to the demodulator 103, respectively.
  • the subscripts 1 and 2 indicate the receiving system 1 and the receiving system 2, respectively.
  • Demodulation unit 103 by demodulating the received signal Y 1 and Y 2 obtained coded bits LLRL E p, 1 and L E p, 2 (subscript p indicates the first letter of Posterior ) Respectively.
  • the coded bit indicates a bit after error correction coding, and the bit before error correction coding is hereinafter referred to as an information bit.
  • Bit LLR is defined as the logarithm of the ratio of the likelihood that the bit is 0 to the likelihood that it is 1.
  • MLD Maximum Likelihood Detection
  • MLD Maximum Likelihood Detection
  • L E a, 1 is a coded bit LLR based on prior information in the reception system 1
  • L E a, 2 is a coded bit LLR based on prior information in the reception system 2, and in this embodiment, prior to transmission signals.
  • the calculated output LLRL E e, 1 of the demodulation unit 103 is output to the deinterleaver unit 104-1, and L E e, 2 is output to the deinterleaver unit 104-2.
  • the deinterleaver unit 104-1 and the deinterleaver unit 104-2 are arranged so that the interleaving performed by the transmission apparatus is returned to the original order with respect to the input L E e, 1 and L E e, 2 respectively . Each process to be replaced is performed.
  • the rearranged outputs L D a, 1 and L D a, 2 are input to the MUX unit 105.
  • the MUX unit 105 performs a process of rearranging the input L D a, 1 and L D a, 2 so that the inter-system distribution process performed by the transmission apparatus returns to the original order.
  • the input LLRL D a of the decoding unit 106 that is the output after the rearrangement is output to the decoding unit 106 and the mutual information amount calculation unit 108.
  • Decoding unit 106 for being inputted LLRL D a for example, performs decoding processing by using a maximum a posteriori probability decoding, calculates output information bits LLRL D u of the decoding unit 106, and outputs the hard decision unit 107 .
  • the hard decision unit 107 outputs a decoding result u obtained by a decision process such as a hard decision.
  • Mutual information amount calculation unit 108 based on the input LLRL D a, and calculates the mutual information.
  • An embodiment of the present invention is characterized by providing an apparatus capable of calculating an appropriate transmission margin even in various transmission path environments by calculating a transmission margin from the mutual information amount.
  • a process of calculating the mutual information amount from L D a will be described, and a method of calculating the margin from the calculated mutual information amount will be described.
  • the mutual information I (X; Y) is obtained by (Equation 3) quantitatively indicating how much information regarding the random variable X is included in the event Y by knowing the value of the event Y.
  • H (X) is called prior entropy in mutual information
  • Y) is called posterior entropy.
  • Prior entropy H (X) in the random variable X is obtained by (Equation 4).
  • H (C n ) is expressed by (Equation 6).
  • Y) is obtained by (Expression 7).
  • mutual information I n is can be calculated by the bit probabilities P '0 and P' 1. Assuming that the probabilities that the input coded bit C n of the n-th decoding unit 106 is 0 and 1 are P ′ 0 (C n ) and P ′ 1 (C n ), respectively, the input LLL D D a of the decoding unit 106 (C n ) is given by (Equation 10). By transforming (Expression 9), P ′ 0 (C n ) and P ′ 1 (C n ) are expressed by (Expression 11) and (Expression 12), respectively. By substituting the equation (9) and (Equation 11) (Equation 12), the mutual information I n is (Equation 13).
  • the mutual information amount calculation unit 108 can calculate from mutual information I n inputted to the L D a (C n).
  • the method of calculating the mutual information I n for example, the Maclaurin expansion that does not require a conversion table or tables for calculating the mutual information I n when the input LLRL D a (C n) is given of the decoding unit 106
  • the approximate calculation used can be mentioned. Since the mutual information amount of (Equation 13) is an instantaneous value, the variation is large. Accordingly, the average mutual information IE that suppresses the variation by taking the sample average with respect to the encoding bit number N (N is a natural number) is calculated by (Equation 14), and is output to the margin calculation unit 109.
  • the average mutual information IE after the demodulation process is a value that takes into account the influence of the antenna correlation that is not considered in the reception CNR or the like. It becomes. Further, the average mutual information IE calculated by the mutual information calculator 108 does not require a parameter related to antenna correlation.
  • the output LLR demodulation unit 103 of the serial transmission and L E e if the average mutual information I E coding bit number N calculated at sufficiently Okere, instead of the input LLRL D a of the decoding unit 106 Since the same value is obtained even when the output LLRL E e of the demodulator 103 is used, I E may be calculated using the output LLRL E e of the demodulator 103.
  • the MLL unit 105 calculates the mutual information amount by bundling the inputs LLRL D a, 1 and L D a, 2 of the decoding unit 106 of each system, but the average mutual information I E for each system. May be calculated.
  • the transmission margin I M is expressed by (Equation 15). Can be sought.
  • the mutual information input / output characteristics of the decoding process are uniquely determined according to only the error correction coding method regardless of the transmission path characteristics and the received CNR. It is a well-known technique that the bit error rate with respect to the input mutual information amount of the decoding unit 106 can be calculated from this input / output characteristic, and can be drawn in a graph as shown in FIG.
  • the transmission margin in each modulation method can be calculated simultaneously.
  • the relationship with the LLR of the demodulator 103 output in each modulation method can be obtained.
  • the user using the receiving apparatus can know the transmission margin I M.
  • the above are representative of transmission margin I M using mutual information, may provide information analogous thereto. For example, a warning alarm is notified when the transmission margin I M approaches zero.
  • the average mutual information I E is calculated from the input LLRL D a of the decoding unit 106, and the transmission margin I M is calculated based on the obtained average mutual information I E. It is possible to provide an appropriate transmission margin considering the influence.
  • FIG. 2 is a second block diagram according to an embodiment of the present invention.
  • the second block diagram is characterized in that the receiving apparatus described in the first block diagram is provided with turbo signal processing for performing iterative processing a plurality of times.
  • a description will be given of a MIMO transmission system including two transmission antennas and two reception antennas, but the present invention can also be applied to a SISO transmission system, a SIMO transmission system, and a MISO transmission system.
  • the demodulation unit 201 and the decoding unit 204 are connected via the deinterleaver units 202-1 and 202-2 and the interleaver units 206-1 and 206-2, and the demodulation unit 201 and the decoding unit are performed while performing iterative processing.
  • This is a technique for improving the decoding performance by passing the encoded bit LLR between the two.
  • the demodulator 201 outputs Y 1 and Y 2 output from the RF units 102-1 and 102-2 in each system, and interleavers 206-1 and 206-2 in each system.
  • the outputs LRL E e, 1 and L E e, 2 of the demodulator 201 in each system are expressed by (Equation 1) And (Equation 2).
  • the obtained output LLRL E e, 1 of the demodulator 201 is output to the deinterleaver unit 202-1 and L E e, 2 is output to the deinterleaver unit 202-2.
  • the deinterleaver units 202-1 and 202-2 perform a process of rearranging the interleaving performed by the transmission device so that the input L E e, 1 and L E e, 2 are returned to the original order. Apply.
  • the input LLRL D a, 1 and L D a of the rearranged decoding unit 204 are output to the MUX unit 203.
  • the MUX unit 203 performs a process of rearranging the inter-system distribution process performed by the transmission apparatus so that the input L D a, 1 and L D a, 2 are returned to the original order. And it outputs the input LLRL D a decoding unit 204 is output after reordering the decoding unit 204 and the mutual information amount calculation unit 108.
  • the decoding unit 204 performs a decoding process on the input L D a using, for example, maximum a posteriori probability decoding, calculates a coded bit LLRL D p based on the posterior information, and outputs the output LLL D D of the decoding unit 204 e is calculated according to (Equation 16).
  • L D a is a coded bit LLR based on the prior information of the decoding unit 204.
  • the calculated output LLRL D p of the decoding unit 204 is output to a DEMUX (DeMultiplexer) unit 205.
  • the DEMUX unit 205 performs the same processing as the inter-system allocation performed by the transmission apparatus on the input L D p .
  • Output for output to the reception system 1 of the allocated L D e, 1 and receiving system 2 L D e, 2 respectively outputted to the interleaver unit 206-1 and 206-2.
  • Interleavers 206-1 and 206-2 perform rearrangement processing on the input L D e, 1 and L D e, 2 in the same manner as the interleaving performed in the transmission apparatus. First iteration process by outputting the demodulation unit after the rearrangement input LLRL E a, 1 and L E a, 2 to demodulation section 201 is completed.
  • the demodulation unit 201 outputs Y 1 and Y 2 output from the RF units 102-1 and 102-2 in each system and the interleaver unit 206- in each system. 1 and 206-2, from the inputs LLRLE E a, 1 and L E a, 2 of the demodulator 201 based on the prior information output from 206-2, the outputs LLRL E e, 1 and L E e, 1 of the demodulator 201 in each system 2 is calculated again according to (Equation 1) and (Equation 2).
  • the prior information about the coded bits is increased by using the outputs LLRL E e, 1 and L E e, 2 of the demodulation unit 201 in each system obtained from the decoding unit 204 (in other words, coding
  • the demodulation process is performed in a state where the ambiguity regarding the bit is reduced). Accordingly, the average mutual information I E obtained from the outputs LLRL E e, 1 and L E e, 2 of the demodulator 201 increases.
  • the decoding unit 203 After repeating the above series of processes a predetermined number of times, the decoding unit 203 performs a decoding process on L D a using, for example, maximum a posteriori probability decoding as in the first embodiment, and sets L D u to Calculate and output to the hard decision unit 107.
  • the hard decision unit 107 outputs a decoding result u obtained by a decision process such as a hard decision.
  • the mutual information amount calculation unit 108 calculates the average mutual information amount IE according to (Equation 14) in the same manner as the operation description of the first block diagram of FIG. Since the description of the operation of the second block diagram of FIG. 2 is based on turbo signal processing, the average mutual information IE may be calculated for each iteration, or the average mutual information I at any number of iterations of 1 or more. E may be calculated.
  • the margin calculation unit 108 calculates a transmission margin I M from the input average mutual information I E according to (Equation 15) as in the description of the operation of the first block diagram. For example, when the maximum number of iterations is two, the average mutual information and transmission margin before iteration are I E, 0 and I M, 0 , respectively, and the average mutual information and transmission margin are the first iteration. If I E, 1 and I M, 1 and the average mutual information amount and transmission margin for the second iteration are I E, 2 and I M, 2 , respectively, the relationship is as shown in FIG. Along with the iterative processing, the average mutual information amount increases, so the transmission margin also increases.
  • FIG. 3 is a third block diagram according to one embodiment of the present invention.
  • the third block diagram is a configuration including an erasure correction unit for an interfered signal in order to suppress deterioration of the bit error rate due to mixing of an interference signal from another system.
  • OFDM Orthogonal Frequency Division Multiplexing
  • the CVI (Carrier Variance Information) disclosed in Non-Patent Document 2 is used to detect the signal Y l of the l-th subcarrier mixed with the interference wave, and the erasure correction unit 302. If the interfered power of Y 1 is larger than the predetermined threshold value than the predetermined threshold value, the erasure correction process is performed.
  • the erasure correction processing indicates data erasure processing, and Y l is converted to 0 or a value close to 0.
  • the signal Y d after erasure correction is output to the demodulator 103.
  • the LLR value may be low due to interference, and the LLR value may be erroneously recognized as the reception level increases due to interference. This will adversely affect the decryption result. Therefore, the reception characteristics can be improved by reducing the likelihood of the subcarrier mixed with the interference wave by erasure correction.
  • the transmission margin I M calculated by Equation 15 also decreases.
  • the interference detection unit 301 and the erasure correction unit 302 are provided before the demodulation unit 103, but may be provided after the demodulation unit 103.
  • Example 4 is demonstrated using FIG.
  • the fourth embodiment includes the erasure processing correction unit described in the third embodiment, feeds back the transmission margin generated by the reception device to the transmission device, and the transmission device has a function of performing AMC based on the feedback information. It is a configuration.
  • Example 4 described below describes a wireless device having a frame configuration of a TDD (Time Division Duplex) system, but also in a wireless device having a frame configuration of an FDD (Frequency Division Duplex) system. Applicable.
  • FIG. 4 is a block diagram of a BS according to an embodiment of the present invention.
  • FIG. 5 is a block diagram of an MS according to an embodiment of the present invention.
  • the wireless system of the fourth embodiment includes a BS (Base Station) 400-1 and an MS (Mobile Station) 400-2, and performs wireless communication between the BS 400-1 and the MS 400-2.
  • one frame includes a DL (Down Link) subframe that transmits from the BS to the MS, and a UL (Up Link) subframe that transmits from the MS to the BS.
  • TTG Transmit Transition Gap
  • RTG Receiveive Transition Gap
  • the DL subframe includes a preamble, FCH (Frame Control Header), and DL data
  • the UL subframe includes CQICH (Channel Quality Information Channel) and UL data.
  • BS 400-1 includes BS transmission processing section 401-1 and BS reception processing section 402-1.
  • the subscripts t1 and r1 indicate the BS transmission processing unit 401-1 and the BS reception processing unit 402-1 respectively.
  • BS transmission processing section 401-1 comprises coding section 403-1, interleaver section 404-1, modulation section 405-1, frame configuration section 406-1, and adaptive modulation and coding control section 407, and coding section 403- 1, the input information bit b t1 is subjected to error correction coding processing to output a coded bit C t1 , and the interleaver 404-1 has a predetermined order with respect to the input C t1 .
  • Adaptive modulation and coding control unit 407 generates MCS information S t1 based on the transmission margin I M, r1 obtained from BS reception processing unit 402-1, an output to the encoding unit 403-1 and modulation unit 405-1 To do. Based on the MCS information S t1, the encoding unit 403-1 in the coding rate in the next frame, it sets the modulation method in the modulation unit 405-1.
  • BS reception processing section 402-1 includes frame extraction section 410-1, interference detection section 411-1, erasure processing section 412-1, demodulation section 413-1, deinterleaver section 414-1, and decoding section 415-1. , Including a hard decision unit 416-1 and a CQICH extraction unit 417, down-converts the signal received by the antenna 409-1 into a baseband signal by the RF unit 408-1, and inputs the Y input to the frame extraction unit 410-1 'establishes frame synchronization with respect to r1, the frame synchronization interference detector the received signal Y r1 after 411-1, and outputs the erasure correction unit 412-1 and the CQICH extractor 417.
  • the interference detection unit 411-1 detects the signal Y l, r1 of the l-th subcarrier mixed with the interference wave from the input Y r1 as in the third embodiment, and the erasure correction unit 412-1 If the interfered power of Y l, r1 is larger than the predetermined threshold value from the predetermined threshold value, erasure correction similar to that in the third embodiment is performed.
  • the signal Y d, r1 after erasure correction is output to the demodulator 413-1.
  • the demodulator 413-1 calculates the output LLRL E e, r1 of the demodulator 413-1 by demodulation processing in the same manner as in the first embodiment , and outputs it to the deinterleaver 414-1.
  • the deinterleaver unit 414-1 receives the input LLRL E a, r1 of the decoding unit 415-1 that has been subjected to the rearrangement process so that the bit rearrangement performed by the interleaver 404-2 in the MS transmission processing unit is restored.
  • the data is output to the decoding unit 415-1.
  • the decoding unit 415-1 performs the same decoding process on the input L D a, r1 as in the first embodiment, calculates the information bit LLLL D u, r1, and outputs it to the hard decision unit 413-1.
  • the hard decision unit 413-1 and outputs the decoded results u r1 obtained by the determination process of such a hard decision with respect to L D u, r1 entered.
  • the CQICH extraction unit 417 extracts CQICH included in a UL subframe to be described later, and outputs a transmission margin I M, r1 included in the CQICH to the adaptive modulation and coding control unit 407.
  • the MS 400-2 includes an MS transmission processing unit 401-2 and an MS reception processing unit 402-2.
  • the MS reception processing unit 402-2 includes a frame extraction unit 410-2, an interference detection unit 411-2, an erasure correction unit 412-2, a demodulation unit 413-2, a deinterleaver unit 414-2, a decoding unit 415-2, a hard unit A determination unit 416-2, a mutual information amount calculation unit 418, and a margin calculation unit 419 are provided, and a signal received by the antenna 408-2 is down-converted to a baseband signal by the RF unit 407-2, and a frame extraction unit 409-2 Then, frame synchronization is performed with respect to the input Y ′ r2 , and the received signal Y r2 after the frame synchronization is output to the interference detection unit 411-2 and the erasure correction unit 412-2.
  • the interference detection unit 411-2 detects the signal Y l, r2 of the l-th subcarrier mixed with the interference wave with respect to the input Y r2 as in the third embodiment, and the erasure correction unit 411-2 When the interference power of Y l, r2 is larger than the predetermined threshold, erasure correction is performed.
  • the signal Y d, r2 after erasure correction is output to the demodulator 413-2.
  • the demodulator 413-2 calculates the encoded bit LLRL E e, r2 of the output of the demodulator 413-2 and outputs it to the deinterleaver 414-2 by the same demodulation processing as in the first embodiment.
  • the deinterleaver unit 414-2 decodes the input LLRL D a, r2 of the decoding unit 415-2 subjected to the rearrangement process so that the bit rearrangement performed by the interleaver unit in the BS transmission processing unit is restored. It outputs to 415-2.
  • the decoding unit 415-2 performs the same decoding process on the input L D a, r2 as in the first embodiment, calculates the information bit LLRL D u, r2, and outputs it to the hard decision unit 413-2.
  • the hard decision unit 413-2 outputs a decoding result u r2 obtained by a decision process such as a hard decision for the input L D u, r2 .
  • the mutual information amount calculation unit 418 calculates the average mutual information amount I E, r2 for the input L D a, r2 as in the first embodiment, and outputs it to the margin calculation unit 419.
  • the margin calculation unit 419 calculates a transmission margin I M, r2 based on the mutual information amount for the input I E, r2 in the same manner as in the first embodiment, and generates a CQICH generation unit in the MS transmission processing unit 401-2. Output to 420.
  • the CQICH generation unit 420 combines the input I M, r2 with feedback information such as channel quality information, and outputs the feedback information f t2 to the frame configuration unit 406-2.
  • MS transmission processing section 401-2 includes coding section 403-2, interleaver section 404-2, modulation section 405-2, frame configuration section 406-2, and CQICH generation section 420.
  • coding section 403-2 input is performed.
  • the encoded information bit b t2 is subjected to error correction coding processing to output a coded bit C t2 , and the interleaver 404-2 receives C t2 in a predetermined order with respect to the inputted C t2.
  • Encoded bits C i, t2 are output, the modulation unit 405-1 performs modulation processing on the input C i, t2 and outputs a modulation signal X t2 , and a frame configuration unit 406-1 against X t2 entered in the X 't2 obtained by constituting the UL sub-frame is output to the RF unit 407-2 combines the like ranging or CQICH, a radio signal from the antenna 408-2 Send.
  • transmission margin based on the input LLRL D a, the average mutual information obtained from r2 I E, r2 of the decoding unit 415-2 the modulation method and encoding rate in AMC I M, r2 Therefore, even when the received signal quality due to the interference signal is deteriorated, an appropriate modulation scheme and coding rate can be set, and the transmission rate can be improved.
  • the configuration example in which only the BS 400-1 includes the AMC is described, but the MS 400-2 may include the AMC.
  • the CQICH extraction unit 417 and the adaptive modulation control unit 407 may be provided in either one of the BS transmission processing unit 401-1 and the BS reception processing unit 402-1.
  • the wireless system including the erasure correction processing described in the third embodiment is described as an example extended to two-way communication with a transmission device including an AMC.
  • the first embodiment and the second embodiment are also described. It is extensible.
  • the radio communication system can improve the transmission rate by selecting an appropriate modulation scheme and coding rate even in a high antenna correlation environment or an environment where a narrowband interference signal is mixed.

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  • Engineering & Computer Science (AREA)
  • Computer Networks & Wireless Communication (AREA)
  • Signal Processing (AREA)
  • Physics & Mathematics (AREA)
  • Probability & Statistics with Applications (AREA)
  • Theoretical Computer Science (AREA)
  • Error Detection And Correction (AREA)
  • Detection And Prevention Of Errors In Transmission (AREA)

Abstract

L'objectif de la présente invention est d'améliorer un débit de transmission en sélectionnant un schéma de modulation et un débit de code appropriés, même dans un environnement ayant une corrélation d'antenne élevée ou un environnement ayant une contamination par un signal d'interférence à bande passante étroite. Le dispositif de réception de la présente invention est un dispositif de réception dans lequel des bits codés sont générés en soumettant une entrée de bit d'information à un processus de codage de correction d'erreurs, et dans lequel un signal modulé comprenant les bits codés qui ont été modulés de façon numérique est reçu, caractérisé en ce que le dispositif de réception est pourvu : d'un moyen de démodulation qui calcule, à partir du signal reçu, un logarithme de rapport de vraisemblance pour les bits codés qui ont été soumis à un codage de correction d'erreurs; d'un moyen pour calculer une quantité moyenne d'informations mutuelles par rapport au logarithme de rapport de vraisemblance pour les bits codés; d'un moyen pour calculer une marge de transmission à partir de la quantité moyenne d'informations mutuelles et d'une quantité d'informations mutuelles d'entrée d'unité de démodulation ou d'une quantité d'informations mutuelles de sortie d'unité de démodulation satisfaisant à un taux d'erreur binaire requis; et d'un moyen de codage de correction d'erreurs qui réalise un codage de correction d'erreurs à partir du logarithme de rapport de vraisemblance pour les bits codés d'entrée.
PCT/JP2016/064157 2015-05-20 2016-05-12 Système de communication sans fil et dispositif de réception WO2016186000A1 (fr)

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