WO2015125637A1 - Circuit frontal haute fréquence - Google Patents

Circuit frontal haute fréquence Download PDF

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Publication number
WO2015125637A1
WO2015125637A1 PCT/JP2015/053465 JP2015053465W WO2015125637A1 WO 2015125637 A1 WO2015125637 A1 WO 2015125637A1 JP 2015053465 W JP2015053465 W JP 2015053465W WO 2015125637 A1 WO2015125637 A1 WO 2015125637A1
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WO
WIPO (PCT)
Prior art keywords
signal
balanced
filter
phase adjustment
circuit
Prior art date
Application number
PCT/JP2015/053465
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English (en)
Japanese (ja)
Inventor
上嶋孝紀
北嶋宏通
有海仁章
早藤久夫
辻口達也
Original Assignee
株式会社村田製作所
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
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Application filed by 株式会社村田製作所 filed Critical 株式会社村田製作所
Publication of WO2015125637A1 publication Critical patent/WO2015125637A1/fr

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    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03H—IMPEDANCE NETWORKS, e.g. RESONANT CIRCUITS; RESONATORS
    • H03H9/00—Networks comprising electromechanical or electro-acoustic devices; Electromechanical resonators
    • H03H9/70—Multiple-port networks for connecting several sources or loads, working on different frequencies or frequency bands, to a common load or source
    • H03H9/72—Networks using surface acoustic waves
    • H03H9/725—Duplexers
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
    • H04B1/06—Receivers
    • H04B1/10—Means associated with receiver for limiting or suppressing noise or interference
    • H04B1/109—Means associated with receiver for limiting or suppressing noise or interference by improving strong signal performance of the receiver when strong unwanted signals are present at the receiver input
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
    • H04B1/38—Transceivers, i.e. devices in which transmitter and receiver form a structural unit and in which at least one part is used for functions of transmitting and receiving
    • H04B1/40—Circuits
    • H04B1/50—Circuits using different frequencies for the two directions of communication
    • H04B1/52—Hybrid arrangements, i.e. arrangements for transition from single-path two-direction transmission to single-direction transmission on each of two paths or vice versa
    • H04B1/525—Hybrid arrangements, i.e. arrangements for transition from single-path two-direction transmission to single-direction transmission on each of two paths or vice versa with means for reducing leakage of transmitter signal into the receiver
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03H—IMPEDANCE NETWORKS, e.g. RESONANT CIRCUITS; RESONATORS
    • H03H7/00—Multiple-port networks comprising only passive electrical elements as network components
    • H03H7/18—Networks for phase shifting
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L5/00—Arrangements affording multiple use of the transmission path
    • H04L5/0001—Arrangements for dividing the transmission path
    • H04L5/0003—Two-dimensional division
    • H04L5/0005—Time-frequency
    • H04L5/0007—Time-frequency the frequencies being orthogonal, e.g. OFDM(A), DMT
    • H04L5/001—Time-frequency the frequencies being orthogonal, e.g. OFDM(A), DMT the frequencies being arranged in component carriers

Definitions

  • the present invention relates to a high-frequency front-end circuit that transmits and receives high-frequency signals.
  • one end of the transmission filter and one end of the reception filter are connected to form a common terminal, and the common terminal is connected to an antenna or a circuit on the antenna side.
  • the other end of the transmission filter is connected to the transmission circuit, and the other end of the reception filter is connected to the reception circuit.
  • the transmission filter side is changed from the transmission filter side to the reception filter side at the basic frequency of the transmission signal in order to prevent the transmission signal from wrapping around the reception filter side.
  • the impedance is set so that it is open when viewed.
  • reception sensitivity may be deteriorated due to noise received by the antenna or noise generated by the reception filter.
  • an object of the present invention is to provide a high-frequency front-end circuit that can suppress reception sensitivity deterioration.
  • the high-frequency front-end circuit of the present invention includes a branching circuit and a phase adjustment circuit.
  • the demultiplexing circuit includes a transmission filter in which a fundamental frequency band of a transmission signal is set in a pass band, and a reception filter in which a fundamental frequency band of a reception signal is set in a pass band.
  • the branching circuit one end of the transmission filter and one end of the reception filter are connected via a common connection point.
  • the phase adjustment circuit is connected to the other end of the reception filter.
  • the other end of the reception filter is a balanced output end having a first balanced terminal and a second balanced terminal.
  • the phase adjustment circuit has a phase difference of about ⁇ 90 between the first balanced signal output from the first balanced terminal and the second balanced signal output from the second balanced terminal at a specific frequency different from the fundamental frequency band of the received signal.
  • the phase is adjusted to be within °.
  • the phase adjustment circuit has a phase difference of about 180 ° between the first balanced signal output from the first balanced terminal and the second balanced signal output from the second balanced terminal in the fundamental frequency band of the received signal. It is preferable to do so.
  • the phase adjustment circuit is phase-adjusted so that the phase difference between the first balanced signal and the second balanced signal at a specific frequency is approximately 0 °.
  • the phase adjustment circuit can be a resonator connected to the first balanced terminal.
  • phase adjustment circuit can be realized with a simple circuit configuration.
  • the phase adjustment circuit may include first and second inductors and capacitors, and may have the following circuit configuration.
  • the first inductor is connected to the first balanced terminal.
  • the second inductor has an inductance different from that of the first inductor.
  • the second inductor is connected to the second balanced terminal.
  • the capacitor connects an end portion of the first inductor opposite to the first balanced terminal and an end portion of the second inductor opposite to the second balanced terminal.
  • phase adjustment circuit can be realized with a circuit configuration including only passive elements.
  • the phase adjustment circuit may be configured to include at least one mounted electronic component.
  • the configuration of the phase adjustment circuit can be easily changed, and the phase difference between the first balanced signal and the second balanced signal at a specific frequency can be easily set to a desired value.
  • At least one of the first inductor and the second inductor constituting the phase adjustment circuit is composed of a transmission line through which a received signal is transmitted.
  • the high-frequency front-end circuit can be realized with a simple configuration while setting the phase difference between the first balanced signal and the second balanced signal at a specific frequency to a desired value.
  • the high frequency front end circuit of the present invention may have the following configuration.
  • the high-frequency front-end circuit includes a transmission filter in which a fundamental frequency band of a transmission signal is set in a pass band, and a reception filter in which a fundamental frequency band of a reception signal is set in a pass band. And a demultiplexing circuit in which one end of the reception filter is connected via a common connection point.
  • the other end of the reception filter is a balanced output end having a first balanced terminal and a second balanced terminal.
  • the reception filter has a phase difference between the first balanced signal output from the first balanced terminal and the second balanced signal output from the second balanced terminal with respect to a specific frequency different from the fundamental frequency component of the received signal. The phase is adjusted to be within 90 °.
  • the reception filter realizes a filter function for a received signal and a phase adjustment function for a signal of a specific frequency.
  • a high-frequency front-end circuit can be realized without a separate phase adjustment circuit.
  • the high frequency front end circuit of the present invention may have the following configuration.
  • the reception filter includes a plurality of resonators, and a ground connected to a resonator on a path for outputting the first balanced signal and a resonator on a path for outputting the second balanced signal are different from each other or the ground is connected.
  • the length of the ground connection line connected to is different.
  • the high frequency front end circuit of the present invention preferably has the following configuration.
  • the received signal constitutes the first communication band.
  • the transmission signal constitutes a second communication band different from the first communication band.
  • the transmission signal and the reception signal are simultaneously communicated.
  • the specific frequency is a fundamental frequency or a harmonic frequency of the transmission signal.
  • the present invention it is possible to suppress propagation of a signal in a frequency band that is not desired to propagate other than the fundamental frequency of the reception signal to the subsequent stage of the reception filter, and it is possible to suppress deterioration in reception sensitivity.
  • FIG. 1 is a block diagram of a high-frequency front end circuit according to a first embodiment of the present invention.
  • FIG. 3 is a circuit diagram illustrating a specific configuration example of a phase adjustment circuit according to the first embodiment of the present invention. It is a figure which shows the phase characteristic of the resonator of the phase adjustment circuit which concerns on the 1st Embodiment of this invention. It is a typical waveform diagram which shows the phase difference of the 1st balanced signal and the 2nd balanced signal which are output from the phase adjustment circuit which concerns on the 1st Embodiment of this invention. It is a figure which shows the IIP2 characteristic with the case where it does not provide with the case where the phase adjustment circuit which concerns on the 1st Embodiment of this invention is provided.
  • FIG. 1 is a block diagram of a high-frequency front-end circuit according to the first embodiment of the present invention.
  • the high frequency front end circuit 10 includes a duplexer 20 and a phase adjustment circuit 30.
  • the duplexer 20 includes a Tx filter 21 corresponding to the “transmission filter” of the present invention and an Rx filter 22 corresponding to the “reception filter” of the present invention.
  • the one end of the Tx filter 21 and the one end of the Rx filter 22 are connected. This connection point is connected to an antenna (not shown) or a circuit on the antenna side.
  • This antenna is an antenna that transmits a transmission signal that has passed through the Tx filter 21 to the outside and receives a reception signal from the outside.
  • the Tx filter 21 is set so that the fundamental frequency of the transmission signal falls within the pass band.
  • the Tx filter 21 is set so as to obtain a predetermined attenuation with respect to the frequency of the received signal.
  • the other end of the Tx filter 21 is connected to the output end of the power amplifier PA of the transmission circuit 80.
  • a matching circuit that performs impedance matching at the frequency of the transmission signal may be provided between the power amplifier PA and the Tx filter 21.
  • the Rx filter 22 is set so that the fundamental frequency of the received signal falls within the pass band.
  • the Rx filter 22 is set so as to obtain a predetermined attenuation with respect to the fundamental frequency of the transmission signal.
  • the Rx filter 22 has an unbalance-balance conversion function.
  • One end of the Rx filter 22 is an unbalanced end including an unbalanced terminal, and the other end is a balanced end corresponding to each of the “first balanced terminal” and the “second balanced terminal” of the present invention.
  • the first input terminal P1P of the Rx filter 22 is connected to the first input terminal of the phase adjustment circuit 30, and is connected to the second input terminal P1N of the Rx filter 22.
  • the first output terminal P2P and the second output terminal P2N of the Rx filter 22 are connected to a balanced input terminal of a differential amplification type low noise amplifier LNA arranged in the reception circuit 90.
  • An impedance matching circuit may be provided between the phase adjustment circuit 30 and the low noise amplifier LNA.
  • the output terminal of the low noise amplifier LNA is connected to a reception demodulation circuit (not shown).
  • FIG. 2 is a circuit diagram showing a specific configuration example of the phase adjustment circuit according to the first embodiment of the present invention.
  • the phase adjustment circuit 30 includes a resonator 301.
  • the resonator 301 is connected between the first input terminal P1P and the first output terminal P2P.
  • the resonator 301 can be realized by an elastic wave resonator such as a SAW resonator or a BAW resonator.
  • FIG. 3 is a diagram showing the phase characteristics of the resonator of the phase adjustment circuit according to the first embodiment of the present invention.
  • FIG. 4 is a schematic waveform diagram showing the phase difference between the first balanced signal and the second balanced signal output from the phase adjustment circuit according to the first embodiment of the present invention.
  • Srxp is a fundamental frequency component of the received signal included in the first balanced signal
  • Srxn is a fundamental frequency component of the received signal included in the second balanced signal
  • Snp is a signal having a specific frequency included in the first balanced signal
  • Snn is a signal having a specific frequency included in the second balanced signal.
  • the phase of the resonator 301 changes greatly at the resonance point. Specifically, a phase shift of 80 ° or more can be generated. That is, the resonator 301 alone can function as a phase shift circuit that greatly shifts the phase.
  • the resonator 301 is set so that the frequency of the resonance point coincides with a specific frequency that is not desired to be amplified by the low noise amplifier LNA.
  • phase adjustment circuit 30 With such a configuration, the phase of the specific frequency signal included in the first balanced signal can be greatly shifted by the phase adjustment circuit 30.
  • phase difference between the characteristic frequency signal included in the first balanced signal output from the Rx filter 22 with a phase difference of about 180 ° and the specific frequency signal included in the second balanced signal is shown in FIG.
  • the phase difference of 90 ° as shown in FIG. 4 or the phase difference of 0 ° as shown in FIG. 4C, that is, the phase shift to the same phase, can be input to the low noise amplifier LNA.
  • the resonator 301 does not shift the phase in most frequency bands except the frequency at the resonance point. Therefore, by setting the fundamental frequency of the received signal in a frequency band in which the phase is not shifted, the phase adjustment circuit 30 can input the fundamental frequency component of the received signal to the low noise amplifier LNA with almost no phase shift. it can. That is, the phase adjustment circuit 30 includes the fundamental frequency component of the reception signal included in the first balanced signal and the fundamental frequency component of the reception signal included in the second balanced signal output from the Rx filter 22 with a phase difference of about 180 °. Can be inputted to the low-noise amplifier LNA while keeping the phase difference between the two and the phase difference at about 180 °.
  • the fundamental frequency component of the received signal can be efficiently amplified, and the amplification of the signal of the specific frequency can be kept low.
  • FIG. 5 is a diagram showing IIP2 characteristics when the phase adjustment circuit according to the first embodiment of the present invention is provided and when it is not provided.
  • the horizontal axis in FIG. 5 indicates the phase at the timing output from the Rx filter 22, and the vertical axis indicates the IIP2 value.
  • the IIP2 characteristic can be improved by providing the phase adjustment circuit 30 according to the present embodiment by comparing the case where the phase adjustment circuit 30 according to the present embodiment is not used.
  • the IIP2 value can be significantly improved by setting the phase difference between the first balanced signal and the second balanced signal to 0 ° (in phase). As a result, it is possible to largely suppress reception sensitivity deterioration.
  • FIG. 3 shows an example in which one resonator is provided, and the phase difference between the preferential signal of the specific frequency of the first balanced signal and the signal of the specific frequency of the second balanced signal is set to approximately 0 °. It's not easy. However, the phase difference can be made substantially 0 ° by adjusting the configuration including a plurality of resonators 301 and the length of the transmission line connected to the resonators 301.
  • FIG. 6 is a circuit diagram showing another aspect of the phase adjustment circuit of the high-frequency front-end circuit according to the first embodiment of the present invention.
  • the phase adjustment circuit 30A includes an inductor 311P corresponding to the “first inductor” of the present invention, an inductor 311N corresponding to the “second inductor” of the present invention, and a capacitor 312.
  • the inductor 311P is connected between the first input terminal P1P and the first output terminal P2P.
  • the inductor 311N is connected between the second input terminal P1N and the second output terminal P2N.
  • the capacitor 312 is connected between the end of the inductor 311P on the first output terminal P2P side and the end of the inductor 311N on the second output terminal P2N side.
  • the inductor 311P and the inductor 311N are set to different inductances. More specifically, the inductor 311P and the inductor 311N are set so that the phase of the transmitted high frequency signal is the same for the fundamental frequency component of the received signal, and the phase of the transmitted high frequency signal is different for the signal of the specific frequency. Yes. At this time, it is preferable to set the phase difference between the two high-frequency signals transmitted within a specific frequency signal within ⁇ 90 °.
  • phase adjustment circuit 30A is composed of only passive elements, the circuit can be easily constructed.
  • the inductors 311P and 311N and the capacitor 312 may be realized by an electrode pattern formed on a substrate, or may be realized by a mounted electronic component.
  • the phase adjustment circuit 30A can be realized with a simple configuration, and thus the high-frequency front-end circuit can be realized with a simple configuration.
  • the inductors 311P and 311N and the capacitor 312 are implemented by mounted electronic components, the inductance and capacitance can be changed by simply replacing the mounted electronic components, so that the inductance and capacitance can be easily adjusted. Therefore, the desired phase difference can be realized more accurately.
  • FIG. 7 is a block diagram of a high-frequency front-end circuit according to the second embodiment of the present invention.
  • the high-frequency front end circuit 10A of the present embodiment is a circuit in which the phase adjustment circuit is omitted from the high-frequency front end circuit 10 shown in the first embodiment, and the Rx filter has a phase adjustment function.
  • Other configurations of the high-frequency front-end circuit 10A are the same as those of the high-frequency front-end circuit 10 shown in the first embodiment. Therefore, only different parts will be specifically described.
  • the Rx filter 22A with phase adjustment function is set so that the fundamental frequency of the received signal falls within the pass band.
  • the Rx filter 22 is set so as to obtain a predetermined attenuation with respect to the fundamental frequency of the transmission signal.
  • the Rx filter 22 has an unbalance-balance conversion function.
  • FIG. 8 is a circuit diagram of an Rx filter with a phase adjustment function of a high-frequency front-end circuit according to the second embodiment of the present invention.
  • the Rx filter 22A with a phase adjustment function includes a plurality of resonators 221, 222, 223P, 223N, 224P, 224N, and 225. Similar to the first embodiment, these resonators can be realized by an elastic wave resonator such as a SAW resonator or a BAW resonator.
  • One end of the resonator 221 is connected to the Tx filter 21.
  • the other end of the resonator 221 is connected to the resonator 222.
  • the resonator 222 is coupled to the resonators 223P and 223N, and a desired position is connected to the ground.
  • the resonator 223P is connected to the resonator 224P, and a desired position is connected to the ground via the ground connection line 226P.
  • the resonator 223N is connected to the resonator 224N, and a desired position is connected to the ground via the ground connection line 226N.
  • the resonator 224P and the resonator 224N are connected to a resonator 225 having a split type IDT.
  • the resonator 225 is connected to the first balanced signal output terminal Pp and the second balanced signal output terminal Pn.
  • the fundamental frequency components of the reception signals output from the first balanced signal output terminal Pp and the second balanced signal output terminal Pn are output with a phase difference of about 180 °. That is, the fundamental frequency component of the received signal included in the first balanced signal and the fundamental frequency component of the received signal included in the second balanced signal are output with a phase difference of approximately 180 °.
  • the grounds to which the resonator 223P and the resonator 223N are connected are different.
  • the phase difference of the signal of the specific frequency different from the fundamental frequency component of the received signal is set within ⁇ 90 °.
  • the length of the ground connection line 226P that connects the resonator 223P to the ground is different from the length of the ground connection line 226N that connects the resonator 223N to the ground.
  • the phase difference of the signal of the specific frequency different from the fundamental frequency component of the received signal is set within ⁇ 90 °.
  • the phase difference between signals of specific frequencies of the first balanced signal and the second balanced signal input to the low-noise amplifier LNA can be ⁇ 90 even without a phase adjustment circuit separately from the Rx filter. Can be within °. Thereby, reception sensitivity degradation can be suppressed.
  • FIG. 9 is a block diagram of a high-frequency front-end circuit according to the third embodiment of the present invention.
  • the second harmonic frequency of the second transmission signal and the fundamental frequency of the first reception signal are close to each other, and the transmission of the second transmission signal and the reception of the first reception signal are performed simultaneously. The case where carrier aggregation is performed is shown.
  • the high-frequency front-end circuit of this embodiment has a triplexer configuration instead of the duplexer configuration shown in the first embodiment.
  • the high-frequency front end circuit 10B includes a triplexer 20B and a phase adjustment circuit 30B.
  • the triplexer 20B includes a Tx1 filter 211 corresponding to the transmission filter of the “first communication band” of the present invention, a Tx2 filter 212 corresponding to the transmission filter of the “second communication band” of the present invention, and the “ An Rx1 filter 220 corresponding to the reception filter of the “first communication band” is provided.
  • the one end of the Tx1 filter 211, the one end of the Tx2 filter 212, and the one end of the Rx1 filter 220 are connected.
  • This connection point is connected to an antenna or a circuit on the antenna side (not shown).
  • This antenna is an antenna that transmits a transmission signal that has passed through the Tx1 filter 211 or the Tx2 filter 212 to the outside and receives a reception signal from the outside.
  • the Tx1 filter 211 is set so that the fundamental frequency of the transmission signal of the first communication band falls within the pass band.
  • the Tx2 filter 212 is set so that the fundamental frequency of the transmission signal of the second communication band falls within the pass band.
  • the other end of the Tx1 filter 211 is connected to the power amplifier PA1.
  • the other end of the Tx2 filter 212 is connected to the power amplifier PA2.
  • a matching circuit that performs impedance matching at the fundamental frequency of the transmission signal of each communication band may be provided between the Tx1 filter 211 and the power amplifier PA1 or between the Tx2 filter 212 and the power amplifier PA2.
  • the Rx1 filter 220 is set so that the fundamental frequency of the received signal of the first communication band falls within the pass band.
  • the Rx1 filter 220 is set so as to obtain a predetermined attenuation for the fundamental frequency of the transmission signal of the first communication band and the transmission signal of the second communication band.
  • the Rx1 filter 220 has an unbalance-balance conversion function.
  • the other end of the Rx1 filter 220 is connected to the low noise amplifier LNA via the phase adjustment circuit 30B.
  • the phase adjustment circuit 30B has the same circuit configuration as that of the phase adjustment circuit 30 shown in the first embodiment. At this time, the phase adjustment circuit 30B sets the specific frequency for changing the phase difference to the second harmonic frequency of the transmission signal of the second communication band.
  • the second harmonic frequency signal of the transmission signal of the second communication band included in the first balanced signal input to the low noise amplifier LNA and the transmission signal of the second communication band included in the second balanced signal can be within ⁇ 90 °.
  • the amplification factor can be kept low. Therefore, even if carrier aggregation is performed, it is possible to suppress the occurrence of reception sensitivity deterioration with respect to the reception signal of the first communication band.
  • the basic frequency of the reception signal of the first communication band and the second harmonic frequency of the transmission signal of the second communication band are close to each other.
  • the reception signal of the first communication band is shown.
  • the high-frequency signal for example, the fundamental frequency component of the second communication band or the harmonic noise generated by the Rx1 filter
  • the above-described configuration Can be applied to obtain the same effect.
  • the phase difference between the specific frequency signal included in the first balanced signal and the specific frequency signal included in the second balanced signal is within ⁇ 90 °, but the phase difference is 180 °. Otherwise, at least an effect of suppressing deterioration of reception sensitivity can be obtained.
  • the power amplifier PA and the low noise amplifier LNA are configured separately from the high frequency front end circuit. However, at least one of them may be configured as one high frequency front end circuit.
  • the connection configuration can be fixed between the phase adjustment circuit 30 and the low noise amplifier LNA, so that the operational effects of the present invention can be more effectively exhibited.

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  • Engineering & Computer Science (AREA)
  • Computer Networks & Wireless Communication (AREA)
  • Signal Processing (AREA)
  • Physics & Mathematics (AREA)
  • Acoustics & Sound (AREA)
  • Transceivers (AREA)

Abstract

La présente invention concerne un circuit frontal haute fréquence (10) qui comprend un duplexeur (20) et un circuit de réglage de phase (30). Une ligne équilibrée relie un filtre de réception (22) du duplexeur (20) à un amplificateur à faible bruit (LNA). Le circuit de réglage de phase (30) est connecté entre le filtre de réception (22) et l'amplificateur à faible bruit (LNA). Le circuit de réglage de phase effectue un réglage de phase de sorte que la différence de phase entre des premier et second signaux équilibrés délivrés en sortie du filtre de réception (22) soit dans une plage entre environ moins 90 degrés et environ plus 90 degrés pour une fréquence particulière différente de la bande de fréquences fondamentales d'un signal reçu. A ce moment, le circuit de réglage de phase (30) a réglé la phase de sorte que la différence de phase entre un premier signal équilibré délivré en sortie d'une première borne équilibrée du filtre de réception (22) et un second signal équilibré délivré en sortie d'une seconde borne équilibrée du filtre de réception (22) pour la bande de fréquences fondamentales du signal reçu soit d'environ 180 degrés.
PCT/JP2015/053465 2014-02-19 2015-02-09 Circuit frontal haute fréquence WO2015125637A1 (fr)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
JP2014-029840 2014-02-19
JP2014029840 2014-02-19

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WO2015125637A1 true WO2015125637A1 (fr) 2015-08-27

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PCT/JP2015/053465 WO2015125637A1 (fr) 2014-02-19 2015-02-09 Circuit frontal haute fréquence

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Citations (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JP2004215244A (ja) * 2002-12-18 2004-07-29 Matsushita Electric Ind Co Ltd 無線通信装置、無線通信方法、アンテナ装置、第１のデュプレクサ

Patent Citations (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JP2004215244A (ja) * 2002-12-18 2004-07-29 Matsushita Electric Ind Co Ltd 無線通信装置、無線通信方法、アンテナ装置、第１のデュプレクサ

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