WO2015033564A1 - 特異点標定装置 - Google Patents
特異点標定装置 Download PDFInfo
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- WO2015033564A1 WO2015033564A1 PCT/JP2014/004538 JP2014004538W WO2015033564A1 WO 2015033564 A1 WO2015033564 A1 WO 2015033564A1 JP 2014004538 W JP2014004538 W JP 2014004538W WO 2015033564 A1 WO2015033564 A1 WO 2015033564A1
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- fmcw
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- G—PHYSICS
- G01—MEASURING; TESTING
- G01R—MEASURING ELECTRIC VARIABLES; MEASURING MAGNETIC VARIABLES
- G01R31/00—Arrangements for testing electric properties; Arrangements for locating electric faults; Arrangements for electrical testing characterised by what is being tested not provided for elsewhere
- G01R31/08—Locating faults in cables, transmission lines, or networks
- G01R31/11—Locating faults in cables, transmission lines, or networks using pulse reflection methods
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- G—PHYSICS
- G01—MEASURING; TESTING
- G01R—MEASURING ELECTRIC VARIABLES; MEASURING MAGNETIC VARIABLES
- G01R31/00—Arrangements for testing electric properties; Arrangements for locating electric faults; Arrangements for electrical testing characterised by what is being tested not provided for elsewhere
- G01R31/08—Locating faults in cables, transmission lines, or networks
- G01R31/081—Locating faults in cables, transmission lines, or networks according to type of conductors
- G01R31/085—Locating faults in cables, transmission lines, or networks according to type of conductors in power transmission or distribution lines, e.g. overhead
Definitions
- the present invention relates to a singularity locating device, and more specifically, the position of a singularity is determined by comparing a transmission wave injected into a metal cable such as a power transmission line used for transmitting power and a reflected wave from the singularity.
- the present invention relates to a singularity locating apparatus using a specifying method.
- Non-Patent Document 1 a fault radar that is an example of a singular point in a transmission line due to disconnection, lightning strike, etc. and a device for confirming the soundness of a transmission line have been put to practical use by a pulse radar type fault locator called C-type.
- C-type a pulse radar type fault locator
- the C-type failure point locating device activates a failure point locating device installed at one end of the transmission line monitoring section in response to the information of the failure detection relay, and transmits a single AC pulse to the transmission line.
- the pulse transmission requires a charging time of the pulse transmission device of the failure point locating device, and therefore cannot be continuously performed many times.
- This C-type failure point locating device observes the time from when a pulse is transmitted until it receives a reflected pulse reflected at the failure point, and measures the distance to the failure point based on this time (for example, non-pointing) Patent Document 1).
- Non-Patent Document 1 when a transmission wave having a center frequency of 400 kHz is used, a transmission wave and a reflected wave cannot be distinguished at a near end of about 2 km or less, which is a section corresponding to a time of about 13 ⁇ s. For this reason, there is a problem that it cannot be determined (for example, Non-Patent Document 1).
- an object of the present invention is to provide a singular point locating apparatus that can determine singular points such as a failure point even in a near end section.
- the singularity locating device of the present invention is a singularity locating device for locating a singularity by comparing a transmission wave and a reflected wave of a transmission wave reflected at a singularity where the impedance changes.
- a frequency-modulated continuous wave (FMCW) whose frequency is modulated is applied, and a singular point is determined based on a frequency difference between a transmitted wave and a reflected wave.
- FMCW frequency-modulated continuous wave
- FIG. 1 is a diagram showing a conceptual block of a failure point locating device in one embodiment of the present invention.
- FIG. 2 is a diagram for explaining the operation principle of the failure point locating apparatus according to the embodiment of the present invention.
- FIG. 3A is a diagram for explaining the operation principle of the method for deriving the position of the failure point in one embodiment of the present invention.
- FIG. 3B is a diagram for explaining the operation principle of the method for deriving the position of the failure point in one embodiment of the present invention.
- FIG. 3C is a diagram for explaining the operation principle of the method for deriving the position of the failure point in one embodiment of the present invention.
- FIG. 3D is a diagram for explaining the operation principle of the method for deriving the position of the failure point in one embodiment of the present invention.
- FIG. 4 is a diagram for explaining a method for deriving the position of the failure point in one embodiment of the present invention.
- the C type failure point locating device has a high transmission pulse voltage of 2 to 3 kV and requires a charging time for the capacitor, so it cannot transmit pulses continuously in a short time. Difficult (constraint of orientation processing time from pulse radar system).
- the C-type failure point locating device has a high transmission pulse voltage of 2 to 3 kV, and it is difficult to downsize it because it is difficult to make semiconductors because of the components used in the impulse generator and the electrical / insulation design (transmission pulse) (Restriction on downsizing of fault location device by voltage).
- Non-Patent Document 1 reports that the distance that can be determined may be about 40 km (constraint of limitation in a transmission line with a large transmission loss).
- ⁇ C-type fault location device cannot monitor the condition of the transmission line. Moreover, although there exists a device which detects the abnormality which generate
- FIG. 1 is a diagram illustrating a failure point locating apparatus according to Embodiment 1 of the present invention.
- the fault location apparatus 1 of this embodiment includes a converter 3, a video high-output amplifier 5, a carrier canceller 7, a differential amplifier 9, a mixer (Mixer) 11, and a low-frequency band pass discriminator (low-pass filter) 13. I have.
- the converter 3 includes a digital-analog converter (DAC) 15 that converts a digital signal into an analog signal, and an analog-digital converter (ADC) 17 that converts the analog signal into a digital signal.
- DAC digital-analog converter
- ADC analog-digital converter
- the circuit board 19 on which the computer is mounted is controlled.
- the DAC 15 included in the converter 3 is connected to the video high-output amplifier 5, converts a digital signal transmitted from the control embedded microcomputer board 19 into an analog signal, and transmits the converted analog signal to the video high-output amplifier 5. .
- the video high-output amplifier 5 is connected to the carrier canceller 7, the + input terminal of the differential amplifier 9, and the mixer 11, and generates a frequency modulation continuous wave (FMCW) from the analog signal received from the DAC 15 of the converter 3. Output as a transmission wave.
- FMCW frequency modulation continuous wave
- the carrier canceller 7 is connected to the negative input terminal of the differential amplifier 9, and the output terminal of the differential amplifier 9 is connected to the mixer 11.
- a carrier canceller 7 and a differential amplifier 9 form a canceller circuit.
- the mixer 11 is an analog multiplier, and receives a signal having two different frequencies, for example, f 1 and f 2 , and outputs a signal having a frequency f 1 ⁇ f 2 of the sum and difference according to the heterodyne principle. It is.
- the principle of heterodyne means that when two waves having slightly different frequencies are superimposed, a beat wave (beat) equal to the difference between the frequencies can be observed.
- the mixer 11 is connected to the low-pass filter 13 and multiplies the transmission FM signal received from the video high output amplifier 5 by the reception FM signal received from the differential amplifier 9 to generate a beat wave signal. Is sent to the low-pass filter 13.
- the low-pass filter 13 is connected to the ADC 17 included in the converter 3, and transmits a beat wave signal from which a high-frequency component has been removed from the beat wave signal received from the mixer 11 to the ADC 17.
- the ADC 17 converts the beat wave signal received from the low-pass filter 13 into a digital signal, and transmits the converted digital signal to the control embedded microcomputer board 19.
- a control phase switching relay 21 and a failure detection relay 23 are connected to the embedded microcomputer board 19 for control.
- the standard phase switching relay 21 is connected to, for example, a three-phase AC overhead power transmission line 29 used for transmitting electric power via a coupling filter (CF) 25 and a capacity transformer (PD) 27. Further, the orientation phase switching relay 21 is connected to the video high output amplifier 5 and the differential amplifier 9 via a delay element (DL) 35 and a balancing transformer 37. The orientation phase switching relay 21 receives the orientation phase switching control signal from the control built-in microcomputer board 19 and the transmission FM signal as a transmission wave from the video high output amplifier 5. Further, the orientation phase switching relay 21 transmits a reception FM signal which is a reception wave to the differential amplifier 9.
- CF coupling filter
- PD capacity transformer
- the capacity transformer (PD) 27 is a power device / electronic component of an existing facility of an electric station 31 that converts the voltage level of AC power using electromagnetic induction, and divides a high-voltage primary voltage. Is converted up to a measurable secondary voltage.
- the delay element (DL) 35 can be used to facilitate detection of a beat wave from a transmission wave and a reception wave when the distance between the orientation phase switching relay 21 and the failure point location device 1 is short.
- the overhead power transmission line 29 is connected to the bus B of the electric station 31, and a blocking coil (BC) 33 is provided on each overhead power transmission line 29.
- the capacitance transformer (PD) 27 can use a coupling capacitor (CC), and the overhead power transmission line 29 may be a direct current. In the case of direct current, the overhead power transmission line 29 is composed of a total of four main lines and two return lines.
- the failure point locating device 1 can also include a semiconductor storage device that stores FMCW in advance.
- the balancing transformer 37 is a transformer (transformer) on the failure point locating device 1 side, and enables measurement even with a cable having an impedance that is not balanced. Thereby, a failure point can be detected even in a combination of arbitrary transmission lines among a plurality of transmission lines.
- FIG. 2 is a diagram for explaining the operation principle of the failure point locating apparatus 1 of the present embodiment in FIG. The operation of detecting a beat wave signal in the fault location apparatus 1 will be described with reference to FIG.
- the video high-output amplifier 5 generates a frequency-modulated continuous wave (FMCW) from the analog signal received from the DAC 15 of the converter 3 and outputs the FMCW to the overhead power transmission line 29 as a transmission wave (thick line 201).
- FMCW flows to the overhead power transmission line 29 via the CF 25.
- the FMCW that is the transmitted wave that has flowed through the overhead power transmission line 29 becomes a reflected wave at a place where the impedance of the overhead power transmission line 29 changes (failure point).
- the reception wave which is a reflected wave, flows back from the path through which the transmission wave flows from the overhead power transmission line 29 to the canceller circuit via the CF 25 (thick line 202). At this time, the received wave has a smaller amplitude and a delayed cycle than the transmitted wave.
- the FMCW generated by the video high output amplifier 5 is also output as a transmission wave to the differential amplifier 9 of the canceller circuit (broken line 203). Therefore, the FMCW generated by the video high output amplifier 5 is also output to the carrier canceller 7 of the canceller circuit 204, the transmitted wave is canceled by the canceller circuit 204, and only the received wave is output from the differential amplifier 9.
- the canceller circuit 204 of the present embodiment conventionally uses a hybrid circuit or a circulator circuit.
- reception wave signal output from the differential amplifier 9 and the local signal (transmission FM signal) having the same waveform as the transmission wave directly received from the video high output amplifier 5 are input to the mixer 11 (line segment 205).
- Mixer 11 generates beat waves by superimposing sine waves of transmission waves and reception waves. In order to generate a beat signal from which the failure point can be detected from the generated beat wave, the beat wave is detected.
- the detection method at this time employs a method called product detection as the most efficient method.
- FIGS. 3A to 3D are diagrams for explaining a failure point detection method by the failure point locating apparatus 1 of the present embodiment.
- a failure point detection method using FMCW in this embodiment will be described with reference to FIGS. 3A to 3D.
- FIG. 3A is a schematic waveform of a transmission wave 301 transmitted from the video high-output amplifier 5 to the overhead power transmission line 29 and a reception wave 302 that the transmission wave 301 reflects at the failure point of the overhead power transmission line 29 and is received by the differential amplifier 9. Is shown.
- the vertical axis represents the wave amplitude and the horizontal axis represents time.
- the reception wave 302 is delayed by the arrival time of the radio wave on the overhead power transmission line 29 as compared with the transmission wave 301, and the frequency is shifted by the delayed arrival time.
- FIG. 3B shows a schematic waveform obtained by synthesizing the transmission wave 301 and the reception wave 302 with the mixer 11.
- the vertical axis represents the wave amplitude and the horizontal axis represents time, but the time axis is longer than that in FIG. 3A. Since waves of two different frequencies are synthesized, the synthesized wave is a beat wave (beat) 303.
- FIG. 3C shows an envelope 304 connecting the peaks of the amplitude (beat amplitude) of the beat wave 303 at each time with a line.
- the vertical axis represents the wave amplitude and the horizontal axis represents time.
- FIG. 3D shows a position (peak point 305) at which the frequency component is changed by performing frequency component analysis (FFT) by Fourier transform on the beat wave 303, reflected at the failure point.
- FFT frequency component analysis
- a transmission wave 301 that is FMCW is transmitted from the video high-output amplifier 5 to the overhead power transmission line 29.
- the transmitted reflected wave (echo) of the FMCW is received by the differential amplifier 9 (FIG. 3A).
- the transmission wave 301 and the reception wave 302 are combined by the mixer 11 to generate a beat wave 303 (FIG. 3B).
- An envelope 304 representing the amplitude of the beat wave 303 is extracted by the low-pass filter 13 (FIG. 3C).
- the extracted envelope 304 is subjected to frequency component analysis (FFT) by the control embedded microcomputer board 19 (FIG. 3D).
- FFT frequency component analysis
- a point where the frequency component reflected at the failure point is strongly changed due to the change in impedance is detected (FIG. 3D).
- the position of the failure point is derived from the frequency at the point where the frequency component changes strongly. A method for deriving the position of the failure point will be described below.
- FIG. 4 is a diagram for explaining a method for deriving the position of the failure point using the FMCW method of the present embodiment.
- the vertical axis represents the wave frequency f
- the horizontal axis represents time t.
- the sweep frequency (the frequency of the transmission wave 301 that changes at a constant cycle) is ⁇ F
- the sweep time is T
- the sweep rate is k
- the beat wave frequency (the difference between the frequencies of the transmission wave 301 and the reception wave 302).
- Is fb the delay time of the reflected wave is ⁇ t
- the propagation speed is c
- the distance to the reflection point (failure point) is X.
- the intensity of a beat wave (beat) between a transmission wave composed of a frequency-modulated continuous wave (FMCW) and its reflected wave corresponds to a change in surge impedance of the transmission line.
- FMCW frequency-modulated continuous wave
- the peak point of the waveform representing the surge impedance change point can be derived as the failure point.
- FMCW has been used for transmission to the air such as weather radar.
- FMCW can only be used in a high frequency band such as a gigahertz band, and has been said to be unable to be used for an individual due to a large attenuation.
- FMCW was applied to the transmission wave actually injected into the overhead power transmission line, it was found that the failure point could be determined.
- the minimum beat frequency fbmin (fbmin ⁇ c) / (2 ⁇ k) (4)
- the minimum beat frequency fbmin 1 / ⁇ T ⁇ (2 ⁇ L / c) ⁇ (5)
- the round trip time (2 ⁇ L / c) corresponds to the delay time ⁇ t of the reflected wave.
- the shortest distance that can be determined is 545 m from Equation (7).
- the following effects can be obtained by applying FMCW to the fault location device 1 and sweeping (sweeping) the frequency within the usable frequency band. That is, the near-end location impossible section from the failure point location device 1 can be reduced. In addition, the distance resolution is improved and the detection sensitivity is improved, so that it is possible to perform orientation on a transmission line with a large transmission loss. Moreover, since the impedance change point can be detected, the line state can be monitored.
- the FMCW according to the present embodiment can be standardized with a low transmission wave voltage, so that no capacitor charging is required.
- the entire device configuration circuit can be made semiconductor, so that the failure point locating device can be miniaturized.
- the entire device configuration circuit a semiconductor, it is possible to shorten the waveform generation interval and to make the waveform processing unit multi-functional, thereby improving the positioning accuracy and reliability.
- the failure point locating apparatus 1 to which the FMCW according to the present embodiment is applied can be used, for example, for locating a failure point in an aerial part of a DC transmission line.
- the failure point locating device 1 of the present embodiment is not limited to the overhead power transmission line, but can also be used for locating failure points of metal cables such as electric wires and coaxial cables.
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Abstract
Description
図1は、本発明の実施形態1の故障点標定装置を示す図である。本実施形態の故障点標定装置1は、変換器3、ビデオ高出力アンプ5、キャリアキャンセラー7、差動増幅器9、混合器(Mixer)11、および低周波帯通過弁別器(ローパスフィルター)13を備えている。
ΔF/T =fb/Δt ・・・(1)
式(1)を変形して、
Δt = (T・fb)/ΔF ・・・(1)´
計測点から故障点までの往復距離2Xは、
2X=c・Δt ・・・(2)
となるため、式(2)に式(1)´を代入すると、
2X=c・(T・fb)/ΔF ・・・(2)´
式(2)´を変形して、
X={(T・c)/(ΔF・2)}・fb ・・・(3)
ここで、ΔF/Tはスイープレートkとなるため、kを式(3)に代入すると、
X={c/(2k)}・fb ・・・(3)´
したがって、スイープレートk(=ΔF/T)と伝搬速度cは既知なのでビート波の周波数fbを求めれば、故障点までの距離Xが式(3)´より求められる。
Lmin=(fbmin・c)/(2・k) ・・・(4)
線路長をL、スイープ時間をTとすると、最少ビート周波数fbminは、
fbmin=1/{T-(2・L/c) } ・・・(5)
なお、往復時間(2・L/c)は、反射波の遅れ時間Δtに対応する。
k=ΔF/T=(Fmax-Fmin)/T ・・・(6)
となる。
Lmin=(c・T)/[2・{T-(2・L/c) }・(Fmax-Fmin)] ・・・(7)
となる。
3 変換器
5 ビデオ高出力アンプ
7 キャリアキャンセラー
9 差動増幅器
11 混合器(Mixer)
13 ローパスフィルター
15 デジタルアナログ変換器(DAC)
17 アナログデジタル変換器(ADC)
19 制御用組込マイコンボード
21 標定相切換リレー
23 故障検出リレー
25 結合フィルタ(CF)
27 容量変成器(PD)
29 架空送電線
31 電気所
33 ブロッキングコイル(BC)
35 遅延素子(DL)
37 平衡化変成器
201、202、205 太線
203 破線
204 キャンセラー回路
301 送信波
302 受信波
303 ビート波
304 包絡線
305 ピーク点
Claims (7)
- 送信波とインピーダンスが変化する特異点で反射した前記送信波の反射波との比較により特異点を標定する特異点標定装置であって、
前記送信波は、連続して周波数が変調する周波数変調連続波(FMCW)を適用し、前記送信波と前記反射波との周波数の差に基づいて前記特異点を標定することを特徴とする特異点標定装置。 - 送信波とインピーダンスが変化する特異点で反射した前記送信波の反射波との比較により特異点を標定する特異点標定装置であって、
前記送信波に適用する、連続して周波数が変調する周波数変調連続波(FMCW)を生成するFMCW生成手段と、
前記反射波を受信する受信回路に回り込む前記FMCWの送信波を打ち消す半導体回路と、
前記FMCWの送信波および前記反射波の周波数の差からビート波を生成する半導体乗算手段と、
前記ビート波の低周波成分を取り出す低周波帯通過弁別器と
を備えることを特徴とする特異点標定装置。 - 前記特異点標定装置は、複数のメタルケーブルと接続する平衡化変成器を備えることを特徴とする請求項1または2に記載の特異点標定装置。
- 前記FMCWを予め記憶させる半導体記憶手段と、
デジタル信号をアナログ信号に変換するデジタルアナログ変換手段と、
半導体論理回路で前記デジタルアナログ変換手段を制御する制御手段と
をさらに備え、
前記制御手段は、前記デジタルアナログ変換手段からアナログ波形の信号を出力させ、
前記FMCW生成手段は、前記アナログ波形の信号を入力し、前記FMCWの信号を連続的に出力する広帯域電子増幅器であることを特徴とする請求項1ないし3のいずれか1項に記載の特異点標定装置。 - 前記送信波とインピーダンスが変化する特異点で反射した前記送信波の反射波との比較により特異点を標定する特異点標定装置は、1つのメタルケーブルの入出力点に入力した送信波と、前記1つのメタルケーブルを伝播しインピーダンスが変化する特異点で反射し前記1つのメタルケーブルを逆伝播して前記入出力点から出力した前記送信波の反射波との比較により前記1つのメタルケーブルの特異点を標定する特異点標定装置を含むことを特徴とする請求項1ないし4のいずれか1項に記載の特異点標定装置。
- 前記メタルケーブルは、送電線であることを特徴とする請求項5に記載の特異点標定装置。
- 前記メタルケーブルは、架空送電線であることを特徴とする請求項5に記載の特異点標定装置。
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US14/915,976 US20160209458A1 (en) | 2013-09-04 | 2014-09-03 | Singularity locator |
EP14841812.2A EP3029475B1 (en) | 2013-09-04 | 2014-09-03 | Singularity location device |
US15/368,916 US20170082676A1 (en) | 2013-09-04 | 2016-12-05 | Singularity locator |
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KR101905434B1 (ko) * | 2016-11-15 | 2018-10-10 | 한국전자통신연구원 | 수동상호변조왜곡 신호 측정 장치 및 방법 |
RU2653583C1 (ru) * | 2017-04-13 | 2018-05-11 | Федеральное государственное бюджетное образовательное учреждение высшего образования "Кубанский государственный технологический университет" (ФГБОУ ВО "КубГТУ") | Способ определения места повреждения кабельной линии |
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DE10331744A1 (de) * | 2003-07-11 | 2005-02-10 | IAD Gesellschaft für Informatik, Automatisierung und Datenverarbeitung mbH | Induktive Ankoppelschaltung und Verfahren zur Nachrichtenübertragung in elektrischen Energieverteilnetzen |
US7061251B2 (en) * | 2004-01-15 | 2006-06-13 | Bae Systems Information And Electronic Systems Integration Inc. | Method and apparatus for transmission line and waveguide testing |
WO2005111635A1 (ja) * | 2004-05-14 | 2005-11-24 | Matsushita Electric Industrial Co., Ltd. | 電気回路パラメータの測定方法および装置 |
US8294469B2 (en) * | 2008-10-06 | 2012-10-23 | Anritsu Company | Passive intermodulation (PIM) distance to fault analyzer with selectable harmonic level |
US8415962B2 (en) * | 2010-11-26 | 2013-04-09 | Xuekang Shan | Transmission line based electric fence with intrusion location ability |
US20130104661A1 (en) * | 2011-10-31 | 2013-05-02 | Raytheon Company | Method and apparatus for range resolved laser doppler vibrometry |
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2013
- 2013-09-04 JP JP2013183212A patent/JP5749306B2/ja active Active
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2014
- 2014-09-03 WO PCT/JP2014/004538 patent/WO2015033564A1/ja active Application Filing
- 2014-09-03 EP EP14841812.2A patent/EP3029475B1/en not_active Not-in-force
- 2014-09-03 US US14/915,976 patent/US20160209458A1/en not_active Abandoned
- 2014-09-04 TW TW103130556A patent/TWI619950B/zh not_active IP Right Cessation
-
2016
- 2016-12-05 US US15/368,916 patent/US20170082676A1/en not_active Abandoned
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Also Published As
Publication number | Publication date |
---|---|
TWI619950B (zh) | 2018-04-01 |
EP3029475A4 (en) | 2017-06-14 |
JP2015049223A (ja) | 2015-03-16 |
EP3029475B1 (en) | 2018-09-19 |
EP3029475A1 (en) | 2016-06-08 |
JP5749306B2 (ja) | 2015-07-15 |
US20160209458A1 (en) | 2016-07-21 |
TW201525478A (zh) | 2015-07-01 |
US20170082676A1 (en) | 2017-03-23 |
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