WO2015025860A1 - Convertisseur multiniveau de type tension - Google Patents

Convertisseur multiniveau de type tension Download PDF

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Publication number
WO2015025860A1
WO2015025860A1 PCT/JP2014/071699 JP2014071699W WO2015025860A1 WO 2015025860 A1 WO2015025860 A1 WO 2015025860A1 JP 2014071699 W JP2014071699 W JP 2014071699W WO 2015025860 A1 WO2015025860 A1 WO 2015025860A1
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Prior art keywords
voltage
short circuit
capacitor
change rate
phase
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PCT/JP2014/071699
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English (en)
Japanese (ja)
Inventor
猛 近藤
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株式会社明電舎
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Publication of WO2015025860A1 publication Critical patent/WO2015025860A1/fr

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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/483—Converters with outputs that each can have more than two voltages levels
    • H02M7/487—Neutral point clamped inverters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/483—Converters with outputs that each can have more than two voltages levels
    • H02M7/4837—Flying capacitor converters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0095—Hybrid converter topologies, e.g. NPC mixed with flying capacitor, thyristor converter mixed with MMC or charge pump mixed with buck
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/32—Means for protecting converters other than automatic disconnection
    • H02M1/34—Snubber circuits
    • H02M1/346—Passive non-dissipative snubbers
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

Definitions

  • the present invention relates to a voltage type multi-level converter using a flying capacitor.
  • switching elements In recent years, multilevel converters have become mainstream in variable speed drive devices and power conversion devices using power devices (for example, IGBTs, etc .: hereinafter referred to as switching elements).
  • FIG. 6 is a diagram showing an example of a conventional voltage type multi-level converter.
  • the voltage type multilevel converter shown in FIG. 6 has first and second capacitors C1 and C2 connected in series between positive and negative electrodes of a DC voltage source (not shown) and current change rate suppressing reactors L1 and L2
  • a phase module 4 having snubber circuits 1a and 1b for suppressing surge voltage, current change rate detection units 3a and 3b for detecting current change rates di / dt in current change rate suppressing reactors L1 and L2, and flying capacitors C3 and C4. And have.
  • FIG. 6 only one phase module 4 is shown for simplification.
  • phase module 4 In the voltage type multi-level converter shown in FIG. 6, it is determined that a short circuit has occurred in phase module 4 when current change rate detected value di / dt output from current change rate detectors 3a and 3b is equal to or more than a predetermined value.
  • a short circuit abnormality signal is transmitted to a controller (not shown) in the phase module 4 via a common controller (not shown). Thereafter, the controller in the phase module 4 transmits a gate shutoff signal to the drive circuit of the switching element to shut off the gate signal safely.
  • the load of the device has a predetermined current waveform, and the current change rate di / dt of the flying capacitor accompanying this is known, and therefore, is set in advance as a reference value, and this reference value and the current change rate detection units 3a and 3b.
  • the short circuit judgment can be made by comparing with the current change rate detected value di / dt of
  • the first and second capacitors C1 and C2 connected to the DC voltage source and the current change rate suppressing reactors L1 and L2 are common to each phase module 4 It is provided only in one place. Therefore, when a short circuit abnormality occurs, the current change rate detection value di / dt needs to transmit a short circuit abnormality signal to the controller in the phase module 4 via the common controller. As a result, it is necessary to speed up the communication speed between the common controller and the controller in the phase module 4 or to suppress the short circuit current by providing larger current change rate suppressing reactors L1 and L2 and snubber circuits 1a and 1b. was there.
  • the present invention was devised in view of the above-mentioned conventional problems, and one aspect thereof is a voltage type multi-level converter which generates an AC output obtained by converting a DC voltage into a plurality of voltage levels, which is a DC voltage
  • a capacitor common to each phase connected in series between both terminals of the source, a flying capacitor provided for each phase and charged with a voltage different from that of the capacitor, and a plurality of switching elements for each phase
  • a voltage selection circuit selectively outputting a plurality of voltage levels based on voltages of the capacitor and the flying capacitor by selectively turning on and off the switching element, and detecting a rate of change in voltage across the flying capacitor Detecting a short circuit when the voltage change rate across the flying capacitor exceeds a threshold value.
  • a short circuit abnormality signal is outputted to a controller in a phase module when a voltage change rate across the flying capacitor exceeds a threshold.
  • the cause of the short circuit is identified by the value of the rate of change in voltage across the flying capacitor.
  • FIG. 2 is a diagram showing an equivalent circuit of a capacitor. It is a time chart which shows each waveform at the time of normal time and a short circuit. It is a circuit block diagram which shows the voltage type
  • the present invention detects, in a voltage type multi-level converter using a flying capacitor, a low impedance short circuit on an output side, an abnormality such as a sudden switching element, or a short circuit failure caused by an accidental drive circuit malfunction. It is intended to prevent the expansion of the fault range.
  • FIG. 1 is a circuit configuration diagram of a voltage type multi-level converter according to the present embodiment.
  • a five-level voltage type power converter is described as an example.
  • first and second capacitors C1 and C2 are connected in series between positive and negative ends of a DC voltage source (not shown).
  • the common connection point between the two capacitors C1 and C2 is taken as an output terminal B.
  • the positive terminal of the direct current voltage source is P
  • the negative terminal is N.
  • the first switching element S1 and the flying capacitor C3 are sequentially connected in series.
  • the Nth to sixth switching elements and the flying capacitor C4 are sequentially connected in series.
  • the flying capacitors C3 and C4 are connected in series, and the first switching element S1, the flying capacitors C3 and C4, and the sixth switching element S6 constitute a first series circuit.
  • the second, third, fourth and fifth switching elements S2, S3, S4 and S5 are sequentially connected in series to form a second series circuit.
  • the second switching element S2 is connected to the common connection point of the first switching element S1 and the flying capacitor C3
  • the fifth switching element S5 is connected to the common connection point of the sixth switching element S6 and the flying capacitor C4.
  • the middle point of the second series circuit (the common connection point of the third and fourth switching elements S3 and S4) is taken as the output terminal A.
  • first and second diodes D1 and D2 are interposed between the common connection point of the second and third switching elements S2 and S3 and the common connection point of the fourth and fifth switching elements S4 and S5, The common connection point of the first and second diodes D1 and D2 is connected to the common connection point of the flying capacitors C3 and C4.
  • a seventh switching element S7 and an eighth switching element S8 are connected in series in the opposite direction between the output terminal B and the common connection point of the flying capacitors C3 and C4.
  • the first to eighth switching elements S1 to S8 constitute a voltage selection circuit.
  • Reference numerals 1a and 1b denote snubber circuits, which respectively include snubber diodes D3, D4, D5 and D6, snubber capacitors C5 and C6, feedback resistors R1 and R2, and current change suppressing reactors L1 and L2.
  • the flying capacitors C3 and C4 are provided with voltage change rate detectors 2a and 2b for detecting the voltage change rate dV / dt at both ends of the flying capacitor via the voltage dividing resistors R3 and R4.
  • the voltage type multi-level converter in this embodiment is the switching element in the drive circuit 7 of each switching element when the voltage of the first and second capacitors C1 and C2 is 2E and the voltage of the flying capacitors C3 and C4 is E.
  • S1 to S8 By turning on and off S1 to S8 according to the switching patterns of modes 1 to 7 shown in Table 1 below, voltages 2E, E, 0, -E, and -2E of five levels can be output between output terminals AB.
  • ⁇ Mode 1> The first, second, and third switching elements S1, S2, and S3 turn on, and the fourth, fifth, sixth, seventh, and eighth switching elements S4, S5, S6, S7, and S8 turn off, and the current I A Flows through the path of output terminal BBfirst capacitor C1 ⁇ P ⁇ S1 ⁇ S2 ⁇ S3 ⁇ output terminal A.
  • the negative side ⁇ positive side of the first capacitor C1 is connected between the output terminals AB, and the voltage between the output terminals A and B is 2E.
  • ⁇ Mode 2> The first, third and fourth switching elements S1, S3 and S4 are turned on, and the second, fifth, sixth, seventh and eighth switching elements S2, S5, S6, S7 and S8 are turned off, and the current I A Is output terminal B ⁇ first capacitor C 1 ⁇ P ⁇ S 1 ⁇ flying capacitor C 3 ⁇ D 1 ⁇ S 3 ⁇ output terminal A (or output terminal B ⁇ first capacitor C 1 ⁇ P ⁇ S 1 ⁇ flying capacitor C 3 ⁇ D 2 ⁇ S 4 ⁇ output It flows along the path of terminal A).
  • ⁇ Mode 3> The second, third, seventh, eighth switching element S2, S3, S7, S8 are turned on, first, fourth, fifth, sixth switching elements S1, S4, S5, S6 are turned off, current I A Flows through a path of output terminal B ⁇ S7 ⁇ S8 ⁇ flying capacitor C3 ⁇ S2 ⁇ S3 ⁇ output terminal A.
  • the negative side ⁇ positive side of the flying capacitor C3 is connected between the output terminals AB, and the voltage between the output terminals A and B is E. In this mode 3, the flying capacitor C3 is charged when the current I A > 0.
  • ⁇ Mode 4> The third, fourth, seventh, eighth switching elements S3, S4, S7, S8 turn on, the first, second, fifth, sixth switching elements S1, S2, S5, S6 turn off, and the current is output terminal B ⁇ S7 ⁇ S8 ⁇ D1 ⁇ S3 ⁇ output terminal a (or, when the current I a is negative, the output terminal B ⁇ S7 ⁇ S8 ⁇ D2 ⁇ S4 ⁇ output terminal a) flows through a path of. Seventh between output terminals AB, eighth, first switching element S7, S8, S1 (or current I A is when negative seventh, eighth, second switching element S7, S8, S2) via the And the voltage between the output terminals AB becomes zero.
  • ⁇ Mode 5> The fourth, fifth, seventh, eighth switching elements S4, S5, S7, S8 are turned on, the first, second, third, sixth switching elements S1, S2, S3, S6 are turned off, and the current I A Flows through the path of output terminal B ⁇ S7 ⁇ S8 ⁇ flying capacitor C4 ⁇ S5 ⁇ S4 ⁇ output terminal A.
  • the positive side to the negative side of the flying capacitor C4 is connected in series between the output terminals AB, and the voltage between the output terminals A and B is -E. In this mode 5, the flying capacitor C4 is discharged when the current I A > 0.
  • ⁇ Mode 7> The fourth, fifth and sixth switching elements S4, S5 and S6 are turned on, and the first, second, third, seventh and eighth switching elements S1, S2, S3, S7 and S8 are turned off, and the current I A Flows through the path of the output terminal B, the second capacitor C2, N, S6, S5, S4, and the output terminal A.
  • the positive side to the negative side of the second capacitor C2 is connected between the output terminals AB, and the voltage between the output terminals A and B is -2E.
  • the voltages of the flying capacitors C3 and C4 can be controlled using switching patterns (Modes 2, 3, 5, 6 in Table 1) which are charged or discharged when the output voltage V AB is E or -E. That is, although both of the output voltages in mode 2 and mode 3 are E, since the flying capacitor C3 can be charged or discharged, the voltage of the flying capacitor C3 can be adjusted. Similarly, although the output voltages of mode 5 and mode 6 are both ⁇ E, it is possible to adjust the voltage of the flying capacitor C 4 because the flying capacitor C 4 can be charged or discharged.
  • the short circuit of the phase module 4 is detected by detecting the current change rate di / dt in the current change rate suppressing inductances L1 and L2 common to each phase, but this embodiment shown in FIG. In the above, the short circuit of the phase module 4 is detected by detecting the increase or decrease of the voltage change rate dV / dt in the flying capacitors C3 and C4 in the phase module 4.
  • phase module 4 when a short circuit abnormality occurs in the phase module 4, the output signals of the voltage change rate detection units 2a and 2b are not driven by the controller common to each phase, and the controller 6 and the drive in each phase module 4 are driven.
  • the gate signals of the switching elements S1 to S8 can be cut off only via the circuit 7.
  • voltage change rate detectors 2a and 2b for detecting voltage change rates dV / dt of flying capacitors C3 and C4 are originally provided for control of the voltage type multi-level converter, so common use may be made as they are. It is possible.
  • the short circuit (1) shown in FIG. 3A shows an example in which the first and second capacitors C1 and C2 and the flying capacitors C3 and C4 are connected in parallel. As described above, the voltage of the flying capacitors C3 and C4 is charged at a voltage lower than the voltage of the first and second capacitors C1 and C2. In the short circuit (1), the voltage change rate dV / dt decreases due to the discharge of the flying capacitors C3 and C4.
  • the short circuit (2) shown in FIG. 3 (b) shows an example in which first and second capacitors C1 and C2 and flying capacitors C3 and C4 are connected in series as voltage sources.
  • the voltage of the first and second capacitors C1 and C2 > the voltage of the flying capacitors C3 and C4. Therefore, the flying capacitors C3 and C4 are charged from the first and second capacitors C1 and C2.
  • the voltage change rate dV / dt rises.
  • the short circuit (3) shown in FIG. 3C shows an example of a short circuit having only the flying capacitors C3 and C4.
  • the voltage change rate dV / dt decreases due to the discharge of the flying capacitors C3 and C4.
  • FIG. 5 (a) is a time chart showing current and voltage at the time of normal operation and FIG. 5 (b) at the time of short circuit (in the case of discharge).
  • the spike-like voltage drop occurs when a short circuit occurs because the voltage drop is superimposed.
  • the capacitor voltage Vc is the following equation (1)
  • the voltage change rate dVc / dt of the capacitor voltage Vc is the following equation (2).
  • C capacity
  • I c capacitor current
  • Vc 0 initial voltage of capacitor.
  • the capacitor current i c in the normal operation has a value in a certain range depending on the load (inductance of the motor, etc.)
  • the capacitor current i cs at the short circuit is limited mainly by the current due to the characteristics of the element and becomes large. Therefore, the relationship between the capacitor current i c in the normal operation and the capacitor current i cs in the short circuit is given by the following equation (3).
  • a short circuit test is performed in advance in three types of short circuit modes (damage of element itself, false ignition, external short circuit), capacitor voltage V c is measured, It is conceivable to determine the threshold value of the rate of voltage change dV / dt of the short circuit failure.
  • the short circuit in the inverter can be roughly divided into the following three types (1) (2) (3).
  • (1) Failure of the element itself (2) In the case of erroneous ignition (3)
  • the short circuit 1 shown in FIG. 3A is, for example, a case where the switching element S1 is damaged and the switching elements S2, S3, S4, S5, and S6 are erroneously turned on.
  • the first and second capacitors C1 and C2 and the flying capacitors C3 and C4 as power supplies, a current flows which is determined by the active characteristics of the element and the impedance of the wiring.
  • the emitter-collector of the switching element S1 is short-circuited with a conductor, and an ON signal is applied to the switching element S6 for measurement.
  • the anode and the cathode of the diode D1 are short-circuited with a conductor, and an ON signal is applied to the switching element S2 (or S5) for measurement.
  • the voltage change rate dV / dt of the flying capacitors C3 and C4 basically becomes different values.
  • the switching element viewed as a broken element of (1) also receives an on signal simultaneously with the other switching elements, and measures the voltage change rate dV / dt.
  • U phase-V phase short circuit For example, U phase switching elements S1, S2, S3 are turned on, V phase switching elements S4, S5, S6 are turned on, and U phase-V phase is shorted In this case, a short circuit current flows from the first and second capacitors C1 and C2 and the flying capacitor C3.
  • the voltage change rate detectors 2a and 2b constantly calculate the voltage change rate dV / dt, and send out a short circuit fault signal to the controller 6 in the phase module 4 when the threshold is exceeded. At the same time, the value of the voltage change rate dV / dt is stored in a storage unit (not shown). Then, a shutoff signal is sent from the controller unit 6 to the drive circuit 7 to turn off the switching elements S1 to S8.
  • a spike-like voltage drop occurs at the occurrence of a short circuit, and the voltage change rate dV / dt measures a large value in section A, but in terms of calculation of the voltage change rate dV / dt
  • the voltage change rate dV / dt at A may or may not be ignored.
  • a measurement value for example, a moving average value of voltage change rate dV / dt at each sampling is used.
  • the controller common to each phase module since the controller common to each phase module is not used, short circuit detection / cut in a short time in the phase module 4 in which the short circuit occurs. Protection action can be performed.
  • short circuit detection / cutoff protection operation can be performed in a short time after a short circuit occurs, the responsibility of the current change rate suppression reactors L1 and L2 can be reduced.
  • the responsibility of the current change rate suppression reactors L1 and L2 can be reduced, the responsibility of the snubber circuits 1a and 1b can be relaxed.
  • the present invention is applicable to any voltage type multi-level converter provided with a flying capacitor.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Inverter Devices (AREA)

Abstract

La présente invention concerne des unités de détection de vitesse de variation de tension (2a, 2b) qui détectent les vitesses de variation des tensions entre les deux extrémités de condensateurs volants (C3, C4) qui sont prévus pour chaque phase et pour lesquels des tensions différentes de celles circulant à travers des condensateurs (C1, C2) sont chargées. Lorsque les vitesses de variation des tensions entre les deux extrémités des condensateurs volants (C3, C4) dépassent une valeur seuil, il est détecté qu'un court-circuit se produit. Un signal d'anomalie de court-circuit est alors transmis à une unité de commande (6) de chaque phase, et un circuit d'attaque (7) pour chaque élément de commutation interrompt un signal de grille. Cela permet qu'un traitement protecteur pour une défaillance de court-circuit soit mis en œuvre avec une configuration simple sans augmenter la vitesse de communication entre un dispositif de commande partagé et un dispositif de commande à l'intérieur d'un module de phase.
PCT/JP2014/071699 2013-08-21 2014-08-20 Convertisseur multiniveau de type tension WO2015025860A1 (fr)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
JP2013-170939 2013-08-21
JP2013170939A JP5910584B2 (ja) 2013-08-21 2013-08-21 電圧型マルチレベル変換器

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WO2015025860A1 true WO2015025860A1 (fr) 2015-02-26

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Cited By (5)

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Publication number Priority date Publication date Assignee Title
CN105305864A (zh) * 2015-11-06 2016-02-03 国家电网公司 一种基于谐振分流回路的换相装置及其实现方法
CN106505899A (zh) * 2016-11-11 2017-03-15 清华大学 中点箝位三电平单极电流模块
CN110187209A (zh) * 2019-06-04 2019-08-30 长沙晟道电气科技有限公司 模块化多电平变换器子模块故障检测方法、系统及介质
JP2020089240A (ja) * 2018-11-30 2020-06-04 パナソニックＩｐマネジメント株式会社 電力変換装置、制御方法、及びプログラム
CN117220476A (zh) * 2023-11-07 2023-12-12 深圳市力生美半导体股份有限公司 开关电源供电控制电路及供电控制方法

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JPH07231674A (ja) * 1994-02-22 1995-08-29 Hitachi Ltd 自己消弧半導体素子を用いたインバータ装置の制御方法
JPH09205779A (ja) * 1996-01-25 1997-08-05 Hitachi Ltd 電力変換装置
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JP2008154420A (ja) * 2006-12-20 2008-07-03 Toshiba Mitsubishi-Electric Industrial System Corp 電力変換装置
JP2013146117A (ja) * 2012-01-13 2013-07-25 Fuji Electric Co Ltd マルチレベル電力変換回路

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JP4120329B2 (ja) * 2002-09-19 2008-07-16 富士電機デバイステクノロジー株式会社 電圧駆動型半導体素子のゲート駆動装置
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JPH07231674A (ja) * 1994-02-22 1995-08-29 Hitachi Ltd 自己消弧半導体素子を用いたインバータ装置の制御方法
JPH09205779A (ja) * 1996-01-25 1997-08-05 Hitachi Ltd 電力変換装置
JP2007184999A (ja) * 2005-12-29 2007-07-19 Toshiba Mitsubishi-Electric Industrial System Corp 電力変換装置
JP2008154420A (ja) * 2006-12-20 2008-07-03 Toshiba Mitsubishi-Electric Industrial System Corp 電力変換装置
JP2013146117A (ja) * 2012-01-13 2013-07-25 Fuji Electric Co Ltd マルチレベル電力変換回路

Cited By (9)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN105305864A (zh) * 2015-11-06 2016-02-03 国家电网公司 一种基于谐振分流回路的换相装置及其实现方法
CN105305864B (zh) * 2015-11-06 2017-12-19 国家电网公司 一种基于谐振分流回路的换相装置及其实现方法
CN106505899A (zh) * 2016-11-11 2017-03-15 清华大学 中点箝位三电平单极电流模块
JP2020089240A (ja) * 2018-11-30 2020-06-04 パナソニックＩｐマネジメント株式会社 電力変換装置、制御方法、及びプログラム
JP7108932B2 (ja) 2018-11-30 2022-07-29 パナソニックＩｐマネジメント株式会社 電力変換装置、制御方法、及びプログラム
CN110187209A (zh) * 2019-06-04 2019-08-30 长沙晟道电气科技有限公司 模块化多电平变换器子模块故障检测方法、系统及介质
CN110187209B (zh) * 2019-06-04 2021-04-09 长沙晟道电气科技有限公司 模块化多电平变换器子模块故障检测方法、系统及介质
CN117220476A (zh) * 2023-11-07 2023-12-12 深圳市力生美半导体股份有限公司 开关电源供电控制电路及供电控制方法
CN117220476B (zh) * 2023-11-07 2024-02-27 深圳市力生美半导体股份有限公司 开关电源供电控制电路及供电控制方法

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