WO2011004546A1 - Appareil de moteur à réluctance - Google Patents

Appareil de moteur à réluctance Download PDF

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Publication number
WO2011004546A1
WO2011004546A1 PCT/JP2010/003748 JP2010003748W WO2011004546A1 WO 2011004546 A1 WO2011004546 A1 WO 2011004546A1 JP 2010003748 W JP2010003748 W JP 2010003748W WO 2011004546 A1 WO2011004546 A1 WO 2011004546A1
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WO
WIPO (PCT)
Prior art keywords
phase
rotor
poles
srm
windings
Prior art date
Application number
PCT/JP2010/003748
Other languages
English (en)
Inventor
Shouichi Tanaka
Original Assignee
Three Eye Co., Ltd.
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Priority claimed from JP2009163580A external-priority patent/JP2010193700A/ja
Application filed by Three Eye Co., Ltd. filed Critical Three Eye Co., Ltd.
Publication of WO2011004546A1 publication Critical patent/WO2011004546A1/fr

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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02K—DYNAMO-ELECTRIC MACHINES
    • H02K19/00—Synchronous motors or generators
    • H02K19/02—Synchronous motors
    • H02K19/10—Synchronous motors for multi-phase current
    • H02K19/103—Motors having windings on the stator and a variable reluctance soft-iron rotor without windings
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P25/00—Arrangements or methods for the control of AC motors characterised by the kind of AC motor or by structural details
    • H02P25/02—Arrangements or methods for the control of AC motors characterised by the kind of AC motor or by structural details characterised by the kind of motor
    • H02P25/08—Reluctance motors
    • H02P25/092—Converters specially adapted for controlling reluctance motors
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02K—DYNAMO-ELECTRIC MACHINES
    • H02K17/00—Asynchronous induction motors; Asynchronous induction generators
    • H02K17/02—Asynchronous induction motors
    • H02K17/16—Asynchronous induction motors having rotors with internally short-circuited windings, e.g. cage rotors
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02K—DYNAMO-ELECTRIC MACHINES
    • H02K21/00—Synchronous motors having permanent magnets; Synchronous generators having permanent magnets
    • H02K21/12—Synchronous motors having permanent magnets; Synchronous generators having permanent magnets with stationary armatures and rotating magnets
    • H02K21/14—Synchronous motors having permanent magnets; Synchronous generators having permanent magnets with stationary armatures and rotating magnets with magnets rotating within the armatures
    • H02K21/16—Synchronous motors having permanent magnets; Synchronous generators having permanent magnets with stationary armatures and rotating magnets with magnets rotating within the armatures having annular armature cores with salient poles

Definitions

  • the invention relates to a reluctance motor apparatus, in particular, a switched reluctance motor apparatus.
  • the switched reluctance motor has advantages as a vehicle motor such as an in-wheel motor and a motor turbo charger and an alternator, which are rotated in hard atmosphere.
  • U. S. Patent. No. 5,111,095 invented by Hendershot discloses a five-phase SRM with the uneven circumferential rotor pole gaps. As shown in Figure 1, the Hendershot's SRM has eight rotor poles and ten stator poles essentially. The Hendershot's SRM has two kinds of rotor pole gaps. A wide rotor pole gap and a narrow rotor pole gap are arranged alternately in the circumferential direction.
  • the Hendershot's SRM has four stator poles producing a motor torque in the same period, because adjacent two rotor poles are magnetized together. Acoustic noise of the Hendershot's SRM with five-phase is less than the conventional three-phase SRM.
  • the Hendershot's SRM with a short flux passage has possibility that the iron loss can be reduced. However, it is required to improve torque/weight and loss reduction for the SRM including the Hendershot's SRM, because the BLDCM with permanent magnets has the superior torque/weight and the superior efficiency.
  • the SRM is very preferable for an in-wheel motor and a motor turbo charger, because the in-wheel motor and the motor turbo charger require superior strength in hot atoms here.
  • the SRM including the Hendershot's SRM still needs to be improved as the in-wheel motor and the motor turbo charger.
  • the in-wheel motor and the motor turbo charger of the vehicle absolutely require a light weight of the motor.
  • the heavy in-wheel motor under a wheel spring gives bad driving feeling to a driver.
  • the heavy rotor of the motor turbo charger decrease acceleration of the vehicle.
  • the SRM has a large volume of a periodical exciting current charging and discharging a battery in order to magnetize the salient periodically.
  • the large volume of the exciting current of the SRM gives bad influence to battery life.
  • a large smoothing capacitor connected to the battery in parallel increases a size and cost of a driving circuit.
  • a five-phase inverter of the Hendershot's SRM shown in Figure 2 has ten transistors and ten diodes.
  • the Hendershot's SRM has a possibility to employ a known common-switch-type unipolar inverter shown in Figure 3.
  • the common-switch-type unipolar inverter turning-on of switches, for example transistors 1000-1002 can not overlap to turning-off of switches, for example transistors 1000, 1003 and 1004.
  • a residual magnetic energy of one phase winding can not charge the battery, if the common upper switch 1000 is turned on. Accordingly, the inverter shown in Figure 3 is not available for the Hendershot' SRM, of which turning-on and turning-off of the lower switches are overlapped.
  • FIG. 4 Another type of a five-phase unipolar inverter is illustrated in Figure 4.
  • the five-phase inverter drives a five-phase SRM with equal rotor pole gaps.
  • Hendershot's SRM with the uneven rotor pole gaps can employ the inverter shown in Figure 4.
  • U. S. Patent. No. 6,252,325 discloses a three-phase driving circuit for a DC-magnetized SRM with six phase windings and six DC windings. Each pair of the phase winding and the DC winding is wound on each stator pole. However, the stator poles produce reverse motor torque, because the all of stator poles are always magnetized by the DC windings.
  • '325 patent does not describe a possibility that the five-phase SRM, for example Hendershot' SRM can employ the DC windings. Furthermore, '325 patent does not describe the SRG employing the DC windings.
  • U. S. Patent. No. 6,646,407 and U. S. Patent. No. 7,049,786 describes a SRM with a one-directional boost DC-DC converter applying a boosted DC voltage to an asymmetrical unipolar inverter.
  • '407 patent and '786 patent do not describe the SRG, the switched reluctance generator, with a bi-directional boost DC-DC converter.
  • a generated current of the SRG is supplied to a power source, for example a battery.
  • the residual magnetic energy of the phase winding generates the exciting current component, the RME current component, which is included in the generated current.
  • the exciting current component is supplied to the power source through the bi-directional boost DC-DC converter.
  • the power source must supply the exciting current component to a next phase winding again for magnetizing the next stator pole. Accordingly, the power loss of the bi-directional boost DC-DC converter increases by the going and coming of the exciting current component.
  • the smoothing capacitor connected to a DC-link between the inverter and the converter reduces the exciting current component passing through the converter.
  • the parallel-connected smoothing capacitor increases the size and the production cost, because the parallel-connected smoothing capacitor must have a large capacitance.
  • U. S. Patent No. 5,973,431 describes a hybrid three-phase SRM having permanent magnets fixed in the rotor gaps between two rotor poles adjacent each other.
  • the increasing of the torque is not enough for the above hybrid SRM, because the phase current is only supplied for an inductance-increase period.
  • the five-phase SRM including the Hendershot's SRM can employ the permanent magnets in the rotor pole gaps.
  • U. S. Patent No. 5,304,882 describes the Hybrid SRM having two fixed permanent magnets in the rotor inside. However, the magnetic flux flows in the soft magnetic rotor salient. As the result, changing of the flux of the rotor pole is restrained and torque of the rotor pole is reduced.
  • Japanese Unexamined Patent No. 2004-248,370 describes the hybrid SRM having the permanent magnet fixed in a concave portion between two rotor magnetic poles adjacent each other.
  • the permanent magnet is arranged on a central portion of the concave portion in the rotation direction. As the result, the increasing torque is not enough even though the permanent magnets are added to the rotor.
  • the present invention has an object to provide a reluctance motor apparatus with a superior torque/weight ratio.
  • the present invention has another object to provide a reluctance motor apparatus with a superior efficiency.
  • the present invention has an object to provide a reluctance motor apparatus with a superior battery life.
  • the five-phase SRM with uneven rotor pole gaps is disclosed. Odd rotor pole gaps are wider than even rotor pole gaps in the circumferential direction.
  • the apparatus includes a power circuit connecting between the phase windings of the SRM and a power source.
  • the SRM has ten stator poles and eight rotor poles. Combination of adjacent two stator poles magnetized in the essentially same period is changed in turn.
  • the adjacent two rotor poles are consisted of two end portions of a U-shaped rotor pole.
  • Each of the U-shaped rotor poles is independent from the other U-shaped rotor poles magnetically.
  • the torque of the five-phase SRM is increased. It is known that the torque is proportional to a inductance difference.
  • the phase windings 403 and 404 is in the smallest inductance timing just before the phase currents are supplied to the phase windings 403 and 404.
  • the stator poles C and D wound by the phase windings 403 and 404 has closed magnetic passages LY1, LY2 and LY3.
  • the magnetic passages LY1 and LY3 are formed across air gaps facing stator poles A and D with a large area.
  • the magnetic passages LY1 and LY3 have smaller magnetic resistances than the magnetic passages LY2. Consequently, the smallest inductances of the phase windings 403 and 404 can not become small, because of the magnetic passages LY1 and LY3.
  • the smallest inductance value of phase windings of the conventional three-phase SRM increases by the magnetic passages LY1, LY2 and LY3, too.
  • the U-shaped rotor poles of the five-phase SRM can reduce the smallest inductance value largely, because the magnetic passages LY1 and LY3 and the other magnetic passages across two U-shaped rotor poles are broken. Furthermore, the rotor weight of the five-phase SRM with the U-shaped rotor poles becomes almost half in comparison with the Hendershot' SRM.
  • the five-phase SRM with the U-shaped rotor poles has the same advantages as the Hendershot' SRM having the many torque-producing stator poles at one time and the iron loss reduction by means of the short magnetic passage.
  • one ends of the five phase windings are connected each other.
  • Each of the other ends of the phase windings (401, 403 and 405) are connected to a high potential line (104) via each upper switches (201, 203 and 205).
  • Each of the other ends of the phase windings (402, 404 and 405) are connected to a low potential line (105) via each lower switches (202, 204 and 206).
  • the connection points between the phase windings (401-405) and the switches (201-205) are connected to a freewheeling diodes (301-305).
  • Each pair of the upper switch and the lower switch turned on at a same period is changed in turn.
  • the five-phase inverter can consist of six pairs of a transistor and a freewheeling diode. By decreasing the transistors and the freewheeling diodes, the inverter cost is reduced.
  • the parallel-connected switch (102) can be constituted with only one diode, if the SRM is not operated as the generator. Almost residual magnetic energy of the phase winding accumulated in the capacitor (103) can be used in order to excite the next stator poles. The battery life is extended. The phase current rises up quickly and falls down quickly.
  • the five-phase inverter (902) is connected to the power source via the capacitor (103).
  • the connecting point between the power source (900) and the capacitor (103) is connected to a connection point between the phase winding and the switch of the five-phase inverter (902) via the freewheeling diode.
  • the residual magnetic energy accumulated in the capacitor (103) can be used in order to excite the next stator poles quickly.
  • the power source (900) supplies the phase current via the freewheeling diodes of the five-phase inverter. The rising-up and the falling-down of the phase current become fast without the parallel-connected switch (102).
  • the five-phase inverter (902) is connected to the power source (900) via a boost DC-to-DC converter (901A). It is preferable to employ the bi-directional boost DC-to-DC converter.
  • the five-phase inverter (902) is not PWM-switched for controlling a motor torque.
  • the total current of all phase windings becomes almost DC current.
  • the motor torque of the SRM can be controlled without the PWM-switching of the inverter.
  • the switching elements of the inverter do not need a low switching loss at switching with high frequency.
  • the converter (901A) consists of a chopper type converter.
  • a connection point between the power source (900) and the reactor (100) is connected to a connection point between the phase windings (401, 403 and 405) and the switches (201, 203 and 205) of the five-phase inverter (902) via the freewheeling diode (301, 303 and 305).
  • the power circuit has a capacitor (103) connecting the power source (900) and the either one of both input terminals (104, 105) of the five-phase inverter (902).
  • the power source (900) supplies the current to the phase winding without passing through the two series-connected switches (102, 201), but via the freewheeling diodes, for example 301, after discharging of the capacitor (103).
  • the converter (901A) applies higher value of the boosted voltage to the five-phase inverter (902) in a rising-up period than the boosted voltage in an inductance-increasing period.
  • the phase current rises up quickly, and the falls down quickly, because of the DC-link voltage applied to the inverter becomes high.
  • a flat reluctance torque is produced in a long period.
  • the torque ripple is reduced.
  • the converter (901A) is stopped, when the capacitor (103) is charged.
  • the capacitor charges the RME energy, the residual magnetic energy of the phase winding, smoothly.
  • the converter (901A) applies the boosted voltage decreasing with a predetermined decreasing rate in an inductance-increasing period while the inductance value of the phase winding is increasing.
  • the torque ripple is reduced, because the phase current, which is proportional to the torque, becomes flat in the inductance-increasing period.
  • the rotor core with the U-shaped rotor poles is fixed to a wheel of a vehicle directly.
  • the rotor core has larger diameter than the stator poles.
  • the driving feeling is improved, because the weight of the wheel is decreased.
  • the rotor core with the U-shaped rotor poles is fixed to an rotating axis of the motor turbo charger. The acceleration of the rotating speed of the motor turbo charger is largely improved by the mass-reduction of the rotor.
  • the odd rotor pole gaps accommodate a first permanent magnet with a first polarity each.
  • the even rotor pole gaps accommodates a second permanent magnets having an opposite polarity to the first permanent magnet.
  • the first permanent magnets is accommodated essentially in one circumferential half of the odd rotor pole gaps between adjacent two U-shaped rotor poles.
  • the motor torque is increased.
  • the permanent magnets covering sides of the rotor poles increase the magnetic resistance. In the other words, the magnetic resistance of the flux passages Ly2 is increased, and the smallest inductance value is decreased by the permanent magnets.
  • stator poles of the SRG are wound by pairs of the phase winding (401-405, 401'-405') and DC windings (51-55, 51'-55').
  • the DC windings (51-55, 51'-55') connected to series each other are connected to a DC power source (900) via a field current switch (910).
  • the five-phase inverter includes a five-phase rectifier (60). As the result, the generated voltage of the SRG is controlled easily.
  • the rotor core is wound by a short-cut winding (200).
  • a going conductor 201 of the short-cut winding (200) extends to an axial direction in the smaller rotor pole gap (201) between the two rotor poles of the U-shaped rotor pole.
  • a coming conductor 201 of the short-cut winding (200) extends to an axial direction in the larger rotor pole gap (202) between the two U-shaped rotor poles.
  • the above five-phase inverter with six pairs of a switch and a freewheeling diode drives the star-shape-connected five-phase windings.
  • the above five-phase unipolar inverter with six switches can be employ the any five-phase SRM.
  • a reluctance motor apparatus comprising a stator core with stator poles, phase windings wound around the stator poles, a rotor core with rotor poles and a power circuit connecting between the phase windings and a power source: wherein (A) a numeral ratio of the stator poles and the rotor poles is five and four; (B) the rotor core has each rotor pole gap between each adjacent two rotor poles; (C) Odd rotor pole gaps have larger circumferential width than even rotor pole gaps; (D) the power circuit has a five-phase inverter exciting adjacent two phase windings in the essentially same period; and (E) one ends of the five phase windings (401-405) are connected each other; the other ends of the phase windings (401, 403 and 405) are connected to a high potential line (104) via upper switches (201, 203 and 205); the other ends of the phase windings (402, 404 and 40).
  • the rotor core is wound by a short-cut winding (200) with a plurality of pairs of a going conductor and the coming conductor.
  • the going conductor is extended in the smaller rotor pole gap (201), and the coming conductor 201 is extended in the larger rotor pole gap (202).
  • the RME the residual magnetic energy of the phase winding is transmitted to the next phase winding with small power loss.
  • a reluctance motor apparatus comprising a stator core with stator poles, phase windings wound around the stator poles, a rotor core with rotor poles and a power circuit connecting between the phase windings and a power source: wherein (A) a numeral ratio of the stator poles and the rotor poles is five and four; (B) the rotor core has each rotor pole gap between each adjacent two rotor poles; (C) Odd rotor pole gaps have larger circumferential width than even rotor pole gaps; (D) the power circuit has a five-phase inverter exciting adjacent two phase windings in the essentially same period; and (E) the rotor core is wound by a short-cut winding (200); a going conductor 201 of the short-cut winding (200) extends to an axial direction in the smaller rotor pole gap (201) between the two rotor poles of the U-shaped rotor pole; and a
  • the five-phase SRM with U-shaped rotor poles the five-phase SRM with five-phase inverter with six switches, and the five-phase SRM with the short-cut rotor winding can be considered.
  • the inventor understands that each preferred embodiment explained above can constitute independent inventions each. Furthermore, the inventor understands that the next embodiments explained later can constitute independent inventions.
  • the SRM for example the three-phase SRM, of one invention is connected to the power source via a capacitor (74). Further, the connection point (X) between the power source (75) and the capacitor (74) is connected to a connection points between the phase windings and the switches of the inverter (902) via the freewheeling diodes (for example D4, D5 and D6).
  • the freewheeling diodes for example D4, D5 and D6.
  • the SRM for example the three-phase SRM, of another invention has each pair of two permanent magnets (6A and 6B) inserted in each rotor pole gap between each pair of two rotor poles (20, 20) being adjacent each other.
  • the two permanent magnets (6A and 6B) with opposite polarities each other are arranged to the circumferential direction in order. The motor torque is improved strongly.
  • the SRM for example the three-phase SRM, of another invention has the short-cut rotor winding wound in only odd rotor pole gaps or only even rotor pole gaps.
  • the short-cut rotor winding can have structure of the well-known squirrel cage conductor. The short-cut rotor winding accelerates the rising-up and the fall-down of the phase current without the low resistance power loss.
  • Figure 1 is a schematic radial section view of a prior five-phase SRM with uneven rotor gaps.
  • Figure 2 is one prior unipolar inverter driving a five-phase SRM.
  • Figure 3 is another prior unipolar inverter capable to drive a five-phase SRM with uneven rotor pole gaps.
  • Figure 4 is another prior unipolar inverter driving a five-phase SRM with even rotor pole gaps.
  • Figure 5 is a circuit diagram showing a three-phase SRM with field DC windings.
  • Figure 6 is a cross section of a five-phase SRM with four U-shaped rotor poles from a time t3 to a time t4 in a motor mode.
  • Figure 7 is another cross section of the five-phase SRM with the four U-shaped rotor poles from a time t4 to a time t5 in a motor mode.
  • Figure 8 is the cross section of the five-phase SRM with the four U-shaped rotor poles from a time t5 to a time t1 in a motor mode.
  • Figure 9 is another cross section of the five-phase SRM with the four U-shaped rotor poles from a time t1 to a time t2 in a motor mode.
  • Figure 10 is another cross section of the five-phase SRM with the four U-shaped rotor poles from a time t2 to a time t3 in a motor mode.
  • Figure 11 is a timing chart showing phase inductances and phase currents of the five-phase SRM shown in Figures 6-11.
  • Figure 12 is a timing table showing polarities of stator poles of the five-phase SRM shown in Figures 6-11.
  • Figure 13 is a circuit diagram of the power circuit driving the five-phase SRM shown in Figures 6-11.
  • Figure 14 is a timing chart showing waveforms of the phase currents of the five-phase SRM shown in Figures 6-11.
  • Figure 15 is a schematic view showing relative positions between the rotor and the stator of a five-phase SRM in a generator mode.
  • Figure 16 is a timing chart showing waveforms of phase inductances and phase currents of the five-phase SRM shown in Figure 15.
  • Figure 17 is another circuit diagram of the power circuit driving the five-phase SRM shown in Figures 6-11.
  • Figure 18 is another circuit diagram of the power circuit driving the five-phase SRM shown in Figures 6-11.
  • Figure 19 is another circuit diagram of the power circuit driving the five-phase SRM shown in Figures 6-11.
  • Figure 20 is a timing chart showing waveforms of phase inductances and phase currents of the five-phase SRM with a DC-to-DC converter shown in Figure 17 and Figure 19.
  • Figure 21 is an axial section view of an in-wheel motor employing the five-phase SRM shown in Figures 6-11.
  • Figure 22 is a part of a radial section view of the in-wheel motor shown in Figures 6-11.
  • Figure 23 is a schematic view showing relative positions between stator poles and rotor poles of the five-phase SRM with permanent magnets accommodated in rotor pole gaps.
  • Figure 24 is another schematic view showing relative positions between the stator poles and the rotor poles of the five-phase SRM with the permanent magnets accommodated in the rotor pole gaps.
  • Figure 25 is a circuit diagram showing a five-phase inverter with five half-bridges, which drives the five-phase hybrid SRM shown in Figures 23-24.
  • Figure 26 is a timing chart showing waveforms of phase inductances and phase currents of the five-phase hybrid SRM shown in Figures 23-24.
  • Figure 27 is a radial cross section of another five-phase hybrid SRM.
  • Figure 28 is a schematic view showing relative positions between stator poles and rotor poles of the five-phase hybrid SRM shown in Figure 27.
  • Figure 29 is another schematic view showing relative positions between the stator poles and the rotor poles of the five-phase hybrid SRM shown in Figure 27.
  • Figure 30 is a radial cross section of a five-phase SRG with DC field windings wound on the stator poles.
  • Figure 31 is a schematic view showing relative positions between stator poles and rotor poles of the five-phase SRG shown in Figure 30.
  • Figure 32 is another schematic view showing relative positions between the stator poles and the rotor poles of the five-phase SRG shown in Figure 30.
  • Figure 33 is a timing chart showing waveforms of generated phase voltages of the five-phase SRG shown in Figures 30-32.
  • Figure 34 is a circuit diagram showing a five-phase rectifier and a field current controller of the five-phase SRG shown in Figures 30-32.
  • Figure 35 is a radial section view showing the Hedershot's five-phase SRM of which stator poles has DC field windings.
  • Figure 36 is a radial section view showing the five-phase SRM with a short-cut rotor winding.
  • Figure 37 is a schematic view showing relative positions between stator poles and rotor poles of the five-phase SRM with the short-cut rotor winding, which is shown in Figure 36.
  • Figure 38 is another schematic view showing relative positions between stator poles and rotor poles of the five-phase SRM with the short-cut rotor winding, which is shown in Figure 36.
  • Figure 39 is a circuit diagram showing a power circuit driving the three-phase SRM, which has a capacitor accumulating the residual magnetic energy.
  • Figure 40 is a timing chart showing the RME-transmission with the capacitor shown in Figure 39.
  • Figure 41 is a circuit diagram showing another power circuit driving the three-phase SRM, which has a capacitor accumulating a residual magnetic energy.
  • Figure 42 is a radial section view of a three-phase SRM with permanent magnets in rotor pole gaps.
  • Figure 43 is another radial section view of the three-phase SRM with the permanent magnets in the rotor pole gaps.
  • Figure 44 is another radial section view of the three-phase SRM with the permanent magnets in the rotor pole gaps.
  • Figure 45 is a timing chart showing the phase inductances and the phase currents of the three-phase SRM shown in Figure 42-44.
  • Figure 46 is a schematic view showing relative positions between stator poles and rotor poles of a three-phase SRM with a short-cut rotor winding.
  • Figure 47 is another schematic view showing relative positions between the stator poles and the rotor poles of the three-phase SRM with a short-cut rotor winding.
  • Figure 48 is a timing chart showing the phase inductances and phase currents of the three-phase SRM shown in Figure 46-47.
  • Figure 49 is a partial cross section of the arranged in-wheel motor shown in Figure 22.
  • a radial gap type SRM which is including the SRG or the SRMG, of the invention are explained with reference to drawings.
  • the invention should not be limited to the radial gap type, but it can be used to any type of SRMs.
  • Figures 6-10 shows a five-phase SRM with the uneven rotor pole gaps.
  • the SRM driving a turbo charger has a large rotor pole gap and a small rotor pole gap in turn.
  • Figures 6-10 show a schematic radial cross-section each.
  • the SRM has a stator 9 and a rotor 10 facing each other in the radial direction.
  • the stator 9 fixed to a housing of the turbo charger has a stator core consisting two sets of five stator poles A-E. Each pitch between adjacent two stator poles is equal in the circumferential direction.
  • Each of stator poles A-E projects radial inward from a cylinder-shaped core back as a yoke.
  • the stator core is made of soft iron sheets laminated to the axial direction.
  • the stator 9 has two sets of five phase windings 401-405, which are wound on the stator poles A-E separately.
  • the rotor 10 has four U-shaped rotor poles fixed on an outer circumferential surface of a non-magnetic rotor cylinder 10A made from aluminum by means of the die-casting method.
  • a rotating axis 11 supported rotatably by the housing is inserted to the rotor cylinder 10A.
  • the U-shaped rotor poles made of soft iron sheets laminated to the axial direction are arranged to the circumferential direction with an equal pitch.
  • the U-shaped rotor pole has two rotor poles projecting radial outward. After all, four U-shaped rotor poles have eight rotor poles 1-8.
  • a small rotor gap 12 is formed between two rotor poles of each one of the U-shaped rotor poles.
  • a large rotor gap 13 is formed between two U-shaped rotor poles being adjacent each other.
  • the small rotor gap 12 has an essentially equal width to the stator pole in the circumferential direction.
  • the small rotor gaps 12 have an essentially equal width to a slot width in the circumferential direction between two stator poles being adjacent each other.
  • the large rotor gap 13 has an essentially equal width to a sum of one stator pole width and one slot width, which constitutes one stator pole pitch.
  • the rotor pole has an essentially equal width to the stator pole in the circumferential.
  • the weight of the rotor 10 becomes almost half in comparison with the Hendershot' SRM having the eight rotor poles connected by a common yoke. Furthermore, a length of a flux passage in the rotor core becomes short.
  • FIG. 6-10 shows a state of the rotor at each rotating angle.
  • Figure 11 shows a timing chart showing the current waveforms of the five-phase windings 401-405.
  • two pairs of the stator poles D and E are magnetized from the time point t3 to the time point t4.
  • Four rotor poles 1, 2, 5 and 6 are pulled to the CW direction.
  • two pairs of the stator poles B and C are magnetized from the time point t4 to the time point t5.
  • Four rotor poles 3, 4, 7 and 8 are pulled to the CW direction
  • real lines La-Le show schematic waveforms of inductances of the phase winding 401-405.
  • Broken lines schematically show waveforms of five phase voltages Va-Ve and five phase currents Iab, Icb, Icd, Ied and Iae.
  • one cycle which is the electric angle 360 degrees divided to an inductance-increasing period Ti, a peak period Tp, an inductance-decreasing period Td and a bottom period Td.
  • An inductance of the phase windings 401-405 becomes the largest in the peak period Tp.
  • the inductance becomes the smallest in the bottom period Tb.
  • the inductance increases in the inductance-increasing period Ti.
  • the inductance decreases in the inductance-decreasing period Td.
  • Each phase current rises up in the bottom period Tb.
  • Each phase current falls down in the peak period Tp.
  • Each phase current is kept to a almost predetermined constant value by means of a PWM-switching in the inductance-increasing period Ti.
  • Each phase current is zero in the inductance-decreasing period Td.
  • the feature of the five-phase SRM shown in Figure 6-11 is described.
  • the five-phase SRM has four pairs of U-shaped rotor poles and ten stator poles.
  • the five-phase SRM can have a set of six pairs of U-shaped rotor poles and fifteen stator poles, a set of eight pairs of U-shaped rotor poles and twenty stator poles.
  • the SRM is similar to the Hendershot' SRM shown in Figure 1.
  • the rotor of the SRM can decrease a weight of the rotor largely in comparison with the Hendershot' SRM by employing the U-shaped rotor poles.
  • the motor turbo charger with the SRM shown in Figure 6 can be accelerated very quickly with small power consumption.
  • stator poles A-E Magnetized polarities of the stator poles A-E are shown in Figures 6-10 and Figure 12.
  • the stator poles A and D are magnetized to the N pole.
  • the stator poles B and C are magnetized to the S pole.
  • the stator pole E is magnetized to the S pole in the period from the time point t3 to the time point t4.
  • the stator pole E is magnetized to the N pole in the period from the time point t5 to the time point t1.
  • the driving circuit has a five-phase inverter 902 and a voltage-changing circuit 901.
  • the voltage-changing circuit 901 consists of a series capacitor 103 and a parallel switch 102, which are connected in parallel.
  • a battery 900 applies a battery voltage to the inverter 902 through the voltage-changing circuit 901.
  • the inverter 902 consists of six transistors 201-206, six freewheeling diodes 301-306.
  • the inverter 902 applies the five phase voltages to the five phase windings 401-405 wound around the stator poles A-E of the five-phase SRM separately.
  • the phase windings 401-405 constitute a star-connection as shown in Figure 12. One ends of the phase windings 401-405 are connected to neutral point N.
  • phase windings 401, 403 and 405 are connected to the high potential line 104 through transistors 201, 203 and 205, which are upper switches.
  • the other ends of the phase windings 402, 404 and 405 are connected to the low potential line 105 through transistors 202, 204 and 206, which are lower switches.
  • the other ends of the phase windings 401, 403 and 405 are connected to the low potential line 105 through freewheeling diodes 301, 303 and 305 separately.
  • the other ends of phase windings 402, 404 and 405 are connected to the high potential line 104 through freewheeling diodes 302, 304 and 306 separately. In the other words, only the other end of the phase windings 405 is connected to the lines 104 and 105 through a half-bridge.
  • transistors 201 and 202 are turned on. Phase current Iab flows through phase windings 401 and 402. Stator poles A and B are magnetized. A tail current flows through freewheeling diodes 301 and 302 after turning-off of transistors 201 and 202.
  • transistors 202 and 203 are turned on. Phase current Icb flows through phase windings 403 and 402. Stator poles C and B are magnetized. After turning-off of transistors 202 and 203, the tail current flows back through freewheeling diodes 303 and 302.
  • transistors 203 and 204 are turned on. Phase current Icd flows through phase windings 403 and 404. Stator poles C and D are magnetized. After turning-off of transistors 203 and 204, the tail current flows back through freewheeling diodes 303 and 304.
  • transistors 204 and 205 are turned on. Phase current Ied flows through phase windings 405 and 404. Stator poles E and D are magnetized. After turning-off of transistors 204 and 205, the tail current flows back through the freewheeling diodes 305 and 304.
  • transistors 201 and 206 are turned on. Phase current Iae flows through phase windings 401 and 405. Stator poles A and E are magnetized. After turning-off of transistors 201 and 206, the tail current flows back through freewheeling diodes 301 and 306. Only phase current through phase windings 405 is an alternative current. Consequently, the five-phase SRM shown in Figures 6-11 are driven by the simple inverter 902.
  • the voltage-changing circuit 901 is explained referring to Figures 13-14. For example, at the time point t3, transistors 201 and 202 are turned off, and transistors 201 and 202 are turned off. In a period T1 from t3 to t3', the freewheeling current component of the phase current Iab flows back, and the rising-up component of the phase current Ied increases. As the result, the alternative current is supplied from the voltage-changing circuit 901 to the inverter 902 in the period T1. The switch 102 of the voltage-changing circuit 901 is turned off in the period T1. The capacitor 103 is charged by the freewheeling current component of the phase current Iab in the first half of the period T1.
  • a DC-link voltage Vx of the line 104 increases.
  • the capacitor 103 is discharged by the rising-up current component of the phase current Ied in the second half of the period T1. Accordingly, a DC-link voltage Vx of the line 104 decreases.
  • the tail current component which is the freewheeling current component, of the phase current Iab falls down quickly by means of increasing of the line 104. Furthermore, the rising-up current component of the phase current Ied increases quickly by means of increasing of the line 104. After all, the period T1 becomes very short.
  • the diode of the transistor 102 turns on after the line voltage 104 is smaller than the voltage Vb of the battery 900. The transistor 102 is turned on, if the line voltage Vx is smaller than the battery voltage Vb. The transistor 102 is turned off, if the line voltage Vx is larger than the battery voltage Vb.
  • the capacitor 103 can have smaller capacitance than the conventional smoothing capacitor connected to the battery in parallel, because the line voltage Vx is increased in order to accelerate the falling-down of the tail current.
  • Figure 15 shows relative pole-positions between the rotor poles and the stator poles at each time point t1-t5 shown in Figure 16.
  • Figure 16 is a timing chart showing inductances and phase currents, which are consist of a exciting current IE and a generating current IG each, of five phase windings 401-405.
  • Rotor 10 is rotating from the left direction to the right direction on Figure 16.
  • Transistors 201 and 206 are turn on.
  • the exciting current IE of a phase current Iae starts to flow through phase windings 401 and 405.
  • Transistors 201 and 206 are turn off, when the phase current Iae reached at a predetermined value which is decided a received instruction value of the generation current. Then, the inductances La and Le of the phase windings 401 and 405 are decreased.
  • the transistor 102 is turned on in the inductance-decreasing period Td.
  • the transistor 102 is turned off in the inductance-increasing period Ti, the peak period Tp and the bottom period Td.
  • the capacitor 103 shown in Figure 13 is charged by the freewheeling current component in the bottom period Tb.
  • the capacitor 103 is discharged by the rising-up current component in the peak period Tp.
  • phase current Icd charges battery 900 through the transistor 102.
  • one pair of rotor poles is facing stator poles A and B. Thu transistors 201 and 202 are turn on. The exciting current IE of a phase current Iab starts to flow through phase windings 401 and 402. Transistors 201 and 202 are turn off, when the phase current Iab reached at the predetermined value. Then, inductances La and Lb of phase windings 401 and 402 are decrease. One pair of rotor poles removes stator poles A and B. Generating current IG of the phase current Iab flows through freewheeling diodes 301 and 302. Battery 900 is charged with the generating current IG of the phase current Iab.
  • one pair of rotor poles is facing stator poles E and D.
  • Transistors 204 and 205 are turn on.
  • the exciting current IE of a phase current Ied starts to flow through phase windings 405 and 404.
  • Transistors 204 and 205 are turn off, when the exciting current IE of the phase current Ied reached at the predetermined value.
  • inductances Le of phase windings 405 and inductances Ld of phase windings 404 start to decrease.
  • One pair of rotor poles removes stator poles D and E.
  • Generating current IG of the phase current Ied flows through freewheeling diodes 305 and 304. Battery 900 is charged.
  • one pair of rotor poles is facing stator poles C and B.
  • Transistors 203 and 202 are turn on.
  • the exciting current IE of a phase current Icb starts to flow through phase windings 403 and 402.
  • Transistors 203 and 202 are turn off, when phase current Icb reached at the predetermined value.
  • inductance Lc of phase winding 403 and inductance L1 of phase winding 402 are decreased.
  • One pair of rotor poles removes stator poles B and C.
  • the generating current IG of the phase current Icb flows through freewheeling diodes 303 and 302. Battery 900 is charged.
  • real lines show inductances La-Le of the phase windings 401-405.
  • Broken lines show phase currents flowing through the phase windings 401-405.
  • Triangle-shaped areas with oblique lines show the phase currents supplied from the inverter 902 to SRG.
  • the voltage-changing circuits 901 shown in Figure 17 has a bi-directional DC-to-DC converter 901A consisting of a reactor 100 and transistors 101 and 102.
  • the chopper type DC-to-DC converter 901A is connected to the capacitor 103 in parallel.
  • the DC-to-DC converter 901A essentially applies the boost voltage to the line 104 in the inductance-increasing Ti period in the motor operation.
  • the DC-to-DC converter 901A essentially applies the reduced voltage to the battery 900 in the inductance-decreasing period Td in the generator operation. Explanation of the PWM operation of the DC-to-DC converter 901A is abbreviated.
  • the voltage-changing circuit 901 shown in Figure 17 is realized by adding the reactor 100 and the transistor 101 to the voltage-changing circuits 901 shown in Figure 13.
  • the voltage-changing circuit 901 shown in Figure 18 consists of only the capacitor 103.
  • a connection point Y between the capacitor 103 and the battery 900 is connected to the upper switch 401, 403 and 405 through the lower freewheeling diodes 301, 303 and 305.
  • the capacitor 103 is connected to the positive terminal of the battery 900.
  • An operation of the driving circuit shown in Figure 18 is explained hereinafter.
  • the transistors 201 and 202 are turned off, the tail current component of the Iab flows through the diodes 301 and 302.
  • the tail current component charges the capacitor 103.
  • the capacitor 103 is discharged through the turning-on transistors 204 and 205. After discharging of the capacitor 103, the battery 900 supplies the current through the diode 305.
  • the voltage-changing circuit 901 shown in Figure 18 is very simple.
  • the capacitor 103 can be connected to the negative terminal of the battery 900.
  • the other end of the capacitor 103 is connected to the upper freewheeling dio
  • the driving circuit shown in Figure 19 is same as the driving circuit shown in Figure 17.
  • the voltage-changing circuit 901 shown in Figure 19 has the capacitor 103 and the DC-to-DC converter 901A.
  • the operation of the motor-driving circuit is essentially same as Figures 17-18.
  • the DC-to-DC converter 901A is PWM-switched in order to control the DC-link voltage Vx in order to keep the constant phase current, for example Iab, in the inductance-increasing period Ti. Furthermore, the DC-to-DC converter 901 applies higher value of the DC-link voltage Vx in the bottom period Tb than the value of the DC-link voltage Vx in the inductance-increasing period Ti. As the result, each of the phase currents can rise up quickly in the bottom period Tb, and the phase current can fall down quickly in the peak period Tp.
  • the DC-link voltage Vx is decreased in a predetermined rate in the inductance-increasing period Ti in order to keep the constant phase current. After all, the DC-to-DC converter 901 applies the DC-link voltage Vx having the waveform, which rises up in the bottom period and decreases gradually. In this operation, the inverter cost becomes low, because the transistors 201-206 does not need to have a low on-resistance value.
  • Figure 21 shows a radial cross-section of an outer rotor type in-wheel motor.
  • Figure 22 shows an axial cross-section of a part of the in-wheel motor.
  • the in-wheel motor shown in Figures 21-22 has the five-phase SRM with uneven rotor pole gaps, which is explained in the embodiment 1.
  • the in-wheel SRM of this embodiment has the outer rotor structure.
  • the in-wheel SRM has an axis 1000, a stator 1001 and a rotor 1002.
  • the stator 1001 is fixed on the axis 1000 fixed to a vehicle, which is not illustrated.
  • the stator 1001 has a supporting disc 1003, a stator core 1004 and the stator winding 1005.
  • the cylinder-shaped stator core 1004 are fixed on an outer circumferential surface of the supporting disc 1003 made from aluminum.
  • the stator winding 1005 consists of five phase windings 401-405 wound on the stator poles A-E separately.
  • the stator core 1004 has four sets of the stator poles A-E. Each of stator poles projects radial outward from a cylinder-shaped core back, the yoke, of the stator core 1004.
  • the rotor 1002 has eight U-shaped rotor poles 1006 fixed on an inner circumferential surface of rotor discs 1007-1008 made from aluminum by means of the die-casting method.
  • the U-shaped rotor poles 1006 are fixed on an inner circumferential surface of the rotor discs 1007-1008.
  • Each of U-shaped rotor poles 1006 has adjacent two rotor poles projecting radial inward.
  • the rotor discs 1007-1008 are fixed to a wheel of the vehicle, which is not illustrated.
  • Each of the U-shaped rotor poles 1006 has a concave portions 1009 each.
  • the rotor discs 1007-1008 have the projecting portions 1010 buried in the concave portions 1009.
  • the projecting portions 1010 hold the U-shaped rotor poles 1006 strongly.
  • the in-wheel SRM of the embodiment 2 can decrease the weight of the rotor 1002.
  • the acceleration of the vehicle is improved.
  • the driver's feeling is improved by decreasing of the weight under the wheel spring...
  • Each of U-shaped rotor poles 1006 can be made by a wire-wound core 3000 as shown in Figure 49.
  • the wire-wound core 3000 is made by means of winding of an iron-wire around a resin member 3001. The production method is explained. First, the iron wire is wound around the resin member 3001. Next, the wound iron wire and the resin member 3001 are cut. A pair of cut surfaces of the wound wire makes a pair of magnet pole surfaces of the U-shaped rotor core 3000.
  • the wound wire is fixed with resin material. This wire-wound core decreases the eddy current loss.
  • the rotor pole, which is the salient, of the SRM does not have trims projecting to the circumferential direction. As the result, the winding of the iron wire is not difficult.
  • An amorphous iron wire can employed.
  • FIG. 23-26 shows a five-phase SRM having the uneven rotor pole pitches and permanent magnets.
  • Figures 23-24 show relative rotor positions between the U-shaped rotor poles and the stator poles.
  • the SRM in Figures 23-24 is essentially same as the SRM explained in the embodiment 1.
  • a difference between the embodiments 1 and 3 is that the SRM of the embodiment 3 has the permanent magnets 21-22 as shown in Figures 23-24.
  • Each surface of the permanent magnets 21 facing the stator poles A-E has S pole each.
  • Each surface of the permanent magnets 22 facing the stator poles A-E has N pole each.
  • the stator core 9 has two groups of the five stator poles A-E.
  • the rotor core 10 has the eight rotor poles 1-8.
  • the narrow rotor pole gaps 12 are disposed between two rotor poles of one each U-shaped rotor pole.
  • the wide rotor pole gaps 13 are disposed between adjacent two U-shaped rotor poles.
  • Four permanent magnets 21 are fixed to the narrow rotor pole gaps 12. Outer surfaces of the permanent magnets 21 are magnetized to S poles each.
  • Four permanent magnets 22 are fixed to the wide rotor pole gaps 13. Outer surfaces of permanent magnets 22 are magnetized to N poles each.
  • Circumferential widths of the permanent magnets 21 and 22 are mostly equal to a circumferential width of the stator poles A-E. Each left side surface of the permanent magnets 22 comes into contact with each right side surface of the stator poles A-E.
  • the SRM shown in Figure 23-24 is called the hybrid five-phase SRM.
  • a preferred motor operation of the hybrid five-phase SRM is explained.
  • a pair of adjacent stator poles C and D is magnetized. Adjacent rotor poles 1 and 2 and adjacent rotor poles 5 and 6 are pulled to the CW direction by the stator poles C and D. Furthermore, the stator poles C and D give repulsion forces to two pairs of permanent magnets. The motor torque is increased.
  • a pair of adjacent stator poles A and B is magnetized. Adjacent rotor poles 3 and 4 and adjacent rotor poles 7 and 8 are pulled to the CW direction by the stator poles A and B. Furthermore, the stator poles A and B give repulsion forces to two pairs of permanent magnets.
  • a pair of adjacent two stator poles D and E are magnetized. Adjacent rotor poles 1 and 2 and adjacent rotor poles 5 and 6 are pulled to the CW direction by the stator poles D and E. Furthermore, the stator poles D and E give repulsion forces to two pairs of permanent magnets.
  • a pair of adjacent stator poles B and C is magnetized. Adjacent rotor poles 3 and 4 and adjacent rotor poles 7 and 8 are pulled to the CW direction by the stator poles B and C. Furthermore, the stator poles B and C give repulsion forces to two pairs of permanent magnets.
  • stator poles E and A In a period from the time point t5 to the time point t1, a pair of adjacent stator poles E and A are magnetized. Adjacent rotor poles 1 and 2 and adjacent rotor poles 5 and 6 are pulled to the CW direction by the stator poles E and A. Furthermore, the stator poles E and A gives repulsion forces to two pairs of permanent magnets.
  • FIG. 23-26 The generator operation of one hybrid five-phase SRM is explained referring to Figures 23-26.
  • the generating operation is fundamentally same as the five-phase SRM of the embodiment 1.
  • alternative phase currents are supplied to the stator windings of the hybrid five-phase SRM shown in Figures 23-24.
  • Figure 25 shows the inverter 902B driving the hybrid five-phase SRM shown in Figures 23-24.
  • the inverter 902B consist of five half bridges.
  • Figure 26 shows a timing chart showing the waveforms of the phase currents and inductances of the phase windings shown in Figures 23-24.
  • the hybrid SRM shown in Figures 23-24 has a special advantage explained hereinafter.
  • the Hendershot' SRM shown in Figure 1 has a relatively large value of the smallest inductance Lmin as explained before.
  • the hybrid SRM shown in Figures 23-24 can have smaller value of the smallest inductance Lmin than the Hendershot' SRM, because magnet field directions of the permanent magnets 21 and 22 are almost opposite to the magnet field directions excited by the phase current at the side surfaces of the rotor poles.
  • the flux passages LY2 shown by real lines are formed through the side surfaces of the rotor poles. As the results, the smallest inductance Lmin is decreased by the permanent magnets 21 and 22, and the torque is increased.
  • FIG. 27 Another hybrid five-phase SRM is explained referring to Figures 27-29.
  • the permanent magnet 22 has a same size as the large rotor pole gap 13.
  • the outer surface of the permanent magnet 22 has the magnetic polarity N.
  • the motor operation of the SRM shown in Figure 27 is shown in Figures 28-29.
  • Figures 28-29 are essentially same as Figures 23-24.
  • the hybrid SRM shown in Figure 27 can use the inverter shown in Figure 25 in accordance with the timing chart shown in Figure 26.
  • the SRG shown in Figure 30 is preferable as the alternator of the vehicle.
  • Figure 30 shows a radial cross-section of the five-phase SRG, which is essential same as the five-phase SRM shown in Figure 7 except DC windings 51-55 and 51-55, which are wound the stator poles A-E and A'-E'.
  • Figures 31-32 show relative rotor positions between the stator poles and the U-shaped rotor poles.
  • Figures 33 is a timing chart showing waveforms of the phase currents.
  • Figure 34 shows a circuit of the SRG.
  • the SRG capable of employing as the alternator of the vehicle can be driven as the SRM. For example, A DC field current If supplied to the DC windings 51-55 and 51-55 becomes zero while the motor operation is executed.
  • the stator poles A-E and A'-E' are magnetized to either one of the N pole and the S pole by the DC field current If supplied to the DC windings 51-55 and 51'-55', which are connected to series as shown in Figure 34.
  • the Stator poles A, C, E', B' and D' are magnetized to the N pole, and the stator poles B, D, A', C' and E' are magnetized to the S pole.
  • Figure 34 shows a five-phase rectifier 60 and a field current controller.
  • the rectifier 60 consists of a five-phase full bridge rectifying circuit with ten diodes D1-D10.
  • the DC field current If supplied from battery 900 to the DC windings 51-55 and 51'-55' is controlled by a field current-controlling transistor 910.
  • a freewheeling diode 911 is connected to the series-connected DC windings 51-55 and 51'-55' in parallel.
  • the duty ratio of the transistor 910 By controlling the duty ratio of the transistor 910, the five-phase generating phase voltages VA-VE and VA'-VE' are controlled.
  • the DC windings 51-55 and 51'-55' have a high generating voltage each.
  • the five-phase SRG shown in Figure 30 the magnet flux of a first half and magnet flux of a second half of the DC windings 51-55 and 51'-55' have the opposite polarity each other.
  • the magnet flux in the stator poles 402, 403, 402' and 403 are increased.
  • the magnet flux in the stator poles 404, 405, 404' and 405 are decreased.
  • the magnet flux in the stator poles 401 and 401' are constant. Accordingly, the sum of the induced voltage of the DC windings 51-55 and 51'-55' becomes essentially zero.
  • the important advantage of the SRM shown in Figure 30 is that the U-shaped rotor poles separated each other decrease a small inductance value to the phase windings 401-405 and 401'-405', which is already explained. As the result, the generating voltage of the phase windings 401-405 and 401'-405' become large.
  • Figure 35 shows the Hendershot's five-phase SRM having the DC windings 401-405 and 401' and 405'.
  • Broken lines show the leakage magnet flux LY1.
  • the leakage magnet flux LY1 flow between adjacent two U-shaped rotor poles. As the result, changing of the magnet flux is reduced by the leakage magnet flux LY1.
  • the leakage magnet flux LY1 becomes almost zero by employing the U-shaped rotor poles shown in Figure 30.
  • Embodiment 5 is explained referring to Figures 36-38.
  • Figure 36 schematically shows a radial section view showing a five-phase SRM with a short-circuit rotor winding 200.
  • Figures 37-38 shows relative positions between the stator poles and the U-shaped rotor poles of the five-phase SRM.
  • the relative positions between the stator poles and the U-shaped rotor poles shown in Figures 37-38 is essentially same as the relative positions between the stator poles and the U-shaped rotor poles shown in Figures 23-24.
  • the SRM shown in Figure 36 can employ the five-phase inverter shown in Figure 25, which is driving in accordance with the timing chart shown in Figure 26.
  • the corrugate-shaped short-circuit rotor winding 200 is accommodated in each rotor pole gaps 12-13.
  • Each of the narrow rotor pole gaps 12 is formed between two rotor poles of each of U-shaped rotor poles.
  • Each of the wide rotor pole gaps 13 is formed between two U-shaped rotor poles.
  • a short-circuit current of the rotor winding 200 has four pairs of a going conductor and a coming conductor connected alternately each other.
  • the going conductors 201, 203, 205 and 207 are accommodated in the narrow rotor pole gaps 12.
  • the coming conductors 202, 204, 206 and 208 are accommodated in the wide rotor pole gaps 13.
  • Each of the conductors 201-208 are connected with rear lines 203 and front lines 204, which are extending to the circumferential direction.
  • the magnet flux between stator poles A and B which is illustrated with real lines, are increased.
  • the magnet flux between stator poles C and D which is illustrated with broken lines, is decreased.
  • the decreasing flux between stator poles C and D induces the secondary voltage V2 on the rotor winding 200.
  • the increasing flux between stator poles A and B induce the secondary voltage V2' on the rotor winding 200.
  • the induced voltage V2 is larger than the induced voltage V2', because the inductance Lb of the phase windings 403-403 on the stator poles C and D is larger than the inductance Ls of the phase windings 401-402 on the stator poles A and B.
  • the short-circuit current I2 the induced secondary current
  • the magnetic residual energy of the stator windings 403-404 is used in order to rise up the phase currents of the stator windings 401-402.
  • the magnetic residual energy of the stator windings 401-402 is used in order to rise up the phase currents of the stator windings 404-405.
  • the magnetic residual energy of the stator windings 404-405 is used in order to rise up the phase currents of the stator windings 402-403.
  • the magnetic residual energy of the stator windings 402-403 is used in order to rise up the phase currents of the stator windings 401 and 405.
  • the magnetic residual energy of the stator windings 401 and 405 is used in order to rise up the phase currents of the stator windings 403 and 404.
  • the transmitting of the residual magnetic energy by the short-circuit rotor winding 200 decreases the size and the cost of the motor-driving circuit. Furthermore, the resistance power loss generated for transmitting of the residual magnetic energy is also decreased, because the rotor winding 200 has a very small resistance value and does not have a switching element and an electric parts such like a reactor or a capacitor. By the smoothing transmitting of the residual magnetic energy, the vibration and the noise sound are reduced, too.
  • the short-cut secondary winding 200 which has the odd conductors in the narrow rotor pole gaps and the even conductors in the wide rotor pole gaps, has another advantage that the phase current-falling-down period and the phase-current-rising-up period becomes short. As the result, the motor torque is increased and the torque ripples are decreased.
  • Figure 39 shows a conventional asynchronous unipolar three-phase inverter 902, called the asynchronous converter, for driving a conventional three-phase SRM. Structure and operation of the conventional three-phase SRM, which has six stator poles and four rotor poles typically, is already well-known.
  • the inverter 902 shown in Figure 39 further has a voltage-changing circuit 901 consisting a capacitor 74 connected to a battery 75 to series. In the other words, the capacitor connected to the battery to series is used in the motor-driving circuit for the three-phase SRM.
  • the three-phase SRM has three phase windings 10U, 10V and 10W.
  • the capacitor 74 accelerates to change the rising-up phase current and the falling-down phase current.
  • the inverter 902 has upper switches 11-13, lower switches 14-16 and freewheeling diodes D1-D6.
  • the capacitor 74 and the battery 75 which are connected to series, supply the current to the inverter 902 through a high-potential line 100 and a ground line 200.
  • the connecting point X between the capacitor 74 and the battery 75 is connected to anodes of the lower freewheeling diodes D4, D5 and D6 through the ground line 300.
  • the capacitor 74 with a relatively small capacitance accumulates the residual magnetic energy of the phase windings 10U, 10V and 10W. For example, the switches 11 and 14 are turned off, the residual magnetic energy of the U-phase winding 10U charges the capacitor 74 through the diodes D1 and D4 as shown in Figure 40.
  • FIG. 40 shows a timing chart showing the transmitting of the residual magnetic energy between each phase windings.
  • a U-phase current Iu is supplied to the U-phase winding 10U with an inductance Lu.
  • a V-phase current Iv is supplied to the V-phase winding 10V with an inductance Lv.
  • a W-phase current Iw is supplied to the W-phase winding 10W with an inductance Lw.
  • the capacitor 74 which is connected to the battery 75 to series, storages the residual magnetic energy RME for a predetermined period. After discharging of the capacitor 74, the battery 75 supplies the phase current to the phase winding through the freewheeling diodes.
  • the voltage-changing circuit 901 consisting the capacitor 74 can be employed another asynchronous unipolar inverter, for example the MIRROR converter shown in Figure 41.
  • the common upper switch 11 shown in Figure 41 is turned on for a period when either one of the switches 11-13 shown in Figure 39 is turned on. Accordingly, the MIRROR converter with the capacitor 74 can increase and decrease the phase current rapidly.
  • Embodiment 7 is explained referring to Figures 42-45.
  • Figures 42-44 show cross sections of the conventional three-phase SRM with six stator poles and four rotor poles.
  • the SRM shown in Figures 42-44 further has a plural pairs of permanent magnets 6A and 6B inserted in the rotor pole gap between adjacent two rotor poles.
  • the SRM shown in Figures 42-44 can produce both of the reluctance torque and the magnet torque such like the SRM shown in Figures 23-24.
  • the rotor 2 press-fixed to axis 5 has four rotor poles 20 and four pairs of the permanent magnets 6A and 6B.
  • the stator 1 has six stator poles 31-36 on which the phase windings 41-46 are wound separately.
  • Each of the permanent magnets 6A has the S pole on the radial outer surface.
  • Each of the magnets 6B has the N pole on the radial outer surface.
  • Each permanent magnet 6A is fixed to the anti-clockwise side in each concave portion, which is each rotor pole gap, of the rotor 2 each.
  • Each of the permanent magnet 6B is fixed to the clockwise side in the concave portion of the rotor 2. Magnets 6A and 6B fixed in one rotor pole gap can be made of one permanent magnet.
  • FIG. 42 Rotation of the hybrid SRM shown in Figures 42-44 is explained.
  • a V-phase current is supplied to the V-phase windings 42 and 45
  • a W-phase current is supplied to the W-phase windings 43 and 46.
  • the V-phase stator poles 32 and 35 produce the reluctance torque and the magnetic repulsion torque toward the counterclockwise direction.
  • the W-phase stator poles 33 and 36 produce the magnetic repulsion torque and the magnetic pulling torque toward the counterclockwise direction.
  • the rotor 2 turns to a position shown on Figure 43.
  • a U-phase current is supplied to the U-phase windings 41 and 44, and the W-phase current is supplied to the W-phase windings 43 and 46.
  • the U-phase stator poles 31 and 34 produce the magnetic repulsion torque and the magnetic pulling torque toward the counterclockwise direction.
  • the W-phase stator poles 33 and 36 produce the reluctance torque and the magnetic repulsion torque toward the counterclockwise direction. As a result, rotor 2 turns to the position shown on Figure 44.
  • the U-phase current is supplied to the U-phase windings 41 and 44, and the V-phase current is supplied to the V-phase windings 42 and 45.
  • the U-phase stator poles 31 and 34 produce the reluctance torque and the magnetic repulsion torque toward the counterclockwise direction.
  • the V-phase stator poles 32 and 35 produce the magnetic repulsion torque and the magnetic pulling torque in a counterclockwise direction.
  • Rotor 2 turns to the position shown on Figure 42.
  • the inductances Lu, Lv and Lw of the three-phase windings 41-46, magnetic flux Fu, Fv and Fw and the three-phase currents Iu, Iv and Iw are shown in Figure 45.
  • the U-phase windings 41 and 44 have the inductance Lu.
  • the V-phase windings 42 and 45 have the inductance Lv.
  • the W-phase windings 43 and 46 have the inductance Lw.
  • Each of the inductance Lu, Lv and Lw changes in accordance with the rotation of the rotor poles 20 of the rotor 2.
  • the three-phase currents Iu, Iv and Iw can be supplied to the three-phase windings 41-46 connected with the known Y-connection.
  • Embodiment 8 is explained referring to Figures 46-48.
  • Figures 46-47 schematically show a radial section view showing a three-phase SRM with short-circuit rotor winding 2000.
  • Figure 48 is a timing chart showing waveforms of the inductances, the phase currents and the short-circuit current I2.
  • the short-circuit rotor winding 2000 has a going conductor 201 and a coming conductor 202.
  • the going conductor 201 extending to the axial direction is accommodated in the rotor pole gap 2004 between the rotor poles 20D and 20A.
  • the coming conductor 202 extending to the axial direction is accommodated in the rotor pole gap 2002 between the rotor poles 20B and 20C.
  • the odd rotor pole gaps 2001 and 2003 does not accommodate any conductor of the short-circuit rotor winding 2000. If one of odd rotor pole gaps 2001 and 2003 accommodates the conductor, the conductor in one of odd rotor pole gaps 2001 and 2003 must be connected to the other one of the odd rotor pole gaps 2001 and 2003 to series.
  • the stator 1 has a stator core 4 having six stator poles 41-46 connected magnetically with a back core 40 each other.
  • the stator 1 has six phase windings wound around the stator poles 41-46 separately.
  • the rotor 2 has the four rotor poles 20.
  • the short circuit rotor winding 2000 constitutes a short circuit with one turn.
  • a U-phase current IU is supplied to the U-phase windings on the stator poles 43 and 46.
  • a V-phase current IV is supplied to the V-phase windings on the stator poles 42 and 45.
  • a W-phase current IW is supplied to the W-phase windings 53 on the stator poles 41 and 44.
  • the above SRM has the same structure and the same operation as the conventional three-phase SRM except the short circuit rotor winding 2000.
  • the U-phase current Iu supplied to the U-phase windings is turned off.
  • the residual magnetic energy accumulated in U-phase windings induced the secondary voltage to the short circuit windings 2000.
  • the induced U-phase voltage is larger than the induced V-phase voltage. Accordingly, the secondary current I2 flows through the short circuit 2000.
  • the secondary current I2 induced by the decreasing of the U-phase current increases the V-phase magnetic flux in the stator poles 42 and 45.
  • the secondary current I2 assists the magnetic excitation by the V-phase current Iv.
  • the V-phase magnetic flux increases quickly.
  • the secondary current I2 induced by the decreasing of the V-phase current increases the W-phase magnetic flux in the stator poles 41 and 44.
  • the secondary current I2 assists the magnetic excitation by the W-phase current Iw.
  • the W-phase magnetic flux increases quickly.
  • the secondary current I2 induced by the decreasing of the W-phase current increases the U-phase magnetic flux in the stator poles 43 and 46.
  • the secondary current I2 assists the magnetic excitation by the U-phase current Iu.
  • the U-phase magnetic flux increases quickly.
  • the phase currents Iu, Iv and Iw are switched in turn.
  • the current-falling-down period of one phase current is overlapped with the current-rising-up period of the other one phase current.
  • the residual magnetic energy of one phase winding in which the phase current is turned off assists the magnetic excitation of the other one phase winding through the short circuit winding 2000 of the rotor 2.
  • the winding portion of the rotor winding 2000 which has the decreasing phase current, has larger inductance than the winding portion of the rotor winding 2000, which has the increasing phase current, because the difference of the facing areas between the stator pole and the rotor pole.
  • This principle is essentially same as the SRM shown in Figures 37-38.
  • the short-cut rotor winding can be made by a squirrel cage conductor, which is well-known in the induction motor technology. However, the two conductors in the two even rotor pole gaps are connected to series each other. Or, the two conductors in the two odd rotor pole gaps are connected to series each other.
  • the SRM is a stepping motor rotating continuously. Accordingly, the above-explained Hendershot-type five-phase SRM can be used as a VR type five-phase stepping motor. Furthermore, the above-explained five-phase inverter with six switching elements, which is shown in Figure 13, can be employed for a five-phase driving circuit for driving the five-phase stepping motor with the VR type.
  • the five-phase stepping motor which has an excellent performance, can be driven by only six active-switching elements.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Control Of Electric Motors In General (AREA)
  • Synchronous Machinery (AREA)

Abstract

L'invention concerne notamment un appareil de moteur à réluctance caractérisé par un rapport couple/poids inégalé. Le moteur pentaphasé à réluctance commutée de type Hendershot comporte une pluralité de pôles de rotor en U qui s’aimantent tour à tour. Les pôles de stator peuvent comporter un enroulement à CC chacun. Les entrefers des pôles de rotor peuvent loger des aimants permanents et/ou des enroulements de court-circuit. L’onduleur pentaphasé peut être constitué de six paires formées d’un transistor et d’une diode de roue libre. L’onduleur peut être relié à la source d’alimentation via un condensateur. Le convertisseur élévateur continu-continu bidirectionnel peut appliquer la tension surélevée à l’onduleur pentaphasé.
PCT/JP2010/003748 2009-07-10 2010-06-04 Appareil de moteur à réluctance WO2011004546A1 (fr)

Applications Claiming Priority (6)

Application Number Priority Date Filing Date Title
JP2009163580A JP2010193700A (ja) 2008-08-25 2009-07-10 スイッチドリラクタンスモータ装置
JP2009-163580 2009-07-10
US27877809P 2009-10-13 2009-10-13
US61/278,778 2009-10-13
JP2010-020225 2010-02-01
JP2010020225 2010-02-01

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Cited By (8)

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US20140159529A1 (en) * 2012-12-11 2014-06-12 Mcmaster University Switched reluctance machine with rotor excitation using permanent magnets
RU2572805C1 (ru) * 2014-11-06 2016-01-20 федеральное государственное бюджетное образовательное учреждение высшего образования "Национальный исследовательский университет "МЭИ" (ФГБОУ ВО "НИУ "МЭИ") Устройство для управления вентильно-индукторным электроприводом
CN107171606A (zh) * 2017-07-06 2017-09-15 中国计量大学 小功率多功能三相开关磁阻电机系统及其控制方法
CN107196575A (zh) * 2017-07-06 2017-09-22 中国计量大学 一种开关磁阻电动机变流器及其控制方法
CN107196576A (zh) * 2017-07-06 2017-09-22 中国计量大学 一种开关磁阻电机功率变换器及其控制方法
WO2018007818A3 (fr) * 2016-07-07 2018-02-15 Arm Ltd Moteur électrique à dents groupées
DE102017110841A1 (de) * 2017-05-18 2018-11-22 Minebea Mitsumi Inc. Elektromotor und Verfahren
CN111769663A (zh) * 2020-07-09 2020-10-13 河北工业大学 开关磁阻电机双模式驱动控制系统及实现方法

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JP2008236906A (ja) * 2007-03-20 2008-10-02 Mitsuba Corp モータの制御装置及びモータの制御方法並びに電動車両

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JPH0568396A (ja) * 1991-09-06 1993-03-19 Secoh Giken Inc インダクタンスコイルの通電制御装置
JP2008236906A (ja) * 2007-03-20 2008-10-02 Mitsuba Corp モータの制御装置及びモータの制御方法並びに電動車両

Cited By (18)

* Cited by examiner, † Cited by third party
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US10608489B2 (en) * 2012-12-11 2020-03-31 Enedym Inc. Switched reluctance machine with rotor excitation using permanent magnets
US20140159529A1 (en) * 2012-12-11 2014-06-12 Mcmaster University Switched reluctance machine with rotor excitation using permanent magnets
RU2572805C1 (ru) * 2014-11-06 2016-01-20 федеральное государственное бюджетное образовательное учреждение высшего образования "Национальный исследовательский университет "МЭИ" (ФГБОУ ВО "НИУ "МЭИ") Устройство для управления вентильно-индукторным электроприводом
US10651713B2 (en) 2016-07-07 2020-05-12 Arm Ltd. Grouped tooth electric motor
US11114925B2 (en) 2016-07-07 2021-09-07 Arm Limited Grouped tooth electric motor
WO2018007818A3 (fr) * 2016-07-07 2018-02-15 Arm Ltd Moteur électrique à dents groupées
GB2565990A (en) * 2016-07-07 2019-02-27 Advanced Risc Mach Ltd Grouped tooth electric motor
CN109792173A (zh) * 2016-07-07 2019-05-21 Arm有限公司 分组齿电机
GB2565990B (en) * 2016-07-07 2022-10-05 Advanced Risc Mach Ltd Grouped tooth electric motor
DE102017110841A1 (de) * 2017-05-18 2018-11-22 Minebea Mitsumi Inc. Elektromotor und Verfahren
CN107196576B (zh) * 2017-07-06 2019-09-10 中国计量大学 一种开关磁阻电机功率变换器及其控制方法
CN107196575A (zh) * 2017-07-06 2017-09-22 中国计量大学 一种开关磁阻电动机变流器及其控制方法
CN107171606A (zh) * 2017-07-06 2017-09-15 中国计量大学 小功率多功能三相开关磁阻电机系统及其控制方法
CN107196575B (zh) * 2017-07-06 2020-06-26 中国计量大学 一种开关磁阻电动机变流器及其控制方法
CN107196576A (zh) * 2017-07-06 2017-09-22 中国计量大学 一种开关磁阻电机功率变换器及其控制方法
CN107171606B (zh) * 2017-07-06 2019-07-30 中国计量大学 小功率多功能三相开关磁阻电机系统及其控制方法
CN111769663A (zh) * 2020-07-09 2020-10-13 河北工业大学 开关磁阻电机双模式驱动控制系统及实现方法
CN111769663B (zh) * 2020-07-09 2021-11-30 河北工业大学 开关磁阻电机双模式驱动控制系统及实现方法

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