WO2010044455A1 - Convertisseur de puissance directe c.a-c.a - Google Patents

Convertisseur de puissance directe c.a-c.a Download PDF

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Publication number
WO2010044455A1
WO2010044455A1 PCT/JP2009/067892 JP2009067892W WO2010044455A1 WO 2010044455 A1 WO2010044455 A1 WO 2010044455A1 JP 2009067892 W JP2009067892 W JP 2009067892W WO 2010044455 A1 WO2010044455 A1 WO 2010044455A1
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WO
WIPO (PCT)
Prior art keywords
converter
current
output
input side
power
Prior art date
Application number
PCT/JP2009/067892
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English (en)
Japanese (ja)
Inventor
中村　和人
耕才 山本
Original Assignee
ナブテスコ株式会社
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Publication date
Application filed by ナブテスコ株式会社 filed Critical ナブテスコ株式会社
Priority to JP2010533933A priority Critical patent/JP5095827B2/ja
Publication of WO2010044455A1 publication Critical patent/WO2010044455A1/fr

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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/12—Arrangements for reducing harmonics from ac input or output
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J3/00—Circuit arrangements for ac mains or ac distribution networks
    • H02J3/01—Arrangements for reducing harmonics or ripples
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M5/00—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases
    • H02M5/02—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases without intermediate conversion into dc
    • H02M5/04—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases without intermediate conversion into dc by static converters
    • H02M5/22—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases without intermediate conversion into dc by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M5/275—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases without intermediate conversion into dc by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M5/293—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases without intermediate conversion into dc by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0003—Details of control, feedback or regulation circuits
    • H02M1/0009—Devices or circuits for detecting current in a converter
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02E—REDUCTION OF GREENHOUSE GAS [GHG] EMISSIONS, RELATED TO ENERGY GENERATION, TRANSMISSION OR DISTRIBUTION
    • Y02E40/00—Technologies for an efficient electrical power generation, transmission or distribution
    • Y02E40/40—Arrangements for reducing harmonics

Definitions

  • the present invention relates to an AC-AC direct conversion power converter, and more particularly to suppression of power supply harmonics.
  • an AC-AC direct conversion type power conversion device a so-called matrix converter
  • An LC filter is provided between the three-phase AC power source and the matrix converter in order to limit the influence of the switching component (carrier ripple) on the power source.
  • diode bridges are provided on the input side and output side of the matrix converter, respectively, and a capacitor is connected between these diode bridges. This is because the load of the matrix converter is an inductive load, and the energy stored in the inductive load is absorbed when all the bidirectional switches constituting the matrix converter are shut off.
  • Such a matrix converter may be connected to a variable frequency AC power source such as a generator to drive a motor.
  • a variable frequency AC power source such as a generator
  • the resonance condition of the LC filter may fluctuate depending on the impedance of the AC power source (for example, the synchronous reactance of the generator) and the motor status.
  • the impedance of the filter reactor increases and the load output voltage decreases as the frequency increases. Considering the occurrence of such a problem, if the reactor value is selected to be small, the effect of reducing the carrier ripple, which is the original purpose of providing the LC filter, is reduced.
  • An object of the present invention is to provide an AC-AC direct conversion type power converter that can actively reduce power supply harmonics.
  • the AC-AC direct conversion power converter includes a power converter.
  • a power converter In this power converter, an AC output from a multiphase AC power source, for example, a three-phase AC power source is supplied to the input side, and the AC output is directly converted into another AC output and output from the output side.
  • This power converter has, for example, a bridge composed of bidirectional switching elements between the input side and the output side, and these switching elements are turned on and off by a PWM control signal, so that an AC input is desired. Direct conversion to AC output.
  • An LC filter is connected between the input side of the power converter and the AC power source.
  • the input side of the diode bridge rectifier is connected to the output side of the power converter.
  • the input side of the bridge converter is connected to the output side of the diode bridge rectifier, and the output side of the bridge converter is connected to the input side of the LC filter.
  • the bridge converter is composed of a plurality of switching elements.
  • a clamp is connected between the output side of the diode bridge rectifier and the input side of the bridge converter.
  • the clamp includes, for example, a clamp capacitor connected between two terminals on the diode bridge output side.
  • the current source includes, for example, a reactor connected in series between one output side of the diode bridge, for example, the positive electrode side, and one of the two output sides of the bridge converter, for example, the positive electrode side. In addition, this reactor is connected to the bridge converter side rather than the connection position with the clamp capacitor.
  • a plurality of current detectors for detecting a phase current of the AC power supply are provided.
  • a plurality of power frequency component removers remove the power frequency components of the AC power source from the detection signals of these current detectors.
  • a plurality of comparators respectively compare the output signal of the power supply frequency component remover and the current flowing through the reactor of the current source.
  • the discriminator discriminates the maximum or minimum output signal from each power supply frequency component remover.
  • the controller selects the output signal of the comparator corresponding to the discrimination result of the discriminator, for example, the comparator supplied with the output signal of the power supply frequency component remover generating the maximum or minimum output signal.
  • the controller selects the switching element of the bridge converter according to the determination result of the classifier, for example, selects the switching element through which the maximum or minimum phase current flows, and outputs the selected switching element to the output of the comparator. Control based on the signal.
  • the control by the controller is preferably synchronized with the cycle of the PWM control signal.
  • the switching element of the bridge converter is controlled based on the comparison result between the maximum or minimum phase current and the current flowing through the reactor of the current source means, for example, in a direction in which the difference between the two is zero, and the LC Harmonic components flowing from the filter to the power supply side can be suppressed. Therefore, the LC filter can be set to a value that does not easily resonate with the power source impedance or the like even if the frequency of the AC power source changes without paying attention to the reduction of the harmonic component to the power source.
  • a voltage monitor for monitoring the voltage of the clamp capacitor can be provided.
  • the controller stops the bridge converter when the voltage of the capacitor monitored by the voltage monitor is lower than a predetermined reference value.
  • the bridge converter when the voltage of the clamp capacitor is lower than a predetermined reference value, for example, the bridge converter can be prevented from operating in an unstable initial state where an AC power source is connected to the power converter. .
  • an inrush current flows through the clamp capacitor.
  • the value of the inrush current can be suppressed to some extent by the reactor of the current source, the value of the reactor is set with priority given to the suppression of the harmonic component described above, and thus the inrush current may not be sufficiently suppressed. Therefore, an initial charger is provided in order to suppress the inrush current.
  • a first diode is connected in series with the reactor of the current source, and the first diode is connected in the direction in which current flows to the input side of the bridge converter.
  • a series circuit is connected to the capacitor.
  • the series circuit includes another reactor and a second diode connected in series with the other reactor, and the second diode is connected in a direction in which a current flows through the capacitor of the clamp. The capacitor is initially charged by the series circuit.
  • the AC-AC direct conversion type power conversion device includes a power converter, an LC filter, a diode bridge rectifier, a bridge, and the AC-AC direct conversion type power conversion device according to the aspect described above. It has a transducer, a clamp, and a current source.
  • a chopper switching element is provided so as to constitute a chopper together with the reactor of the current source.
  • a chopper current detector detects the current flowing through the chopper switching element.
  • a plurality of power source current detectors detect at least two-phase currents of the AC power source.
  • a plurality of power supply frequency component removers remove the power supply frequency component of the AC power supply from the detection signals of these power supply current detectors.
  • the controller calculates a target value from the output signals of these power frequency component removers, compares the target value with the chopper current of the chopper current detector, and switches the bridge converter according to the comparison result. To control. For example, the controller stores the energy of the capacitor in the LC reactor by turning on and off the chopper switching element. When the current of the reactor becomes equal to or higher than the target value, the controller supplies the LC filter to the input side of the LC filter via the bridge converter. As a result, the harmonic component of the power supply current is suppressed.
  • a diode can be connected in series to each of the switching elements of the bridge converter and operated as a clamp. Furthermore, the switching elements of the bridge converter can be constituted by MOSFETs.
  • the present invention even when connected to an AC power supply whose drastically fluctuates, it is set to a value that does not resonate with the power supply impedance without paying attention to the reduction of harmonic components to the power supply. Even if the inductance of the LC filter is selected with an emphasis on doing this, the power supply harmonics can be canceled out.
  • FIG. 1 is a block diagram of an AC-AC direct conversion power converter according to a first embodiment of the present invention.
  • FIG. 2a is an explanatory diagram of symbols attached to the IGB of the PWM converter unit used in FIG. 2b.
  • FIG. 2b is an operation explanatory diagram of the PWM converter unit of the AC-AC direct conversion type power converter of FIG. 3a to 3f are explanatory diagrams of a current flow in the PWM converter unit of the AC-AC direct conversion type power converter of FIG. 4a to 4c are waveform diagrams of the AC-AC direct conversion type power converter of FIG.
  • FIG. 8 is a block diagram showing a part of a modification of the AC-AC direct conversion type power conversion device of FIG. 1.
  • FIG. 7a to 7c are operation explanatory diagrams of the PWM converter of the AC-AC direct conversion type power converter of FIG. 8a and 8b are waveform diagrams of the chopper of the AC-AC direct conversion type power converter shown in FIG. It is explanatory drawing of the ripple compensation of the alternating current-alternating-current direct conversion type power converter device of FIG. It is a block diagram of the AC-AC direct conversion type power converter device of the 3rd embodiment of the present invention. It is operation
  • FIG. 11 is a block diagram illustrating a part of a modification of the PWM converter unit of the AC-AC direct conversion type power conversion device of FIG. 10.
  • the AC-AC direct conversion power converter has a power converter, for example, a matrix converter main circuit 2, as shown in FIG.
  • the input side of the matrix converter main circuit 2 is connected to a multiphase AC power source, for example, a three-phase AC power source 4 via an LC filter 6.
  • the three-phase AC power source 4 is a variable frequency unit such as a generator.
  • the LC filter 6 includes an inductor 6L connected in series to each phase of the three-phase alternating current, and a capacitor 6C that is star-connected between the phases.
  • the output side of the matrix converter main circuit 2 is connected to a load 8. For example, a three-phase motor can be used as the load 8.
  • the matrix converter main circuit 2 is connected to all three output sides of the LC filter 6 and three input sides of the load 8 by a plurality of, for example, nine bidirectional switching elements, as is well known. An AC output having a desired frequency is supplied to the load 8 by turning on and off the switching element by a PWM signal.
  • a voltage sensor 10 In order to control the matrix converter main circuit 2, a voltage sensor 10, a current detection circuit 12, a matrix converter gate signal generator 14, a gate block unit 16, a gate driver 18, a PWM carrier clock generator 20, and the like are provided. Since these structures are not directly related to the gist of the present invention, further explanation is omitted.
  • the three input sides of the diode bridge rectifier, for example, the diode rectifier circuit 22 are connected to the three output sides of the matrix converter main circuit 2.
  • the diode rectifier circuit 22 is, for example, a known circuit in which six diodes are bridge-connected, and has two output sides.
  • a clamp circuit 24 is connected to two positive and negative output sides of the diode rectifier circuit 22.
  • the clamp circuit 24 includes a clamp capacitor 26 connected between the two output sides of the diode rectifier circuit 22.
  • a free-wheeling diode 28 is connected to the clamp capacitor 26 in antiparallel.
  • a series circuit 30 is connected in parallel with the freewheeling diode 28.
  • the series circuit 30 includes a discharge resistor 32 and a switching element, for example, a discharge IGBT switch 34.
  • the positive output side of the diode rectifier circuit 22 and the negative output side of the diode rectifier circuit 22 constitute the positive output side and the negative output side of the clamp circuit 24.
  • one end of a current source for example, a reactor 36 is connected to the positive output side of the clamp circuit 24.
  • a bridge converter for example, a PWM converter unit 38
  • the PWM converter unit 38 has three parallel circuits between its two input sides, and each parallel circuit includes switching elements, for example, IGBTs 40 connected in series.
  • the interconnection points of the IGBTs 40 in each parallel circuit are the three output sides 38R, 38S, 38T of the PWM converter unit 38, and are connected to the corresponding ones of the three input sides R, S, T of the LC filter 6, respectively. Yes.
  • current sensors 42R, 42S, and 42T are provided in each phase of the three-phase AC power supply 4. These current sensors 42R, 42S, and 42T are connected to current detectors (CD) 44R, 44S, and 44T, and currents of respective phases of the three-phase AC power supply 4 are detected by these current detectors 44R, 44S, and 44T. .
  • the detection signals of these current detectors 44R, 44S, 44T are supplied to power supply frequency component removers (PFR) 46R, 46S, 46T.
  • PFR power supply frequency component removers
  • a clamp current detector 48 for detecting a current flowing through the reactor 36 is provided.
  • the clamp current detected by the clamp current detector 48 is compared with the detection signals of the power supply frequency component removers 46R, 46S, and 46T in the comparators (CMP) 50R, 50S, and 50T, respectively.
  • One of the output signals of the comparators 50R, 50S, 50T is selected by a selector, for example, the changeover switch 52.
  • the changeover switch 52 is switched in synchronization with the PWM carrier clock from the PWM carrier clock generator 20.
  • the switching control is performed by inputting the detection signals of the power supply frequency component removers 46R, 46S, and 46T and synchronizing them with the PWM carrier clock, and the maximum or minimum of these detection signals, that is, the absolute value is the maximum.
  • a current comparator (CCMP) 54 performs the comparison.
  • the output signal of the comparator 50R is selected by the changeover switch 52
  • the comparator when the detection signal of the power supply frequency component remover 46S is maximum or minimum, the comparator When the output signal of 50S is selected by the changeover switch 52 and the detection signal of the power supply frequency component remover 46T is maximum or minimum, the output signal of the comparator 50T is selected by the changeover switch 52.
  • the output signal of the selected comparator 50R, 50S or 50T is supplied to the gate signal distributor 56.
  • the gate signal distributor 56 is also supplied with the result of comparison by the current comparator 54 (representing the maximum or minimum of the detection signals of the power supply frequency component removers 46R, 46S, 46T). . Based on these, the gate signal distributor 56 determines which IGBT 40 of the PWM converter unit 38 is to be conducted.
  • the IGBT 40 of the PWM converter unit 38 is named Qr, Qs, Qt, Qr, Qs, Qt, respectively, as shown in FIG. 2a
  • the AC power supply 4 as shown in the column 1 of FIG. 2b.
  • Qs, Qt and Qr are made conductive.
  • Qr, Qt, and Qs are made conductive.
  • Qr, Qs, and Qt are made conductive.
  • a current having a polarity opposite to that of the harmonic component discharged from the clamp capacitor 26 flows to the input side of the LC clamp filter 6, and the harmonic component can be reduced.
  • the switching frequency of the PWM converter unit 38 is synchronized with the PWM carrier clock, only one phase can be current-compensated at a time, and from one of the three phases to another phase. Current compensation can be made with the flowing current.
  • the sum of the harmonic currents of the three phases is zero, and if the compensation current is passed from the phase with the largest absolute value of the harmonic current to the other two phases, the peak value of the ripple component is suppressed and the result is In addition, harmonic components can be reduced.
  • L inductance of the reactor 36
  • C capacitor of the clamp capacitor 26
  • R resistance value of the discharge resistor 32
  • the sum of the harmonic currents of each phase becomes zero as in the principle of the three-phase alternating current.
  • the harmonic current flows from the R phase to the S and T phases. Therefore, current compensation can be performed if current flows from one of the three phases to the other two phases within the period of the carrier frequency.
  • the gate driver 58 makes the determined IGBT conductive every carrier period.
  • the gate driver 58 blocks all the IGBTs 40 when the overcurrent detector (OCD) 60 detects that an overcurrent is flowing from the AC power supply 4. At this time, the operation of the matrix converter main circuit 2 is also stopped by the overcurrent detector 60 at the same time. At this time, the discharge IGBT switch 34 is turned on based on a signal from the discharge timing gate driver (OTGD) 61 to discharge the clamp capacitor 26. As a result, the clamp capacitor 26 effectively absorbs the surge generated due to all the IGBTs 40 being blocked or the matrix converter main circuit 2 being deactivated.
  • a voltage detector (VD) 62 is provided in parallel with the clamp capacitor 26, and the detected voltage at the voltage detector 62 is derived from a variable resistor 66 used as a reference voltage setter in the comparator (CMP) 64. Compared to the reference voltage.
  • the comparator 64 supplies a signal to the gate driver 58 when the voltage of the clamp capacitor 26 is lower than the reference voltage, and the gate driver 58 blocks the IGBT 40.
  • the inductance of the reactor 36 is set in consideration of the current increase rate so that the ripple current can be sufficiently compensated at the period of the switching carrier frequency.
  • the reactor 36 also functions to suppress an inrush current when the charge of the clamp capacitor 26 is discharged when the matrix converter main circuit 2 is powered on.
  • the inrush current may not be sufficiently suppressed depending on the inductance value.
  • a charger comprising a series circuit of a reactor 68 provided separately and a diode 70 connected in a direction in which current flows to the clamp capacitor 26 side is connected to the AC power source 4. Can also be connected between the positive electrode of the clamp capacitor 26.
  • the inductance of the reactor 68 is set to a value that can sufficiently suppress the inrush current, and the clamp capacitor 26 is initially charged.
  • the diode 72 is connected in series with the reactor 36 in a direction in which current flows only to the PWM converter unit 38 side. These diodes 70 and 72 are for backflow prevention, respectively.
  • FIGS. 6 to 9 show an AC-AC direct conversion type power converter according to the second embodiment of the present invention.
  • the AC-AC direct conversion power converter according to the first embodiment is based on the premise that the voltage of the clamp capacitor 26 is higher than the power supply voltage, and is sufficient when the power supply voltage is close to the voltage of the clamp capacitor 26. It may not be possible to pass a large compensation current.
  • the AC-AC direct conversion type power converter according to the second embodiment has improved this point.
  • a chopper switch for example, a chopper IGBT 74 is provided between the end of the reactor 36 on the PWM converter unit 38 side and the negative output side of the clamp circuit 24, and a clamp capacitor A chopper circuit is configured by providing a filter capacitor 78 through a backflow prevention diode 76 in parallel with H.26.
  • the IGBT 74 for chopper is turned on, the clamp capacitor 26 and the reactor 36 are resonated to generate a voltage higher than the power supply voltage, and the current based thereon is input to the LC filter 6 through the PWM converter unit 38 as a compensation current. It is natural to flow to the side.
  • the clamp capacitor 26 since the clamp capacitor 26 has a relatively large capacity, there is a possibility that the current due to resonance does not rise within the period of the carrier frequency. Therefore, a filter capacitor 78 having a small capacity is provided to resonate with the reactor 36.
  • the end of the reactor 36 on the PWM converter unit 38 side is connected to the positive input side of the PWM converter unit 38 via a backflow prevention diode 80. Further, the anode of the recirculation diode 82 is connected to the positive input side, and the cathode is connected to the end of the reactor 36 on the clamp capacitor 26 side.
  • the energy of the reactor 36 circulates through the backflow prevention diode 80 and the backflow diode 82, but is connected in series to the backflow diode 82 (not shown).
  • the resistor consumes energy and decays rapidly.
  • FIG. 8a to 8c show the current Ic of the clamp capacitor 26, the voltage Vc, the current IL flowing through the reactor 36, and the compensation current Ip.
  • FIG. 8a shows the case where the on-time of the chopper IGBT 74 is short, and FIG. The case where the ON time of IGBT74 for choppers is long is shown.
  • the current Ic of the clamp capacitor 26 changes in a sine wave shape as indicated by a broken line in FIGS. 8a and 8b. However, when discharging to the peak value, the polarity of the voltage of the clamp capacitor 26 is reversed. Therefore, before the peak value is exceeded, the chopper IGBT 74 is turned off to adjust the magnitude of the compensation current Ip.
  • FIG. 9 shows the ripples included in the power supply current, the ripples to be compensated, and the compensation currents that are supplied to compensate, according to the chopper current target value Icp determined as described later according to the ripple component to be compensated.
  • the chopper current target value Icp removes the power supply frequency component from the R-phase and T-phase power supply currents detected by the current sensors 42R and 42T, the current detectors 44R and 44T, and the power supply frequency component removers 46R and 46T shown in FIG. Based on this, the power source chopper current target value calculator 84 calculates. Since this calculation is necessary for each carrier period, it is performed in synchronization with the carrier signal from the PWM carrier clock generator 20.
  • the chopper current target value Icp and the chopper current detected by the chopper current detector 86 connected in series to the chopper IGBT 74 are compared by the comparator (CMP) 88, and the chopper current matches the chopper current target value Icp.
  • the signal of the chopper IGBT gate signal generator (GSG) 90 is supplied to the gate driver 92, and the chopper IGBT 74 is turned off. That is, the chopper IGBT gate signal generator 90 is also synchronized with the carrier signal from the PWM carrier clock generator 20, and the chopper IGBT 74 is turned on at the start of the carrier cycle. When the chopper current matches the target value Icp, the chopper IGBT 74 is turned off.
  • the output signals of the current sensors 42R and 42T are supplied to a two-phase / three-phase converter (2-3C) 94, and the gate signal distributor 96 is converted into a PWM converter based on the output signal of the two-phase / three-phase converter 94. It is determined which phase of the IGBT 40 of the section 38 is to be conducted, and is supplied to the gate driver 58.
  • FIG. 10 and FIG. 11 show an AC-AC direct conversion type power converter according to the third embodiment.
  • this AC-AC direct conversion type power converter is provided with a diode bridge circuit 100 for operating as a clamp circuit, and the PWM converter unit 38 is operated as a 180-degree conduction type current converter. Is.
  • the same parts as those of the second embodiment are denoted by the same reference numerals, and the description thereof is omitted.
  • the gate signal distributor 96 determines that the positive and negative IGBTs 40 are always turned on in the six patterns shown in FIG. Since the PWM converter 38 operates as a 180-degree conduction type current type converter as described above, the AC reactor 102 is inserted on the output side thereof.
  • the switching element of the PWM converter part 38a can also be comprised by MOSFET40a. High speed switching can be performed by using the MOSFET 40a.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Ac-Ac Conversion (AREA)
  • Rectifiers (AREA)

Abstract

L'invention porte sur un convertisseur de puissance directe c.a-c.a qui peut activement réduire une harmonique supérieure d'une source d'alimentation. Un circuit principal de convertisseur matriciel (2) comprend un filtre LC (6) connecté à une source de courant alternatif (c.a) (4) et convertit une sortie c.a de la source de courant alternatif triphasé (4) en une autre sortie c.a. Un circuit redresseur à pont de diodes (22) et une unité de convertisseur à modulation d'impulsions en durée (PWM) (38) sont connectés entre le côté sortie du circuit principal de convertisseur matriciel (2) et le côté entrée du filtre LC (6). Un circuit de fixation de niveau (24) est connecté entre le côté sortie du circuit redresseur (22) et le côté entrée de l'unité de convertisseur PWM (38). Une commande est effectuée de la façon suivante. Un courant de la source de courant alternatif (4) est détecté par des unités de détection de courant (44R, 44S, 44T). Le signal de sortie maximal ou minimal d'éliminateurs de composante de fréquence industrielle (46R, 46S, 46T) est détecté par un comparateur de courant (54). Les signaux de sortie de comparateurs (50R, 50S, 50T) sont sélectionnés par un commutateur de sélection (52). Un élément de commutation de l'unité de convertisseur (38) est sélectionné selon le signal de sortie des comparateurs.
PCT/JP2009/067892 2008-10-17 2009-10-16 Convertisseur de puissance directe c.a-c.a WO2010044455A1 (fr)

Priority Applications (1)

Application Number Priority Date Filing Date Title
JP2010533933A JP5095827B2 (ja) 2008-10-17 2009-10-16 交流−交流直接変換型電力変換装置

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JP2008-268155 2008-10-17
JP2008268155 2008-10-17

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WO2010044455A1 true WO2010044455A1 (fr) 2010-04-22

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Cited By (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
WO2012126515A1 (fr) * 2011-03-22 2012-09-27 Siemens Aktiengesellschaft Installation électrique dotée d'un convertisseur matriciel et procédé correspondant permettant de faire fonctionner ladite installation électrique
CN104253538A (zh) * 2013-06-28 2014-12-31 株式会社安川电机 矩阵变换器
US10110139B1 (en) 2017-04-21 2018-10-23 Kabushiki Kaisha Yaskawa Denki Matrix converter and method for determining constants of alternating-current motor
JP2020532262A (ja) * 2017-08-29 2020-11-05 イートン インテリジェント パワー リミテッドＥａｔｏｎ Ｉｎｔｅｌｌｉｇｅｎｔ Ｐｏｗｅｒ Ｌｉｍｉｔｅｄ 固体状態回路遮断器を有するマトリックスコンバータ

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WO2012126515A1 (fr) * 2011-03-22 2012-09-27 Siemens Aktiengesellschaft Installation électrique dotée d'un convertisseur matriciel et procédé correspondant permettant de faire fonctionner ladite installation électrique
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EP2822167A3 (fr) * 2013-06-28 2015-09-30 Kabushiki Kaisha Yaskawa Denki Commande d'un convertisseur matriciel dans le domaine de saturation de tensions de sortie
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CN104253538B (zh) * 2013-06-28 2017-04-12 株式会社安川电机 矩阵变换器
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EP3393033A1 (fr) * 2017-04-21 2018-10-24 Kabushiki Kaisha Yaskawa Denki Convertisseur de matrice et procédé de détermination de constantes de moteur à courant alternatif
CN108736792A (zh) * 2017-04-21 2018-11-02 株式会社安川电机 矩阵变换器以及交流电动机的常数确定方法
CN108736792B (zh) * 2017-04-21 2021-11-09 株式会社安川电机 矩阵变换器以及交流电动机的常数确定方法
JP2020532262A (ja) * 2017-08-29 2020-11-05 イートン インテリジェント パワー リミテッドＥａｔｏｎ Ｉｎｔｅｌｌｉｇｅｎｔ Ｐｏｗｅｒ Ｌｉｍｉｔｅｄ 固体状態回路遮断器を有するマトリックスコンバータ

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