WO2007063855A1 - Appareil de transmission multiporteuse, appareil de reception multiporteuse, procede de reception et de transmission - Google Patents

Appareil de transmission multiporteuse, appareil de reception multiporteuse, procede de reception et de transmission Download PDF

Info

Publication number
WO2007063855A1
WO2007063855A1 PCT/JP2006/323727 JP2006323727W WO2007063855A1 WO 2007063855 A1 WO2007063855 A1 WO 2007063855A1 JP 2006323727 W JP2006323727 W JP 2006323727W WO 2007063855 A1 WO2007063855 A1 WO 2007063855A1
Authority
WO
WIPO (PCT)
Prior art keywords
signal
transmission signal
transmission
received signal
complex
Prior art date
Application number
PCT/JP2006/323727
Other languages
English (en)
Japanese (ja)
Inventor
Shoichi Fujita
Sadaki Futagi
Original Assignee
Matsushita Electric Industrial Co., Ltd.
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Matsushita Electric Industrial Co., Ltd. filed Critical Matsushita Electric Industrial Co., Ltd.
Publication of WO2007063855A1 publication Critical patent/WO2007063855A1/fr

Links

Classifications

    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/32—Carrier systems characterised by combinations of two or more of the types covered by groups H04L27/02, H04L27/10, H04L27/18 or H04L27/26
    • H04L27/34—Amplitude- and phase-modulated carrier systems, e.g. quadrature-amplitude modulated carrier systems
    • H04L27/36—Modulator circuits; Transmitter circuits
    • H04L27/366—Arrangements for compensating undesirable properties of the transmission path between the modulator and the demodulator
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/26—Systems using multi-frequency codes
    • H04L27/2601—Multicarrier modulation systems
    • H04L27/2626—Arrangements specific to the transmitter only
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/32—Carrier systems characterised by combinations of two or more of the types covered by groups H04L27/02, H04L27/10, H04L27/18 or H04L27/26
    • H04L27/34—Amplitude- and phase-modulated carrier systems, e.g. quadrature-amplitude modulated carrier systems
    • H04L27/36—Modulator circuits; Transmitter circuits
    • H04L27/362—Modulation using more than one carrier, e.g. with quadrature carriers, separately amplitude modulated
    • H04L27/364—Arrangements for overcoming imperfections in the modulator, e.g. quadrature error or unbalanced I and Q levels

Definitions

  • Multicarrier transmission apparatus multicarrier reception apparatus, transmission method, and reception method
  • the present invention relates to a multicarrier transmission apparatus, a multicarrier reception apparatus, a transmission method, and a reception method, and in particular, an imbalance in amplitude or delay time between an in-phase component (I component) and a quadrature component (Q component)
  • the present invention relates to a multicarrier transmission apparatus, a multicarrier reception apparatus, a transmission method, and a reception method.
  • LPF analog Z digital
  • AZD analog Z digital
  • LPF is necessary to remove aliasing noise that occurs at the time of DZA conversion and AZD conversion and is more than half of the sampling frequency.
  • an amplitude imbalance and a delay time imbalance occur between the I channel and the Q channel. Amplitude imbalance and delay time imbalance between the I channel and Q channel cause inter-carrier interference and degrade performance.
  • FIG. 1 is a diagram showing a reception constellation result when there is no delay time imbalance between the in-phase component and the quadrature component caused by individual differences in LPF
  • FIG. It is a figure which shows the performance degradation by the imbalance of the delay time between the in-phase component and quadrature component which arise by a difference.
  • Figure 2 shows the case where a delay time difference of 1Z8 samples occurs between the in-phase component and the quadrature component.
  • the delay time difference is greatly affected, and even a slight difference of one sample time or less greatly deteriorates. This is because even a baseband signal has subcarriers, and the delay time difference cannot be ignored with respect to the subcarrier period. Therefore, the influence is greater for subcarriers with higher frequencies, and for IFZRF band modulation signals, the effect of the delay time difference is greater for subcarriers that are farther away from the center of the signal band.
  • analog LPFs are more difficult to avoid because they are more sensitive to variations near the cutoff, that is, at the end of the passband, and the variation becomes larger.
  • the group delay time is 48 ns
  • FIG. 3 is a diagram showing a reception constellation result when there is no amplitude imbalance between the in-phase component and the quadrature component caused by individual differences in LPF.
  • Fig. 4 shows individual differences in LPF.
  • FIG. 5 is a diagram showing performance deterioration due to an amplitude imbalance between an in-phase component and a quadrature component generated by the above.
  • Figure 4 shows the case where an amplitude difference of ldB occurs between the in-phase component and the quadrature component.
  • interference between subcarriers also occurs due to amplitude imbalance, which degrades performance.
  • the amplitude difference is less affected than the delay time difference. For example, suppressing the LPF passband amplitude difference to ldB is easier than suppressing the group delay difference to 1%.
  • Patent Document 1 Japanese Patent Laid-Open No. 2001-24722
  • the first method and the second method have strict LPF specifications, which increases the cost and cannot achieve low cost. is there.
  • the third method it is possible to compensate for a delay time smaller than one sample period, but there is a problem that the circuit scale becomes large because two timing extraction circuits are required.
  • the third method has a problem that it cannot compensate for the amplitude imbalance.
  • An object of the present invention is to provide a multicarrier transmission device, a multicarrier reception device, a transmission method, and a reception method capable of compensating for delay time and amplitude imbalance at low cost without increasing the circuit scale. It is to be.
  • the multicarrier transmission device of the present invention performs complex transmission consisting of a first transmission signal that is an I-component frequency domain signal and a second transmission signal that is a Q-component frequency domain signal by orthogonally modulating transmission data.
  • a digital modulation means for generating a signal, and a fifth transmission signal which is a frequency domain signal of the third transmission signal which becomes an I component time domain signal when the complex transmission signal is subjected to inverse high-speed Fourier transform, and a time domain of the Q component Separating means for separating the complex transmission signal into a sixth transmission signal that is a frequency domain signal of a fourth transmission signal that becomes a signal, and the third transmission signal and the fourth transmission signal when band-limiting the fourth transmission signal.
  • Three transmission signals and the fourth transmission Correction means for correcting the fifth transmission signal or the sixth transmission signal so that an amplitude difference and a delay time difference from the signal become small, and the fifth transmission signal and the sixth transmission signal after correction by the correction means.
  • Combining means for combining the transmission signal to regenerate the complex transmission signal; and inverse fast Fourier transform of the complex transmission signal regenerated by the combining means to perform the third transmission signal and the fourth transmission signal.
  • An inverse fast Fourier transform unit for generating the band, a band limiting unit for limiting a band between the third transmission signal and the fourth transmission signal generated by the inverse fast Fourier transform unit, and the band limiting unit A transmission unit configured to transmit a transmission signal composed of the third transmission signal and the fourth transmission signal which are band-limited.
  • the multicarrier receiver of the present invention performs orthogonal demodulation to generate a first received signal that is an I component time domain signal and a second received signal that is a Q component time domain signal by performing orthogonal demodulation on the received signal.
  • band limiting means for limiting the band of the first received signal and the second received signal, and fast Fourier transform of the first received signal and the second received signal band-limited by the band limiting means
  • Fast Fourier transform means for generating a complex received signal composed of a third received signal that is a frequency domain signal of I component and a fourth received signal that is a frequency domain signal of Q component, and the frequency domain of the first received signal
  • Separating means for separating the complex received signal into a fifth received signal that is a signal and a sixth received signal that is a frequency domain signal of the second received signal, and the first received signal and the second received signal are divided into the band
  • the fifth received signal or the sixth received signal is corrected so that an amplitude difference and a delay time difference between the first received signal and the second received signal generated when band limiting is performed by the limiting means are reduced.
  • transmission data is orthogonally modulated to generate a complex transmission signal composed of a first transmission signal that is an I component frequency domain signal and a second transmission signal that is a frequency domain signal of a Q component. And a fifth transmission signal and a Q component which are frequency domain signals of a third transmission signal that becomes an I component time domain signal by performing inverse fast Fourier transform on the complex transmission signal. Separating the complex transmission signal from the sixth transmission signal, which is the frequency domain signal of the fourth transmission signal to be the time domain signal, and band-limiting the third transmission signal and the fourth transmission signal.
  • Send transmission signal was to be provided and the step, the.
  • the reception method of the present invention includes a step of generating a first reception signal that is an I-component time-domain signal and a second reception signal that is a Q-component time-domain signal by performing orthogonal demodulation on the reception signal; A step of limiting the bands of the first reception signal and the second reception signal, and a third Fourier transform of the band-limited first reception signal and the second reception signal to form an I component frequency domain signal. Generating a complex received signal comprising a received signal and a fourth received signal that is a frequency domain signal of the Q component; and a fifth received signal that is a frequency domain signal of the first received signal and a second received signal.
  • FIG. 1 is a diagram showing a simulation result of a reception constellation.
  • FIG.2 Diagram showing simulation results of reception constellation
  • FIG. 8 is a diagram showing a simulation result of a reception constellation according to Embodiment 1 of the present invention.
  • FIG. 9 is a diagram showing a simulation result of a reception constellation according to Embodiment 1 of the present invention.
  • FIG. 10 is a diagram showing a simulation result of a reception constellation according to Embodiment 1 of the present invention.
  • FIG. 11 is a diagram showing a simulation result of the reception constellation according to Embodiment 1 of the present invention.
  • FIG. 12 is a diagram showing a simulation result of a reception constellation according to Embodiment 1 of the present invention.
  • FIG. 13 is a diagram showing a simulation result of a reception constellation according to Embodiment 1 of the present invention.
  • FIG. 14 is a diagram showing a simulation result of a reception constellation according to Embodiment 1 of the present invention.
  • FIG. 15 is a diagram showing a simulation result of a reception constellation according to Embodiment 1 of the present invention.
  • FIG. 18 is a diagram showing a simulation result of the reception constellation according to Embodiment 1 of the present invention.
  • FIG. 19 is a diagram showing a simulation result of a reception constellation according to Embodiment 1 of the present invention.
  • FIG. 20 is a block diagram showing a configuration of a correction coefficient storage unit according to the second embodiment of the present invention.
  • FIG. 5 is a block diagram showing a configuration of multicarrier transmission apparatus 100 according to Embodiment 1 of the present invention.
  • the digital modulation unit 101 performs quadrature modulation on transmission data encoded by an encoding unit (not shown) using a modulation scheme such as QPSK or 16QAM, and performs first transmission as a frequency domain signal of I component A second transmission signal that is a frequency domain signal of the signal and the Q component is generated. Also, when providing a guard band, digital modulation section 101 inserts data “0” into the subcarriers assigned to the guard band. For example, when the inverse fast Fourier transform (hereinafter referred to as “IF FT”) point is 512, 1S can generate 512 subcarriers. In this case, the digital modulation unit 101 includes OHz including the inner negative frequency.
  • IF FT inverse fast Fourier transform
  • Digital modulation section 101 converts the generated complex transmission signal (first transmission signal (I component) + j X second transmission signal (Q component)) composed of the first transmission signal and the second transmission signal in units of lOFDM symbols. To output to separation unit 102.
  • Separating section 102 converts a complex transmission signal composed of the first transmission signal and the second transmission signal input from digital modulation section 101 into two transmission signals, a fifth transmission signal and a sixth transmission signal, in units of lOFDM symbols.
  • the signal is separated into complex transmission signals and output to the correction unit 103.
  • the fifth transmission signal is the frequency domain signal of the third transmission signal, which is the time domain signal of the I component after IFFT of the complex transmission signal that also has the first transmission signal and the second transmission signal power, and the sixth transmission signal.
  • the signal is a frequency domain signal of the fourth transmission signal, which is a time domain signal of the Q component after IFFT of the complex transmission signal composed of the first transmission signal and the second transmission signal.
  • Correction section 103 corrects one of two complex transmission signals of the fifth transmission signal and the sixth transmission signal input from separation section 102 in the frequency domain. As a result, the delay time difference and the amplitude difference between the third transmission signal and the fourth transmission signal generated by band limiting the third transmission signal and the fourth transmission signal by LPF 109 and LPF 110, which will be described later, are reduced. Can be compensated. Then, after correcting the delay time difference and the amplitude difference, the correction unit 103 outputs the fifth transmission signal and the sixth transmission signal to the synthesis unit 104.
  • the combining unit 104 combines the fifth transmission signal and the sixth transmission signal input from the correction unit 103 and forms a complex composed of the first transmission signal and the second transmission signal before being separated by the separation unit 102. Regenerate the transmission signal. Then, combining section 104 outputs the regenerated first transmission signal and second transmission signal to the IFFT section 105.
  • IFFT section 105 converts the complex transmission signal composed of the first transmission signal and the second transmission signal input from combining section 104 into an IFFT, that is, a frequency domain signal and a time domain signal, and transmits the third transmission signal. A signal and a fourth transmission signal are generated. Then, IFFT section 105 outputs the generated third transmission signal and fourth transmission signal to GI adding section 106.
  • GI adding section 106 adds GI to the third transmission signal and the fourth transmission signal input from IFFT section 105.
  • the GI adding unit 106 outputs the third transmission signal to which the GI is added to the DZA unit 107, and outputs the fourth transmission signal to which the GI is added to the DZA unit 108.
  • the DZA unit 107 converts the third transmission signal input from the GI adding unit 106 from a digital signal to an analog signal and outputs the analog signal to the LPF 109.
  • DZA unit 108 converts the fourth transmission signal input from GI adding unit 106 from a digital signal to an analog signal, and outputs the analog signal to LPF 110.
  • the LPF 109 which is a band limiting unit, limits the band of the third transmission signal input from the DZA unit 107 by passing only the low frequency region and outputs the third transmission signal to the quadrature modulation unit 111.
  • LPF 110 which is a band limiting unit, limits the band of the fourth transmission signal input from DZA unit 107 by passing only the low frequency region and outputs the fourth transmission signal to quadrature modulation unit 111. Due to the individual difference between LPF110 and LPF109, the fourth transmission signal that has passed through LPF110 has a delay time difference and amplitude difference from the third transmission signal that has passed through LPF109. Since the delay time difference and the amplitude difference are corrected by the force correction unit 103, the delay time difference and the amplitude difference generated with the third transmission signal that has passed through the LPF 109 are suppressed.
  • the orthogonal modulation unit 111 generates an IF (intermediate frequency) signal by performing orthogonal modulation on the third transmission signal input from the LPF 109 and the fourth transmission signal input from the LPF 110, and outputs the IF (intermediate frequency) signal to the wireless transmission unit 112.
  • Radio transmission section 112 up-converts the IF signal input from quadrature modulation section 111 to the radio frequency and outputs it to antenna 113 as a transmission signal.
  • the antenna 113 transmits the transmission signal input from the wireless transmission unit 112.
  • FIG. 6 is a block diagram showing a configuration of multicarrier receiving apparatus 200.
  • Antenna 201 receives a signal and outputs the signal to radio reception section 202.
  • Radio reception section 202 down-converts the received signal input from antenna 201 from a radio frequency to a baseband frequency and outputs the result to orthogonal demodulation section 203.
  • the quadrature demodulating unit 203 performs quadrature demodulation on the received signal input from the wireless receiving unit 202 to obtain a first received signal that is an I component time domain signal and a second received signal that is a Q component time domain signal. Generate. Then, quadrature demodulation section 203 outputs the generated first received signal to LPF 204 and outputs the generated second received signal to LPF 205.
  • LPF 204 serving as band limiting means performs band limiting by passing only the low frequency region of the first received signal input from quadrature demodulating section 203 and outputs the result to AZD section 206.
  • LPF 205 serving as band limiting means performs band limiting by passing only the low frequency region of the second received signal input from quadrature demodulating section 203 and outputs the result to AZD section 207.
  • the second received signal that has passed through the LPF 205 is a signal that has a delay time difference and an amplitude difference from the first received signal that has passed through the LPF 204 due to individual differences between the LPF 204 and the LPF 205.
  • the AZD unit 206 converts the first reception signal input from the LPF 204 into an analog signal power digital signal and outputs the analog signal power digital signal to the GI removal unit 208.
  • the AZD unit 207 converts the second received signal input from the LPF 205 into a digital signal and also outputs it to the GI removing unit 208.
  • GI removal section 208 removes GI from the first received signal input from AZD section 206 and the second received signal force input from AZD section 207, and outputs the result to FFT section 209.
  • the FFT unit 209 performs FFT on the first received signal and the second received signal input from the GI removing unit 208 and converts them into a time domain force frequency domain, and a third reception signal that is an I component frequency domain signal. And a fourth received signal that is a frequency domain signal of the Q component. Then, the FFT unit 209 outputs the generated complex reception signal (third reception signal (I component) + j X fourth reception signal (Q component)) composed of the third reception signal and the fourth reception signal to the separation unit 210. To do.
  • Separation section 210 receives the complex reception signal that also has the third reception signal and the fourth reception signal power input from FFT section 209, in two complex receptions of the fifth reception signal and the sixth reception signal in lOFDM symbol units.
  • the signal is separated and output to the correction unit 211.
  • the fifth received signal is the frequency domain signal of the first received signal after band limitation, GI removal and AZD conversion
  • the sixth received signal is the second after the band limitation, GI removal and AZD conversion. This is the frequency domain signal of the received signal.
  • the I component of the fifth received signal and the sixth received signal consists of the third received signal
  • the Q component of the fifth received signal and the sixth received signal consists of the fourth received signal.
  • Correction section 211 corrects one of the two complex reception signals, the fifth reception signal and the sixth reception signal, input from separation section 210 in the frequency domain. As a result, it is possible to compensate for the delay time difference and the amplitude difference between the first received signal and the second received signal that are generated by band limiting the first received signal and the second received signal with the LPF 204 and the LPF 205. Then, after correcting the delay time difference and the amplitude difference, the correction unit 211 outputs the fifth reception signal and the sixth reception signal to the synthesis unit 212.
  • the combining unit 212 combines the fifth received signal and the sixth received signal input from the correcting unit 211 and forms a complex composed of the third received signal and the fourth received signal before being separated by the separating unit 210. Regenerate the received signal. Then, combining section 212 outputs the regenerated third received signal and the complex received signal having the fourth received signal power to transmission path estimation compensating section 213.
  • Transmission path estimation / compensation section 213 performs transmission path estimation of a complex reception signal composed of the third reception signal and the fourth reception signal input from combining section 212. That is, the transmission path estimation compensation unit 213 Compensation is performed by estimating the amplitude and phase responses of the transmission paths of the third reception signal and the fourth reception signal input from the synthesis unit 212 using the known signal. Then, the transmission path estimation compensation unit 213 outputs the compensated third reception signal and fourth reception signal to the demodulation unit 214.
  • Demodulation section 214 demodulates the third reception signal and the fourth reception signal input from transmission path estimation compensation section 213 for each subcarrier and outputs the received data.
  • FIG. 7 is a block diagram showing the configuration of the correction unit 103.
  • the configuration of the correction unit 211 is the same as that in FIG.
  • Delay section 301 delays the fifth transmission signal input from demultiplexing section 102 and outputs the delayed signal to combining section 104.
  • the delay unit 301 delays the fifth transmission signal to be output at substantially the same timing as the timing at which the sixth transmission signal is output from the multiplication unit 302.
  • Multiplying section 302 performs correction by performing complex multiplication on the sixth transmission signal input from demultiplexing section 102 and the complex correction coefficient input from correction coefficient storage section 303. Then, multiplication section 302 outputs the corrected sixth transmission signal to combining section 104.
  • the correction coefficient storage unit 303 stores a plurality of complex correction coefficients (correction values) in advance, and multiplies the stored correction coefficient based on symbol head information that is information indicating the head of the symbol. Output to unit 302. The method for setting the correction coefficient will be described later.
  • digital modulation section 101 performs orthogonal modulation on transmission data to generate a first transmission signal and a second transmission signal.
  • the digital modulation unit 101 outputs in units of 1 OFDM symbol.
  • lOFDM symbols can be represented by first transmission signals for the number of IFFT points and second transmission signals for the number of IFFT points.
  • separation section 102 converts a complex transmission signal composed of a first transmission signal and a second transmission signal into two complex transmission signals, a fifth transmission signal and a sixth transmission signal. Separate into signals.
  • A is the complex output of digital modulator 101 (I + j X Q)
  • a * is the complex conjugate of A
  • N is the number of IFFT points
  • A is the complex output of digital modulator 101 (I + j X Q)
  • a * is the complex conjugate of A
  • N is the number of IFFT points
  • the separation unit 102 outputs the fifth transmission signal of the equation (1) and the sixth transmission signal of the equation (2).
  • multicarrier transmitting apparatus 100 uses correction section 103 to determine the amplitude difference and delay time difference between LPF 109 and LPF 110 for either one of equations (1) and (2).
  • Complex multiplication of complex correction coefficient Ck (k 0, 1, "',? ⁇ 1) that corrects imbalance of.
  • multicarrier transmitting apparatus 100 adds and combines the corrected fifth transmission signal and sixth transmission signal in combining section 104, and performs IFFT in IFFT section 105 to perform the time domain.
  • a third transmission signal and a fourth transmission signal converted into signals are generated.
  • the multicarrier transmission apparatus 100 converts the third transmission signal and the fourth transmission signal from a digital signal to an analog signal in the DZA unit 107 and the DZA unit 108, and only the low frequency is output in the LPF 109 and the LPF 110. Let it pass, quadrature-modulate by quadrature modulator 111 and send I believe.
  • FIG. 8 is a diagram showing a simulation result of reception constellation in the case where the delay time difference is 1Z8 sample period and there is no amplitude difference and multicarrier transmission apparatus 100 does not compensate.
  • FIG. 9 is a diagram showing a simulation result of reception constellation when the multicarrier transmitting apparatus 100 compensates when the delay time difference is 1Z8 sample period and there is no amplitude difference.
  • 8 and 9 show the simulation results when the number of subcarriers is 384, the number of FFT points is 512, the GI is 256 samples, the modulation method is 16QAM, and the channel estimation is estimated using a time-multiplexed pilot signal. 8 and 9, the interference can be almost completely eliminated by correcting the imbalance in the delay time difference between the third transmission signal and the fourth transmission signal.
  • FIG. 10 is a diagram showing a simulation result of the reception constellation when there is no delay time difference and the amplitude difference is ldB and the multicarrier transmission apparatus 100 does not compensate.
  • FIG. 11 is a diagram showing a simulation result of reception constellation when there is no delay time difference and the amplitude difference is Id B and compensation is performed by multicarrier transmitting apparatus 100. From Fig. 10 and Fig. 11, the interference can be almost completely eliminated by correcting the phase difference imbalance between the third transmission signal and the fourth transmission signal.
  • multicarrier receiving apparatus 200 that has received the multicarrier signal generates a first reception signal and a second reception signal by performing quadrature demodulation at orthogonal demodulation section 203, and LPF109 and LPF1 10 at a low frequency Only pass through.
  • the first received signal that has passed through LPF 109 and the second received signal that has passed through LPF 110 are signals in which an amplitude difference and a delay difference are added due to individual differences between LPFs 204 and 205.
  • the correction unit 211 needs to perform correction.
  • separation section 210 converts a complex received signal made up of the third received signal and the fourth received signal into a fifth received signal as shown in equation (1) and (2 This is separated into the sixth received signal as shown in equation (4).
  • multicarrier receiving apparatus 200 uses correction section 211 to perform equation (1) and equation (2) above.
  • Complex correction coefficient Ck (k 0, 1, "',? ⁇ 1) for correcting the imbalance between LPF204 and LPF205 for either the fifth received signal or the sixth received signal as shown in the equation Is a complex multiplication.
  • transmission path estimation / compensation section 213 performs compensation by estimating the amplitude and phase response of the transmission path using a known signal. Note that the transmission path estimation compensation unit 213 cannot compensate for the imbalance between the third received signal and the fourth received signal.
  • multicarrier receiving apparatus 200 performs demodulation processing on each subcarrier in demodulation section 214 and outputs received data.
  • FIG. 12 is a diagram showing a simulation result of reception constellation when the multicarrier receiving apparatus 200 does not compensate when the delay time difference is 1Z8 sample period and there is no amplitude difference.
  • FIG. 13 is a diagram illustrating a simulation result of reception constellation when the multicarrier receiving apparatus 200 compensates for a delay time difference of 1Z8 sample period and no amplitude difference. From Fig. 12 and Fig. 13, the interference can be almost completely eliminated by correcting the imbalance in the delay time difference between the first received signal and the second received signal.
  • FIG. 14 is a diagram showing a simulation result of reception constellation when there is no delay time difference and the amplitude difference is ldB and the multicarrier receiving apparatus 200 does not compensate.
  • FIG. 15 is a diagram showing a simulation result of reception constellation when there is no delay time difference and the amplitude difference is Id B and compensation is performed by multicarrier receiving apparatus 200. 14 and 15 show the simulation results when the number of subcarriers is 384, the number of FFT points is 512, the GI is 256 samples, the modulation method is 16QAM, and the channel estimation is estimated by a time-multiplexed pilot signal. From FIG. 14 and FIG. 15, the interference can be almost completely eliminated by correcting the imbalance in the phase difference between the first received signal and the second received signal.
  • FIG. 16 is a diagram showing LPF delay time characteristics when both the delay time difference and the amplitude difference exist and the delay time difference and the amplitude difference have frequency characteristics (ripple).
  • Is the group delay and the horizontal axis is the normal frequency.
  • Fig. 17 shows the LP when both the delay time difference and the amplitude difference exist and the delay time difference and the amplitude difference have frequency characteristics. It is a figure which shows the amplitude characteristic of F, A vertical axis
  • the I component has a ripple of ⁇ 1Z4 sample period, and the Q component is flat within the signal band.
  • the I component has a ⁇ ldB ripple, and the Q component is flat within the signal band.
  • FIG. 18 is a diagram illustrating a simulation result of reception constellation in the case of FIGS. 16 and 17 when the multicarrier receiving apparatus 200 does not compensate.
  • FIG. 19 is a diagram showing a simulation result of reception constellation in the case of FIG. 16 and FIG. From Fig. 18 and Fig. 19, interference can be almost completely eliminated even when there are frequency characteristics in the delay time difference and amplitude difference.
  • correction coefficients calculated in advance using LPFs 109 and 110 and LPFs 204 and 205 are set.
  • the correction unit 103 determines a correction coefficient based on the LPF characteristics that have been preliminarily measured using a network analyzer or the like.
  • Real frequency subcarrier k 0 to (NZ2) — LPF109 gain MAk (dB), group delay DAk (s), LPF110 gain MBk (dB), group delay DBk (s) at frequency 1 ) If the sampling period is Ts (s), the amplitude difference and delay time difference based on the LPF109 side (in-phase component side) are as shown in Equations (3) and (4).
  • Ck 10 "(-Mk / 20) X exp (j X D ZTs X k X 2 w ZN) (0 ⁇ k ⁇ (N / 2) — 1) k
  • Ck 10 "(-M Z20) X exp (—j X D / Ts X (N ⁇ k) X 2 ⁇ / N) (N / 2 ⁇ k
  • N-k is the part that corrects the amplitude difference.
  • jXD / TsX (N-k) X2 [pi] / N) is a portion for correcting the group delay time difference.
  • the complex transmission signal composed of the first transmission signal and the second transmission signal is converted into two complex signals, that is, the fifth transmission signal and the sixth transmission signal.
  • the reception side separates the complex reception signal composed of the third reception signal and the fourth reception signal into two complex reception signals of the fifth reception signal and the sixth reception signal. Since the fifth transmission signal and the sixth transmission signal are corrected and the separated fifth reception signal and sixth reception signal are corrected, the circuit scale is increased compared to the case where the delay time difference and the amplitude difference are corrected by other methods. It is possible to compensate for delay time and amplitude imbalance at low cost.
  • the first embodiment by correcting the amplitude difference and the delay time difference in the frequency domain, the high-order oversampling and the interpolation calculation required for correcting one sample or less in the time domain are unnecessary. Therefore, it is possible to reduce the manufacturing cost of the multicarrier transmission apparatus and the multicarrier reception apparatus and to prevent the circuit scale from increasing.
  • FIG. 20 is a block diagram showing a configuration of correction coefficient storage section 303 according to Embodiment 2 of the present invention.
  • the configuration of the multicarrier transmission apparatus is as shown in FIG.
  • the configuration of the multicarrier receiver is the same as in FIG. 6, and the configurations of the correction unit 103 and the correction unit 211 are the same as those in FIG.
  • the selection information storage unit 1601 stores the address of the amplitude coefficient storage unit 1602 in which the amplitude coefficient that optimizes the constellation is stored for each subcarrier, and the constellation is optimal. It stores the address of exp (j ⁇ 0 m) storage unit 1603 in which exp (j. 0 m) is stored. Then, the selection information storage unit 1601 stores the symbol head information as a trigger, and stores the address information, which is the address information, in order of the subcarrier numbers in the order of the amplitude coefficient storage unit 1602 and exp (j′ ⁇ m). Output to part 1603.
  • the amplitude coefficient storage unit 1602 outputs the amplitude coefficient stored in the address information address input from the selection information storage unit 1601 to the multiplier 1604 and the multiplier 1605.
  • exp (j-0 m) storage unit 1603 outputs exp (j' ⁇ m) stored in the address information address input from selection information storage unit 1601 to multiplier 1604 and multiplier 1605
  • Multiplier 1604 multiplies the amplitude coefficient input from amplitude coefficient storage section 1602 by the real part of exp (j′ ⁇ m) input from exp (j ⁇ ⁇ m) storage section 1603, thereby correcting coefficient. Calculate the real part of (correction value). Then, the multiplier 1604 outputs the real part of the calculated correction coefficient to the multiplication unit 302.
  • the multiplier 1605 multiplies the amplitude coefficient input from the amplitude coefficient storage unit 1602 by the imaginary part of exp (j′ ⁇ m) input from the exp (j ⁇ m) storage unit 1603, thereby correcting the correction coefficient. Calculate the imaginary part of (correction value). Then, the multiplier 1605 outputs the imaginary part of the calculated correction coefficient to the multiplication unit 302. Note that the operations of the multicarrier transmission apparatus and the multicarrier reception apparatus are the same as those in the first embodiment, and a description thereof will be omitted.
  • the correction coefficient is set by adjusting the constellation of each subcarrier to be the best in the apparatus adjustment stage.
  • the correction coefficient storage unit 303 stores 16 exp (j. 0 m) values in advance, and sets a constant for each subcarrier. Best for best or least error vector magnitude (EVM) e Select xp (j- ⁇ m).
  • EVM error vector magnitude
  • correction coefficient storage section 303 stores exp (j ⁇ 0 m) selected for each subcarrier. Based on exp (j. ⁇ m) for each subcarrier stored in the correction coefficient storage unit 303, exp (j ⁇ 0m) is called and used for correction.
  • a plurality of correction coefficients are stored for each predetermined amplitude difference, and the one with the best constellation or the minimum EVM is selected for each subcarrier.
  • ⁇ Rub For example, when it is desired to suppress the amplitude difference to 0.5 dB or less, the correction coefficient storage unit 303 sets the maximum amplitude difference of LPF, for example, “1, ⁇ 0.5 dB, ⁇ ldB, ⁇ 1.5 dB---J
  • the correction coefficient is the product of the amplitude coefficient and exp (j ′ ⁇ m). It becomes.
  • the delay time difference is corrected first, and then the amplitude difference is corrected. If necessary, repeat the delay time difference correction and the amplitude difference correction again. Even when delay time correction and amplitude difference correction are performed repeatedly, the delay time difference is corrected first, and then the amplitude difference is corrected.
  • a complex transmission signal composed of the first transmission signal and the second transmission signal is converted into two complex signals, the fifth transmission signal and the sixth transmission signal.
  • Transmission signal And the reception side separates the complex reception signal composed of the third reception signal and the fourth reception signal into two complex reception signals of the fifth reception signal and the sixth reception signal, and separates the fifth reception signal. Since the transmission signal and the sixth transmission signal are corrected and the separated fifth reception signal and sixth reception signal are corrected, the circuit scale must be increased compared to the case where the delay time difference and the amplitude difference are corrected by other methods. It is possible to compensate for delay time and amplitude imbalance at low cost.
  • the second embodiment by correcting the amplitude difference and the delay time difference in the frequency domain, the high-order oversampling and the interpolation calculation required for correcting one sample or less in the time domain are unnecessary. Therefore, it is possible to reduce the manufacturing cost of the multicarrier transmission apparatus and the multicarrier reception apparatus and to prevent the circuit scale from increasing.
  • correction is performed on the sixth transmission signal.
  • the present invention is not limited to this, and correction may be performed on the fifth transmission signal. Corrections may be made to both the fifth transmission signal and the sixth transmission signal.
  • the sixth received signal is corrected.
  • the present invention is not limited to this, and the fifth received signal may be corrected. Corrections may be made to both the fifth received signal and the sixth received signal.
  • the power for correcting the amplitude difference and the delay time difference in both the multicarrier transmission apparatus 100 and the multicarrier reception apparatus 200 is not limited to this. The amplitude difference and the delay time difference may be corrected by only one of the apparatus 100 and the multicarrier receiving apparatus 200.
  • the multicarrier transmission apparatus, multicarrier reception apparatus, transmission method, and reception method that are useful in the present invention are particularly suitable for compensating for an imbalance in amplitude or delay time between the in-phase component and the quadrature component. is there.

Abstract

La présente invention concerne un appareil de transmission multiporteuse dans lequel les inégalités dans les temps de retard et les amplitudes peuvent être compensés à un faible coût et sans augmenter l’échelle du circuit. Dans cet appareil, une partie de modulation numérique (101) effectue une modulation en quadrature de manière à générer un signal de transport complexe comprenant à la fois un premier signal de transport, qui est un signal de domaine de fréquence de composante Q, et un deuxième signal de transport qui est un signal de domaine de fréquence de composante Q. Une partie de séparation (102) sépare le signal de transport complexe en un cinquième signal de transport qui est le signal de domaine de fréquence d’un troisième signal de transport qui sera un signal de domaine de temps de composante U après IFFT, et un sixième signal de transport qui est le signal de domaine de fréquence d’un quatrième signal de transport qui sera un signal de domaine de temps de composante Q après IFFT. Une partie de correction (103) corrige un des cinquième ou sixième signal de transport de manière à réduire la différence du temps de retard et la différence d’amplitude entre le troisième et le quatrième signal de transport se produisant à une limitation de bande du troisième ou quatrième signal.
PCT/JP2006/323727 2005-11-29 2006-11-28 Appareil de transmission multiporteuse, appareil de reception multiporteuse, procede de reception et de transmission WO2007063855A1 (fr)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
JP2005-344130 2005-11-29
JP2005344130 2005-11-29

Publications (1)

Publication Number Publication Date
WO2007063855A1 true WO2007063855A1 (fr) 2007-06-07

Family

ID=38092188

Family Applications (1)

Application Number Title Priority Date Filing Date
PCT/JP2006/323727 WO2007063855A1 (fr) 2005-11-29 2006-11-28 Appareil de transmission multiporteuse, appareil de reception multiporteuse, procede de reception et de transmission

Country Status (1)

Country Link
WO (1) WO2007063855A1 (fr)

Cited By (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JP2009111900A (ja) * 2007-10-31 2009-05-21 Kenwood Corp シンボル判定装置およびシンボル判定方法
JP2009272683A (ja) * 2008-04-30 2009-11-19 Toshiba Corp 無線通信装置
JP2011215128A (ja) * 2010-03-16 2011-10-27 Denso Corp Ｇｌｏｎａｓｓ受信機

Citations (9)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JPH04274642A (ja) * 1991-03-01 1992-09-30 Nippon Telegr & Teleph Corp <Ntt> 直交変調回路
WO1997008866A1 (fr) * 1995-08-31 1997-03-06 Usa Digital Radio Partners, L.P. Recuperation du rythme des trames a formes d'ondes numeriques compatibles a modulation d'amplitude, et mesure de la puissance synchrone des trames
WO2003003686A1 (fr) * 2001-06-29 2003-01-09 Nokia Corporation Desequilibre en phase et en quadrature
JP2003032314A (ja) * 2001-07-18 2003-01-31 Fujitsu General Ltd 位相誤差補正方法および装置
US20030231726A1 (en) * 2002-06-12 2003-12-18 Andreas Schuchert Arrangement and method for frequency domain compensation of OFDM signals with IQ imbalance
WO2004039028A2 (fr) * 2002-10-25 2004-05-06 Koninklijke Philips Electronics N.V. Compensation de defaut d'adaptation quadratique
US20040095993A1 (en) * 2002-11-20 2004-05-20 Der-Zheng Liu Method and apparatus for I/Q imbalance estimation
WO2004082232A1 (fr) * 2003-03-12 2004-09-23 Koninklijke Philips Electronics N.V. Emetteur-recepteur a systeme de compensation de desadaptation des composantes en phase et en quadrature
US20050118963A1 (en) * 2003-12-02 2005-06-02 Mao-Ching Chiu Method and apparatus for I/Q imbalance calibration of a transmitter system

Patent Citations (9)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JPH04274642A (ja) * 1991-03-01 1992-09-30 Nippon Telegr & Teleph Corp <Ntt> 直交変調回路
WO1997008866A1 (fr) * 1995-08-31 1997-03-06 Usa Digital Radio Partners, L.P. Recuperation du rythme des trames a formes d'ondes numeriques compatibles a modulation d'amplitude, et mesure de la puissance synchrone des trames
WO2003003686A1 (fr) * 2001-06-29 2003-01-09 Nokia Corporation Desequilibre en phase et en quadrature
JP2003032314A (ja) * 2001-07-18 2003-01-31 Fujitsu General Ltd 位相誤差補正方法および装置
US20030231726A1 (en) * 2002-06-12 2003-12-18 Andreas Schuchert Arrangement and method for frequency domain compensation of OFDM signals with IQ imbalance
WO2004039028A2 (fr) * 2002-10-25 2004-05-06 Koninklijke Philips Electronics N.V. Compensation de defaut d'adaptation quadratique
US20040095993A1 (en) * 2002-11-20 2004-05-20 Der-Zheng Liu Method and apparatus for I/Q imbalance estimation
WO2004082232A1 (fr) * 2003-03-12 2004-09-23 Koninklijke Philips Electronics N.V. Emetteur-recepteur a systeme de compensation de desadaptation des composantes en phase et en quadrature
US20050118963A1 (en) * 2003-12-02 2005-06-02 Mao-Ching Chiu Method and apparatus for I/Q imbalance calibration of a transmitter system

Non-Patent Citations (1)

* Cited by examiner, † Cited by third party
Title
HORI T. ET AL.: "OFDM System ni okeru Hencho Seido no Kitei ni Kansuru Kento", TECHNICAL REPORT OF IEICE, vol. 98, no. 535, 21 January 1999 (1999-01-21), pages 15 - 20, XP003013268 *

Cited By (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JP2009111900A (ja) * 2007-10-31 2009-05-21 Kenwood Corp シンボル判定装置およびシンボル判定方法
JP2009272683A (ja) * 2008-04-30 2009-11-19 Toshiba Corp 無線通信装置
JP2011215128A (ja) * 2010-03-16 2011-10-27 Denso Corp Ｇｌｏｎａｓｓ受信機

Similar Documents

Publication Publication Date Title
JP5524943B2 (ja) 受信装置
US7961800B2 (en) Adaptive radio/modulation apparatus, receiver apparatus, wireless communication system, and wireless communication method
CN101361307B (zh) 无线通信装置
JP4213734B2 (ja) Ｏｆｄｍを用いた無線通信方法及びｏｆｄｍ受信装置
US20090092193A1 (en) Multi carrier transmission device, multi carrier reception device, and communication method
JP2007208654A (ja) Ｏｆｄｍを用いた無線通信方法、ｏｆｄｍ送信装置及びｏｆｄｍ受信装置
JP5632457B2 (ja) マルチキャリア信号におけるピーク電力対平均電力比の低減
KR101468514B1 (ko) 통신 시스템에서의 잔류 주파수 에러를 추정하는 방법 및 장치
WO2007014067A2 (fr) Superposition/addition avec correction du decalage en continu
EP2159980B1 (fr) Appareil et procédé de réception de signaux multiplexés à division de fréquence orthogonale
JP4311132B2 (ja) Ｏｆｄｍ伝送方式における受信装置
JP2004080731A (ja) Ｏｆｄｍ受信装置及びｏｆｄｍ信号の補正方法
CN101133580A (zh) 接收装置
US20110167321A1 (en) Apparatus and method of transmitting and receiving data for improving transmission rate
JP2005192109A (ja) Ｏｆｄｍ無線通信システムのための伝搬路推定器及びこれを用いた受信装置
US20080101216A1 (en) Orthogonal frequency division multiplex (ofdm) signal equalizier
WO2007063855A1 (fr) Appareil de transmission multiporteuse, appareil de reception multiporteuse, procede de reception et de transmission
JP6743327B2 (ja) 無線通信システム、無線送信装置および無線受信装置
JP2007142603A (ja) 受信装置並びにチャネル推定装置
US7321550B2 (en) Method of equalization in an OFDM system
WO2001017149A1 (fr) Appareil de communication ofdm et procede d&#39;estimation du chemin de propagation
US8311137B1 (en) Method for DC offset removal in OFDM systems
JP3539383B2 (ja) Ｏｆｄｍ通信装置
KR100874011B1 (ko) 무선 통신 시스템에서의 주파수 옵셋 보상 장치 및 방법
JP2008022339A (ja) 無線通信装置及び無線通信方法

Legal Events

Date Code Title Description
121 Ep: the epo has been informed by wipo that ep was designated in this application
NENP Non-entry into the national phase

Ref country code: DE

122 Ep: pct application non-entry in european phase

Ref document number: 06833531

Country of ref document: EP

Kind code of ref document: A1

NENP Non-entry into the national phase

Ref country code: JP