WO2007063855A1 - Multicarrier transmitting apparatus, multicarrier receiving apparatus, transmitting method and receiving method - Google Patents

Multicarrier transmitting apparatus, multicarrier receiving apparatus, transmitting method and receiving method

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Publication number
WO2007063855A1
WO2007063855A1 PCT/JP2006/323727 JP2006323727W WO2007063855A1 WO 2007063855 A1 WO2007063855 A1 WO 2007063855A1 JP 2006323727 W JP2006323727 W JP 2006323727W WO 2007063855 A1 WO2007063855 A1 WO 2007063855A1
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WO
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Patent type
Prior art keywords
signal
transmission
transmission signal
received
complex
Prior art date
Application number
PCT/JP2006/323727
Other languages
French (fr)
Japanese (ja)
Inventor
Shoichi Fujita
Sadaki Futagi
Original Assignee
Matsushita Electric Industrial Co., Ltd.
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Classifications

    • HELECTRICITY
    • H04ELECTRIC COMMUNICATION TECHNIQUE
    • H04LTRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00Modulated-carrier systems
    • H04L27/32Carrier systems characterised by combinations of two or more of the types covered by groups H04L27/02, H04L27/10, H04L27/18 or H04L27/26
    • H04L27/34Amplitude- and phase-modulated carrier systems, e.g. quadrature-amplitude modulated carrier systems
    • H04L27/36Modulator circuits; Transmitter circuits
    • H04L27/366Arrangements for compensating undesirable properties of the transmission path between the modulator and the demodulator
    • HELECTRICITY
    • H04ELECTRIC COMMUNICATION TECHNIQUE
    • H04LTRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00Modulated-carrier systems
    • H04L27/26Systems using multi-frequency codes
    • H04L27/2601Multicarrier modulation systems
    • H04L27/2626Arrangements specific to the transmitter
    • HELECTRICITY
    • H04ELECTRIC COMMUNICATION TECHNIQUE
    • H04LTRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00Modulated-carrier systems
    • H04L27/32Carrier systems characterised by combinations of two or more of the types covered by groups H04L27/02, H04L27/10, H04L27/18 or H04L27/26
    • H04L27/34Amplitude- and phase-modulated carrier systems, e.g. quadrature-amplitude modulated carrier systems
    • H04L27/36Modulator circuits; Transmitter circuits
    • H04L27/362Modulation using more than one carrier, e.g. with quadrature carriers, separately amplitude modulated
    • H04L27/364Arrangements for overcoming imperfections in the modulator, e.g. quadrature error or unbalanced I and Q levels

Abstract

A multicarrier transmitting apparatus wherein the inequalities of the delay times and amplitudes can be compensated for at a low cost without increasing the circuit scale. In this apparatus, a digital modulating part (101) performs a quadrature modulation to generate a complex transport signal comprising both a first transport signal, which is an I-component frequency domain signal, and a second transport signal that is a Q-component frequency domain signal. A separating part (102) separates the complex transport signal into a fifth transport signal, which is the frequency domain signal of a third transport signal that will be an I-component time domain signal after IFFT, and a sixth transport signal that is the frequency domain signal of a fourth transport signal that will be a Q-component time domain signal after IFFT. A correcting part (103) corrects one of the fifth and sixth transport signals such that the delay time difference and amplitude difference between the third and fourth transport signals occurring at band limitation of the third and fourth transport signals are reduced.

Description

Specification

Multicarrier transmission apparatus, multicarrier receiving apparatus, transmission method and reception method

Technical field

[0001] The present invention is a multicarrier transmission apparatus, multicarrier receiving apparatus, a transmitting method and a receiving method, in particular, an imbalance of amplitude or time delay between the in-phase component (I component) and quadrature component (Q component) multicarrier transmitting apparatus that compensates for, multicarrier receiving apparatus, a transmitting method and a receiving method.

BACKGROUND

[0002] For example, in wideband multi-carrier communication signal band 100 MHz, it is difficult to digital linear 交検 waves, generally analog quadrature detection is used. In this case, (hereinafter referred to "DZA") digital Z-analog conversion of the post filter (hereinafter referred to "AZD") analog Z digital I and Q channels to Ana port grotesque one-pass filter as a transformation of the pre-filter ( hereinafter referred to as "LPF") is required. That, LPF occurs during DZA conversion and AZD conversion is necessary to remove one or more aliasing noise-half the sampling frequency. At this time, due to individual differences of the LPF, the amplitude imbalance of imbalance and the delay time between the I channel and the Q Chiyane Le occurs. Imbalance amplitude imbalance and the delay time between the I and Q channels, the performance is degraded causing inter-carrier interference.

[0003] the OFDM is one of multicarrier communication in (Orthogonal Frequency Division Multiplexi ng), effects of delay difference between the I channel and the Q channel (hereinafter referred to "FFT") large appliances Fast Fourier transform suppressed without the deterioration in the delay time difference of about 1Z10 sample period that is greater I have one I force. In the following description, one sample at or between 1 sample period of the FFT is referred to as a "sample". At the time of AZD, because it may be over-sampling, not always be matched with one sample of one sample and FFT of AZD.

[0004] However, the suppressing the delay time difference of about 1Z10 sample period, connexion and the analog LPF are very strict. Therefore, it becomes necessary method of compensating a digital circuit the amplitude imbalance and the delay time between the I and Q channels.

[0005] Conventionally, as a method for compensating for amplitude imbalance of imbalance and the delay time between the I and Q channels, a method of using a small LPF individual differences of the amplitude and group delay (hereinafter, "first there is a method of describing the method "), or by adjusting individual LPF suppress the amplitude difference and differential group delay (hereinafter referred to as" second method "). Conventionally, to extract the timing separately from the in-phase and quadrature components, is described as a method of absorbing the delay time difference by AZ D converter at the optimum timing of each phase and quadrature components (hereinafter "third method" ) is the known, Ru (e.g., Patent Document 1).

[0006] FIG. 1 is a diagram showing a receiving cons Talay Chillon result when there is no imbalance of the delay time between the in-phase and quadrature components caused by the individual difference of the LPF, FIG. 2, individual LPF it is a diagram showing the performance deterioration due to imbalance in the delay time between the in-phase component and the quadrature component generated by the difference. Figure 2 shows a case where the delay time difference between 1Z8 sample between the in-phase component and the quadrature component has occurred.

[0007] In a multi-carrier such as OFDM, the influence of the delay time difference is significantly deteriorated even a slight difference subatmospheric instrument 1 Sample hour. It has a sub-carrier be a baseband signal, because the delay time difference with respect to the period of the sub-carrier can not be ignored. Thus, the effect as the high frequency sub-carrier is increased, the influence of the more delay time difference subcarriers away from the center of the modulation signal in the signal band of IFZRF band increases. Also, the analog LPF cutoff vicinity, that is, the element sensitivity higher end of the passband variation increases high, it is difficult to avoid degradation.

[0008] As shown in FIG. 2, in the delay time difference 1Z8 sample, orthogonality between subcarriers collapsed been in cons Talay Chillon greatly deteriorates. The signal band and 100 MHz (base band signal is 50 MHz), when the number of FFT points in the 384 the number of subcarriers to 512, sub pump ring clock becomes ΙΟΟΜΗζ Χ 512Z384 = 133MHz about, 1 sample time and 7. 5 ns Become. Therefore, 1/8 sample is to 940ps. On the other hand, the group delay time of the 50MHz bandwidth of the LPF is on the order of ordinary number 10 ns. For example, if the 48ns of group delay time of the LPF, the case of using the LPF in the transmitting side and the receiving side, the group delay time is a 48 X 2 = 96ns. Therefore, In order to suppress the delay difference 1Z8 sample = 940Ps, about 1% of the variation, i.e. not allowed about one percent of individuals feed force.

[0009] FIG. 3 is a diagram showing a receiving cons Talay Chillon result when the amplitude imbalance is not the name of the between the in-phase and quadrature components caused by the individual difference of the LPF, FIG. 4, the individual difference of the LPF by illustrates the performance degradation due to imbalance amplitude between arising phase and quadrature components. Figure 4 shows a case where the amplitude difference ldB between the in-phase and quadrature components arises. As shown in FIG. 4, interference occurs between subcarriers by the amplitude imbalance, performance deteriorates. Amplitude difference is, the impact is small compared to the delay time difference. For example, to suppress the passband amplitude difference LPF to ldB is easier to suppress the group delay difference of 1%.

Patent Document 1: JP 2001- 24722 JP

Disclosure of the Invention

Problems that the Invention is to you'll solve

While [0010] is the force, in the conventional apparatus, in the first method and the second method, the specification of the LPF is severe, and ヽ such Hakare cost is up to low Kosuti spoon for, cormorants problem is there. Further, in the third method, one sample is periodic possible compensation of delay time smaller than, there is a problem that timing extraction circuit, the circuit scale becomes large because two required. Further, in the third method, Do can compensate for the imbalance of the amplitude, and it is cormorants problem.

[0011] An object of the present invention, multicarrier transmitting apparatus capable of compensating for the imbalance of the delay time and amplitude at a low cost without increasing the circuit scale, multicarrier reception apparatus, provides a transmission method and a receiving method It is to be.

Means for Solving the Problems

[0012] Multi-carrier transmission system of the present invention, the complex transmission comprising a second transmission signal is a frequency domain signal of the first transmission signal and the Q component is a frequency domain signal of quadrature modulation to I component transmission data a digital modulating means for generating a signal, the time domain of the fifth transmission signal and the Q-component Ru frequency domain signal der third transmission signal comprising the complex transmission signal to the inverse fast off one Fourier time domain signals converted to the I component separating means for separating the complex transmission signal to the sixth transmission signal is a frequency domain signal of the fourth transmission signal comprising a signal, the at the time of band-limiting said third transmission signal and the fourth transmission signal first and correcting means for correcting the fifth transmission signal or the previous SL sixth transmission signal so that the amplitude difference and the delay time difference is reduced between the three transmission signal and the fourth transmission signal, the after correction by said correcting means the fifth transmission signal Synthesizing means for regenerating the complex transmission signal by combining said sixth transmission signal, said inverse fast Fourier transform of the complex transmission signal regenerated third transmission signal and at the synthesizing means first an inverse fast Fourier transform means for generating and four transmission signals, the band limiting means for limiting the bandwidth of said third transmission signal generated and the fourth transmission signal by the inverse fast Fourier transform unit, the band-limited It adopts a configuration comprising a transmission means for transmitting a transmission signal composed of the third transmission signal and the fourth transmission signal band-limited by means.

[0013] Multi-carrier receiver apparatus of the present invention, an orthogonal demodulation to generate a second received signal which is a time domain signal of the first received signal and the Q component is the time domain signal of the I component by orthogonal demodulating the received signal means and the band limiting means to limit the bandwidth of the first receive signal and the second received signal, fast Fourier transform said first receive signal and the second received signal band-limited by the band limiting means and fast Fourier transform means for generating a complex reception signal comprising a fourth received signal is a frequency domain signal of the third received signal and the Q component is a frequency domain signal of the I component and the frequency region of the first received signal separating means for separating the received complex signal to a sixth received signal is a frequency domain signal of the fifth received signal and the second reception signal is a signal, the first reception signal and the second received signal to the band Correcting the fifth received signal or pre-Symbol sixth received signal so that the amplitude difference and the delay time difference is reduced between the first reception signal and the second reception signal generated when the band-limited by limiter means a correction unit, a synthesizing means for regenerating the complex received signal by combining said fifth received signal and the sixth received signal after correction by the correction unit, the complex that has been regenerated by said synthesizing means It adopts a configuration comprising demodulating means for demodulating the received signal.

[0014] transmission method of the present invention, generates a complex transmission signal consisting of a second transmission signal is a frequency domain signal of the first transmission signal and the Q component is a frequency domain signal of the quadrature modulation on the I component of the transmission data the method comprising the complex transmission signal of the inverse fast Fourier transform to the fifth transmission signal and the fourth transmission signal comprising a time domain signal of the Q component is the frequency domain signal of the third transmission signal comprising a time domain signal of the I component steps and, the third transmission signal and the third transmission signal when that band-limits the fourth transmission signal and the fourth transmission signal to separate the pre-SL complex transmission signal to the sixth transmission signal is a frequency domain signal combines the step of amplitude difference and delay time difference correcting the fifth transmission signal or said sixth transmission signal so as to reduce, the fifth transmission signal after the correction and the said sixth transmission signal between the the multi-Te And re-generating a transmission signal, and generating said fourth transmission signal and the third transmission signal the complex transmission signal regenerated by converting the inverse fast off one Rie, that were generated the first as comprising the step of limiting the band of the three transmission signal and the fourth transmission signal, the step that sends a transmission signal composed of the limited bandwidth the third transmission signal and the fourth transmission signal, the did.

[0015] reception method of the present invention includes a Sutetsu flop to generate a second received signal which is a time domain signal of the first received signal and the Q component is the time domain signal of the I component by orthogonal demodulating the received signal, a step of limiting the bandwidth of said first receiving signal and the second reception signal, a third of the frequency domain signals of the I component the first received signal is band-limited and the second received signal by fast Fourier transform generating a complex reception signal comprising a fourth received signal to be a frequency-domain signal of the received signal and Q components, the fifth received signal is a frequency domain signal of the first reception signal and the second received signal steps and, the first reception signal and the second received and the first received signal generated in limiting the band of the second received signal to separate the received complex signal to a sixth received signal is a frequency-domain signal signal of Steps and, said combining the fifth received signal and the sixth received signal to the corrected complex amplitude difference and the delay time difference of correcting the fifth received signal or said sixth received signal so as to decrease a step of regenerating the received signal, the received complex signal which is regenerated and so includes the steps of: demodulating.

Effect of the invention

[0016] According to the present invention, it is possible to compensate for the imbalance of the delay time and amplitude at a low cost without increasing the circuit scale.

BRIEF DESCRIPTION OF THE DRAWINGS

[0017] shows the Figure 1 receiver cons Talay Figure [2] show simulation results for Chillon received cons Talay Chillon simulation results

Shows the FIG. 3 receives cons Talay Chillon simulation results

Shows the FIG. 4 receives cons Talay Chillon simulation results

圆 5] Block diagram 圆 7 shows the configuration of a multicarrier receiving apparatus according to a first embodiment of a block diagram 圆 6] The present invention showing the configuration of a multicarrier transmitting apparatus according to a first embodiment of the present invention] of the present invention block diagram showing the configuration of a correction unit according to the first embodiment

[8] show simulation results of the reception cons Talay Chillon according to the first embodiment of the present invention

[9] show simulation results of the reception cons Talay Chillon according to the first embodiment of the present invention

It shows the FIG. 10 simulation result of the reception cons Talay Chillon according to the first embodiment of the present invention

[11] show simulation results of the reception cons Talay Chillon according to the first embodiment of the present invention

It shows the FIG. 12 simulation result of the reception cons Talay Chillon according to the first embodiment of the present invention

It shows the FIG. 13 simulation result of the reception cons Talay Chillon according to the first embodiment of the present invention

[14] show simulation results of the reception cons Talay Chillon according to the first embodiment of the present invention

It shows the FIG. 15 simulation result of the reception cons Talay Chillon according to the first embodiment of the present invention

圆 16] shows a delay time characteristic of the LPF according to the first embodiment of the present invention

圆 17] shows an amplitude characteristic of the LPF according to the first embodiment of the present invention

[18] show simulation results of the reception cons Talay Chillon according to the first embodiment of the present invention

Implementing the block diagram invention shown Figure [20] configuration of the correction coefficient storage unit according to the second embodiment of the present invention showing the [19] simulation result of the reception cons Talay Chillon according to the first embodiment of the present invention bEST mODE fOR

[0018] Hereinafter, embodiments of the present invention, with reference to the accompanying drawings.

[0019] (Embodiment 1)

Figure 5 is a block diagram showing the configuration of a multicarrier transmitting apparatus 100 according to the first embodiment of the present invention.

[0020] digital modulating section 101, the transmission data encoded by the encoding unit (not shown), orthogonally modulated by a modulation scheme such as Q PSK or 16QAM, the first transmission is a frequency domain signal I component generating a second transmission signal is a frequency-domain signal of the signal and the Q-component. The digital modulation section 101, in the case of providing the guard bands, inserts data "0" to the sub-carriers allocated to the guard bands. For example, in the case of 1S this can generate the 512 subcarriers when inverse fast Fourier transform (hereinafter referred to as "IF FT") point 512, digital modulation unit 101, 0Hz including negative frequency of the inner the insert data on both sides of the 384 subcarriers, the total 128 subcarriers and remaining outer subcarriers OHz inserting data "0". Thus, the subcarrier data is inserted is only lower frequencies bands, facilitates removal of the aliasing noise. Then, Digitally Le modulation unit 101, a complex transmission signal consisting of the first transmit signal and the second transmit signal produced (first transmission signal (I component) + j X second transmission signal (Q component)) the lOFDM symbol unit in output to separation section 102.

[0021] separating unit 102, a complex transmission signal consisting of the first transmit signal and the second transmission signal inputted from the digital modulation unit 101, in lOFDM symbol units, the two fifth transmission signal and the sixth transmit signal separating the complex transmission signal to output to the correction unit 103. Here, the fifth transmission signal is a frequency domain signal of the third transmission signal which is a time domain signal of the I component after the complex transmission signal becomes the first transmission signal and a second transmission signal power to IFFT, sixth transmission signal is a frequency domain signal of the first transmission signal and the fourth transmission signal complex transmission signal consisting of the second transmission signal is a time domain signal of the Q component after IFFT. Also, I component of the fifth transmission signal and the sixth transmission signal consists first transmission signal, Q components of the fifth transmission signal and the sixth transmit signal is the second transmission signal power. [0022] correction unit 103, in the frequency domain, to correct one of the two complex transmission signal of the fifth transmission signal and the sixth transmission signal inputted from demultiplexing section 102. Thus, by the delay time difference and amplitude difference between the third transmission signal and a fourth transmission signal caused by the band limitation by LPF109 and LPF110 later a third transmission signal and a fourth transmission signal is reduced urchin it can be compensated. Then, the correction unit 103, after compensating the delay time difference and amplitude difference, and outputs the fifth transmission signal and the sixth transmission signal to the combining unit 104.

[0023] synthesis unit 104 synthesizes the fifth transmission signal and the sixth transmission signal inputted from the correction unit 103, and a first transmission signal and the second transmission signal before separating in the separation unit 102 complex to regenerate the No. transmission signal. Then, the composition unit 104 outputs the first transmission signal regenerated and a second transmission signal Kakara becomes complex transmission signal to the IFFT unit 105.

[0024] IFFT unit 105, a complex transmission signal ing from the first transmission signal and a second transmission signal inputted from the synthesis unit 104 converts IFFT, i.e. the frequency domain signal mosquitoes ゝ et time domain signal, the third transmission generating a signal and a fourth transmission signal. Then, IFFT unit 105 outputs the generated third transmission signal and the fourth transmission signal to the GI adding section 106.

[0025] GI adding section 106 adds a GI to the third transmission signal and a fourth transmission signal inputted from IFFT section 105. The GI adding unit 106 outputs the third transmission signal added the GI to DZA unit 107, and outputs the fourth transmission signal added the GI to DZA unit 108.

[0026] DZA unit 107 outputs the third transmission signal inputted from the GI adding unit 106 from a digital signal to LPF109 into an analog signal.

[0027] DZA unit 108 outputs the fourth transmission signal inputted from the GI adding unit 106 from a digital signal to LPF110 into an analog signal.

[0028] a band limiting means LPF109 is to the third transmission signal inputted from DZA unit 107, and outputs it to the orthogonal modulation section 111 performs band limitation by passing only the low frequency range.

[0029] a band limiting means LPF110 is to fourth transmission signal inputted from DZA unit 107, and outputs it to the orthogonal modulation section 111 performs band limitation by passing only the low frequency range. Fourth transmission signal passing through the LPF110 is therefore the individual difference between the LPF110 and LPF 109, because Ji roughness force at force correcting section 103 which will be the third transmission signal time difference and amplitude difference delay and having passed through the LPF 109 is generated since the delay time difference and amplitude difference are corrected, the delay time difference and amplitude difference occurs between the third transmission signal that has passed through the LPF109 is to have been suppressed.

[0030] Orthogonal modulation unit 111 generates and outputs the third transmission signal and IF quadrature modulation to a fourth transmission signal inputted from LPF 110 (intermediate frequency) signal inputted from LPF109 to the radio transmitting section 112.

[0031] Radio transmitting section 112 outputs IF force IF signal input from the quadrature modulation unit 111 also § Ppukonbato a radio frequency to the antenna 113 as a transmission signal.

[0032] Antenna 113 transmits a transmission signal input from radio transmission section 112.

[0033] Next, the configuration of a multicarrier receiving apparatus 200 will be described with reference to FIG. Figure 6 is a block diagram showing the configuration of a multicarrier receiving apparatus 200.

[0034] Antenna 201 receives and outputs a signal to the radio receiving section 202.

[0035] Wireless receiver 202 outputs the received signal input from the antenna 201 from a radio frequency down-converted to baseband frequency to a quadrature demodulator 203.

[0036] quadrature demodulator 203, a second reception signal is a time domain signal of the first reception signal and the Q component is the time domain signal of the I component and quadrature demodulates the received signal inputted from radio receiving section 202 generated. The quadrature demodulation unit 203, together with the LPF204 outputs the first reception signal generated, and outputs the generated second receive signal to the LPF 205.

[0037] a band limiting means LPF204 is you output to AZD unit 206 performs band limitation by passing only the low frequency region of the first received signal input from the orthogonal demodulation section 203.

[0038] a band limiting means LPF205 is you output to AZD section 207 performs band limitation by passing only the low frequency region of the second received signal input from the orthogonal demodulation section 203. Second reception signal that has passed through the LPF 205 is the individual difference between the LPF 204 and the LPF 205, is decreased to a signal time difference and amplitude difference delay occurs between the first received signal passing through the LPF 204.

[0039] AZD unit 206 outputs the first reception signal inputted from the LPF204 to an analog signal power Digitally Le signal to GI removing section 208. [0040] AZD unit 207 outputs the second reception signal inputted from the LPF205 converts analog signals force to Digitally Le signal to GI removing section 208.

[0041] GI removing section 208, the second received signal strength inputted from the first reception signal and AZD 207 input from AZD 206 be removed GI, is outputted to the FFT unit 209.

[0042] FFT section 209 converts the first received signal and second received signal input from GI removing section 208 FF T to the time domain force frequency domain, the third receiving a frequency domain signal I component generating a fourth reception signal is a frequency domain signal signal signal and the Q component. Then, FFT section 209, outputs the generated third received signal and the complex reception signals consisting of the fourth reception signal (the third reception signal (I component) + j X fourth reception signal (Q component)) to the separation unit 210 to.

[0043] separating unit 210, a third reception signal and also complex reception signal fourth reception signal power inputted from FFT section 209, in lOFDM symbol unit, two complex reception of the fifth received signal and the sixth received signal It is separated into the signal output to the correction unit 211. Here, the fifth received signal is band-limited, the frequency domain signal of the first received signal after GI removal and AZD conversion, sixth received signal is band-limited, the second after the GI removal, and AZD conversion a frequency domain signal of the received signal. Also, I component of the fifth received signal and the sixth received signal and the third received signal or Rannahli, Q components of the fifth received signal and the sixth received signal consists of a fourth received signal.

[0044] correction unit 211, in the frequency domain, to correct one of the two complex reception signal of the fifth received signal and the sixth received signal inputted from demultiplexing section 210. This makes it possible to compensate for the delay time difference and amplitude difference between the first reception signal and the second received signal caused by band limiting the first reception signal and the second reception signal at LPF204 and LPF 205. Then, the correction unit 211 outputs after compensating the delay time difference and amplitude difference, a fifth received signal and the sixth received signal to the combining unit 212.

[0045] synthesis unit 212 synthesizes the fifth received signal and the sixth received signal input from the correction unit 211, and a third received signal and the fourth received signal before separating in the separation unit 210 complex to regenerate the received signals. Then, the composition unit 212 outputs the third reception signal and the complex reception signal comprising a fourth received signal power that is regenerated to the transmission path estimation compensator 213.

[0046] channel estimation compensation unit 213 performs channel estimation of the third received signal and the complex reception signal comprising a fourth received signal input from combining section 212. That is, channel estimation compensation unit 213, using known signals, and estimates to compensate for the amplitude and phase response of the transfer sending passage of the third received signal and the fourth received signal input from combining section 212. Then, channel estimation compensation unit 213 outputs the third reception signal and the fourth received signal after compensation to demodulation section 214.

[0047] demodulator 214 outputs the received data by demodulating the third reception signal and the fourth received signal input from the transmission path estimation compensator 213 for each subcarrier.

[0048] Next, the configuration of the correction unit 103 will be described with reference to FIG. Figure 7 is a block diagram showing a configuration of the correction unit 103. Since configuration of the correction unit 211 is the same as that in FIG. 7, a description of its omitted.

[0049] Delay unit 301, and input from the separation unit 102 delays the fifth transmission signal and outputs it to the combining unit 104. Delay unit 301, a sixth transmission signal is substantially at the same timing as the timing output from the multiplying unit 302 delays as the fifth transmission signal is output.

[0050] multiplication unit 302 performs correction by relative sixth transmission signal inputted from demultiplexing section 102, a correction coefficient of a complex number input from the correction coefficient storage unit 303 to complex multiplication. Then, the multiplication unit 302 outputs the sixth transmission signal corrected to the combining unit 104.

[0051] correction coefficient storage unit 303 stores in advance a correction coefficient of the plurality of complex (correction value), based on the symbol start information indicating a start of the symbol, multiplied by the correction coefficient stored and outputs it to the section 302. Note that predicate post is how to set the correction coefficient.

[0052] Next, a description will be given of the operation of the multi-carrier transmitting apparatus 100 and the multicarrier receiving apparatus 200.

[0053] First, multicarrier transmitting apparatus 100, digital modulation unit 101, to generate a first transmission signal and the second transmission signal by orthogonally modulating transmission data. In this case, the digital modulating section 101 outputs at 1 OFDM symbol unit. lOFDM symbols may be represented by the first transmission signal and the IFFT point fraction second transmission signal IFFT point fraction.

[0054] Next, multicarrier transmitting apparatus 100, the separation unit 102, a complex transmission signal consisting of the first transmit signal and the second transmission signal, two complex transmit the fifth transmission signal and the sixth transmission signal to separate the signal. Fifth transmission signals separated by the separation unit 102, ing as equation (1). [0055] X = 1/2 (A + A *) (1)

kk Nk

However, X is the fifth transmission signal

k

A is the complex output of the digital modulating section 101 (I + j XQ)

kkk

The complex conjugate of A * is A

N is the number of IFFT points

A = A

N 0

k = 0, 1, · · ·, N- 1

[0056] Further, a sixth transmission signal separated by the separation unit 102 is as shown in equation (2).

[0057] Y = 1/2 (A -A *) (2)

kk Nk

However, Y is the sixth transmission signal

k

A is the complex output of the digital modulating section 101 (I + j XQ)

k

The complex conjugate of A * is A

N is the number of IFFT points

A = A

N 0

k = 0, 1, · · ·, N- 1

[0058] Then, the separation unit 102 outputs the fifth transmission signal and (2) Sixth transmission signals formula of the equation (1). In addition, X

k is the complex conjugate symmetry (X = X *)

To become a k NK, Ri by the symmetry of the IFFT, after IFFT is the real number. Further, Y may, k NK to become a complex conjugate antisymmetric (Yk = -Y *)

For the same reason, after the IFFT will be purely imaginary.

[0059] Next, multicarrier transmitting apparatus 100, the correction unit 103, with respect to one of the above (1) and equation (2), the amplitude difference and the delay time difference between the LPF109 and LPF110 complex correction coefficient Ck to correct the imbalance of (k = 0, 1, " ',? ^ 1) to complex multiplication a.

[0060] Next, multicarrier transmitting apparatus 100, the synthesis unit 104 synthesizes by adding the fifth transmission signal and the sixth transmission signal after correction at IFFT section 105, IFFT to the time domain generating a third transmission signal and a fourth transmission signal converted into the signal.

[0061] Then, multicarrier transmitting apparatus 100, DZA unit 107 and DZA unit 108, the third transmission signal and a fourth transmission signal is converted from a digital signal to an analog signal, only the low frequency at LPF109 and LPF110 passed, quadrature modulation and to send it in the quadrature modulation unit 111.

[0062] Figure 8, when the delay time difference is not amplitude difference 1Z8 sample period, a diagram illustrating a reception cons Talay Chillon simulation into four results of the case were one compensation Shinano force at multicarrier Yaria transmitting apparatus 100. Further, FIG. 9, when the delay time difference is no amplitude difference 1Z8 sample period, a diagram illustrating a simulation result of the reception Konsuta Reshiyon in the case where the compensation by multicarrier transmission apparatus 100. Incidentally, FIGS. 8 and 9, Sabukiyari § number 384, FFT points is 512, GI is 256 samples, the modulation method is a simulation result when 16QAM and channel estimation estimated by time-multiplexed pilot signals. 8 and 9, by correcting the imbalance in the delay time difference between the third transmission signal and a fourth transmission signal, can be removed almost completely interference.

[0063] Further, FIG. 10, when the amplitude difference in the absence of a delay time difference is LDB, is a diagram illustrating a simulator Shiyon result of the reception constellation in the case of failed to compensate by multi-carrier transmission device 100 . Further, FIG. 11, when the amplitude difference in the absence of the delay time difference is Id B, is a diagram illustrating a simulation result of the reception cons Tareshiyon in the case where the compensation by multicarrier transmission apparatus 100. From 10 and 11, by correcting the imbalance of the phase difference of the third transmission signal and a fourth transmission signal, it can be removed almost completely interference.

[0064] Next, the multicarrier receiving apparatus 200 that receives a multicarrier signal, generates a first receive signal and the second received signal orthogonally demodulated by the orthogonal demodulator 203, a low frequency at LPF109 and LPF1 10 passing only. Second reception signal that has passed through the first reception signal and the LPF 11 0 passing through the LPF109 is the individual difference between the LPF204 and 205, and has a signal delay difference and amplitude difference is applied. Such first reception signal and the second received signal, FFT and removes the guard-in interval Then, the third received signal and the fourth received signal after FFT is assumed that applied interference between Sabukiyari §. Therefore, it must be corrected by the correction unit 211 occurs.

[0065] Next, the multicarrier receiving apparatus 200, in the separation unit 210, the received complex signal consisting of a third received signal and the fourth received signal, (1) the fifth received signal and as shown in the expression (2 ) is separated into sixth received signal as shown in the expression.

[0066] Next, the multicarrier receiving apparatus 200, by the correction unit 211, with respect to one of the above (1) and (2) the fifth received signal and the sixth received signal as shown in equation , complex correction coefficient Ck (k = 0, 1, " ',? ^ 1) to correct the imbalance between LPF204 and LPF205 the complex-multiplication.

[0067] Next, the multicarrier receiving apparatus 200, at channel estimation compensation unit 213 performs the estimation to compensate for the amplitude and phase response of the channel using a known signal. The transmission path estimation compensator 213, an imbalance between the third received signal and the fourth received signal can not be compensated.

[0068] Next, the multicarrier receiving apparatus 200, by the demodulation unit 214 performs demodulation processing on each subcarrier, and outputs the received data.

[0069] Figure 12, when the delay time difference is no amplitude difference 1Z8 sample period, a diagram illustrating a reception cons Talay Chillon simulator one Chillon result of if one compensation Shinano force in multicarrier receiving apparatus 200. Further, FIG. 13, when the delay time difference is no amplitude difference 1Z8 sample period, a diagram illustrating a simulation result of the reception Con Sutareshiyon in the case of compensation in multicarrier receiving apparatus 200. From 12 and 13, by correcting the imbalance in the delay time difference between the first received signal and second received signal, it can be removed interference almost completely.

[0070] Further, FIG. 14 is a diagram showing when the amplitude difference is LDB, the reception cons Talay Chillon of simulators Shiyon results of the one compensation Shinano force in multi-carrier receiver apparatus 200 in the absence of the delay time difference it is. Further, FIG. 15, when the amplitude difference in the absence of the delay time difference is Id B, is a diagram illustrating a simulation result of the reception cons Tareshiyon in the case of compensation in multicarrier receiving apparatus 200. Incidentally, 14 and 15, the number of subcarriers 384, FFT points is 512, GI is 256 samples, the modulation method is a simulation result when 16QAM and channel estimation estimated by time-multiplexed pilot signals. From 14 and 15, by correcting the imbalance of the phase difference of the first received signal and second received signal, it can be removed almost completely interference.

[0071] Further, FIG. 16 is a diagram showing a delay time characteristic of the LPF when the delay time difference and amplitude difference when both are present in the delay time difference and amplitude difference has a frequency characteristic (ripple), the vertical axis There horizontal axis is the group delay is a regular I spoon frequency. Further, FIG. 17 is a diagram showing the amplitude characteristics of the LP F when there is a frequency characteristic to the delay time difference and amplitude difference if there are both a delay time difference and amplitude difference, and the vertical axis represents the amplitude horizontal axis it is a regular I spoon frequency. In Figure 16, I component has a ripple of ± 1Z4 sample period, Q component is flat within the signal band. Further, in FIG. 17, I component has a ripple of ± LDB, Q component is flat within the signal band.

[0072] Figure 18, in the case of FIG. 16 and FIG. 17 is a diagram showing a receiving cons Talay Chillon simulation result when not compensated by the multicarrier receiving apparatus 200. Also, FIG. 19, in the case of FIG. 16 and FIG. 17 is a diagram showing a receiving cons Talay Chillon simulation results in the case of compensation in multicarrier receiving apparatus 200. From 18 及 beauty 19, it can be removed almost completely interference even if there is a frequency characteristic in the delay time difference and amplitude difference.

[0073] Next, a method for setting the correction coefficient by the correction unit 103. In the first embodiment, first set the LPF 109, 110 and LPF 204, 205 calculated correction coefficients using.

[0074] correction unit 103, using a network analyzer or the like, to determine a correction factor based on the LPF characteristic that has been fit measured Ji roughness force. In the complex baseband signal, subcarriers, the number k = 0 and DC, and that toward the sampling frequency number up to N-1 being shaken from DC. In this case, k = 0~ (NZ2) - 1 real frequency carrier, k = NZ2 ~N-1 is an image carrier. Actual frequency subcarriers k = 0~ (NZ2) - 1 of the frequency, MAk the gain of LPF 109 (dB), the group delay DAK (s), the gain of the LPF110 MBk (dB), the group delay DBk (s ), placing the sampling period and Ts (s), the amplitude difference and the delay time difference relative to the LPF109 side (in-phase component side) is as shown in (3) and (4).

[0075] an amplitude difference Mk (dB) = MBk- MAk (0≤k≤ (NZ2) - 1) (3)

[0076] differential delay Dk (s) = DBk- DAk (0≤k≤ (NZ2) - 1) (4)

[0077] In this case, the correction coefficient Ck is as (5) and (6).

[0078] Ck = 10 "(-Mk / 20) X exp (j XD ZTs X k X 2 w ZN) (0≤k≤ (N / 2) - 1) k

(Five)

[0079] Ck = 10 "(-M Z20) X exp (-j XD / Ts X (N ~ k) X 2 π / N) (N / 2≤k

Nk Nk

≤N- 1) (6) [0080] In the correction coefficient Ck, (5) formula 10 and M Z20) - '(- MkZ20) and (6) of 10' (

Nk is a portion for correcting the amplitude difference, (5) the (j XD ZTs X kX 2 w ZN; ^ (6) (k

The j XD / Ts X (N- k) X 2 π / N) is a part for correcting a group delay time difference.

Nk

[0081] In the multicarrier transmission apparatus 100, the absolute value of the correction coefficient Ck is symmetrical with respect to the frequency axis of the frequency of 1Z2 sampling frequency, the phase that has a left-hand direction. Thus, complex conjugate antisymmetry of Yk be multiplied by the correction coefficient Ck to the sixth transmission signal Yk (Yk = Y *) is not lost, and also multiplied by the correction coefficient Ck to the fifth transmission signal Xk of Xk

NK

Complex conjugate symmetry (Xk = X *) is lost, such ヽ. That, IFFT calculated I component even when the Q component

NK

It does not interfere with.

[0082] The correction coefficient Ck, by multiplying the component Yk pertaining only to the quadrature component of the IFFT output, L PF109, 110 imbalance between in-phase and quadrature components after passing through are eliminated. Stores the determined metadata complex correction coefficient Ck in the above calculation the correction coefficient storage unit 303, used by calling for each symbol.

[0083] Thus, according to the first embodiment, at the transmission side, two complex of the complex transmission signal consisting of the first transmit signal and the second transmission signal fifth transmission signal and the sixth transmission signal with separating the transmission signal, the receiving side separates the complex received signal composed of a third received signal and the fourth received signal into two complex reception signal of the fifth received signal and the sixth received signal and separated thereby correcting the fifth transmission signal and the sixth transmission signal, so to correct the fifth received signal and the sixth received signal separated, increasing the circuit scale as compared with the case of correcting the delay time difference and amplitude difference by other methods ingredients delay time at a low cost and amplitude imbalance, such that it is possible to compensate for. Further, according to the first embodiment, by correcting the amplitude Sa及 beauty delay time difference in the frequency domain, a high-order oversampling and interpolation operations required in the case of one sample following the correction in the time domain required it is possible to, it is possible to reduce the manufacturing cost of the multicarrier transmitting apparatus and multicarrier receiving apparatus, it is possible to prevent the circuit scale becomes large.

[0084] (Embodiment 2)

Figure 20 is a block diagram showing the configuration of a correction coefficient storage unit 303 according to the second embodiment of the present invention. In the second embodiment, the configuration of a multicarrier transmitting apparatus is the same as FIG. 5, the configuration of the multicarrier receiving apparatus is the same as FIG. 6, the configuration of the correction unit 103 and the correction unit 211 FIG. 7 It is the same as, and a description thereof will be omitted.

[0085] selection information storage unit 1601, for each subcarrier, and the address of the amplitude coefficient storage unit 1602 cons Talay Chillon is best to such so that amplitude coefficients are stored, such as Konsutare one Chillon is best exp (j. 0 m) to store the address of exp (j · 0 m) storage unit 1603 stored. Then, the selection information storage unit 1601, as triggers symbol beginning information, stored by simply an address information at a forward address information to the subcarrier number order following the amplitude coefficient storage unit 1602 and exp (j 'Θ m) storage and outputs it to the part 1603.

[0086] amplitude coefficient storage unit 1602, and outputs stored in the address of the address information input from the selection information storage unit 1601 by the Ru amplitude coefficient to multiplier 1604 and multiplier 1605.

[0087] exp (j - 0 m) storage unit 1603 outputs a exp (j 'Θ m) stored in the address of the address information input from the selection information storage section 1601 to multiplier 1604 and multiplier 1605

[0088] Multiplier 1604, the correction coefficient by multiplying the real part of the amplitude coefficient and exp input from the amplitude coefficient storage unit 1602 (j · Θ m) exp input from the storage unit 1603 (j 'Θ m) calculating the real part of (correction value). Then, the multiplier 1604 outputs a real part of the calculated correction coefficient to the multiplication unit 30 2.

[0089] The multiplier 1605, an amplitude coefficient and exp input from the amplitude coefficient storage unit 1602 - correction factor by multiplying the imaginary part of the (j theta m) exp input from the storage unit 1603 (j 'Θ m) calculating the imaginary part of (correction value). Then, the multiplier 1605 outputs the imaginary part of the calculated correction coefficient to the multiplication unit 30 2. The operation of the multicarrier transmitting apparatus and multicarrier reception apparatus is the same as the first embodiment, description thereof will be omitted.

[0090] Next, a method for setting the correction coefficient by the correction unit 103. In the second embodiment, the correction coefficient is set by consing Talay Chillon of each sub-carrier in the apparatus adjustment step is adjusted to be best.

[0091] For example, if you need to delay time difference 1Z16 sample period following, correction coefficient storage unit 303 stores in advance the value of the sixteen exp (j. 0 m), Konsuta for each subcarrier so as to select a - (Θ m j) Reshiyon is best or EVM (Error Vector Magnitude) is minimized e xp. Here, exp (j 'Θ m) is Ru can be obtained from equation (7).

[0092] exp (j - Θ m) = cos Θ m + j X sin θ m (m = 0 ~ 15) (7)

[0093] Further, 0 m can be obtained from equation (8).

[0094] 0 πι = πι Χ 2 π Ζΐ6 (πι = Ο~15) (8)

[0095] However, the adjustment of each sub-carrier by a half of the sub-carriers! /,. Image sub-carrier (k

= K = the value of the N-n) is the opposite phase to n. Because not in the above set by theta m of 0 to 2 [pi, reverse phase Θ m - Θ m is, 2 [pi - a 0 m = 0. Sub-carrier k-th correction

16-m

When, in order to Uni'm not destroying the complex conjugate symmetry of the complex conjugate anti-symmetry or Xk of Yk, it is necessary to perform also the selection of N-k-th time. That is, when correcting the sub-carrier k-th corrects by selecting and 0 111 and 0 as a pair.

16-m

[0096] Then, the correction coefficient storage unit 303, exp selected for each subcarrier - you store (j 0 m). Based on the exp of each subcarrier correction coefficient storage unit 303 stores (j Θ m.), Exp - used (j 0 m) it is called and corrected.

[0097] For the amplitude, similarly, a predetermined allowed to store a plurality of correction coefficients (real numbers) for each amplitude difference, so that cons Talay Chillon each subcarrier is best or EVM is to select the ones with the smallest 〖Rub. For example, if it is desired to suppress the amplitude difference below 0. 5 dB, the correction coefficient storage unit 303, up to a maximum of the amplitude difference of the LPF, for example, "1, ± 0 5dB, ± ldB, ± 1. 5dB- -. - J of stores each correction coefficient, during adjustment, to memorize the correction coefficient selected for each subcarrier. as with the delay time difference, adjustment k relative Yogu image sub-carrier (k = N at half the subcarrier = N-1) has the value becomes the same value. when adjusting the sub-carrier k-th also performed. correction factor is the choice of N-k-th time, the product of the amplitude coefficient and exp (j 'Θ m) to become.

[0098] Since the influence of the amplitude difference compared to the delay time difference small, performed before the correction of the delay time difference, to correct the amplitude difference thereon. If necessary, repeated correction and correction of amplitude difference again delay time difference. When repeatedly performing correction of the correction and amplitude difference of the delay time also to perform correction of the delay time difference each time destination, to correct the amplitude difference thereon.

[0099] Thus, according to the second embodiment, at the transmission side, two complex of the complex transmission signal consisting of the first transmit signal and the second transmission signal fifth transmission signal and the sixth transmission signal with separating the transmission signal, the receiving side separates the complex received signal composed of a third received signal and the fourth received signal into two complex reception signal of the fifth received signal and the sixth received signal and separated thereby correcting the fifth transmission signal and the sixth transmission signal, so to correct the fifth received signal and the sixth received signal separated, increasing the circuit scale as compared with the case of correcting the delay time difference and amplitude difference by other methods ingredients delay time at a low cost and amplitude imbalance, such that it is possible to compensate for. Further, according to the second embodiment, by correcting the amplitude Sa及 beauty delay time difference in the frequency domain, a high-order oversampling and interpolation operations required in the case of one sample following the correction in the time domain required it is possible to, it is possible to reduce the manufacturing cost of the multicarrier transmitting apparatus and multicarrier receiving apparatus, it is possible to prevent the circuit scale becomes large.

[0100] In Embodiment 1 and Embodiment 2 described above, but having conducted correcting the sixth transmission signal, not limited thereto, may be corrected with respect to the fifth transmission signal, the it may be corrected for both five transmission signal and the sixth transmission signal. Further, in the second embodiment 1 及 beauty embodiment of the above-described, were subjected to correction with respect to the sixth received signal is not limited thereto, it may also be carried out correcting the fifth received signal!, And, it may be corrected for both the fifth received signal and the sixth received signal. Also, to Embodiment 2 of the first embodiment and the above-described V Te, in both the multicarrier transmitting apparatus 100 and the multicarrier receiving apparatus 200 is not limited to this force obtained by correcting the amplitude Sa及 beauty delay time difference, multicarrier transmission one of devices 100 and multi-carrier receiver apparatus 200 only may be corrected amplitude difference and the delay time difference.

[0101] herein included in Japanese Patent Application 2005 November 29th Patent Application No. 2005- 344130, the disclosure of FIG surface and abstract are all incorporated herein.

Industrial Applicability

[0102] The present invention multicarrier transmitting apparatus mow force, multicarrier receiving apparatus, transmission method and reception method is suitable particularly for compensation for imbalance amplitude or time delay between the in-phase component and the quadrature component is there.

Claims

The scope of the claims
[1] and Digitally Le modulating means for generating a complex transmission signal consisting of a second transmission signal is a frequency domain signal of the first transmission signal and the Q component is a frequency domain signal of the I component of the transmission data quadrature modulated and,
In the frequency domain signal of the fourth transmission signal comprising a time domain signal of the fifth transmission signal and the Q-component is a frequency domain signal of the third transmission signal comprising a time domain signal of the I component when inverse fast Fourier transforming the complex transmission signal separating means for separating the complex transmission signal to a certain sixth transmission signal,
The fifth transmission signal or the like amplitude difference and the delay time difference is reduced between the third transmission signal and the fourth transmission signal and the third transmission signal when that band-limits the fourth transmission signal and correcting means for correcting the sixth transmission signal,
Synthesizing means for regenerating the complex transmission signal by combining the fifth transmission signal and the sixth transmission signal after correction by said correcting means,
An inverse fast Fourier transform means for generating a Symbol before inverse fast Fourier transform of the complex transmission signal regenerated a third transmission signal and the fourth transmission signal by said synthesizing means, the inverse fast Fourier transform unit and band limiting means for limiting the bandwidth of the generated third transmission signal and the fourth transmission signal Te,
Transmission means for transmitting a transmission signal composed of the third transmission signal and the fourth transmission signal band-limited by the band limiting means,
Multicarrier transmitting apparatus comprising.
[2] The correcting means may Maruchikiya rear transmission apparatus according to claim 1, wherein performing the correction by multiplying the correction value stored in advance to the fifth transmission signal or said sixth transmission signal.
[3] and the quadrature demodulating means for generating a second received signal which is a time domain signal of the first received signal and the Q component is the time domain signal of the I component by orthogonal demodulating the received signal,
And band limiting means for limiting the bandwidth of said first receiving signal and the second reception signal, a band-limited the first reception signal and the second received signal by the band-limiting means to fast Fourier transform I and fast Fourier E converting means for generating a complex reception signal comprising a fourth received signal is a frequency domain signal of the third received signal and the Q component is the frequency domain signal components,
Fifth received signal and the second separating the complex reception signal into a sixth received signal is a frequency-domain signal of the received signal separating means and said first receiving signal and the a frequency-domain signal of the first reception signal second the received signal so that the amplitude difference and the delay time difference between the first reception signal and the second received signal caused when you band limitation is reduced by the band limiting unit fifth received signal or and correction means to correct the sixth received signal,
Synthesizing means for regenerating the complex received signal by combining said fifth received signal and the sixth received signal after correction by said correcting means,
Multicarrier receiver comprising a demodulating means for demodulating the received complex signal regenerated by said synthesizing means.
[4] The correcting means may Maruchikiya rear receiving apparatus according to claim 3, wherein performing the correction by multiplying the correction value stored in advance for the fifth received signal and the sixth received signal.
Generating a complex transmission signal consisting of a second transmission signal is a frequency domain signal of the first transmission signal and the Q component is a frequency domain signal I component [5] quadrature modulation to the transmission data,
In the frequency domain signal of the fourth transmission signal comprising a time domain signal of the fifth transmission signal and the Q-component is a frequency domain signal of the third transmission signal comprising a time domain signal of the I component when inverse fast Fourier transforming the complex transmission signal separating said complex transmission signal to a certain sixth transmission signal,
The fifth transmission signal or the like amplitude difference and the delay time difference is reduced between the third transmission signal and the fourth transmission signal and the third transmission signal when that band-limits the fourth transmission signal and correcting the sixth transmission signal,
Wherein the step of regenerating the complex transmit signal and said after correction fifth transmission signal and said sixth transmission signal synthesized and, regenerated the complex transmission signal an inverse fast Fourier transform to the third transmission signal and generating a pre-Symbol fourth transmission signal when,
A step of sending said third transmission signal is step and band limitation restricts generated the third transmission signal and a band of the fourth transmission signal and the transmission signal consisting of the fourth transmission signal,
Transmission method comprising a.
And generating a second received signal which is a time domain signal of the first received signal and the Q component is the time domain signal of the I component by orthogonal demodulating the received signal,
A step of limiting the bandwidth of said first receiving signal and the second reception signal, a third of the frequency domain signals of the I component the first received signal is band-limited and the second received signal by fast Fourier transform generating a complex reception signal comprising a fourth received signal to be a frequency-domain signal of the received signal and Q components,
Separating said received complex signal to a sixth received signal is a frequency domain signal of the fifth received signal and the second reception signal is a frequency domain signal of the first reception signal, the first received signal and the the amplitude difference and prior to the delay time difference is smaller Symbol fifth received signal or said sixth received signal between the first reception signal and the second received signal generated in limiting the band of the second reception signal and a step of correcting,
And re-generating the complex received signal by combining said fifth received signal and the sixth received signal after the correction,
A step of demodulating the received complex signal which is regenerated,
Receiving method comprising a.
PCT/JP2006/323727 2005-11-29 2006-11-28 Multicarrier transmitting apparatus, multicarrier receiving apparatus, transmitting method and receiving method WO2007063855A1 (en)

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