WO2005122331A1 - Antenne dipole orientee - Google Patents

Antenne dipole orientee Download PDF

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Publication number
WO2005122331A1
WO2005122331A1 PCT/US2005/012528 US2005012528W WO2005122331A1 WO 2005122331 A1 WO2005122331 A1 WO 2005122331A1 US 2005012528 W US2005012528 W US 2005012528W WO 2005122331 A1 WO2005122331 A1 WO 2005122331A1
Authority
WO
WIPO (PCT)
Prior art keywords
antenna
specified
radiating element
dual
director
Prior art date
Application number
PCT/US2005/012528
Other languages
English (en)
Inventor
Kevin Le
Louis J. Meyer
Pete Bisiules
Original Assignee
Andrew Corporation
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Andrew Corporation filed Critical Andrew Corporation
Priority to CN2005800116350A priority Critical patent/CN101080848B/zh
Priority to EP05746446.3A priority patent/EP1751821B1/fr
Priority to JP2007515075A priority patent/JP2008507163A/ja
Priority to KR1020067025462A priority patent/KR101085814B1/ko
Publication of WO2005122331A1 publication Critical patent/WO2005122331A1/fr

Links

Classifications

    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q19/00—Combinations of primary active antenna elements and units with secondary devices, e.g. with quasi-optical devices, for giving the antenna a desired directional characteristic
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q9/00—Electrically-short antennas having dimensions not more than twice the operating wavelength and consisting of conductive active radiating elements
    • H01Q9/04—Resonant antennas
    • H01Q9/16—Resonant antennas with feed intermediate between the extremities of the antenna, e.g. centre-fed dipole
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/12—Supports; Mounting means
    • H01Q1/22—Supports; Mounting means by structural association with other equipment or articles
    • H01Q1/24—Supports; Mounting means by structural association with other equipment or articles with receiving set
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q19/00—Combinations of primary active antenna elements and units with secondary devices, e.g. with quasi-optical devices, for giving the antenna a desired directional characteristic
    • H01Q19/005—Patch antenna using one or more coplanar parasitic elements
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q19/00—Combinations of primary active antenna elements and units with secondary devices, e.g. with quasi-optical devices, for giving the antenna a desired directional characteristic
    • H01Q19/28—Combinations of primary active antenna elements and units with secondary devices, e.g. with quasi-optical devices, for giving the antenna a desired directional characteristic using a secondary device in the form of two or more substantially straight conductive elements
    • H01Q19/30—Combinations of primary active antenna elements and units with secondary devices, e.g. with quasi-optical devices, for giving the antenna a desired directional characteristic using a secondary device in the form of two or more substantially straight conductive elements the primary active element being centre-fed and substantially straight, e.g. Yagi antenna
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q21/00—Antenna arrays or systems
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q21/00—Antenna arrays or systems
    • H01Q21/06—Arrays of individually energised antenna units similarly polarised and spaced apart
    • H01Q21/08—Arrays of individually energised antenna units similarly polarised and spaced apart the units being spaced along or adjacent to a rectilinear path

Definitions

  • the present invention is related to the field of antennas, and more particularly to antennas having dipole radiating elements utilized in wireless communication systems.
  • Wireless mobile communication networks continue to be deployed and improved upon given the increased traffic demands on the networks, the expanded coverage areas for service and the new systems being deployed.
  • Cellular type communication systems derive their name in that a plurality of antenna systems, each serving a sector or area commonly referred to as a cell, are implemented to effect coverage for a larger service area. The collective cells make up the total service area for a particular wireless communication network.
  • each cell is an antenna array and associated switches connecting the cell into the overall communication network.
  • the antenna array is divided into sectors, where each antenna serves a respective sector.
  • three antennas of an antenna system may serve three sectors, each having a range of coverage of about 120°.
  • These antennas are typically vertically polarized and have some degree of downtilt such that the radiation pattern of the antenna is directed slightly downwardly towards the mobile handsets used by the customers. This desired downtilt is often a function of terrain and other geographical features.
  • the optimum value of downtilt is not always predictable prior to actual installation and testing. Thus, there is always the need for custom setting of each antenna downtilt upon installation of the actual antenna.
  • Figure 1 is a perspective view of a dual polarized antenna according to a first preferred embodiment of the present invention
  • Figure 2 is a perspective view of a multi-level groundplane structure with a broadband slant 45 cross dipole radiating element removed therefrom, and a tray cutaway to illustrate a tilting of the groundplanes and an RF absorber in a RF choke;
  • Figure 3 is a perspective view of N cross-shaped directors supported above the dipole radiating element
  • Figure 4 is a backside view of one element tray illustrating a microstrip phase shifter design employed to feed each pair of the cross dipole radiating elements;
  • Figure 5 is a backside view of the dual polarized antenna illustrating the cable feed network, each microstrip phase shifter feeding one of the other dual polarized antennas;
  • Figure 6 is a perspective view of the dual polarized antenna including an RF absorber functioning to dissipate RF radiation from the phase shifter microstriplines, and preventing the RF current cross coupling;
  • Figure 7 is a graph depicting the high roll-off radiation pattern achieved by the present invention, as compared to a typical cross dipole antenna radiation pattern;
  • Figure 8A and 8B are graphs depicting the beam patterns in a three sector site utilizing standard panel antennas;
  • Figure 9A and 9B are graphs depicting the beam patterns in a three sector site utilizing antennas according to the present invention.
  • Figure 10 is a perspective view of another embodiment of the invention including dual-band radiating elements
  • Figure 11 is a perspective view of the embodiment shown in Figure 10 having director rings disposed over one of the radiating elements;
  • Figure 12 is a perspective view of an embodiment of the invention having director rings disposed over each of the radiating elements;
  • Figure 13 is a view of various suitable configurations of directors;
  • Figure 14 is a close-up view of a dual-band antenna; and Figure 15 depicts an array of dual-band and single-band dipole radiating elements.
  • FIG. 1 there is generally shown at 10 a wideband dual polarized base station antenna having an optimized horizontal radiation pattern and also having a variable vertical beam tilt.
  • Antenna 10 is seen to include a plurality of element trays 12 having disposed thereon broadband slant 45 cross dipole (x-dipole) radiating elements 14 arranged in dipole pairs 16.
  • Each of the element trays 12 is tilted and arranged in a " fallen domino" arrangement and supported by a pair of tray supports 20.
  • the integrated element trays 12 and tray supports 20 are secured upon and within an external tray 22 such that there is a gap laterally defined between the tray supports 20 and the sidewalls of tray 22, as shown in Figure 1 and Figure 2.
  • Each tray element 12 has an upper surface defining a groundplane for the respective dipole pair 16, and has a respective air dielectric micro stripline 30 spaced thereabove and feeding each of the dipole radiating elements 14 of dipole pairs 16, as shown.
  • a plurality of electrically conductive arched straps 26 are secured between the sidewalls of tray 22 to provide both rigidity of the antenna 10, and also to improve isolation between dipole radiating elements 14.
  • a pair of cable supports 32 extend above each tray element 12. Supports 32 support a respective low IM RF connection cables 34 from a cable 76 to the air dielectric micro stripline 30 and to microstrip feed network defined on a printed circuit board 50 adhered therebelow, as will be discussed in more detail shortly with reference to Figure 4.
  • FIG 2 there is shown a perspective view of the element trays 12 with the sidewall of one tray support 20 and tray 22 partially cut away to reveal the tilted tray elements 12 configured in the " fallen domino" arrangement.
  • Each tray element 12 is arranged in a this " fallen domino" arrangement so as to orient the respective dipole radiating element 14 pattern boresight at a predetermined downtilt, which may, for example, be the midpoint of the array adjustable tilt range.
  • the desired maximum beam squint level of antenna 10 in this example is consistent with about 4° downtilt off of mechanical boresight, instead of about 8° off of mechanical boresight as would be the case without the tilt of the element trays 12.
  • maximum horizontal beam squint levels have been reduced to about 5° over conventional approaches, which is very acceptable considering the antenna's wide operating bandwidth and tilt range.
  • the tray supports 20 are separated from the respective adjacent sidewalls of tray 22 by an elongated gap defining an RF choke 36 therebetween.
  • This choke 36 created by physical geometry advantageously reduces the RF current that flows on the backside of the external tray 22.
  • the reduction of induced currents on the backside of the external tray 22 directly reduces radiation in the rear direction.
  • the critical design criteria of this RF choke 36 involved in maximizing the radiation front- to-back ratio includes the height of the folded up sidewalls 38 of external tray 22, the height of the tray supports 20, and the RF choke 36 between the tray supports 20 and the sidewall lips 38 of tray 22.
  • the RF choke 36 is preferably lambda /4 of the radiating element 14 center frequency, and the RF choke 36 has a narrow bandwidth which is frequency dependent because of internal reflection cancellation in the air dielectric, the choke bandwidth being about 22 percent of the center frequency.
  • an RF absorber 39 may be added into the RF choke 36 to make the RF choke less frequency dependent, and thus create a more broadband RF choke.
  • the RF absorber 39 preferably contains a high percentage of carbon that slows and dissipates any RF reflection wave from effecting the main beam radiation produced by the cross dipole antenna 12.
  • the slant 45 cross dipole antenna 14, as shown, produces a cross polarized main beam radiation at a +/-45 degree orientation, each beam having a horizontal component and a vertical component. The cross polarization is good when these components are uniform and equal in magnitude in 360 degrees. For the panel antenna 10 shown in Figure 1 with the linearly arranged cross dipoles 14, the horizontal component of each beam orientation rolls off faster than the vertical component.
  • the vertical beamwidth is broader than the horizontal beamwidth for each beam orientation, and the vertical components travel along the edge of the respective trays 12 more than the horizontal components. Because the thin metal trays 12 have limited surface area, the surface currents thereon are less likely to reflect the horizontal components back to the main beam radiation. In contrast, along the edges of the respective trays 12 the stair cased baffles 35 have to contain many of the vertical component vector currents.
  • the RF absorber 39 into the RF choke 36, the vertical components of each beam orientation are minimized from reflecting back into the main beam radiation of the cross dipole 14. As such, cross dipoles 14 are not provided with a reflector behind them.
  • the element trays 12 are fabricated from brass alloy and are treated with a tin plating finish for solderability.
  • the primary function of the element trays is to support the radiating element 14 in a specific orientation, as shown. This orientation provides more optimally balanced vertical and horizontal beam patterns for both ports of the antenna 10. This orientation also provides improved isolation between each port. Additionally, the element trays 12 provide an RF grounding point at the coaxial cable/airstrip interface.
  • the tray supports are preferably fabricated from aluminum alloy.
  • the primary function of the tray supports is to support the five element trays 12 in a specific orientation that minimizes horizontal pattern beam squint .
  • the external tray 22 is preferably fabricated from a thicker stock of aluminum alloy than element trays 12, and is preferably treated with an alodine coating to prevent corrosion due to external environment conditions.
  • a primary functions of the external tray 22 is to support the internal array components.
  • a secondary function is to focus the radiated RF power toward the forward sector of the antenna 10 by minimizing radiation toward the back, thereby maximizing the radiation pattern front-to-back ratio, as already discussed.
  • FIG. 3 there is depicted one radiator element 14 having N laterally extending parasitic broadband cross dipole directors 40 disposed above the radiating element 14 and fed by the airstrip feed network 30, as shown.
  • N is 1,2,3,4 , where N is shown to equal 4 in this embodiment.
  • the upper laterally extending members of parasitic broadband cross dipole director 40 are preferably uniformly spaced from one another, with the upper members preferably having a shorter length, as shown for bandwidth broadening.
  • the lower members of director 40 are more closely spaced from the radiating element 14, so as to properly couple the RF energy to the director in a manner that provides pattern enhancement while maintaining an efficient impedance match such that substantially no gain is realized by the director 40, unlike a Yagi-Uda antenna having a reflector and spaced elements each creating gain.
  • an improved pattern rolloff is achieved beyond the 3dB beamwidth of the radiation pattern while maintaining a similar 3dB beamwidth.
  • the upper elements of directors 40 are spaced about .033 lambda (center frequency) from one another, with the lower director elements spaced from the radiating element 14 about .025 lambda by parasitic 42 (lambda being the wavelength of the center frequency of the radiating element 14 design) .
  • PCB printed circuit board
  • the low loss PCB 50 is secured to the backside of the respective element tray 12.
  • Microstrip capacitive phase shifter system 52 is coupled to and feeds the opposing respective pair of radiating elements 14 via the respective cables 34.
  • each microstrip phase shifter system 52 comprises a phase shifter wiper arm 56 having secured thereunder a dielectric member 54 which is arcuately adjustable about a pivot point 58 by a respective shifter rod 60.
  • Shifter rod 60 is longitudinally adjustable by a remote handle (not shown) so as to selectively position the phase shifter wiper arm 56 and the respective dielectric 54 across a pair of arcuate feedline portions 62 and 64 to adjust the phase velocity conducting therethrough.
  • Shifter rod 60 is secured to, but spaced above, PCB 50 by a pair of non-conductive standoffs 66.
  • the low loss coaxial cables 34 are employed as the main transmission media providing electrical connection between the phase shifter system 52 and the radiating elements 14. Gain performance is optimized by closely controlling the phase and amplitude distribution across the radiating elements 14 of antenna 10. The very stable phase shifter design shown in Figure 4 achieves this control.
  • each microstrip phase shifter system 52 feeding one of the other polarized antennas 14.
  • Input 72 is referred as port I and is the input for the -45 polarized Slant
  • input 74 is the port II input for the +45 polarized Slant.
  • Cables 76 are the feed lines coupled to one respective phase shifter system 52, as shown in Figure 4.
  • the outputs of phase shifter system 52 depicted as outputs 1-5, indicate the dipole pair 16 that is fed by the respective output of the phase shifter 52 system.
  • antenna 10 further including an RF absorber 78 positioned under each of the element trays 12, behind antenna 10, that functions to dissipate any rearward RF radiation from the phase shifter microstrip lines, and preventing RF current from coupling between phase shifters systems 52.
  • RF absorber 78 positioned under each of the element trays 12, behind antenna 10, that functions to dissipate any rearward RF radiation from the phase shifter microstrip lines, and preventing RF current from coupling between phase shifters systems 52.
  • FIG. 7 there is generally shown at 68 the high roll-off and front-to-back ratio radiation pattern achieved by antenna 10 according to the present invention, as compared to a standard 65° panel antenna having a dipole radiation pattern shown at 69.
  • This high roll-off radiation pattern 68 is a significant improvement over the typical dipole radiation pattern 69.
  • the horizontal beam width still holds at approximately 65 degree at the 3 dB point .
  • the design of the radiating elements 14 with directors 40 provides dramatic improvements in the antenna's horizontal beam radiation pattern, "where the Front-to-Side levels are shown to be 23dB in Figure 7.
  • Conventional, cross dipole radiating elements produce a horizontal beam radiation pattern with about a 17 dB front-to-side ratio, as shown in Figure 7.
  • the broadband parasitic directors 40 integrated above the radiating elements 14 advantageously improve the antenna front-to-side ratio by up to 10 dB, and is shown as 6dB delta in the example of Figure 7.
  • This improved front-to-side ratio effect is referred to as a "high roll-off" design.
  • radiating elements 14 and cross dipole directors 40 advantageously maintain an approximately 65 degree horizontal beamwidth at the antenna's 3 dB point, unlike any conventional Yagi-Uda antenna having more directors to get more gain and thus reducing the horizontal beamwidth.
  • Figure 7 there is shown the excellent front-to-back ratio of antenna 10.
  • panel antenna 10 has a substantially reduced backside lobe, thus achieving a front-to-back ratio of about 40 dB. Moreover, antenna 10 has a next sector antenna/antenna isolation of about 40 dB, as compared to 26 dB for the standard 65° panel antenna. As can also be appreciated in Figure 7, with the significant reduction of a rear lobe, a 120° sector interference free zone is provided behind the radiation lobe, referred to in the present invention as the "cone of silence" . Referring now to Figure 8A and 8B, there is shown several advantages of the present invention when employed in a three sector site.
  • Figure 8A depicts standard 65° flat panel antennas used in a three sector site
  • Figure 8B depicts standard 90° panel antennas used in a three sector site.
  • the significant overlap of these antenna radiation patterns creates imperfect sectorization that presents opportunities for increased softer hand-offs, interfering signals, dropped calls, and reduced capacity.
  • Figure 9A and 9B there is shown technical advantages of the present invention utilizing a 65° panel antenna and a 90° panel antenna, respectively according to the present invention, employed in a three sector site.
  • Figure 9A there is depicted significantly reduced overlap of the antenna radiation lobes, thus realizing a much smaller hand-off area. This leads to dramatic call quality improvement, and further, a 5-10% site capacity enhancement .
  • the undesired lobe extending beyond the 120° sector of radiation creates overlap with adjacent antenna radiation patterns, as shown in Figure 8A-8B and Figure 9A-9B.
  • SPR Sector Power Ratio
  • the present invention achieves a SPR being less than 2%, where the SPR is defined by the following equation:
  • the N directors 82 are configured as vertically spaced parallel polygon-shaped members, shown as concentric rings, although limitation to this geometry of directors 82 is not to be inferred. Other geometric configurations of the directors may be utilized as shown in Figure 13.
  • the ring directors 82 react with the corresponding dipole radiating element 14 to enhance the front-to-side ratio of antenna 10 with improved rolloff .
  • the ring directors 82 are preferably uniformly spaced above the corresponding x-dipole radiating element 14, with the ascending ring directors 82 having a continually smaller circumference .
  • the ring directors 82 maintain a relatively close spacing with one another being separated by electrically non-conductive spacers, not shown, preferably being spaced less than 0.15 lambda (lambda being the wavelength of the center frequency of the antenna design) . Additionally, the grouping of ring directors 82 maintain a relatively close spacing between the bottommost director 82 and the top of the corresponding dipole radiating element 14, preferably less than 0.15 lambda.
  • There are a variety of methods to build the set of planar directors 82 such as molded forms and electrically insulating clips.
  • the set of stacked ring directors 82 may also consist of rings of equal circumference while maintaining similar performance of improved roll-off leading to an improved SPR with the previously stated system benefits while maintaining a similar 3dB beamwidth.
  • MAR Microstrip Annular Ring
  • FIG. 11 there is shown at 90 a dual-band antenna including a set of director rings 92 disposed above a stacked Microstrip Annular Ring (MAR) radiator 94.
  • MAR Microstrip Annular Ring
  • the directors 92 in this embodiment of the invention are thin rings stacked above the respective MAR radiator 94, as shown.
  • this dual-band antenna 90 also has improved element pattern roll-off beyond the 3dB beamwidth thus increasing the SPR while maintaining an equivalent 3dB beamwidth.
  • a dual-band antenna 100 having ring directors 82 and 92.
  • the ring directors 92 above the MAR radiator 94 also interact with the x-dipole radiating element 14 and provide some additional beamshaping for the x- dipole radiating element, including improved roll-off of the main beam outside of the 3dB beamwidth as well as improved front-to-back radiation leading to an improved SPR and the system benefits previously mentioned while maintaining a similar 3dB beamwidth.
  • Both the MAR radiator element 94 and the x-dipole radiating element 14 have respective ring directors thereabove.
  • the ring directors 82 for the x-dipole radiating element 14 are also concentric to the ring directors 92 for the MAR radiator 94.
  • the same benefits as discussed earlier for the directors are applicable here as well per frequency band (i.e. improved roll-off beyond the 3dB beamwidth and front- to-back ratio leading to improved SPR.
  • FIG. 13 there is shown other suitable geometrical configurations of directors 82 and 92, and limitation to a circular ring-like director is not to be inferred.
  • a circle is considered to be an infinitely sided polygon where the term polygon is used in the appending claims .
  • FIG 14 there is shown a close-up view of dual band antenna 80 having cross shaped directors 40 extending over the radiating element 14, and the MAR radiator 94 without the associated annular director.
  • FIG 15 there is shown a panel antenna 110 having an array of radiating elements 14, each having cross directors 40, alternately provided with the MAR radiators 94, each disposed over common groundplane 112.
  • the advantages of this design include an improved H-plane pattern for the higher frequency radiating element in a dualband topology.
  • the improved H-plane pattern provides improved roll-off beyond the 3dB beamwidth and improved front-to-back ratio.
  • the improved roll-off additionally provides a slight decoupling of the radiators depending on the number of directors incorporated due to lower levels of side and back radiation.

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  • Variable-Direction Aerials And Aerial Arrays (AREA)
  • Aerials With Secondary Devices (AREA)

Abstract

L'invention concerne une double antenne polarisée à inclinaison de faisceau variable présentant un rapport de puissance secteur (SPR) supérieur. L'antenne peut comprendre des éléments de rayonnement dipôle oblique à 45° comprenant des dispositifs d'orientation, et peut être disposée sur une pluralité de plaques d'éléments inclinés permettant d'orienter l'inclinaison vers le bas de la ligne d'orientation de l'antenne. Les éléments d'orientation peuvent être disposés au-dessus ou autour des éléments de rayonnement dipôle correspondants. L'antenne présente un rapport de faisceau avant-latéral supérieur à 20 dB, un rapport de faisceau horizontal avant-latéral supérieur à 40 dB, et une décroissance élevée, et peut être utilisée sur une gamme de fréquence étendue.
PCT/US2005/012528 2004-06-04 2005-04-13 Antenne dipole orientee WO2005122331A1 (fr)

Priority Applications (4)

Application Number Priority Date Filing Date Title
CN2005800116350A CN101080848B (zh) 2004-06-04 2005-04-13 定向偶极子天线
EP05746446.3A EP1751821B1 (fr) 2004-06-04 2005-04-13 Antenne dipole orientee
JP2007515075A JP2008507163A (ja) 2004-06-04 2005-04-13 指向性ダイポール・アンテナ
KR1020067025462A KR101085814B1 (ko) 2004-06-04 2005-04-13 지향성 다이폴 안테나

Applications Claiming Priority (4)

Application Number Priority Date Filing Date Title
US57713804P 2004-06-04 2004-06-04
US60/577,138 2004-06-04
US73721404A 2004-12-16 2004-12-16
US10/737,214 2004-12-16

Publications (1)

Publication Number Publication Date
WO2005122331A1 true WO2005122331A1 (fr) 2005-12-22

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ID=34968962

Family Applications (1)

Application Number Title Priority Date Filing Date
PCT/US2005/012528 WO2005122331A1 (fr) 2004-06-04 2005-04-13 Antenne dipole orientee

Country Status (4)

Country Link
EP (1) EP1751821B1 (fr)
JP (1) JP2008507163A (fr)
KR (1) KR101085814B1 (fr)
WO (1) WO2005122331A1 (fr)

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WO2009153640A1 (fr) 2008-06-17 2009-12-23 Fracarro Radioindustrie S.P.A. Antenne
US7868843B2 (en) 2004-08-31 2011-01-11 Fractus, S.A. Slim multi-band antenna array for cellular base stations
US8497814B2 (en) 2005-10-14 2013-07-30 Fractus, S.A. Slim triple band antenna array for cellular base stations
EP2681801A2 (fr) * 2011-03-03 2014-01-08 Tangitek, LLC Dispositif d'antenne et procédé permettant de réduire le bruit de fond et d'augmenter la sensibilité de réception
US8854275B2 (en) 2011-03-03 2014-10-07 Tangitek, Llc Antenna apparatus and method for reducing background noise and increasing reception sensitivity
US9055667B2 (en) 2011-06-29 2015-06-09 Tangitek, Llc Noise dampening energy efficient tape and gasket material
WO2016090463A1 (fr) * 2014-12-09 2016-06-16 Communication Components Antenna Inc. Antenne dipôle dotée d'un anneau de formation de faisceau
WO2016137526A1 (fr) * 2015-02-25 2016-09-01 CommScope Technologies, LLC Réseau de dipôles pleine onde à performances d'angle de strabisme améliorées
US9525212B2 (en) 2012-10-10 2016-12-20 Huawei Technologies Co., Ltd. Feeding network, antenna, and dual-polarized antenna array feeding circuit
WO2017084979A1 (fr) * 2015-11-16 2017-05-26 Huawei Technologies Co., Ltd. Antenne de station de base bipolarisée ultra large bande et ultra compacte
US9722321B2 (en) 2015-02-25 2017-08-01 Commscope Technologies Llc Full wave dipole array having improved squint performance
WO2017185184A1 (fr) * 2016-04-27 2017-11-02 Communication Components Antenna Inc. Éléments de réseau d'antennes dipôles pour antenne de station de base multi-ports
US10262775B2 (en) 2011-07-11 2019-04-16 Tangitek, Llc Energy efficient noise dampening cables
US11426950B2 (en) 2015-07-21 2022-08-30 Tangitek, Llc Electromagnetic energy absorbing three dimensional flocked carbon fiber composite materials
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WO2010018896A1 (fr) * 2008-08-11 2010-02-18 Ace Antenna Corp. Antenne équipée d’un élément de découplage
FR2939569B1 (fr) * 2008-12-10 2011-08-26 Alcatel Lucent Element rayonnant a double polarisation pour antenne large bande.
EP2256860B1 (fr) * 2009-05-26 2018-12-19 Alcatel Lucent Réseau d'antenne
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JP5677494B2 (ja) * 2013-03-29 2015-02-25 日本電業工作株式会社 移相器、アンテナ及び無線装置
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JP5877241B2 (ja) * 2014-12-26 2016-03-02 日本電業工作株式会社 移相器、アンテナ及び無線装置
DE102016112257A1 (de) * 2016-07-05 2018-01-11 Kathrein-Werke Kg Antennenanordnung mit zumindest einer dipolförmigen Strahleranordnung
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KR102158982B1 (ko) * 2019-08-09 2020-09-24 주식회사 에이치에스에이디씨 케이블 연결 부재 및 이를 이용한 분리도 개선 안테나
KR20230074589A (ko) * 2020-10-05 2023-05-30 후아웨이 테크놀러지 컴퍼니 리미티드 방사 루프를 갖는 안테나 장치
KR102459972B1 (ko) * 2021-07-13 2022-10-26 국방과학연구소 고출력 이중 편파 t-로드 대수 주기 다이폴 어레이 안테나
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CN115313065A (zh) * 2022-09-29 2022-11-08 微网优联科技(成都)有限公司 一种共口径基站天线阵
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KR101085814B1 (ko) 2011-11-22
EP1751821A1 (fr) 2007-02-14
KR20070020272A (ko) 2007-02-20
EP1751821B1 (fr) 2016-03-09
JP2008507163A (ja) 2008-03-06

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