WO2003044933A1 - Circuit de correction de facteur de puissance du type a compensation aval en parallele pour source de courant triphase - Google Patents

Circuit de correction de facteur de puissance du type a compensation aval en parallele pour source de courant triphase Download PDF

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Publication number
WO2003044933A1
WO2003044933A1 PCT/CN2002/000828 CN0200828W WO03044933A1 WO 2003044933 A1 WO2003044933 A1 WO 2003044933A1 CN 0200828 W CN0200828 W CN 0200828W WO 03044933 A1 WO03044933 A1 WO 03044933A1
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WIPO (PCT)
Prior art keywords
phase
circuit
output
bridge
phases
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PCT/CN2002/000828
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English (en)
French (fr)
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WO2003044933B1 (fr
Inventor
Yufu Wang
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Yufu Wang
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Publication date
Application filed by Yufu Wang filed Critical Yufu Wang
Priority to EP02782645A priority Critical patent/EP1460752B1/en
Priority to US10/496,177 priority patent/US7068523B2/en
Priority to JP2003546464A priority patent/JP4019047B2/ja
Priority to AU2002349446A priority patent/AU2002349446A1/en
Publication of WO2003044933A1 publication Critical patent/WO2003044933A1/zh
Publication of WO2003044933B1 publication Critical patent/WO2003044933B1/zh

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Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
    • H02M1/4208—Arrangements for improving power factor of AC input
    • H02M1/4216—Arrangements for improving power factor of AC input operating from a three-phase input voltage
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02P—CLIMATE CHANGE MITIGATION TECHNOLOGIES IN THE PRODUCTION OR PROCESSING OF GOODS
    • Y02P80/00—Climate change mitigation technologies for sector-wide applications
    • Y02P80/10—Efficient use of energy, e.g. using compressed air or pressurized fluid as energy carrier

Definitions

  • the present invention relates to a power factor correction technology for a three-phase power supply, and particularly to a parallel feed-forward compensation type power factor correction circuit for a three-phase power supply.
  • US patent US006043997A discloses a three-phase power supply parallel feed-forward compensation type power factor correction circuit.
  • the circuit includes a main rectifier circuit and a boost switch.
  • the correction circuit is connected to the input terminal of the three-phase power and the three-phase boost conversion.
  • a method for reducing harmonic distortion of the input current is to use an auxiliary circuit, which includes first, second, and third pairs of auxiliary boost inductors They are connected between the three-phase power input and the main rectifier circuit.
  • the auxiliary circuit also includes an auxiliary boost switch, which is connected to the auxiliary boost electric induction coils behind the first, second and third three-phase rectifier bridges. And the output, this makes the phases of the first, second, and third auxiliary boost inductors consistent, so the harmonic components of the input current of the three-phase boost converter can be reduced.
  • the circuit is in a full power processing state, reducing power efficiency and high cost.
  • the object of the present invention is to provide a three-phase power supply parallel feed-forward compensation type power factor correction circuit, so that the circuit can selectively work, so that it can not only reduce the harmonic component of the power supply, but also significantly improve efficiency and reduce costs.
  • the solution adopted by the present invention is: an auxiliary compensation circuit II is connected in parallel to the main rectifier circuit I of a normal three-phase power supply, and this compensation circuit is a feedforward compensation circuit II.
  • the main rectifier circuit I includes a three-phase bridge 12 and a filter capacitor 13;
  • the feedforward compensation circuit II includes a bidirectional switch 15, a rectifier circuit 16, a boost converter 17, an output current sample 18, and a control circuit 19; the feedforward type in FIG. 2
  • the compensation circuit II works in 12 cycles in a complete cycle.
  • the control circuit 19 controls the bidirectional switch 15 to turn off phase C in sections a-b, turn off phase A in section b-c, and turn off in cd section.
  • feedforward compensation Circuit II shuts off the phase with the largest absolute value in the two phases of the same polarity in the corresponding phase interval, so that the a-b and B-phases of phase A and the bc and B-phases of phase C in FIG. 1 Phases, Phases C-d of Phase C and Phase A, Phases d-e of Phase B and Phase A, B Phases e-f and C, phase A-f-g and phase C, phase A, gh and phase B ...
  • the feedforward compensation circuit II works in 12 cycles in a complete cycle, and the compensation circuit II in the corresponding phase interval through the control circuit 19 causes the bidirectional switch 15 to turn off the two in the same polarity respectively.
  • the phase power the phase with the larger absolute value of the voltage, the phase with the smaller absolute value and the phase of the opposite polarity output DC through the bridge rectifier circuit 16, and then controls the current waveform through the boost converter 17, and the boost is injected into the original three-phase bridge 12 for rectification. After the output terminal 14.
  • the above solution uses a feedforward compensation circuit II in parallel with the main rectifier circuit I, it can significantly reduce the harmonic components in the circuit.
  • the taxi phase interval before and after each phase of the three-phase electricity was non-conducting.
  • the feed-forward compensation circuit II could generate a forced current waveform (for example, as shown in the figure respectively). 3 and the sine wave portion of this phase shown in Fig. 4), so that Ji / 6 before and after zero crossing of each phase of the three-phase electricity is equivalent to being conductive.
  • the voltage waveform of the rectification part of the main circuit is not affected, so the output voltage and current waveforms are also unchanged.
  • the A phase that is in the same polarity as the C phase in this phase interval is turned off.
  • the current forced by the generator 17 can be a 5 JI / 6--JI phase interval sinusoidal waveform proportional to the output current, and is injected into the output 14 after being boosted.
  • the opposite polarities B are the same, they are connected to the A and C phases through the main rectifier circuit and the auxiliary circuit, respectively. Therefore, the current waveform of the B phase is the same as that without the feedforward compensation circuit II.
  • the current passes through the main rectifier circuit, and the current waveform forcibly given by the feedforward compensation circuit II reduces the current in the phase phase corresponding to phase A of the same polarity.
  • the remaining 11 beats work exactly the same. It is precisely because the feedforward compensation circuit ⁇ not only compensates for the lack of current in the phase interval of JI / 6, but also improves the current waveform of the same polarity phase during this period. As a result, the output voltage and current waveforms of the rectifier are not changed.
  • the current waveforms of the opposite polarity phases are not changed, but only the phases with lower absolute voltage values in the two phases of the same polarity have a suitable waveform current, and the currents of the phases with higher absolute voltage values are reduced, so that harmonic distortion is caused. Significantly reduced, the circuit works very efficiently.
  • Figure 1 is the voltage waveform of the three-phase circuit
  • FIG. 2 is a schematic block diagram of a circuit of the present invention
  • Figure 3 and Figure 4 are optional-/ 6 to 0, 0 to JI / 6 forced current waveforms;
  • Figure 5 is the voltage waveform after three-phase bridge rectification;
  • Figure 6 is the current waveform (constant power load) output after three-phase bridge rectification
  • Figure 7 is the current waveform when there is no capacitor and no feedforward compensation circuit II after a phase bridge rectification
  • Figure 8 is the current waveform when there is no capacitor and feedforward compensation circuit II after a phase bridge rectification
  • Figure 9 is the current waveform when there is capacitance and no feedforward compensation circuit II after a phase bridge rectification
  • Figure 10 is the current waveform when a phase bridge rectifier has a capacitor and a feedforward compensation circuit II;
  • FIG. 11 is a circuit schematic diagram of a first embodiment of the present invention.
  • Fig. 12 is a schematic circuit diagram of a second embodiment of the present invention.
  • FIG. 1 is a three-phase power supply voltage waveform of the present invention.
  • the main rectifier circuit I and the feedforward compensation circuit II are connected in parallel.
  • the main rectifier circuit I includes a three-phase bridge circuit 12 and a filter capacitor 13.
  • the input terminal of the three-phase bridge 12 is connected, and the output terminal of the three-phase bridge 12 is connected to the filter capacitor 13.
  • the feedforward compensation circuit ⁇ includes a bidirectional switch 15, a rectifier circuit 16, a boost converter 17, an output current pattern 18, and a control.
  • the input of the bidirectional switch 15 in the feedforward compensation circuit II is connected to the three-phase power 11 in the main rectifier circuit I, the output of the bidirectional switch 15 is connected to the input of the rectifier circuit 16, and the output of the rectifier circuit 16 is connected to The boost converter 17 is connected, the control circuit 19 is connected to three-phase power 11, one end of the output current pattern 18, the bidirectional switch 15, and the boost converter 17, respectively, and the other end of the output current sample 18 is connected to the output terminal 14;
  • the feedforward compensation circuit ⁇ is processed in 12 beats in a complete cycle.
  • Middle control circuit 19 makes Directional switch 15, in the ab section closes phase C, bc section closes phase A, C-d section closes phase B, de section closes phase C, e-f section closes phase A, and f-g section closes phase B respectively.
  • Phase gh, phase gh ..., gp, feedforward compensation circuit II turns off the phase with the absolute value of the same polarity voltage in the corresponding phase interval, so that phase a-b and phase b of phase A in three-phase power Phase, phase b-c and phase B of phase C, phase c-d and phase A of phase C, phase de and phase A of phase B, phase e-f of phase B and phase c, phase f-g of phase A
  • the phase and phase C, phase A and phase gh of phase A and phase B ..., the DC voltage is given by the bridge rectifier circuit 16 in the feedforward compensation circuit II, and the current waveform is controlled by the boost converter 17 and injected into the original In the output 14 of the three-phase bridge rectifier circuit I.
  • the phase C current is changed from no current to a current with a suitable waveform, the phase A current is reduced and the waveform is improved, and the phase B current is unchanged.
  • Such a treatment scheme requires very little power, and the current waveform is significantly improved. Harmonic distortion is significantly reduced. From the changes of the current waveforms in Fig. 5 to Fig. 10, the influence of the feedforward compensation circuit ⁇ on the higher harmonics can be seen as follows:
  • the three-phase electrical connection is a three-phase bridge, and the feed-forward compensation circuit II is added, and the capacitance can be ignored.
  • the typical current waveform of one phase output is shown in Figure 8, and the first-order harmonics in the current are significantly reduced.
  • curve A is a standard sine wave for comparison, and the amplitude of the current waveform is determined by normalizing the output power.
  • the main rectifier circuit I and the feedforward compensation circuit II are connected in parallel, and the main rectifier circuit I is a general three-phase bridge rectifier circuit including the three-phase bridge 12 And filter capacitor 13;
  • the bidirectional switch 15 in the feedforward compensation circuit II is bidirectional thyristor 21, 22, 23,
  • the rectifier circuit is rectifier bridge 16
  • the boost converter 17 includes boost inductors 28, 29, and high frequency rectification
  • the diodes 24, 25 and the switching tube 27 as the switching device, as well as the output current sampling 18 and the control circuit 19;
  • the three phases A, B, and C of the three-phase power 11 are respectively input with the three-phase bridge 12 in the main rectifier circuit I
  • the positive and negative output terminals of the three-phase bridge 12 are connected in parallel to the filter capacitor 13 and connected to the output terminal 14;
  • the three input terminals of the triacs 23, 22, and 21 in the feedforward compensation circuit II are respectively connected to A, B, C three-phase electrical connection, the three output terminals of the triac 23, 22,
  • the inductors 28 and 29 are connected, and the output ends of the boost inductors 28 and 29 are respectively connected to the anode of the diode 25
  • the negative pole of 24, the negative pole of diode 25 is connected to the positive pole of output 14, the positive pole of diode 24 is connected to the negative pole of output 14, and the output ends of boost inductors 28 and 29 are respectively connected to the collector and emitter of switch tube 27, which functions as a boost switch.
  • the control circuit 19 in the feedforward compensation circuit II includes a trigger circuit 30, three phase detection terminals 31, 32, 33, three bidirectional switch control terminals 34, 35, 36, and an output current detection terminal 37.
  • the trigger circuit 30 is connected to the gate of the switching tube 27, and the three phase detection terminals 31, 32, and 33 are respectively connected to the eight, three, and three phases of the three-phase electricity 11, and the three bidirectional switch control terminals 34, 35, 36 is connected to the three control electrodes of the three triacs 21, 22, 23 respectively, the current detection terminal 37 is connected to one end of the output current sample 18, and the other end of the output current sample 18 is connected to the positive terminal of the output terminal 14;
  • the control circuit 19 obtains the amplitude of the output current by using the output current sample 18 to determine the amplitude of the current given by the boost converter 17.
  • the control circuit 19 in the feedforward compensation circuit II obtains the phase signal from the three-phase input 11, and the bidirectional thyristor 21 is turned off in the a-b section in FIG. 1 to cut off the phase C, and the phase A and the phase B are bridged.
  • the rectifier circuit 16 provides a DC voltage to the boost converter 17, the bc section turns off the triac 23 to cut off the A phase, and the C and B phases provide the DC voltage to the boost converter 17 through the bridge rectifier circuit 16,
  • the triac 22 is turned off to cut off the B phase, and the C phase and the A phase provide a DC voltage to the boost converter 17 through the bridge rectifier circuit 16, and the lm section is turned off in FIG.
  • the triac 22 thus cuts off the B phase, and the A and C phases provide a DC voltage to the boost converter 17 through the bridge rectifier circuit 16, and so on.
  • Phase That is, the feed-forward type compensation circuit II sequentially turns off the phases with the absolute voltages of the same polarity in the corresponding phase interval in order, so that the remaining two phases are rectified by the bridge rectifier circuit 16 and the boost converter 17 Output an appropriate forced current waveform.
  • any one of the inductors 28 and 29 works in the step-up inductor state, and the voltage across the other is approximately zero, as shown in a, c, and e in Figure 1.
  • G, i, k, m point inductors 28 and 29 state transition just force the current waveform to zero at these points, at 13, d, f, h, j, 1 point inductor 28 and 29 state unchanged, and
  • the triac to be turned off and to be turned on happens to be in series with the inductor working in the step-up inductor state, which brings great convenience to the zero-crossing shutdown of the triac.
  • the working principle of the circuit is the same as that shown in FIG. 11.
  • the main rectifier circuit I and the feedforward compensation circuit II are connected in parallel, and the main rectifier circuit I is a general three-phase bridge rectifier circuit, including a three-phase bridge 12 and a filter capacitor 13;
  • the bidirectional switch 15 in the feedforward compensation circuit II is a bidirectional thyristor 21, 22, 23, and the rectifier circuit is a rectifier bridge 16,
  • the boost converter 17 is a flyback boost converter.
  • the boost converter includes an IGBT switch tube 27, a transformer 28, a diode 26, an output current sample 18 and a control circuit 19, three-phase power A, B, C three phases are respectively connected to the input terminals of the three-phase bridge 12 in the main rectifier circuit I, and the positive and negative output terminals of the three-phase bridge 12 are connected in parallel with the filter capacitor 13 to the output terminal 14;
  • the three input terminals of the thyristors 23, 22, and 21 are respectively electrically connected to the three phases of A, B, and C.
  • the three output terminals of the triac 23, 22, and 21 are connected to the rectifier bridge 16 of the feedforward compensation circuit.
  • the control circuit 19 includes a trigger circuit 30 and three phase detections.
  • Terminals 31, 32, 33, three bidirectional switch control terminals 34, 35, 36 and output current detection terminal 37 the trigger circuit 30 is connected to the gate of the switch 27, and the three phase detection terminals 31, 32, 33 and A, B, and C of the three-phase power 11 are three-phase electrically connected.
  • the three bidirectional switch control terminals 34, 35, and 36 are respectively connected to the three control poles of the three bidirectional thyristors 21, 22, and 23.
  • the current detection terminal 37 It is connected to one end of the output current sample 18, and the other end of the output current sample 18 is connected to the positive terminal of the output terminal 14.
  • the control circuit 19 obtains the amplitude of the output current by using the output current sample 18 to determine the voltage given by the boost converter 17. The magnitude of the flow.
  • the three-phase electric parallel feed-forward compensation power factor correction circuit of the present invention is not limited to the embodiment, such as using other forms of power switch 15, rectifier circuit 16, boost converter 17, output current sampling 18, The control circuit 19 and the like all fall within the protection scope of the present invention.

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Description

三相电源并联前馈补偿式功率因数校正电路
技术领域
本发明涉及三相电源功率因数校正技术， 尤其是一种并联前馈补偿式三相电源功率 因数校正电路。
技术背景
美国专利 US006043997A公开了一种三相电源并联前馈补偿式功率因数校正电路， 该电路包括一个主整流电路和一个升压开关， 该校正电路连接在三相电的输入端和三相 升压转换器的输出端之间， 在三相升压转换器中， 减少输入电流谐波失真的方法是， 使 用一个辅助电路， 该电路包括第一、 第二、 第三， 共三对辅助升压电感， 它们连接在三 相电的输入端和主整流电路之间， 辅助电路还包括一个辅助升压开关， 连接在第一、 第 二、 第三的三相整流桥之后的辅助升压电感应圈和输出之间， 这使得通过第一、 第二、 第三辅助升压电感的相位一致， 所以能减少三相升压转换器的输入电流的谐波分量。 该 电路处于全功率处理状态、 降低了电源效率、 成本高。
发明内容
本发明的目的是提供一种三相电源并联前馈补偿式功率因数校正电路， 使电路有 选择性地进行工作， 使其不仅能降低电源的谐波分量， 还能显著提高效率， 降低成本。
本发明采用的解决方案是： 在正常三相电源的主整流电路 I上并联辅助的补偿电 路 II， 这种补偿电路为前馈式补偿电路 II。
主整流电路 I包括三相桥 12和滤波电容 13; 前馈式补偿电路 II包括双向开关 15、 整流电路 16、 升压变换器 17、 输出电流采样 18、 控制电路 19; 图 2中前馈式补偿电路 II在一个完整的周期中分 12个节拍工作， 控制电路 19控制双向幵关 15， 分别在图 1 中 a- b段关断 C相， b- c段关断 A相、 c-d段关断 B相、 d- e段关断 C相、 e- f段关断 A 相、 f- g段关断 B相， g h段关 C相……， 周而复始地循环， BP, 前馈式补偿电路 II在 对应的相位区间关断处于同极性两相中电压绝对值大的相， 使图 1中三相电 11中 A相 的 a- b段与 B相、 C相的 b-c段与 B相、 C相的 C- d段与 A相、 B相的 d- e段与 A相、 B 相的 e- f段与 C相、 A相的 f- g段与 C相、 A相的 g-h段与 B相……分别通过前馈式补 偿电路 II中的整流电路 16给出直流电压， 再由升压变换器 17控制电流波形并注入到原 三相桥式整流电路 I的输出 14 中。 换句话说就是， 前馈式补偿电路 II在一个完整的周 期中分 12个节拍工作， 补偿电路 II在对应的相位区间通过控制电路 19按照顺序使双向 开关 15分别关断处于同极性的两相电中电压绝对值大的相， 绝对值小的相与异极性相 通过桥式整流电路 16输出直流， 再经升压变换器 17控制电流波形， 升压注入到原三相 桥 12整流后的输出端 14中。
由于上述解决方案采用了与主整流电路 I相并联的前馈式补偿电路 II， 所以能显 著降低电路中的谐波分量。 未采用本电路前， 三相电每相过零前后的士 相位区间 是不导通的，加入前馈式补偿电路 Π后，前馈式补偿电路 II能产生一个强制电流波形（例 如分别如图 3和图 4所示该相位之中的正弦波部分)，使得三相电每相过零前后的土 Ji /6 相当于是导通的。经过前馈式补偿电路强制处理后， 不影响主电路整流部分的电压波形， 因此， 输出电压和电流波形也不变。 例如在图 1中 C相 b-c段，'在前馈式补偿电路 II中 关断在该相位区间与 C相处于同极性的 A相， C相与 B相通过整流电路 16整流， 升压 变换器 17强制的电流可如图 3所示， 与输出电流成比例的 5 JI /6-- JI相位区间正弦波 形， 升压后注入输出 14。 在该相位区间中， 异极性 B相同时通过主整流电路和辅助电路 分别与 A相和 C相导通， 所以 B相的电流波形与不加前馈式补偿电路 II时相同， C相无 电流通过主整流电路， 其通过前馈式补偿电路 II强制给出的电流波形降低了同极性的 A 相对应相位区间的电流。 其余 11 个节拍的工作原理完全相同。 正是由于前馈式补偿电 路 Π不仅补偿了土 JI /6相位区间的电流缺失， 而且改善了该时段内与之同极性相的电 流波形， 其结果是不改变整流器的输出电压电流波型， 也不改变异极性相的电流波形， 只是使两同极性相中电压绝对值低的相有了适宜波形的电流， 同时降低了电压绝对值高 的相的电流， 所以使得谐波失真明显降低， 电路工作效率很高。
下面结合附图和具体实施例对本发明作进一步详细的说明
附图说明
图 1是三相电路的电压波形；
图 2是本发明的电路原理框图；
图 3和图 4分别是一个可选用的- /6到 0， 0到 JI /6强制电流波形； 图 5是三相桥式整流后的电压波形；
图 6是三相桥式整流后输出的电流波形（恒功率负载)；
图 7是某一相桥式整流后无电容、 无前馈式补偿电路 II时的电流波形；
图 8是某一相桥式整流后无电容、 有前馈式补偿电路 II时的电流波形；
图 9是某一相桥式整流后有电容、 无前馈式补偿电路 II时的电流波形；
图 10是某一相桥式整流后有电容、 有前馈式补偿电路 II时的电流波形；
图 11是本发明第一个实施例的电路原理图；
图 12是本发明第二个实施例的电路原理图。
具体实施方式
图 1为本发明之三相电源电压波形。 在图 2所示之电路原理框图中， 主整流电路 I 和前馈式补偿电路 II相并联， 主整流电路 I包括三相桥电路 12和滤波电容 13， 三相电 11与主整流电路 I中的三相桥 12输入端相连， 三相桥 12的输出端与滤波电容 13相连， 前馈式补偿电路 Π包括双向开关 15、 整流电路 16、 升压变换器 17、 输出电流釆样 18、 控制电路 19; 前馈式补偿电路 II中的双向开关 15输入端与主整流电路 I中的三相电 11 相连， 双向开关 15输出端与整流电路 16的输入端相连， 整流电路 16的输出端与升压 变换器 17相连，控制电路 19分别与三相电 11、输出电流釆样 18的一端、双向开关 15、 升压变换器 17相连， 输出电流采样 18的另一端连接在输出端 14上； 该电路工作时， 前馈式补偿电路 Π在一个完整周期中分 12个节拍进行处理， 针对在主整流电路 I中不 导通的每相电过零前后的 ± /6相位区间， 由图 2中控制电路 19使双向开关 15， 分别 在图 1中 a-b段关 C相、 b-c段关 A相、 C- d段关 B相、 d-e段关 C相、 e- f段关 A相、 f - g段关 B相、 g-h段关 C相……， gp， 前馈式补偿电路 II在对应的相位区间关断处于 同极性的电压绝对值大的相， 使三相电中 A相的 a- b段与 B相、 C相的 b- c段与 B相、 C相的 c- d段与 A相、 B相的 d-e段与 A相、 B相的 e- f段与 C相、 A相的 f- g段与 C相、 A相的 g-h段与 B相……， 分别通过前馈式补偿电路 II中的桥式整流电路 16给出直流 电压， 再由升压变换器 17控制电流波形并注入到原三相桥式整流电路 I的输出 14中。 经过如此处理， 例如在图 1的 b-c时段， C相由无电流到有适宜波形的电流， A相的电 流减小波形改善， B相电流不变。 如此的处理方案所需功率很少， 电流波形明显改善， 谐波失真明显降低。 从图 5至图 10的电流波形的变化， 可以看出前馈式补偿电路 Π对高次谐波的影响， 具体如下：
三相电连接三相桥后其输出的典型电压波形如图 5所示（参考）， 如为恒功率负载， 其输出的典型电流波形如图 6所示。
三相电连接三相桥， 在不加前馈式补偿电路， 并且电容可以忽略不计时， 其某一相 的典型电流波形如图 7所示， 存在着高次谐波。
三相电连接三相桥， 在加前馈式补偿电路 II， 并且电容可以忽略不计时， 其某一相 输出的典型电流波形如图 8所示， 电流中的髙次谐波明显减少。
三相电连接三相桥， 在不加前馈式补偿电路， 并且有电容时， 其某一相的典型电流 波形如图 9所示， 电路依然存在着高次谐波。
三相电连接三相桥， 在加前馈式补偿电路 II， 并且有电容时， 其某一相的典型电流 波形如图 10所示， 电流中的高次谐波同样明显减少。
在以上各图中， 曲线 A为比较用的标准正弦波， 电流波形的幅值均按输出功率归一 化确定。
在图 11 所示的本发明的第一个具体实施例中， 主整流电路 I和前馈式补偿电路 II 相并联， 主整流电路 I为通常的三相桥式整流电路， 包括三相桥 12和滤波电容 13; 前 馈式补偿电路 II中的双向开关 15为双向可控硅 21、 22、 23, 整流电路为整流桥 16， 升 压变换器 17包括升压电感 28、 29、高频整流二极管 24、 25和作为开关器件的幵关管 27， 还有输出电流采样 18和控制电路 19; 三相电 11的 A、 B、 C三相分别与主整流电路 I 中的三相桥 12输入端相连， 三相桥 12的正负输出端与滤波电容 13并联后连接到到输 出端 14中； 前馈式补偿电路 II中的双向可控硅 23、 22、 21的三个输入端分别与 A、 B、 C三相电连接， 双向可控硅 23、 22、 21的三个输出端接前馈式补偿电路的整流桥 16的 输入端， 整流桥 16的正负输出端分别与升压电感 28、 29相连， 升压电感 28、 29的输 出端分别接二极管 25的正极和 24的负极， 二极管 25的负极接输出 14的正极， 二极管 24的正极接输出 14的负极， 同时升压电感 28、 29的输出端分别与起升压开关作用的 开关管 27的集电极和发射极相连； 前馈式补偿电路 II中控制电路 19包括触发电路 30、 三个相位检测端 31、 32, 33， 三个双向开关控制端 34、 35、 36和输出电流检测端 37, 触发电路 30连接到开关管 27的栅极上， 三个相位检测端 31、 32、 33分别与三相电 11 的八、 B、 C三相电相连， 三个双向开关控制端 34、 35、 36分别与三个双向可控硅 21、 22、 23的三个控制极相连， 电流检测端 37与输出电流釆样 18的一端相连， 输出电流 采样 18的另一端连接到输出端 14的正极； 控制电路 19通过输出电流采样 18得到输出 电流的幅值， 用以确定升压变换器 17给出电流的幅值。
这样， 前馈式补偿电路 II中控制电路 19由三相输入 11获得相位信号， 在图 1中的 a - b段关断双向可控硅 21从而切断 C相， A相与 B相通过桥式整流电路 16给出直流电 压到升压变换器 17， b-c段关断双向可控硅 23从而切断 A相， C相与 B相通过桥式整 流电路 16给出直流电压到升压变换器 17， 在 c- d段关断双向可控硅 22从而切断 B相， C相与 A相通过桥式整流电路 16给出直流电压到升压变换器 17， ……在图 1中的 l-m 段关断双向可控硅 22从而切断 B相， A相与 C相通过桥式整流电路 16给出直流电压到 升压变换器 17，如此循环往复，该相位信号同时决定了升压变换器给出电流的相位。即， 前馈式补偿电路 II在对应的相位区间按照顺序依次关断处于同极性的电压绝对值大的 相， 使其余两相通过桥式整流电路 16进行整流， 并由升压变换器 17输出适当的强制电 流波形。
还应说明的是在任意一个节拍的相位区间中， 电感器 28和 29中只有其中之一工作 于升压电感状态， 另一个两端电压近似为零， 在图 1中的 a、 c、 e、 g、 i、 k、 m点电感 器 28和 29状态转换， 恰好强制电流波形在这些点归零， 在13、 d、 f、 h、 j、 1点电感 器 28和 29状态不变， 而需关断和将要导通的双向可控硅恰好是与工作于升压电感状态 的电感串通， 以上为双向可控硅的过零关断带来极大的方便。
在图 12所示的本发明的第二个具体实施例中， 电路的工作原理与图 11所示电路相 同， 图 12 中， 主整流电路 I和前馈式补偿电路 II相并联， 主整流电路 I为通常的三相 桥式整流电路， 包括三相桥 12和滤波电容 13; 前馈式补偿电路 II中的双向开关 15为 双向可控硅 21、 22、 23， 整流电路为整流桥 16， 升压变换器 17为反激式升压变换器， 升压变换器包括 IGBT开关管 27、 变压器 28， 二极管 26， 还有输出电流采样 18和控制 电路 19， 三相电 11的 A、 B、 C三相分别与主整流电路 I中的三相桥 12输入端相连， 三相桥 12的正负输出端与滤波电容 13并联后连接到输出端 14中； 前馈式补偿电路 II 中的双向可控硅 23、 22、 21的三个输入端分别与 A、 B、 C三相电连接， 双向可控硅 23、 22、 21 的三个输出端接前馈式补偿电路的整流桥 16 的输入端， 整流桥 16的正极与变 压器 28的初级线圈一端连接， 变压器 28 ,初级线圈的另一端与起升压开关作用的开关管 27的集电极连接， 再经发射极与整流桥 16的负极相连，二极管 26的负极接在输出端 14 的正极上， 二极管 26正极与变压器 28的次级线圈一端连接， 变压器 28的次级线圈的 另一端接在输出端 14的负极上，控制电路 19包括触发电路 30、三个相位检测端 31、 32、 33， 三个双向开关控制端 34、 35、 36和输出电流检测端 37，触发电路 30连接到开关管 27的栅极上， 三个相位检测端 31、 32、 33分别与三相电 11的 A、 B、 C三相电相连， 三个双向开关控制端 34、 35、 36分别与三个双向可控硅 21、 22、 23 的三个控制极相 连， 电流检测端 37与输出电流采样 18的一端相连， 输出电流采样 18的另一端连接到 输出端 14的正极； 控制电路 19通过输出电流采样 18得到输出电流的幅值， 用以确定 升压变换器 17给出电流的幅值。
当然， 本发明之三相电并联前馈补偿式功率因数校正电路并不局限于所举实施例， 如采用其它形式的电源开关 15、 整流电路 16、 升压变换器 17、 输出电流采样 18、 控制 电路 19等， 这些变化均落在本发明的保护范围之内。

Claims

权 利 要 求
1、 一种三相电源并联前馈补偿式功率因数校正电路， 包括三相主整流电路 I和辅 助的补偿电路 II， 其特征在于： 三相主整流电路 I和补偿电路 II相并联， 补偿电路 II为 前馈式补偿电路。
2、 根据权利要求 1 所述的三相电源并联前馈补偿式功率因数校正电路， 其特征在 于： 主整流电路 I包括三相桥和滤波电容； 前馈式补偿电路 II包括双向开关、整流电路、 升压变换器、 输出电流采样、 控制电路； 前馈式补偿电路 Π在一个完整的周期中分 12 个节拍工作， 前馈式补偿电路 II在对应的相位区间通过控制电路按照顺序使双向开关分 别关断处于同极性的电压绝对值大的相， 绝对值小的相与异极性相通过整流电路输出直 流， 再经升压变换器控制电流波形， 升压注入到原三相桥整流后的输出端中。
3、 根据权利要求 2所述的三相电源并联前馈补偿式功率因数校正电路， 其特征在 于： 三相电与主整流电路 I中的三相桥输入端相连， 三相桥的输出端与滤波电容相连， 前馈式补偿电路 II中的双向开关输入端与主整流电路 I中的三相电相连， 双向开关输出 端与整流电路的输入端相连， 整流电路的输出端与升压变换器相连， 控制电路分别与三 相电、 输出电流采样的一端、 双向开关、 升压变换器相连， 输出电流采样的另一端连接 在输出端上； 前馈式补偿电路 II在一个完整周期中分 12个节拍进行处理， 针对在主整 流电路 I中不导通的每相电过零前后土 /6相位区间，控制电路使双向开关，分别在 a - b 段关 C相、 b-c段关 A相、 C- d段关 B相、 d- e段关 C相、 e- f段关 A相、 f- g段关 B相、 g- h段关 C相， 周而复始地循环， gp, 前馈式补偿电路 II在对应的相位区间关断处于同 极性两相中电压绝对值大的相， 使三相电中 A相的 a- b段与 B相、 C相的 b- c段与 B相、 C相的 C- d段与 A相、 B相的 d-e段与 A相、 B相的 e_f段与 C相、 A相的 f-g段与 C相、 A相的 g- h段与 B相分别通过前馈式补偿电路 II中的整流电路给出直流电压， 再由升压 变换器控制电流波形并注入到原三相桥式整流电路 I的输出中。
4、 根据权利要求 3所述的三相电源并联前馈补偿式功率因数校正电路， 其特征在 于： 前馈式补偿电路 II中的双向幵关为双向可控硅或 GT0， IGBT组合双向电子开关， 整 流电路为整流桥， 升压变换器包括升压电感， 高频整流二极管和作为开关器件的幵关管， 还有输出电流采样和控制电路， 三相电的八、 B、 C三相分别与主整流电路 I中的三相桥 输入端相连， 三相桥的正负输出端与滤波电容并联后连接到输出端中； 前馈式补偿电路 II中的三个双向可控硅的三个输入端分别与 A、 B、 C三相电连接， 三个双向可控硅的三 个输出端分别接前馈式补偿电路的整流桥的三个输入端， 整流桥的正负输出端分别与二 个升压电感相连， 二个升压电感的输出端分别接一个二极管的正极和另一个二极管的负 极， 一个二极管的负极接输出的正极， 另一个二极管的正极接输出的负极， 同时二个升 压电感的输出端分别与起升压开关作用的开关管的集电极和发射极相连； 前馈式补偿电 路 II中控制电路包括触发电路， 三个相位检测端， 三个双向开关控制端和输出电流检测 端,触发电路连接到开关管的栅极上， 三个相位检测端分别与三相电 11的八、 B、 C三相 电相连， 三个双向开关控制端分别与三个双向可控硅的三个控制极相连， 电流检测端与 输出电流采样的一端相连， 输出电流采样的另一端连接到输出端的正极； 控制电路通过 输出电流采样得到输出电流的幅值， 用以确定升压变换器给出电流的幅值； 这样， 前馈 式补偿电路 II中控制电路由三相电获得相位信号， 在 a-b段关断一双向可控硅从而切断 C相， A相与 B相通过桥式整流电路给出直流电压到升压变换器， b-c段关断另一双向 可控硅从而切断 A相， C相与 B相通过桥式整流电路给出直流电压到升压变换器， 在 c - d段关断第三个双向可控硅从而切断 B相， C相与 A相通过桥式整流电路给出直流电压 到升压变换器， 在 1- m段关断一双向可控硅从而切断 B相， A相与 C相通过桥式整流电 路给出直流电压到升压变换器， 如此循环往复， 即， 前馈式补偿电路 II在对应的相位区 间按照顺序依次关断处于同极性的电压绝对值大的相， 使其余两相通过桥式整流电路进 行整流， 并由升压变换器输出适当的强制电流波形。
5、 根据权利要求 3所述的三相电源并联前馈补偿式功率因数校正电路， 其特征在 于： 前馈式补偿电路 II中的双向开关为双向可控硅， 整流电路为整流桥， 升压变换器为 反激式升压变换器， 升压变换器包括 IGBT开关管， 变压器， 二极管， 还有输出电流采 样和控制电路， 三相电的八、 B、 C三相分别与主整流电路 I中的三相桥输入端相连， 三 相桥的正负输出端与滤波电容并联后连接到输出端中； 前馈式补偿电路 II中的三个双向 可控硅的三个输入端分别与 A、 B、 C三相电连接， 三个双向可控硅的三个输出端接前馈 式补偿电路的整流桥的三个输入端， 整流桥的输出正极与变压器的初级线圈一端连接， 变压器初级线圈的另一端与起升压开关作用的开关管的集电极连接， 再经发射极与整流 桥的输出负极相连， 二极管的负极接在输出端的正极上， 二极管的正极与变压器的次级 线圈一端连接， 变压器的次级线圈的另一端接在输出端的负极上， 控制电路包括触发电 路， 三个相位检测端， 三个双向开关控制端和输出电流检测端，触发电路连接到开关管 的栅极上， 三个相位检测端分别与三相电的 A、 B、 C三相电相连， 三个双向开关控制端 分别与三个双向可控硅的三个控制极相连， 电流检测端与输出电流采样的一端相连， 输 出电流采样的另一端连接到输出端的正极； 控制电路通过输出电流采样得到输出电流的 幅值， 用以确定升压变换器给出电流的幅值。
PCT/CN2002/000828 2001-11-20 2002-11-19 Circuit de correction de facteur de puissance du type a compensation aval en parallele pour source de courant triphase WO2003044933A1 (fr)

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* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US7157886B2 (en) 2002-10-21 2007-01-02 Microsemi Corp. —Power Products Group Power converter method and apparatus having high input power factor and low harmonic distortion
US8624514B2 (en) * 2012-01-13 2014-01-07 Power Integrations, Inc. Feed forward imbalance corrector circuit
CN102624249B (zh) * 2012-04-23 2014-04-16 湖南大学 带无功补偿功能的三相变两相正交逆变电源复合控制方法
CN103683993A (zh) * 2013-12-25 2014-03-26 唐山松下产业机器有限公司 一种逆变焊接电源
CN103840684B (zh) * 2014-03-12 2016-08-24 中国矿业大学(北京) 大功率补偿型级联二极管h桥单位功率因数整流器
CN104079159B (zh) * 2014-06-11 2017-05-17 成都芯源系统有限公司 数字功率因数校正电路及其方法

Citations (6)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US5784269A (en) 1997-02-21 1998-07-21 Lucent Technologies, Inc. Three phase high power factor converter using phase selection circuit
JPH10201236A (ja) * 1997-01-13 1998-07-31 Toshiba Corp 電源装置
US5886891A (en) * 1998-07-17 1999-03-23 Lucent Technologies Inc. Three-phase boost converter having wye-connected input capacitors and method of operation thereof
US6043997A (en) 1998-08-12 2000-03-28 Lucent Technologies Inc. Two stage, three-phase boost converter with reduced total harmonic distortion
CN1057174C (zh) * 1998-11-27 2000-10-04 深圳市华为电气股份有限公司 带有功率因数校正和谐波抑制电路的三相整流电路
CN1317859A (zh) * 2000-04-13 2001-10-17 深圳市华为电气技术有限公司 用于三相供电系统的功率因数校正电路

Family Cites Families (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US4384321A (en) * 1980-04-29 1983-05-17 California Institute Of Technology Unity power factor switching regulator
US5574636A (en) * 1994-09-09 1996-11-12 Center For Innovative Technology Zero-voltage-transition (ZVT) 3-phase PWM voltage link converters
US5936855A (en) * 1996-09-03 1999-08-10 Mercury Electric Corporation Harmonic correction of 3-phase rectifiers and converters
US6038151A (en) * 1998-07-17 2000-03-14 Lucent Technologies Inc. Switching network and method of reducing input current total harmonic distortion for a boost converter

Patent Citations (6)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JPH10201236A (ja) * 1997-01-13 1998-07-31 Toshiba Corp 電源装置
US5784269A (en) 1997-02-21 1998-07-21 Lucent Technologies, Inc. Three phase high power factor converter using phase selection circuit
US5886891A (en) * 1998-07-17 1999-03-23 Lucent Technologies Inc. Three-phase boost converter having wye-connected input capacitors and method of operation thereof
US6043997A (en) 1998-08-12 2000-03-28 Lucent Technologies Inc. Two stage, three-phase boost converter with reduced total harmonic distortion
CN1057174C (zh) * 1998-11-27 2000-10-04 深圳市华为电气股份有限公司 带有功率因数校正和谐波抑制电路的三相整流电路
CN1317859A (zh) * 2000-04-13 2001-10-17 深圳市华为电气技术有限公司 用于三相供电系统的功率因数校正电路

Non-Patent Citations (1)

* Cited by examiner, † Cited by third party
Title
See also references of EP1460752A4 *

Cited By (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN101499771B (zh) * 2008-01-28 2013-03-06 王玉富 三相电源能量反馈三相电机变频调速驱动器

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AU2002349446A1 (en) 2003-06-10
CN1420611A (zh) 2003-05-28
CN100517927C (zh) 2009-07-22
JP4019047B2 (ja) 2007-12-05
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US7068523B2 (en) 2006-06-27
EP1460752B1 (en) 2012-03-14

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