WO1995022065A1 - Synchroniseur d'ondes sonores - Google Patents

Synchroniseur d'ondes sonores Download PDF

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Publication number
WO1995022065A1
WO1995022065A1 PCT/US1994/001601 US9401601W WO9522065A1 WO 1995022065 A1 WO1995022065 A1 WO 1995022065A1 US 9401601 W US9401601 W US 9401601W WO 9522065 A1 WO9522065 A1 WO 9522065A1
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WO
WIPO (PCT)
Prior art keywords
signal
frequency
generator
transducer
responsive
Prior art date
Application number
PCT/US1994/001601
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English (en)
Inventor
Lawrence Garde
Original Assignee
Lawrence Garde
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Lawrence Garde filed Critical Lawrence Garde
Priority to JP7521177A priority Critical patent/JPH09509252A/ja
Priority to PCT/US1994/001601 priority patent/WO1995022065A1/fr
Priority to EP94917877A priority patent/EP0745227A4/fr
Priority to AU69411/94A priority patent/AU6941194A/en
Publication of WO1995022065A1 publication Critical patent/WO1995022065A1/fr

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Classifications

    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B11/00—Transmission systems employing sonic, ultrasonic or infrasonic waves
    • G—PHYSICS
    • G01—MEASURING; TESTING
    • G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
    • G01S7/00—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00
    • G01S7/52—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00 of systems according to group G01S15/00
    • G01S7/523—Details of pulse systems
    • G—PHYSICS
    • G01—MEASURING; TESTING
    • G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
    • G01S7/00—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00
    • G01S7/52—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00 of systems according to group G01S15/00
    • G01S7/534—Details of non-pulse systems

Definitions

  • This invention relates in particular to electronic devices which use sound waves: for measurement, for communicating, for energy transmission or for operating acoustic devices.
  • Sonic devices are being used in a broad range of products. They have for many years been used in depth sounders, cameras, and in medical analysis machines, but now they are being incorporated into automobiles, sporting goods, for transmission of acoustic sound and data on an ultrasonic carrier, and for a multitude of other items. Sonics are becoming important in the world of measurement and control. At low power levels sonic waves provide non-intrusive and safe methods for object detection and distance measurement.
  • interface circuits are designed for pulsed-burst mode operation. These interface circuits radiate short sonic chirps and detect the amplitude of the returned signal from the sensing transducer. They are used for distance and motion measurement.
  • a typical example is an ultrasonic ranging system marketed by the Poloroid Corporation 119 Windsor Street, Cambridge, MA 02139. This is disclosed in US Patent No. 4,199,246 by Muggli 1980.
  • This circuit is specifically designed to use a single capacitive broad bandpass transducer in the pulsed-burst mode.
  • Another example is the LM1812 Ultrasonic Transceiver marketed by National Semiconductor, 2900 Semiconductor Drive, P.O. Box 58090, Santa Clara, CA 95052-8090. This is designed to use a single piezoelectric transducer in the pulse-burst mode.
  • Interface circuits for sending and receiving a continuous sonic signal for improved resolution are specifically designed to suit the particular application and are not suitable for use as general purpose sonic interface circuits.
  • Typical examples of this type of interface circuit are disclosed in U.S. Patent No. 4,122,427 by Karsh, 1978 and U.S. Patent No. 4,197,856 by Northrop, 1980. These circuits are used for high resolution motion measurement and provide a clock signal synchronized to the signal from the sensing transducer. They detect phase change and provide no amplitude detection They lose synchronism in signal gaps therefore they are not adaptable for pulse-burst, or single transducer operation.
  • There is partial disclosure of the present invention in US Continuation in part dated Jan. 14. 1994, of original application No. 08-011,369, filed Jan. 29,1993
  • a sonic interface circuit is needed to satisfy the above needs. It should preferably adapt to user circuits, such as microprocessors.
  • the present invention is a sonic wave synchronizer interface circuit, invented to satisfy the needs described in the Background Section. It converts signals provided by an external user circuit into signals for driving a radiating sonic transducer, and detects the amplitude of the sensing transducer signal. It detects phase variations in the sensing transducer signal by comparison with an internal generator signal synchronized to an average of the input signal frequency. A reference input gives it self-test and signal comparison capability.
  • the basic synchronizer circuit can be adapted to make distance and motion measurements in the continuous, chopped, and pulsed-burst operating modes. It can adapt to control separate or shared transducers for radiating and sensing, and has many uses throughout the sound range. Two generator types
  • the synchronizer is made using a stimulated tuned amplifier generator or a phase-locked-loop driven generator.
  • the synchronizer When used in a receiving mode, the synchronizer produces a generator signal synchronized to an average frequency of the sensed sonic waves.
  • the generator signal is sustained at that average frequency when sonic waves are intermittent, and when they cease being received.
  • a sustaining circuit reduces frequency change in the absence of a detected signal to a slow drift rate. This enables the synchronizer to operate in a chopped or pulsed-burst mode.
  • a reference signal input may be used to synchronize the generator signal at the desired initializing, or continuing radiating frequency. It can provide a variable radiating frequency for scanning a sonic frequency range, or for radiating modulated sonic waves, and it is useful as a comparison signal when measuring sonic wave strength, or for testing the synchronizer circuit.
  • the synchronizer provides a detected-amplitude signal in proportion to an average amplitude of either the sensing transducer signal or the reference signal. It also provides a detected-cycle signal from each cycle of the signal being detected. Amplitude modulation can be measured from the detected- amplitude signal. Likewise phase modulation of either the transducer signal or reference signal can be measured from a comparator output signal which combines digital transitions from the generator signal and the detected-cycle signal. A detector control signal makes the input signal selection.
  • a phase adjusting circuit in the comparator circuit is used to align phase relationships within the synchronizer for low drift conditions and can be used to introduce phase modulation into the generator signal for phase modulating radiated waves responding to a phase modulation signal from the user circuit.
  • a driver circuit interfaces with the radiating transducer and can include a circuit for amplitude modulating the radiated waves responsive to an amplitude modulation signal. Phase modulation may be introduced in the driver circuit by means of a modulated delay circuit (not shown) responding to a phase control signal.
  • a single transducer can be used for both radiating and sensing.
  • An analog switch in the driver controlled by a radiate control signal isolates the driver from the transducer while the single transducer is sensing.
  • a drive-current signal from the driver provides a signal responsive to the alternating current flowing in the radiating transducer.
  • a frequency adjuster circuit responding to the comparator signal adjusts the generator signal frequency to be at a moving average of the frequency of the detected-cycle signals.
  • a sensitivity control input adjusts the response of the frequency adjuster to determine the period over which the averaging will take place.
  • the sensitivity control input is provided by the detected- amplitude signal, the averaging period will decrease as the detected- amplitude signal responds to an increase in the input signal amplitude. This results in the generator signal being most responsive to the highest amplitude input signal.
  • the sensitivity control signal can be used to provide fast synchronization to the input signal under control of the user circuit.
  • the drive-current signal provides the reference signal, while the detector is switched to detect it.
  • the generator responds by synchronizing to the detected-cycle signal and adjusting its frequency to maximize the alternating current in the radiating transducer, sensitized by the detected-amplitude signal.
  • the peaking admittance characteristic of a radiating piezoelectric transducer will caused it to automatically radiate at the optimum radiating frequency. Limited frequency detection
  • a filter is usually included in the detector circuit to limit its frequency passband sensitivity when the sensing transducer has a broad frequency passband.
  • the sonic wave synchronizer provides a versatile sonic interface circuit which adapts for two way communication by amplitude and phase modulated signals.
  • FIG. 1 Basic synchronizer schematic.
  • Figure 2. Tuned amplifier synchronizer schematic.
  • Figure 3. Phase-locked-loop synchronizer schematic.
  • Figure 4. Tuned amplifier synchronizers in two-way communication.
  • Figure 5a Synchronizer 100a and piezoelectric transducers (91 & 92) characteristics.
  • Figure 5b. Synchronizer 100b and piezoelectric transducer (93) characteristics.
  • Figure 6. Phase-locked-loop synchronizers in two-way communication.
  • Figure 7a Synchronizer 100c and piezoelectric transducers (91 & 92) characteristics.
  • Figure 7b. Synchronizer lOOd and piezoelectric transducers (93) characteristics.
  • Figure 8. A preferred embodiment of a detector circuit.
  • FIG. 9a Typical waveforms from figure 9 embodiment.
  • Figure 10. Preferred embodiment of frequency adjuster 40a and tuned amplifier 50a.
  • Figure 10a Typical waveforms from figure 10 embodiment.
  • Figure 11. A preferred embodiment of analog adjuster 40b, analog generator 50b, and driving circuit 60.
  • DEFINITIONS for clarity and brevity Sound. A vibration which can be heard, and also that which is beyond human hearing and travels at the speed of sound through an elastic medium.
  • Acoustic sound That sound which can be heard by a human being.
  • Sonic Having to do with sound, including acoustic sound, ultrasonic, or ultrasound. Having waves which propagate at the speed of sound (about 331.3 meters per second in air).
  • Sonic wave An undulating cyclical displacement of medium particles oscillating within a small distance about an undisturbed mean position.
  • Each wave transmitting pressure energy by propagating an adjacent wave through the medium away from the source or reflecting surface.
  • the wave propagation rate being at the speed of sound, eg. a 40 kHz. vibration traveling at 331.3 m/sec. propagates waves 8.2825 mm. in length.
  • Sonic waves sensed by a sound transducer providing input to a synchronizer circuit which were originally transmitted by that synchronizer. They may be reflected from a surface, or re-radiated by another synchronizer circuit.
  • Sensing transducer A sonic transducer which is sensing sonic waves in a medium and producing an electrical signal, referred to in this disclosure as the sensing transducer signal.
  • the identical sonic transducer may also be referred to as the sensing transducer when it is performing as a single alternating sense/radiate transducer.
  • Radiating transducer A sonic transducer which is radiating sonic waves into a medium, responsive to an electrical signal, referred to in this disclosure as the driver signal.
  • the identical sonic transducer may also be referred to as the sensing transducer when it is performing as a single alternating sense /radiate transducer.
  • Generator A device for producing an oscillating signal. It may include oscillating signals at higher frequencies than the frequency of generator signal 52 and may include more than one tuned circuit, or no tuned circuits.
  • FIG. 1 shows basic synchronizer 100 radiating sonic waves from transducer 92 (optionally single transducer 93) and sensing sonic waves with transducer 91 (optionally single transducer 93).
  • Transducer 93 is optionally used to alternately radiate and sense waves.
  • the synchronizer is controlled by signals from user circuit 90.
  • Detector 20 detects either a reference signal 23 supplied by, or via, user circuit 90, or detects a transducer signal 21 from transducer 91 (optionally 93).
  • Detector control signal 25 from user circuit 90 selects the signal to be detected by means of a two input analog switch.
  • the selected signal is amplified and produces a detected- amplitude signal 24 and a detected-cycle signal 22.
  • the detected-amplitude signal 24 is an analog signal responsive to the amplitude of the signal being detected, and the detected-cycle signal 22 is a digital signal having at least one digital transition responsive to each cycle of the signal being detected.
  • a comparator circuit 30 receives detected-cycle signal 22 and also a generator signal 52 from a generator circuit 50. Comparator 30 produces a signal which is usually digital and preferably a square waveform having transitions responsive to detected-cycle signal 22 and to generator signal 52. The time separation between comparator signal transitions is responsive to the frequency and phase difference between detected-cycle 22, and generator 50, signals.
  • An adjuster circuit 40 receives comparator signal 32 and produces a frequency adjuster signal 42 responsive to the time period between selected transitions in comparator signal 32.
  • Frequency adjuster signal 42 is received by generator 50 to adjust the frequency of generator signal 52.
  • the sensitivity of frequency adjuster signal 42 to comparator signal 32 is controlled by sensitivity control signal 43.
  • Comparator 30, frequency adjuster 40, and generator 50 cooperate to provide generator signal 52 which has good stability and will synchronize to a moving average frequency and phase position of detected-cycle signal 22.
  • a driver circuit 60 receives generator signal 52 and produces driver signal 62 responding to the frequency of generator signal 52.
  • the driver signal is used to drive a radiating transducer 92 (optionally 93) such that it radiates sonic waves.
  • the alternating drive current flowing in the radiating transducer is measured and produces a drive-current signal 64.
  • a circuit may be included for selectively shutting off driver signal 62 to prevent it from driving the radiating transducer, responding to a radiate control signal 65.
  • this circuit includes an analog switch for disconnecting transducer 92 (optionally 93) from driver 60.
  • Driver 60 can amplitude modulate driver signal 62 by including a mixing circuit, or gain controlled amplifier responsive to an amplitude modulation signal 65.
  • Comparator 30 and frequency adjuster 40 cooperate to present a neutral frequency adjuster signal to generator 50 input when no detected-cycle signal is produced by detector 20.
  • the frequency of generator signal 52 will not be urged to change when the detected cycle signal is missing. See figs. 9 and 9a.
  • This flywheel effect sustains the frequency of generator 50 when in the radiating mode using a single transducer 93 and during signal blanking gaps between the radiating and sensing modes, to avoid the damped self- oscillation inherent to most sonic transducers immediately after radiating periods, and on other occasions when the detected-cycle signal is not present.
  • the preferred digital square-shaped waveform of comparator signal 32 has one transition responding to detected cycle signal 22 and a second transition responding to generator signal 52.
  • the period between the first and second transitions is adjusted to be equal, on average, by means of a phase adjustment circuit in comparator 30.
  • Phase-neutral transitions may be inserted in place of missing detected-cycle transitions.
  • Generator signal responsive transitions of comparator signal 32 can be used by user circuit 90 as a high inertia, stable clock for demodulating modulation in the detected cycle responsive transitions.
  • Sensitivity control signal 43 is normally set for low sensitivity during phase demodulation to give generator signal 52 more stability, but it can be set for high sensitivity to achieve fast synchronization.
  • Phase modulation may be introduced into generator signal 52 for modulating radiated sonic waves, by making the phase control circuit in comparator 30 responsive to a phase modulation signal 35.
  • reference signal 23 may be a phase modulated to introduce modulation into the radiated waves.
  • Sensitivity control signal 43 is normally set for high sensitivity during phase modulation so that generator signal 52 follows the modulation. If synchronizer 100 does not include the sensitivity control circuit phase modulation may be introduced in driver circuit 60 by means of a modulated delay circuit (not shown) responding to phase control signal 35.
  • Detector 20 operates over a wider range of input signals if it includes a gain controlled amplifier responsive to a gain control signal.
  • the amplifier is connected to detected amplitude signal 24 to form an automatic-gain-control (AGC) circuit.
  • AGC automatic-gain-control
  • the amplitude range of input signals is responsive to amplitude control signal 27 See figure 8.
  • Reference signal 23 makes synchronizer 100 adaptable to many applications. Providing: means for totally testing synchronizer 100, a standard signal with which to compare transducer signal 21, an encoded phase-modulated driver signal 62, a reference frequency for centering the radiated waves within the receiving range of the sensing transducer and the adjustment range of frequency adjuster 40, a means for scanning through a range of radiated frequencies, and a means for locking the radiating frequency to the admittance characteristic of the radiating transducer to optimize sonic wave radiation.
  • Figure 2 shows synchronizer 100 operating a single sonic transducer 93, alternately radiating and sensing bursts of sonic waves. The waves travel in medium 96 and reflect from surface 95.
  • generator 50 is of the tuned amplifier type.
  • Reference signal 23 is not required because the tuned amplifier resonant frequency is the synchronizer reference frequency. This embodiment is useful for accurate measurement of Doppler modulation in received reflected waves, distance measurement, ultrasound scanning, and totally synchronous communication.
  • the sustaining mode fills a gap following the radiating mode to allow time for damped self-oscillation to dissipate.
  • the "ringing" occurs in most sonic transducers after a radiating period. Synchronization is sustained during the radiating mode, and in the gap, and when no sonic waves are being sensed.
  • Driver 60 includes an analog switch responsive to radiate control signal 65, for switching transducer 93 into the radiating mode. Radiating, detector 20 is isolated from transducer 93, responding to detector control signal 25. With no input signal, detector 20 cannot produce detected-cycle signal 22, therefore, comparator 30 provides a phase-neutral output signal to frequency adjuster 40a. In a preferred embodiment comparator signal 32 inserts sustaining transitions in place of detected-cycle triggered transitions. See figure 9a. Sustaining transitions are derived from generator signal 52, and are phase adjusted to have a neutral effect on the generator frequency. This minimizes the frequency drift rate toward the resonant frequency of the tuned circuit.
  • Sustaining transitions received by frequency adjuster 40a trigger short energy pulses. These pulses are preferably no longer than 10 % of each cycle of the oscillation produced by the tuned circuit in generator 50a. Their energy urges the low-Q tuned circuit to synchronize to the average period between pulses; bucking the tuned circuits' cyclic currents to slow oscillation, and boosting them to speed oscillation, within a limited oscillation frequency range about the tuned circuit resonant frequency.
  • Sensitivity control signal 43 adjusts the energy in the energy pulses and hence the rate at which they can change the frequency of oscillating signal 52. In the initial radiating mode sensitivity is usually held at a fixed low level by user circuit 90 with user sensitivity switch 97 open.
  • a gap is left to allow transducer 93 to "ring" before it can successfully sense waves.
  • Another gap may be left after sensing and before radiating again.
  • the generator signal frequency is sustained, but will drift slowly toward the tuned circuit resonant frequency.
  • the sensitivity is lowered by sensitivity control signal 43 from user circuit 90 to reduce drift.
  • Detector control signal 25 connects sensing transducer signal 21 to be detected. Detected-amplitude 24, and detected-cyde 22, signals are produced. Detected-amplitude signal 24 is fed forward via user a closed switch 97 to provide sensitivity signal 43. Detected-cyde signal 22 produces transitions in comparator signal 30 responsive to the sonic wave cycles sensed by transducer 93. Energy pulses are triggered by the transitions and influence the tuned drcuit to produce generator signal 52 at the average frequency of the sonic waves synchronized to the average phase position of the detected- cyde transitions in comparator signal 32.
  • Synchronizer 100 will cause the radiated and returning waves to travel as efficiently as possible in medium 96 because the sound path is a portion of a generator feedback loop having a loop gain responsive to detected- amplitude 24. Synchronizer 100 automatically finds the optimum transmission frequency. Once sonic waves are established to and from transducer 93, modulation can be induded to measure distance. Doppler modulation caused by the motion of reflecting surface 95 can be measured from comparator signal 35.
  • FIG. 3 shows synchronizer 100 driving radiating sonic transducer 92 and simultaneously sensing sonic waves with transducer 91.
  • the waves travel in medium 96.
  • Generator 50b is of the phase-locked loop (PLL) type.
  • Reference signal 23 is needed because the PLL has a linear frequency response. It is necessary to establish a reference radiating frequency well within the end limits of the generator's adjusting range to allow for modulation.
  • This embodiment is useful for accurate measurement of Doppler modulation in reflected or dirertly received waves, distance measurement, ultrasound scanning, and for communicating with other sonic wave synchronizers.
  • Synchronizer 100 operates in three modes for this application; a reference radiating mode, a simultaneous radiating and receiving mode, and a sustaining mode.
  • control signal 65 switches driver 60 so that drive signal 62 causes transducer 92 to radiate sonic waves at a frequency within the adjusting range of generator 50b
  • Drive-current signal 64 supplies reference signal 23 via dosed user switch 94.
  • Detector control signal 25 connects reference signal 23 to be detected.
  • Detected-amplitude signal 24 is therefore, responsive to the amplitude of drive-current signal 64.
  • Detected-cycle signal 22 is responsive to the drive-current signal cycles.
  • Comparator 30 produces comparator signal 32 as in the figure 1 and 2 descriptions.
  • Frequency adjuster 40b uses comparator signal 32 to operate charge-current pumps to develop a voltage across an integrating filter to provide frequency adjusting signal 42 (also see figure 11) having frequency and phase responsive parameters responsive to time periods in comparator signal 32 intermediate between deterted-cyde responsive transitions and generator signal responsive transitions.
  • Generator 50b indudes a voltage adjustable osdllator influenced by frequency adjusting signal 42.
  • a phase-locked-loop (PLL) drcuit is formed, induding generator 50b, phase comparator 30, and frequency adjuster 40b.
  • the frequency of generator signal 52, and the voltage of frequency adjusting signal 42 are interdependent. This feedback loop strives to adjust osdllating signal 52 to synchronize with the average frequency and period between transitions in comparator signal 32.
  • Detected-amplitude signal 24 provides sensitivity control signal 43 via an external connection. Therefore, the sensitivity and hence the loop gain of the PLL responds to the amplitude of drive-current signal 64, which is responsive to the amplitude of the alternating current flowing in radiating transducer 92. This makes the generator signal frequency strive to reach the frequency at which transducer alternating current is maximized.
  • transducer 92 If transducer 92 is has an admittance characteristic which does not peak within the desired radiating range, a low-Q peaking filter added to driver 60 can establish the reference frequency at which maximum drive current flows.
  • a sustaining comparator signal 32 is produced as in the figure 2 description.
  • An alternative provision for sustaining the generator signal frequency is to make the charge-current pumps operative only when the detected-cyde signal 22 is present.
  • the radiating mode establishes reference sonic waves prior to the simultaneous mode.
  • Detector 20 is switched to detect transducer signal 21 from sensing transducer 91 and driver 60 is switched to cause transducer 92 to radiate.
  • User switch 94 is left open.
  • Transducer signal 21 is detected as in the figure 1 and 2 descriptions.
  • Synchronizer 100 will continually strive to adjust the frequency of the received and radiated waves so that an exact number of sonic waves is in the sound path separating the transducers. It will also strive to receive the waves at their greatest amplitude, as the loop gain of this dosed loop is dependent on sensitivity signal 43 which responds to the amplitude of transducer signal 21.
  • the detector selection switch is initially toggled several times by means of detertor control signal 25 to break and make the loop to prevent the synchronizer from settling at a phase-locked condition away from the optimum frequency.
  • Figure 4 Shows two tuned-amplifier synchronizers 100a and 100b in two- way communication.
  • Synchronizer 100a drives a piezoelectric radiating transducer 92 and senses using a piezoelectric transducer 91.
  • Synchronizer 100b drives a piezoelectric radiating and sensing transducer 93.
  • the natural optimum radiating frequency of transducer 92 is matched to the natural optimum sensing frequency of transducer 93 and the natural optimum radiating frequency of transducer 93 is matched to the natural optimum sensing frequency of transducer 91.
  • Transducer 92 radiates at its optimum radiating frequency synchronized to drive-current signal 64a at the maximum transducer alternating current.
  • Transducer 93 senses sonic waves from transducer 92 and synchronizer 100b locks to the frequency of the sensed waves.
  • transducer 93 radiates at its optimum radiating frequency synchronized to drive-current signal 64b at the maximum transducer alternating current.
  • Transducer 91 senses sonic waves from transducer 93 and synchronizer 100a locks to the frequency of the sensed waves.
  • Synchronizers 100a and 100b cause transducers 91, 92, and 93, to communicate at their most effident. Two-way communication of this kind avoids most interference from refleded sonic waves due to the limited frequency passband of the receiving transducer and the separate radiating and receiving frequendes.
  • Figure 5a relates to the figure 4 embodiment. It shows the low-Q tuned amplifier charaderistic curve 501 for synchronizer 100a, and the admittance vs frequency charaderistic curve 591 of transducer 91, and the admittance vs frequency charaderistic curve 592 of transducer 92.
  • Frequency 502 is the low admittance point of transducer 91 corresponding to its internal parallel resonance condition, where it produces the maximum voltage signal from sensed sonic waves.
  • Frequency 503 is the high admittance point of transducer 92 corresponding to its internal series resonance condition where it produces the maximum radiating capability.
  • Curve 501 is centered between frequendes 502 and 503 and is the resonant frequency of the tuned- amplifier in synchronizer 100a.
  • Figure 5b relates to the figure 4 embodiment. It shows the low-Q tuned amplifier charaderistic curve 504 for synchronizer 100b, and the admittance vs frequency charaderistic curve 593 of transducer 93.
  • Frequency 503 is the low admittance point of transducer 93 corresponding to an internal parallel resonance condition, where it produces the maximum voltage signal from sensed sonic waves.
  • Frequency 502 is the high admittance point of transducer 93 corresponding to an internal series resonance condition, where it produces the maximum radiating capability.
  • Curve 504 is centered between frequendes 502 and 503 and is the resonant frequency of the tuned- amplifier in synchronizer 100b.
  • FIG. 6 Shows two PLL synchronizers 100c and lOOd in two-way communication.
  • Synchronizer 100c drives piezoelectric radiating transducer 92 and senses using piezoelectric transducer 91.
  • Synchronizer lOOd drives a piezoelectric radiating and sensing transducer 93.
  • the natural optimum radiating frequency of transducer 92 is matched to the natural optimum sensing frequency of transducer 93 and the natural optimum radiating frequency of transducer 93 is matched to the natural optimum sensing frequency of transducer 91.
  • Transducer 92 radiates at its optimum radiating frequency synchronized to drive-current signal 64c at the maximum transducer alternating current.
  • Transducer 93 senses sonic waves from transducer 92 and synchronizer lOOd lodes to the frequency of the sensed waves. In reverse communication, transducer 93 radiates at its optimum radiating frequency synchronized to drive-current signal 64d at the maximum transducer alternating current.
  • Transducer 91 senses sonic waves from transducer 93 and synchronizer 100c locks to the frequency of the sensed waves.
  • Figure 7a relates to the figure 6 embodiment. It shows the analog oscillator voltage vs frequency characteristic 701 for synchronizer 100c, and the admittance vs frequency charaderistic curve 791 of transducer 91, and the admittance vs frequency characteristic curve 792 of transducer 92.
  • Frequency 705 is the low admittance point of transducer 91 corresponding to a parallel resonance condition internal to transducer 91 where it produces the maximum voltage signal from sensed sonic waves.
  • Frequency 707 is the high admittance point of transducer 92 corresponding to a series resonance condition internal to transducer 92 where it produces the maximum radiating capability.
  • Frequencies 705 and 707 are equidistant from the non ⁇ linear edges of charaderistic 701.
  • Curve 703 represents the peak alternating current when transducer 92 is radiating and the sensitivity control in the synchronizer responds to the transducer alternating current amplitude.
  • Curve 708 (broken line) represents a response curve relating the absolute operating position of a frequency controlling voltage when the frequency of the voltage-controlled oscillator of synchronizer 100c directly responds to the alternating current in transducer 92. See figure 11. Circuit adjustment is critical to achieve the optimum radiating frequency and maximum current at the absolute operating position.
  • Figure 7b relates to the figure 6 embodiment. It shows the analog osdllator voltage vs frequency characteristic 702 for synchronizer lOOd, and the admittance vs frequency characteristic curve 793 of transducer 93.
  • Frequency 707 is the low admittance point of transducer 93 corresponding to a parallel resonance condition internal to transducer 91 where it produces the maximum voltage signal from sensed sonic waves.
  • Frequency 705 is the high admittance point of transducer 93 corresponding to a series resonance condition where it produces the maximum radiating capability.
  • Frequencies 705 and 707 are equidistant from the non-linear edges of characteristic 702.
  • Curve 704 represents the peak alternating current when transducer 93 is radiating and the sensitivity control in the synchronizer responds to the transducer alternating current amplitude.
  • Curve 709 (in broken line) represents a response curve relating the absolute operating position of a frequency controlling voltage when the frequency of the voltage-controlled osdllator of synchronizer lOOd directly responds to the alternating current in transducer 93. See figure 11. Circuit adjustment is critical to achieve the optimum radiating frequency and maximum current at the absolute operating position.
  • Synchronizers 100c and lOOd cause transducers 91, 92, and 93, to communicate at their most efficient.
  • Two-way communication using limited frequency passband transducers and separate radiating and receiving frequendes avoids most interference from reverberating sonic waves .
  • Figure 8 shows a preferred embodiment of detedor 20.
  • Analog switch 201 responsive to detedor control signal 25 connects either transducer signal 21 or reference signal 23 to amplifier 202.
  • Filter 203 limits the frequency passband sensitivity of amplifier 202 and is usually necessary when the sensing transducer has a broad frequency passband.
  • Amplitude detector 204 receives the amplified signal and produces a rectified voltage level responsive to its amplitude.
  • Amplitude comparator 205 produces a difference signal responsive to the difference between the rectified voltage level and amplitude control signal 27 as a reference voltage.
  • Integrating amplifier 206 removes high frequendes from the difference signal to produce detected-amplitude signal 24 which is fed back to a gain controlling input of amplifier 202.
  • This negative feedback provides a controlled amplitude, amplified signal over a wide range of input signals, whereby the operating range of input signals is determined by amplitude control signal 27.
  • Deteded amplitude signal 24 responds to the amplitude of the signal being deteded.
  • Schmitt trigger 207 receives the amplified signal and produces a digital output when the amplified signal exceeds the Schmitt threshold levels.
  • Crossover detector 208 receives the amplified signal and forms a digital signal having transitions responsive to each zero-crossover point of the amplified signal.
  • Flip flop 209 is set by one transition from the Schmitt trigger per signal cycle, and reset by one transition from the crossover detedor per signal cyde to produce deteded-cyde signal 22 responsive to each cyde of the signal from switch 201.
  • detector 20 An important feature of detector 20 can be useful for power saving. Only amplifier 202, rectifying amplitude detector 204, amplitude comparator 205 and integrating amplifier 206 in synchronizer 100 need to be powered via sensing power supply 210 until sonic waves are sensed. User drcuit 90 will switch on main power supply 211 if detected amplitude signal 24 indicates recognition of sonic waves.
  • Figure 9 shows a preferred embodiment of comparator 30.
  • generator signal 52 is compared with deteded-cycle signal 22. If generator signal 52 is a sine- wave, Schmitt trigger 301 forms a digital signal from it.
  • Digital comparator 302 indudes a look ahead and priority gate and latch to ensure that if deteded cycle signals are present comparator signal 32 will respond to them.
  • Phase control signal 35 can adjust the average relative phase relationship between positive and negative transitions in comparator signal 32.
  • Figure 9a shows typical waveforms and dependency linkages showing the effeds of the priority gate when detected-cycle signal 22 is average, early, late, and missing.
  • Link 901 shows the positive transition of waveform 932 depending from the positive transition of waveform 922 when waveforms 922 and 952 are coinddent.
  • Link 902 shows the positive transition of waveform 932 depending from the positive transition of waveform 922 when it is earlier than waveform 952.
  • Link 903 shows the positive transition of waveform 932 depending from the positive transition of waveform 922 when it is later than the 952 waveform.
  • Comparator waveform 932 shows the negative transition of waveform 932 depending from the negative transition of waveform 952 under all conditions. Comparator waveform 932 is adjusted to be a square waveform, on average. Positive transitions respond to any modulation in the sonic waves, and the negative transitions respond to the stable generator signal 52.
  • FIG 10 shows a preferred frequency adjuster 40a and tuned-amplifier generator 50a.
  • Comparator signal 32 (waveform 932 in fig. 9a) triggers pulse generator 402 to form voltage pulses from its positive transitions having an amplitude responsive to sensitivity control signal 43.
  • Transistor 403 and current control resistor 404 produce current pulses having an energy content responsive to the amplitude and duration of the voltage pulses.
  • Generator 50a indudes tuned drcuit 501, stimulated to osdllate by the energy of the current pulses in frequency adjusting signal 42. Damping resistor 401 reduces the Q of tuned circuit 501.
  • Amplifier 502 amplifies the oscillation.
  • Figure 10a shows the voltage pulses 1001 produced by pulse generator 402 in figure 10.
  • Oscillation waveform 1052 shows generator signal 52.
  • Frequency adjuster signal 42 ceases when voltage pulses 1001 cease, and generator signal 52 reduces amplitude and frequency exponentially to zero.
  • the generator signal frequency synchronizes to the average period between pulses 1001 and hence to the average frequency of comparator signal 32.
  • FIG 11 shows frequency adjuster 40b and generator 50b for a PLL synchronizer.
  • Comparator signal 32 drives bi-directional current pump 405 to charge and disd arge filter 406 and produce controlled voltage frequency adjuster signal 42, induding frequency and phase adjusting parameters.
  • Generator 50b includes a voltage adjustable oscillator made from voltage controlled tuned drcuit 503 responding to frequency adjuster signal 42; and osdllates due to positive feedback amplifier 504.
  • Current pump 405 pumps current at a rate responsive to sensitivity control signal 43.
  • Direct frequency control can be included to control the frequency adjuster signal 42 responsive to a frequency control signal 45 (see figure 7a and 7b).
  • Driver 60 indudes: amplifier 603 receiving generator signal 52 and providing drive signal 62, and an output impedance suitable to cause sonic transducer 93 to radiate sonic waves, frequency peaking filter 604 providing peak transducer current at a preset frequency when transducer 93 is non- peaking, analog switch 605 for selectively connecting driver 60 to transducer 93 responding to radiate control signal 65, and resistor 601 providing drive- current signal 64 via capadtor 602 responsive to the alternating current flowing in radiating transducer 93.
  • a circuit for modulating the amplitude of drive signal 62 responsive to an amplitude modulation signal 63 may also be induded.

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  • Engineering & Computer Science (AREA)
  • Computer Networks & Wireless Communication (AREA)
  • Physics & Mathematics (AREA)
  • General Physics & Mathematics (AREA)
  • Radar, Positioning & Navigation (AREA)
  • Remote Sensing (AREA)
  • Signal Processing (AREA)
  • Investigating Or Analyzing Materials By The Use Of Ultrasonic Waves (AREA)
  • Measurement Of Velocity Or Position Using Acoustic Or Ultrasonic Waves (AREA)

Abstract

L'invention se rapporte à un dispositif adaptable, tous usages, qui relie des transducteurs acoustiques et ultrasoniques à des circuits en vue d'effectuer des mesures de distances et de déplacement à haute résolution, et une communication bidirectionnelle. Un signal (52) de générateur se synchronise à un signal (21) de détection d'un transducteur ou à un signal de référence (23). Un détecteur (20) fournit un signal à cycle détecté (22) et un signal à amplitude détectée (24) à partir du signal en cours de détection. Un comparateur (30) génère (32) à partir du signal à cycle détecté et du signal générateur. Un circuit de maintien assure le fonctionnement du volant moteur lors des intervalles. Un circuit d'attaque (60) commande un transducteur de rayonnement. Les options sont: fonctionnement à transducteur unique ou double, fonctionnement en continu ou par salve d'impulsions, communication par fréquence optimum à l'aide de transducteurs piézo-électriques de faible coût, balayage de fréquence d'ondes sonores, modulation et démodulation de phase et d'amplitude, synchronisation rapide, comparaison du signal détecté au signal de référence, et auto-contrôle.
PCT/US1994/001601 1994-02-14 1994-02-14 Synchroniseur d'ondes sonores WO1995022065A1 (fr)

Priority Applications (4)

Application Number Priority Date Filing Date Title
JP7521177A JPH09509252A (ja) 1994-02-14 1994-02-14 音波同期装置
PCT/US1994/001601 WO1995022065A1 (fr) 1994-02-14 1994-02-14 Synchroniseur d'ondes sonores
EP94917877A EP0745227A4 (fr) 1994-02-14 1994-02-14 Synchroniseur d'ondes sonores
AU69411/94A AU6941194A (en) 1994-02-14 1994-02-14 Sonic wave synchronizer

Applications Claiming Priority (1)

Application Number Priority Date Filing Date Title
PCT/US1994/001601 WO1995022065A1 (fr) 1994-02-14 1994-02-14 Synchroniseur d'ondes sonores

Publications (1)

Publication Number Publication Date
WO1995022065A1 true WO1995022065A1 (fr) 1995-08-17

Family

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Application Number Title Priority Date Filing Date
PCT/US1994/001601 WO1995022065A1 (fr) 1994-02-14 1994-02-14 Synchroniseur d'ondes sonores

Country Status (4)

Country Link
EP (1) EP0745227A4 (fr)
JP (1) JPH09509252A (fr)
AU (1) AU6941194A (fr)
WO (1) WO1995022065A1 (fr)

Cited By (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
EP1075098A1 (fr) * 1999-08-03 2001-02-07 Eta SA Fabriques d'Ebauches Convertisseur électronique d'un signal acoustique en un signal pseudo-numérique et procédé de communication bidirectionnelle par ondes acoustiques
WO2001071953A1 (fr) * 2000-03-23 2001-09-27 Onera (Office National D'etudes Et De Recherches Aerospatiales) Installation a element piezoelectrique pour l'equipement d'une structure et element piezoelectrique pour une telle installation
US6577559B1 (en) 1999-08-04 2003-06-10 Eta Sa Fabriques D'ebauches Electronic converter for converting an acoustic signal into a pseudo-digital signal, timepiece including such a converter and two-directional communication method via acoustic waves
US7669478B2 (en) * 2006-10-13 2010-03-02 Zmi Electronics Ltd. Ultrasonic driving device with multi-frequency scanning

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US4197856A (en) * 1978-04-10 1980-04-15 Northrop Robert B Ultrasonic respiration/convulsion monitoring apparatus and method for its use
US4199246A (en) * 1976-10-04 1980-04-22 Polaroid Corporation Ultrasonic ranging system for a camera
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US5012449A (en) * 1989-06-30 1991-04-30 Ferranti O.R.E. Inc. Sonic flow meter
EP0484565A1 (fr) * 1990-11-05 1992-05-13 Siemens Aktiengesellschaft Commande de mode local intégrée pour commutateurs de proximité à ultrasons

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US4122427A (en) * 1976-06-24 1978-10-24 Herbert Karsh Motion monitor
US4199246A (en) * 1976-10-04 1980-04-22 Polaroid Corporation Ultrasonic ranging system for a camera
US4197856A (en) * 1978-04-10 1980-04-15 Northrop Robert B Ultrasonic respiration/convulsion monitoring apparatus and method for its use
US4914638A (en) * 1984-02-28 1990-04-03 Applied Design Laboratories, Inc. Doppler effect speedometer

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See also references of EP0745227A4 *

Cited By (7)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
EP1075098A1 (fr) * 1999-08-03 2001-02-07 Eta SA Fabriques d'Ebauches Convertisseur électronique d'un signal acoustique en un signal pseudo-numérique et procédé de communication bidirectionnelle par ondes acoustiques
US6577559B1 (en) 1999-08-04 2003-06-10 Eta Sa Fabriques D'ebauches Electronic converter for converting an acoustic signal into a pseudo-digital signal, timepiece including such a converter and two-directional communication method via acoustic waves
SG97904A1 (en) * 1999-08-04 2003-08-20 Ebauchesfabrik Eta Ag Electronic converter for converting an acoustic signal into a pseudodigital signal, timepiece including such a converter and two-directional communications method via acoustic waves
WO2001071953A1 (fr) * 2000-03-23 2001-09-27 Onera (Office National D'etudes Et De Recherches Aerospatiales) Installation a element piezoelectrique pour l'equipement d'une structure et element piezoelectrique pour une telle installation
FR2806823A1 (fr) * 2000-03-23 2001-09-28 Onera (Off Nat Aerospatiale) Installation a element piezoelectrique pour l'equipement d'une structure; element piezoelectrique pour une telle installation
US6960867B2 (en) 2000-03-23 2005-11-01 Onera (Office National D'etudes Et De Recherches Aerospatiales) Installation with piezoelectric element for equipping a structure and piezoelectric element for same
US7669478B2 (en) * 2006-10-13 2010-03-02 Zmi Electronics Ltd. Ultrasonic driving device with multi-frequency scanning

Also Published As

Publication number Publication date
AU6941194A (en) 1995-08-29
EP0745227A4 (fr) 1997-10-15
EP0745227A1 (fr) 1996-12-04
JPH09509252A (ja) 1997-09-16

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