US8699253B2 - Control method for soft switch circuit in switch power source - Google Patents

Control method for soft switch circuit in switch power source Download PDF

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US8699253B2
US8699253B2 US12/676,639 US67663908A US8699253B2 US 8699253 B2 US8699253 B2 US 8699253B2 US 67663908 A US67663908 A US 67663908A US 8699253 B2 US8699253 B2 US 8699253B2
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current
resonant
primary power
switching devices
closed
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US20110278953A1 (en
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Chuntao Zhang
Xiaofei Zhang
Xueli Xiao
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Vertiv Corp
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Liebert Corp
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Assigned to JPMORGAN CHASE BANK, N.A., AS COLLATERAL AGENT reassignment JPMORGAN CHASE BANK, N.A., AS COLLATERAL AGENT SECURITY AGREEMENT Assignors: ALBER CORP., ASCO POWER TECHNOLOGIES, L.P., AVOCENT CORPORATION, AVOCENT FREMONT, LLC, AVOCENT HUNTSVILLE, LLC, AVOCENT REDMOND CORP., ELECTRICAL RELIABILITY SERVICES, INC., EMERSON NETWORK POWER, ENERGY SYSTEMS, NORTH AMERICA, INC., LIEBERT CORPORATION, LIEBERT NORTH AMERICA, INC., NORTHERN TECHNOLOGIES, INC.
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
    • H02M7/538—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a push-pull configuration
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/4811—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode having auxiliary actively switched resonant commutation circuits connected to intermediate DC voltage or between two push-pull branches
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

Definitions

  • the present invention relates to a switch power source, and in particular to a control method for a soft switch circuit in a switch power source.
  • Switch power sources are currently in the trend of evolving towards miniaturization at a high frequency, a high power density, a high efficiency and a low cost. Since semiconductor devices in traditional switch power sources function as hard switches, the sources suffer from a great loss, fail to improve their own efficiencies and thus become less and less competitive for the market due to their bulkiness. In view of limitations by the development in the industry of semiconductor devices, the cost, etc., a soft switch circuit topology has been an option for the majority of switch power source manufacturers to improve product competitiveness.
  • FIG. 1 illustrates a schematic diagram of an operation principle of the soft switch circuit in the form of “inductor connected with switch in series” as follows:
  • Positive and negative direct current input voltage source ⁇ 1 ⁇ 2Ud and primary power switching transistors SW 1 and SW 2 constitute a primary power half bridge inverter circuit, so that a high frequency pulse voltage of ⁇ 1 ⁇ 2Ud is generated at the point B by closing and opening SW 1 and SW 2 constantly, and a desired power frequency output voltage Uo is generated across a filter capacitor C 3 and a primary power filter current I 1 is generated across a filter inductor L 1 by a primary power filter circuit.
  • the primary power switching devices SW 1 and SW 2 belonging to traditional hard switch circuits, which suffer from a great loss.
  • two unidirectional auxiliary switching devices SW 3 and SW 4 and a resonant inductor L 2 are added in the ARCP soft switch circuit, and the primary power switching devices SW 1 and SW 2 respectively are arranged in parallel across resonant capacitors C 1 and C 2 with large capacitances relative to parasitic capacitances of SW 1 and SW 2 .
  • a resonant current I 2 is generated on the resonant inductor L 2 in the same direction as the primary power filter current I 1 by controlling the unidirectional auxiliary switching devices SW 3 and SW 4 to be closed and opened, and closing of the primary power switching devices SW 1 and SW 2 at a zero voltage is achieved by the resonance of the resonant inductor L 2 and the resonant capacitor C 3 .
  • the parallel arrangement of the resonant capacitors C 1 and C 2 with much larger capacitances than parasitic capacitances of the primary power switching devices SW 1 and SW 2 across SW 1 and SW 2 respectively achieves opening of the primary power switching devices at a zero voltage.
  • the ARCP soft switch circuit can achieve both closing and opening of the primary power switching devices SW 1 and SW 2 at a zero voltage to thereby significantly decrease the loss of the primary power switching devices.
  • the additional unidirectional auxiliary switching devices SW 3 and SW 4 no the sudden changes of current will occur due to the presence of the resonant inductor L 2 in series therewith to thereby achieve closing at a zero current, and opening of the auxiliary switching devices SW 3 and SW 4 at a zero current can be achieved by controlling the moments of SW 3 and SW 4 to be closed and opened reasonably and effectively, so that the additional unidirectional auxiliary switching devices SW 3 and SW 4 can operate in a status of being both closed and opened at a zero current with a very small switching loss.
  • FIG. 2A and FIG. 2B illustrate schematic diagrams of switching logics in positive and negative halves of a cycle respectively of this ARCP soft switch circuit.
  • the ARCP soft switch circuit achieve both switching of the primary power switching devices SW 1 and SW 2 at a zero voltage with a reduced loss and switching of the unidirectional auxiliary switching devices SW 3 and SW 4 at a zero current with a very small switching loss that substantially can be negligible to thereby archive a significantly improved overall operation efficiency, a greatly decreased overall loss, a markedly reduced volume and hence an enhanced competitiveness of the whole machine production.
  • the ARCP soft switch circuit is rather satisfactory in terms of the reduced loss of the switching devices and the improved efficiency, this circuit suffers from a significant drawback, i.e., imbalance of power output from the positive and negative direct current input voltage sources and consequent imbalance of positive and negative direct current input voltages, which may result in a series of problems, for example:
  • a resonant current introduced in the ARCP soft switch circuit between the midpoint N of the positive and negative direct current input voltage sources ⁇ 1 ⁇ 2Ud and the output point B of the half bridge circuit may cause inconsistency of output power of the positive and negative direct current input voltage sources ⁇ 1 ⁇ 2Ud to thereby result in an offset of their voltages and further a series of problems. This may be an inevitable and fatal drawback of the ARCP soft switch circuit topology and consequently limit the application scope and reliability thereof.
  • an additional balance circuit has to be provided for the use of the ARCP soft switch circuit, and this balance circuit will scale up along with increasing power of the primary power circuit. If output power of the primary power circuit is tens to hundreds of kilowatts, the disadvantages of the additional balance circuit, such as volume, cost, efficiency, reliability, etc. will become more prominent and may even cancel off the benefit from the use of the ARCP soft switch circuit.
  • a technical issue to be addressed by the invention is how to overcome the foregoing imbalance problem of output power of the positive and negative direct current input voltage sources without any additional balance circuit.
  • the invention proposes a novel control method based upon an ARCP soft switch circuit, wherein under the control of the existing soft switch circuit, a balance current with the same magnitude as and in the opposite direction to the subsequently generated resonant current is generated in the resonant branch in at least a period of time during the resting of the resonant current by further controlling the forward and backward auxiliary switching devices to be closed and opened to thereby achieve an average current of zero in the resonant branch during a switching cycle and thus address the imbalance problem of the positive and negative direct current input voltages.
  • a particular control method is provided as the following: in the positive half of a cycle, i.e., when the primary power current is in the positive direction, the forward auxiliary switching devices is closed after the first primary power switching device is closed, and opened at the moment when the first primary power switching device is opened to generate the balance current with the same magnitude as and in the opposite direction to the resonant current in the resonant branch to thereby achieve an average current of zero in the resonant branch during the positive half of a cycle; and in the negative half of a cycle, i.e., when the primary power current is in the negative direction, the backward auxiliary switching devices is closed after the second primary power switching device is closed, and opened at the moment when the second primary power switching device is opened to generate the balance current with the same magnitude as and in the opposite direction to the resonant current in the resonant branch to thereby achieve an average current of zero in the resonant branch during the negative half of a cycle.
  • a particular control method is provided as the following: in the positive half of a cycle, i.e., when the primary power current is in the positive direction, the forward auxiliary switching devices is closed after the first primary power switching device is closed, and opened in a period of first dead area to generate the balance current with the same magnitude as and in the opposite direction to the resonant current in the resonant branch to thereby achieve an average current of zero in the resonant branch during the positive half of a cycle; and in the negative half of a cycle, i.e., when the primary power current is in the negative direction, the backward auxiliary switching devices is closed after the second primary power switching device is closed, and opened in a period of second dead area to generate the balance current with the same magnitude as and in the opposite direction to the resonant current in the resonant branch to thereby achieve an average current of zero in the resonant branch during the negative half of a cycle.
  • a particular control method is provided as the following: in the positive half of a cycle, i.e., when the primary power current is in the positive direction, the forward auxiliary switching devices is closed after the first primary power switching device is closed, and opened prior to the moment when the first primary power switching device is opened to generate the balance current with the same magnitude as and in the opposite direction to the resonant current in the resonant branch to thereby achieve an average current of zero in the resonant branch during the positive half of a cycle; and in the negative half of a cycle, i.e., when the primary power current is in the negative direction, the backward auxiliary switching devices is closed after the second primary power switching device is closed, and opened prior to the moment when the second primary power switching device is opened to generate the balance current with the same magnitude as and in the opposite direction to the resonant current in the resonant branch to thereby achieve an average current of zero in the resonant branch during the negative half of a cycle.
  • At least one of the primary switching devices and the auxiliary switching devices may be an IGBT, MOSFET, GTO or SCR.
  • the invention can remedy the drawback inherent in the ARCP soft switch circuit without any additional external circuit and can both offer the original function for implementing a soft switch and overcome the imbalance problem of output power of the positive and negative direct current input voltage sources to thereby avoid a series of problems due to imbalance of the positive and negative direct current input voltages. Moreover, no additional balance circuit will be required to thereby greatly simplify the circuit, reduce the overall volume thereof, improve the efficiency thereof and hence achieve a significant technical effect.
  • FIG. 1 illustrates a schematic diagram of an operation principle of an ARCP soft switch circuit in the prior art.
  • FIG. 2A and FIG. 2B illustrate schematic diagrams of switch logics in positive and negative halves of a cycle of the ARCP soft switch circuit in the prior art.
  • FIG. 3 illustrates a schematic diagram of an operation principle of a method in which an external balance circuit is added.
  • FIG. 4 illustrates a schematic diagram of an operation status at a moment SW 4 is closed in the positive half of a cycle according to a first embodiment of the invention.
  • FIG. 5 illustrates a schematic diagram of an operation status at a moment SW 3 is closed in the positive half of a cycle according to the first embodiment of the invention.
  • FIG. 6 illustrates a schematic diagram of an operation status at a moment SW 3 is closed in the negative half of a cycle according to the first embodiment of the invention.
  • FIG. 7 illustrates a schematic diagram of an operation status at a moment SW 4 is closed in the negative half of a cycle according to the first embodiment of the invention.
  • FIG. 8A and FIG. 8B illustrate schematic diagrams of switch logics in the positive and negative halves of a cycle according to the first embodiment of the invention.
  • FIG. 9A and FIG. 9B illustrate schematic diagrams of switch logics in positive and negative halves of a cycle according to a second embodiment of the invention.
  • FIG. 10A and FIG. 10B illustrate schematic diagrams of switch logics in positive and negative halves of a cycle according to a third embodiment of the invention.
  • FIG. 1 illustrating a schematic diagram of the operation principle, essentially a resonant branch is added in this circuit between the output point B of the half bridge circuit and the midpoint N of the positive and negative direct current input voltage sources, and the resonant current is generated in this branch to achieve soft switching of the primary power switching devices SW 1 and SW 2 .
  • the invention proposes the following embodiments.
  • FIG. 4 illustrates a schematic diagram of a circuit operation status corresponding to a moment when the forward auxiliary switching device SW 4 is closed in the positive half of a cycle of a soft switch circuit according to the embodiment of the invention
  • FIG. 5 illustrates a schematic diagram of a circuit operation status corresponding to a moment when the backward auxiliary switching device SW 3 is closed in the positive half of a cycle of the soft switch circuit according to the embodiment of the invention
  • FIG. 6 illustrates a schematic diagram of a circuit operation status corresponding to a moment the backward auxiliary switching device SW 3 is closed in the negative half of a cycle of the soft switch circuit according to the embodiment of the invention
  • FIG. 5 illustrates a schematic diagram of a circuit operation status corresponding to a moment when the forward auxiliary switching device SW 4 is closed in the positive half of a cycle of a soft switch circuit according to the embodiment of the invention
  • FIG. 6 illustrates a schematic diagram of a circuit operation status corresponding to a moment the backward auxiliary switching device SW 3 is closed in the negative
  • the circuit includes a primary power half bridge inverter circuit composed of positive and negative direct current input voltage sources and the primary power switching devices SW 1 and SW 2 , a primary power filter circuit which generates a power frequency output voltage Uo and a primary power filter current I 1 and further includes the unidirectional auxiliary switching devices SW 3 and SW 4 and the auxiliary inductor L 2 for reducing a loss of the primary power switching devices SW 1 and SW 2 , and a PWM signal generator for controlling the primary power switching devices SW 1 and SW 2 and the auxiliary switching devices SW 3 and SW 4 to be closed and opened.
  • the PWM signal generator for controlling the primary power switching devices SW 1 and SW 2 and the forward and backward auxiliary switching devices SW 4 and SW 3 to be closed and opened can alternatively be a PFM signal generator, a PWM-PFM hybrid signal generator, another square wave signal generator or CPU, etc.
  • the invention can further address the imbalance problem of output power of the positive and negative direct current input voltage sources in the following embodiments.
  • a timing control for the switching devices is performed as in the schematic diagrams of switch logics illustrated in FIG. 9A and FIG. 9B . That is, under the control logic of the ARCP soft switch circuit, SW 4 is closed after SW 1 is closed, and opened during a period of first dead area [T 1 ⁇ T 2 ] in the positive half of a cycle to thereby generate the balance current I 4 with the same magnitude as and in the opposite direction to the subsequently generated resonant current I 2 ; and SW 3 is closed after SW 2 is closed, and opened during a period of second dead area [T 3 ⁇ T 4 ] in the negative half of a cycle to thereby generate the balance current I 3 with the same magnitude as and in the opposite direction to the subsequently generated resonant current I 2 .
  • a timing control for the switching devices is performed as in the schematic diagrams of switching logics illustrated in FIG. 10A and FIG. 10B . That is, under the control logic of the ARCD soft switch circuit, SW 4 is closed after SW 1 is closed, and opened prior to the moment T 1 when SW 1 is opened in the positive half of a cycle to thereby generate the balance current I 4 with the same magnitude as and in the opposite direction to the subsequently generated resonant current I 2 ; and SW 3 is closed after SW 2 is closed, and opened prior to the moment T 3 when SW 2 is opened in the negative half of a cycle to thereby generate the balance current I 3 with the same magnitude as and in the opposite direction to the subsequently generated resonant current I 2 .
  • the two unidirectional auxiliary switching devices are defined as forward and backward auxiliary switching devices respectively to distinguish between their uni-directivity of conducting a current in the circuit but not to represent any actual current direction.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Inverter Devices (AREA)
  • Dc-Dc Converters (AREA)
US12/676,639 2007-09-05 2008-09-05 Control method for soft switch circuit in switch power source Expired - Fee Related US8699253B2 (en)

Applications Claiming Priority (4)

Application Number Priority Date Filing Date Title
CN200710147384.X 2007-09-05
CN200710147384 2007-09-05
CN200710147384XA CN101383562B (zh) 2007-09-05 2007-09-05 一种开关电源中软开关电路的控制方法
PCT/CN2008/072281 WO2009033414A2 (fr) 2007-09-05 2008-09-05 Procédé de commande de commutation douce d'un circuit dans une alimentation à découpage

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US8699253B2 true US8699253B2 (en) 2014-04-15

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US10014714B2 (en) 2014-03-05 2018-07-03 Vartiv S.R.L. System and method for uninterruptible power supply intelligent transfer
US11171508B2 (en) 2019-05-06 2021-11-09 Vertiv Corporation System and method for shared hybrid transfer switch

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CN101388612B (zh) * 2007-09-14 2011-08-31 力博特公司 一种开关电源中软开关电路的控制方法
CN102148573B (zh) * 2011-04-19 2013-03-20 苏州工业职业技术学院 一种半桥式软开关直流变换器及其控制方法
SE539852C2 (sv) 2012-12-19 2017-12-19 Comsys Ab Symmetrisk krets
EP2800265A1 (fr) * 2013-05-03 2014-11-05 ALSTOM Technology Ltd Convertisseur
CN103701356B (zh) * 2013-12-31 2016-05-04 东北大学 一种双辅助谐振极型三相软开关逆变器
JP2015181329A (ja) * 2014-03-04 2015-10-15 パナソニックＩｐマネジメント株式会社 電力変換装置
CN108123605B (zh) * 2018-01-31 2020-06-26 华为技术有限公司 电源变换电路的控制方法以及相关电源变换电路
CN112398359B (zh) * 2020-11-09 2022-04-19 国创移动能源创新中心(江苏)有限公司 辅助谐振换流极变换器的控制电路、控制方法
CN112532086B (zh) * 2020-11-25 2022-06-28 青岛鼎信通讯股份有限公司 一种检测chb电压滤波分量零点提高pet效率方法
CN116207989B (zh) * 2023-04-27 2023-09-05 合肥乘翎微电子有限公司 直流-直流转换器及其控制方法

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US10014714B2 (en) 2014-03-05 2018-07-03 Vartiv S.R.L. System and method for uninterruptible power supply intelligent transfer
US11171508B2 (en) 2019-05-06 2021-11-09 Vertiv Corporation System and method for shared hybrid transfer switch

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US20110278953A1 (en) 2011-11-17
CN101383562A (zh) 2009-03-11
CN101383562B (zh) 2011-03-30

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