US3809788A - Computor organ using parallel processing - Google Patents

Computor organ using parallel processing Download PDF

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Publication number
US3809788A
US3809788A US00298365A US29836572A US3809788A US 3809788 A US3809788 A US 3809788A US 00298365 A US00298365 A US 00298365A US 29836572 A US29836572 A US 29836572A US 3809788 A US3809788 A US 3809788A
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harmonic
interval
value
calculated
components
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R Deutsch
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Nippon Gakki Co Ltd
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Nippon Gakki Co Ltd
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Priority to US00298365A priority Critical patent/US3809788A/en
Priority to GB4515973A priority patent/GB1441776A/en
Priority to DE2350143A priority patent/DE2350143C3/de
Priority to AU61308/73A priority patent/AU471179B2/en
Priority to IT30143/73A priority patent/IT995881B/it
Priority to JP48116239A priority patent/JPS5210373B2/ja
Priority to CA183,641A priority patent/CA1004886A/en
Priority to NL7314278.A priority patent/NL166812C/xx
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    • G—PHYSICS
    • G10—MUSICAL INSTRUMENTS; ACOUSTICS
    • G10H—ELECTROPHONIC MUSICAL INSTRUMENTS; INSTRUMENTS IN WHICH THE TONES ARE GENERATED BY ELECTROMECHANICAL MEANS OR ELECTRONIC GENERATORS, OR IN WHICH THE TONES ARE SYNTHESISED FROM A DATA STORE
    • G10H7/00—Instruments in which the tones are synthesised from a data store, e.g. computer organs
    • G10H7/08—Instruments in which the tones are synthesised from a data store, e.g. computer organs by calculating functions or polynomial approximations to evaluate amplitudes at successive sample points of a tone waveform
    • G10H7/10—Instruments in which the tones are synthesised from a data store, e.g. computer organs by calculating functions or polynomial approximations to evaluate amplitudes at successive sample points of a tone waveform using coefficients or parameters stored in a memory, e.g. Fourier coefficients
    • G10H7/105—Instruments in which the tones are synthesised from a data store, e.g. computer organs by calculating functions or polynomial approximations to evaluate amplitudes at successive sample points of a tone waveform using coefficients or parameters stored in a memory, e.g. Fourier coefficients using Fourier coefficients

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  • ABSTRACT bodiment, odd and even harmonics are calculated in separate, parallel channels.
  • waveshape synthesis is accomplished by computing the sample point amplitudes of a complex waveshape at regular time intervals, and converting these amplitudes to musical notes as the computations are carried out.
  • a discrete Fourier algorithm is implemented to calculate the individual harmonic components at each sample point, using a stored set of harmonic coefficients which characterize the resultant waveshape. The computations are carried out at a constant time rate regardless of the note fundamental frequency.
  • An objective of using parallel processing in a computor organ of this type is to reduce the computational rate requirements of the system.
  • the waveshape is synthesized in real time.
  • each amplitude calculation must be completed within a fixed time interval t established by the pitch or frequency f of the highest note on the organ keyboard and the number N of amplitude sample points for the highest frequency note. If exactly N sample point amplitudes are computed for that note, the computational time interval t is given by:
  • the highest eight-foot pitch on a standard organ keyboard is C which has a fundamental frequency f 2.093 kHz.
  • W 16 16 harmonics
  • the waveshape should be evaluated at at least 32 sample points per cycle. This criteria will avoid the phenomenon of frequency aliasing which might occur if the system sample rate is less than the Nyquist frequency f which is twice the frequency of the highest harmonic component. If the note C is evaluated at exactly N 32 sample points, the computational time inverval is:
  • the instrument includes two or more computation channels which concurrently evaluate different subsets of Fourier components. These components are combined to obtain the amplitude values at successive sample points of a musical waveshape. The amplitudes are converted to musical'tones as the computations are carried out in real time.
  • the system computation clock rate is reduced, even though all Fourier components for each amplitude sample point are computed within a constant time interval.
  • low and high order harmonic components, or'odd and even harmonics are calculated concurrently in separate channels.
  • the tonal quality of the synthesized musical sounds is established by a set of harmonic coefficients used in the amplitude calculations.
  • these coefficients are contained in a recirculating shift register which is shifted in unison with the individual Fourier component calculations.-Such a recirculating shift register harmoniccoefficient memory, useful in a parallel processing computor organ, also is disclosed.
  • FIG. 1 is an electrical block diagram of a computor organ employing parallel processing, wherein low order harmonic components are calculated in one channel and high order harmonics are evaluated inanother channel.
  • FIG. 2 is'an electrical block diagram of a computor even harmonic components are calculated respectively in separate parallel channels.
  • FIG. 3 is an electrical block diagram showing the use of recirculating shift registers to supply harmonic coefficient values to the'parallel computation channels of a computor organ like that of FIG. 1 or 2.
  • FIG. 4 is a'simplified electrical logic diagram showing load circuitry useful with the recirculating shift registers of FIG. 3.
  • FIG. 5 is a timing diagram illustrating one mode of operation ofthe system of FIG. 3.
  • the computor organ 10 of FIG. 1 utilizes parallel processing to produce'via a sound system 1 1 a musical note selected by the keyboard switches 12., This is accomplished by. calculating in parallel computation channels 13a, 13b the discrete Fourier components associated with amplitudes at successive sample points of a waveshape characterizing the selected note, The components are algebraically summed in an accumulator 14 which, at the 'end of each computation time interval t, contains the amplitude at the current sample point. This amplitude is providedvia a gate 15, enabled bythe t, signal on a line 16, to a digital-to-analog converter 17 which supplies to the sound system 1 1 a voltage corresponding to the waveshape amplitude just computed. Computation of the amplitude at the next sample point immediately is initiated, so that the analog voltage supplied fromthe converter 17 comprises a musical waveshape generated in real time.
  • the period of the computed waveshape, and hence the fundamental frequency of the generated note, is established by a-frequency number R selected by the key board switches 12.
  • a set of suchfrequency numbers corresponding to the notes of theinstrument is stored in a frequency number memory 19.
  • the waveshape it-' self, and hence the tonal quality of the produced musical note is established by a set of harmonic coefficients C stored in a pair of memories 20a, 20b and used in computing the Fourier components at each sample point.
  • the waveshape amplitude X, (qR) at each sample point is computed in accordance with the following discrete Fourier representation of a sampled periodic complex waveshape
  • equation 7 is implemented by computing the ampl itude value x, (qR) for each sample point during a time interval t
  • the individual harmonic component amplitudes F"" C,, sin (rr/W) nqR for each of the W'harmonic components are calculated separately.
  • the low order harmonic components, for .values n 1,2, W/2 are calculated in the channel 13a and the high order components, for the values n (W/2 I), (W/2 2),...,W are evaluated in' the parallel channel 13b.
  • the harmonic calculations are carried on concurrently. For example, while the amplitude of the fundasummed by theadder 22 and added to the contents of the accumulator 14. This routine is iterated until all W harmonic components have been calculated. The resultant algebraic sum then contained in the accumulator 14 will correspond to the amplitude for the sample point designated by the value qR. As noted earlier, the waveshape amplitude x, (qR) in the accumulator 14 is gated to the digital-to-analog converter 17 at the end of the computation interval t,. The accumulator 14 then is cleared by the signal on the line 16, and computation of the amplitude at the next sample point immediately is initiated.
  • the value qR is incremented and the W harmonic component amplitudes F are calculatedvfor the sample point designated by the new value of qR. Eventually the entire waveshape will be generated, the sound system ll'reproducing the musical note as the amplitude computations are carried out..
  • a note interval adder contains the value qR identifying the sample point at which the waveshape amplitude currently 'is being evaluated. This value qR is incremented at the beginning of each computation interval t, by'adding the selected frequency number R to the previous contents of the adder 25.
  • the selected value R is supplied to the adder 25 via a gate 26 enabled by the t, signal on the line 16.
  • the adder 25 is of modulo N.
  • the values nqR (for n 1,2,...,W/ 2) are obtained in a harmonic interval adder 27 which is cleared before each amplitude computation cycle.
  • the current value qR contained in the mode interval adder 25 is entered into the harmonic interval adder 27 via a line 28 and a gate 29.
  • the value qR is added to the previous contents of the adder 27.
  • the harmonic interval adder 27 will contain the value nqR, where n l,2,...,W/2 for the n'" low order harmonic component currently being evaluated in the channel 13a.
  • the harmonic interval adder 34 also is of modulo N.
  • An address decoder 31a accesses from a sinusoid table 32a the value sin (qr/W) nqR corresponding to the harmonic component and is supplied via the line 21a to the adder 22.
  • the appropriate coefficient C is ac Stepd from the low order harmonic coefficient memory 20a by an address control unit 36 advanced by the clock pulses 2 To evaluate the high order harmonic components,
  • the values (W/2 +n) qR for n 1,2,...W/2 are obtained at successive clock times r
  • the value qR contained in the note interval adder 25 is multiplied by the value W/2 in a multiplier 37.
  • the quotient (W/Z) qR is added to the value nqR present on the line 33 by an adder 38.
  • the sum, present on a line 39, is the value (w/2 q
  • a memory address decoder 31b accesses from a sinusoid table 32b the value sin (qr/W) (W/2 n) qR. That sin value, supplied via a line 34b, is multiplied by the corresponding high order harmonic coefficient C supplied from a memory 20b, in a multiplier 35b.
  • the multiplication product, supplied via the line 21b to the adder 22, represents the amplitude F" of the currently evaluated, high order harmonic component.
  • the odd harmonic components (n l,3,5,%) are calculated in a first channel 51a, while the even harmonic components (n 246,%) are evaluated concurrently in a second channel 50b.
  • the keyboard switches 12, the frequency number 19, the gate 26' and the note interval adder 25 correspond in operation to the like numbered, but unprimed, components shown in FIG. 1. These components provide on a line 28' a signal representing the value qR identifying the sample point at which the waveshape amplitude currently is being evaluated.
  • Separate harmonic interval adders 52a, 52b are associated with the respective channels 50a, 50b.
  • the harmonic interval adder 52a is used to accumulate nqR for odd values of n, while the values nqR for even values of n are obtained in the adder 52b.
  • a times two multiplier 53 provides on a line 54 a signal representingthe value 2qR throughout each computation interval t,,.
  • a clock 41' of frequency f provides calculation clock pulses t on a line 42.
  • a counter 55 of modulo W/2 provides one computation time interval pulse t, on a line 16 for each W/2 pulses t received from the clock 41'.
  • the counter 52 provides pulses at the calculation clock time r on a line 56a, and at the times r through t on the respective lines 56b 56h.
  • the timing pulses r t all are provided via an OR gate 57 to a line 58.
  • the value qR is supplied via a gate 60 to the harmonic interval adder 52a.
  • the value 2qR supplied from the line 54 via a gate 61, is added to the contents of the harmonic interval adder 52a.
  • the contents of the adder 52a will contain nqR for odd values of n.
  • a memory address decoder 31a accesses from a sinusoid table 32a the value sin ("rr/W) nqR corresponding to the argument nqR received from the adder 52a. This sin value is multiplied by the appropriate odd harmonic coefficient C, supplied from a memory 20a utilizing a multiplier 35a.
  • the quotient representing the value F for the corresponding odd value of n, is provided via a line 21a to an adder 22. Accessing of the memory 20a is under control of a memory address control unit 36' advanced by the clock pulses A similar operation occurs in the channel 51b, except that the harmonic interval adder 52b accumulates nqR even values of n. To this end, at each calculation interval t the value 2qR, supplied from the line 54 via a gate 62, is added to the contents of the harmonic interval adder 52b. Amemory address decoder 31b accesses from a sinusoid table 32b the value sin (w/W) nqR corresponding to the argument nqR received from the adder 52b.
  • This sin value is multiplied by the appropriate even harmonic coefficient C from the memory 20b utilizing a multiplier 35b, and the product is supplied via a line 21b to the adder 22'.
  • the adder 22' sums the odd and even harmonic component pair simultaneously evaluated in the parallel channels 51a and 51b, and supplies the sum via a line 23' to an accumulator, digital-to-analog converter and sound system like that shown in FIG. 1.
  • Additional parallel channels may be employed. For example, four parallel channels may be used, calculating one-fourth of the W harmonic components in each channel. In such instance, the clock frequency f would be one-quarter that required of a single channel system. In general, the clock frequency will be inversely proportional to the number of parallel channels. Nor is there any requirement that the same number of harmonic components be evaluated in each channel; Thus a three channel system may be set up wherefve harmonic components are calculated in one channel, five different components in a second channel, and six other components are evaluated in a third channel. Of course, the calculations all must be done within the time period t,, but the order in which they are performed is not important, since it is merely the sum accumulated in the accumulator 14 (FIG. 1) which represents the amplitude at the waveshape sample point qR and which is gated via the digital-toanalog-converter 17 to the sound system 11.
  • the accumulator 14 FIG. 1
  • any subset of harmonics may be evaluated in either chanwaveshape of the generated musical notes. Thus, it is nel.
  • Parallel processing also maybe employed in systems wherein certain of the components are nonharmonic. Further, although only monophonic instruments are shown in FIGS. 1 and 2, it is clearly to be understood that parallel processing in accordance with the present invention also canbe employed in polyphonic computor organs or like instruments.
  • the harmonic coefficient memories 20a, 20b (FIG. 1 advantageously may be implemented using recirculating shift registers. Such an arrangement is shown in FIG. 3'wherein a recirculating shift register a
  • the register 65a is shifted one position to the left (as viewed'in FIG. 3) at each clock pulse t supplied on the line 16. As such shifting occurs, the coefficient value present in the end register position 66a is transferred via a line 67a, certain load circuitry 68a, and a line 69a back to the position 70a at the other endof the shift register 65a.
  • the shift register 65b issimilarly con-' nected. I
  • the coefficient C uponoccurrence of the first clock pulse (r for a particular calculation cycle, the coefficient C, will be available via the line 71a to the harmonic amplitude multiplier 35a, and the coefficient C will be supplied to the multiplier 35b via a line 71b.
  • the recirculating registers 65a, 65b will shift one position to the left, so that the respective coefficients C and C are supplied via the lines 71a, 71bto the multipliers 35a, 35b.
  • This operation continues throughout the computation cycle, until all of the harmonic coefficients stored in the registers 65a, 65b are supplied to the multipliers 35a, 35b.
  • the next computation cycle (for an incremented value of'qR) begins immediately, and again the stored coefficients are supplied from the registers 65a, 65b to the parallel processing organ.
  • coefficient values C establish the value of these coefficients which will determine whether the sounds produced by the computor organ will have the characteristics of e.g., a diapason, a tibia or a bourdon voice.
  • An arrangement for supplying different sets of harmonic coefficients to the shift registers 65a, 65b also is shown in FIG. 3. This arrangement facilitates organ voice selection by the use. of stop tab switches.
  • a first set A of harmonic coefficients are maintained in a storage device 73A, and a different set B of coefficients are stored in a memory 738.
  • the stop tab switch ST is closed, the coefficients from the storage device 73A are transferred via an adder 74, the lines 75a, 75b and the load circuitry 68a, 68b into the shift registers 65a, 65b.
  • the computor organ may e.g., produce a diapason sound.
  • the set B of coefficients maintained in the storage device 73B will be supplied via the adder 74 to the shift registers 65a, 65b. Thereafter, the computer organ will produce a different sound, for example, a tibia, established by the coefficient set B.
  • the arrangement of FIG. 3 also permits'use of combined voices.
  • the coefficient sets A and fB will be summed by the adder 74, and the combined coefficients supplied via the load circuitry 68a, 68b to the shift registers 65a, 65b.
  • the organ will produce a sound representative of the combined selected stops.
  • FIGS. 3 and 4 Illustrative means for transferring coefficients from the storage device 73A or 738 to the recirculating shift registers 65a, 65b is shown in FIGS. 3 and 4, and by the timing diagram of FIG. 5.
  • individual coefficients are transferred during successive computation cycles, so that when a new stop tab is selected, the change in voice occurs gradually over approximately W/2 time intervals This changeover time is sufficiently rapid so as to be unobjectionable to a listener.
  • a counter 76 of modulo (W/2 l receives the calculation clock pulses t from the line 16.
  • the counter 76 provides one .LOAD pulse on a line 77 for each (W/2 l) pulses i received from the clock 41.
  • the LOAD pulses advance a storage access control unit 78 which causes successive harmonic coefficients to be read from the selected storage device 73A or 738.
  • Each LOAD pulse also causes the accessed coefficients to be transferred by the load-circuitry 68a, 68b onto the lines 69a, 69b in place of the coefficinets previously in the shift register end positions 66a, 66b.
  • a new harmonic coefficient is transferred into each shift register 65a and 65b. The process is repeated until all of the coefficients from the selected storage device 73a, 73b have been transferred.
  • the load circuitry 68a, 68b may be implemented using the circuit shown in FIG. 4.
  • a three-input AND gate 81 receives as inputs the signal from the end shift register position 66a, the shift pulses t from the line 16, and the output of an inverter 82 which receives the LOAD pulses from the line 77. g When no LOAD pulse is present on the line 77, the output of the inverter 82 is high. In this instance, the AND gate 81 transfers the coefficient signal from the line 67a onto the line 69a each time a shift pulse t is received. Recirculation is implemented.
  • the output of the inverter 82 will be low, disabling the AND gate 81 and hence inhibiting recirculation of the coefficient received from the. register position 66a.
  • the LOAD signal enables another AND gate 83 which transfers the new harmonic coefficient supplied via the line 75a onto the line 69a.
  • the new coefficient value will be entered into the register end position 70a instead of the value previously in the register position 66a.
  • the LOAD pulses need not be inhibited after all of the new coefficients have been transferred into the registers 65a, 65b. The reason is that on successive cycles, at the time of each LOAD pulse occurrence, the coefficient supplied on the line a will be'identical to that present on the line'67a from the position 66a. As a consequence, the signal returned on the line 69a will be identical to that which would have been recirculated if the LOAD pulse had been'inhibited.
  • the timing diagram of FIG. 5 illustrates the shift register 65a, 65b reloading process.
  • the shift registers initially contain the coefficients C through C of the set A.
  • the stop tab ST is selected at the time designated by the arrow 35.
  • the coefficient C and C of the newly selected set B are transferred by the load circuitry 68a, 68b to the shift registers 65a, 65b.
  • the next coefficients C and C are loaded into the registers. This procedure is iterated until all coefficients of the set B have been loaded.
  • each coefficient C may be represented by a multi-bit binary number.
  • each shift register position would contain a byte equal to the number of bits representing each coefficient. Additional circuits like that of FIG. 4 may be employed for each bit.
  • the storage devices 73A, 738 may contain the sets of coefficients listed in TABLE 1 below and associated with typical pipe organ sounds. Decimal values of the coefficients are listed. In a digital computor organ, these values typically would be. stored in the equivalent binary form. The listedcoefficients indicate the relative amplitude of each Fourier component; the corresponding decibel values also are tabulated.
  • the following Table II lists the frequency, frequency number R, and number of sample points per period for each note in octave six.
  • the note C (the key of C in octave 7) is designated as the note of highest fundamental frequency produced by the computor-organ 10, and hence is assigned the frequency number'R of unity.
  • N 32 sample points are computed for the note C this value of N being satisfactory for accurate synthesis for an organ pipe or most'other musical sounds.
  • a recirculating shift register for storing said harmonic coefficient values, means for shifting said register in unison with said sequential calculations,
  • a multiplier for multiplying said trigonometric function by said accessed harmonic coefficient to obtain the calculated Fourier component value.
  • a musical instrument according to claim 1 further comprising;
  • one or more storage devices each containing a set of harmonic coefficients associated with a particular instrument voice
  • a musical instrument according to claim 2 wherein said means for transferring transfers individual coefficients into said register during successive ones of said certain intervals.
  • said means for transferring includes load circuitry which transfers individual coefficients into said register during successive ones of said certain intervals.
  • said means for transferring includes an adder circuit which combines the coefficients of two or more sets, the combined coefficients being transferred into said recirculating shift register.
  • a musical instrument comprising;
  • control means for causing said processing channels and said accumulator to perform said calculating and combining operations repetitively for successive sample points during successive regular time intervals t and converter means for producing musical sounds from said obtained amplitudes as said calculating and combining are carried out in real time.
  • a frequency number memory storing values of R for selectable notes, a certain value R being accessed from said memory upon actuation ofa corresponding key on said keyboard
  • a note interval adder incremented by-the selected value R at the beginning of each interval t the content of said note interval adder representing the value qR,
  • a harmonic interval adder cleared before each interval t, and incremented by the value qR during successive calculation subintervals within each interval 1,, the contents of said harmonic interval adder representing the values nqR for n l,2,3,... W/2, signals representing said values being provided to said one channel, multiplier for multiplying the value 'qR from said note interval adder by (W/2) to obtain the value (W/2) qR throughout said interval t,, and an adder for adding the value (W/2) qR from said multiplier to the currently available value nqR for n l ,2,...,W from said harmonic interval adder and for providing the sum to said other channel.
  • a keyboard a frequency number memory storing values of R for selectable notes, a certain value R being accessed from said memory upon actuation of a correspond ing key on said keyboard, a note interval adder incremented by the value R at the beginning of each interval t the content of said note interval adder representing the value qR,
  • first and second harmonic interval adders each cleared before each interval t means for loading the value qR from said note interval adder into the first harmonic interval adder and the value 2qR into the second harmonic interval adder during the first calculation subinterval within said interval t and means for adding the value 2qR to the contents of each harmonic interval adder at each subsequent calculation subinterval within said interval t signals representing the contents of said harmonicinterval adders being provided respectively to said parallel processing channels.
  • each harmonic coefficient memory comprises a recirculating shift register shifted in unison with successive Fourier component calculations in that channel.
  • control means comprises:
  • a clock providing timing pulses at harmonic component calculation subintervals t and a counter receiving said clock timing pulses and providing one computation interval pulse t, for each W/P subinterval pulses t received thereby, wherein W is the total number of Fourier components calculated to obtain said amplitude, and P is the number of parallel channels.

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US00298365A 1972-10-17 1972-10-17 Computor organ using parallel processing Expired - Lifetime US3809788A (en)

Priority Applications (8)

Application Number Priority Date Filing Date Title
US00298365A US3809788A (en) 1972-10-17 1972-10-17 Computor organ using parallel processing
GB4515973A GB1441776A (en) 1972-10-17 1973-09-26 Computer organ using parallel processing
DE2350143A DE2350143C3 (de) 1972-10-17 1973-10-05 Digitaler Tonsynthesizer für ein elektronisches Musikinstrument
AU61308/73A AU471179B2 (en) 1972-10-17 1973-10-11 Computer organ using parallel processing
IT30143/73A IT995881B (it) 1972-10-17 1973-10-15 Organo computatore impiegante un sistema di elaborazione a canali paralleli
JP48116239A JPS5210373B2 (de) 1972-10-17 1973-10-16
CA183,641A CA1004886A (en) 1972-10-17 1973-10-17 Computer organ using parallel processing
NL7314278.A NL166812C (nl) 1972-10-17 1973-10-17 Elektronisch orgel.

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JP (1) JPS5210373B2 (de)
AU (1) AU471179B2 (de)
CA (1) CA1004886A (de)
DE (1) DE2350143C3 (de)
GB (1) GB1441776A (de)
IT (1) IT995881B (de)
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US3894463A (en) * 1973-11-26 1975-07-15 Canadian Patents Dev Digital tone generator
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US3908504A (en) * 1974-04-19 1975-09-30 Nippon Musical Instruments Mfg Harmonic modulation and loudness scaling in a computer organ
US3910150A (en) * 1974-01-11 1975-10-07 Nippon Musical Instruments Mfg Implementation of octave repeat in a computor organ
US3913442A (en) * 1974-05-16 1975-10-21 Nippon Musical Instruments Mfg Voicing for a computor organ
US3915047A (en) * 1974-01-02 1975-10-28 Ibm Apparatus for attaching a musical instrument to a computer
DE2524062A1 (de) * 1974-05-31 1975-12-11 Nippon Musical Instruments Mfg Elektronisches musikinstrument mit vibratoerzeugung
DE2523881A1 (de) * 1974-05-31 1975-12-11 Nippon Musical Instruments Mfg Elektronisches musikinstrument mit rauschueberlagerungseffekt
US3926088A (en) * 1974-01-02 1975-12-16 Ibm Apparatus for processing music as data
US3929053A (en) * 1974-04-29 1975-12-30 Nippon Musical Instruments Mfg Production of glide and portamento in an electronic musical instrument
US3951030A (en) * 1974-09-26 1976-04-20 Nippon Gakki Seizo Kabushiki Kaisha Implementation of delayed vibrato in a computor organ
US3952623A (en) * 1974-11-12 1976-04-27 Nippon Gakki Seizo Kabushiki Kaisha Digital timing system for an electronic musical instrument
US3956960A (en) * 1974-07-25 1976-05-18 Nippon Gakki Seizo Kabushiki Kaisha Formant filtering in a computor organ
US3972259A (en) * 1974-09-26 1976-08-03 Nippon Gakki Seizo Kabushiki Kaisha Production of pulse width modulation tonal effects in a computor organ
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US3994195A (en) * 1974-11-15 1976-11-30 Nippon Gakki Seizo Kabushiki Kaisha Electronic musical instrument
FR2321161A1 (fr) * 1975-08-11 1977-03-11 Deutsch Res Lab Synthetiseur de sons polyphonique
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US4119005A (en) * 1973-03-10 1978-10-10 Nippon Gakki Seizo Kabushiki Kaisha System for generating tone source waveshapes
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US4135422A (en) * 1976-02-12 1979-01-23 Nippon Gakki Seizo Kabushiki Kaisha Electronic musical instrument
US4150600A (en) * 1977-05-10 1979-04-24 Nippon Gakki Seizo Kabushiki Kaisha Computer organ with extended harmonics
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US4202234A (en) * 1976-04-28 1980-05-13 National Research Development Corporation Digital generator for musical notes
US4205577A (en) * 1977-06-06 1980-06-03 Kawai Musical Instrument Mfg. Co. Ltd. Implementation of multiple voices in an electronic musical instrument
US4249448A (en) * 1979-04-09 1981-02-10 Kawai Musical Instrument Mfg. Co. Ltd. Even-odd symmetric computation in a polyphonic tone synthesizer
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US4393742A (en) * 1980-09-08 1983-07-19 Nippon Gakki Seizo Kabushiki Kaisha Electronic musical instruments of the type synthesizing a plurality of partial tone signals
US4437377A (en) 1981-04-30 1984-03-20 Casio Computer Co., Ltd. Digital electronic musical instrument
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USRE31648E (en) * 1973-03-10 1984-08-21 Nippon Gakki Seizo Kabushiki Kaisha System for generating tone source waveshapes
USRE31653E (en) * 1978-04-24 1984-08-28 Nippon Gakki Seizo Kabushiki Kaisha Electronic musical instrument of the harmonic synthesis type
EP0823699A1 (de) * 1996-08-05 1998-02-11 Yamaha Corporation Software-Tonerzeuger
US20080229917A1 (en) * 2007-03-22 2008-09-25 Qualcomm Incorporated Musical instrument digital interface hardware instructions
US20080229919A1 (en) * 2007-03-22 2008-09-25 Qualcomm Incorporated Audio processing hardware elements

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USRE31648E (en) * 1973-03-10 1984-08-21 Nippon Gakki Seizo Kabushiki Kaisha System for generating tone source waveshapes
US4119005A (en) * 1973-03-10 1978-10-10 Nippon Gakki Seizo Kabushiki Kaisha System for generating tone source waveshapes
US3888153A (en) * 1973-06-28 1975-06-10 Nippon Gakki Seiko Kk Anharmonic overtone generation in a computor organ
US3894463A (en) * 1973-11-26 1975-07-15 Canadian Patents Dev Digital tone generator
US3926088A (en) * 1974-01-02 1975-12-16 Ibm Apparatus for processing music as data
US3915047A (en) * 1974-01-02 1975-10-28 Ibm Apparatus for attaching a musical instrument to a computer
US3910150A (en) * 1974-01-11 1975-10-07 Nippon Musical Instruments Mfg Implementation of octave repeat in a computor organ
US3884108A (en) * 1974-01-11 1975-05-20 Nippon Musical Instruments Mfg Production of ensemble in a computor organ
US3908504A (en) * 1974-04-19 1975-09-30 Nippon Musical Instruments Mfg Harmonic modulation and loudness scaling in a computer organ
US3978755A (en) * 1974-04-23 1976-09-07 Allen Organ Company Frequency separator for digital musical instrument chorus effect
US3929053A (en) * 1974-04-29 1975-12-30 Nippon Musical Instruments Mfg Production of glide and portamento in an electronic musical instrument
US3913442A (en) * 1974-05-16 1975-10-21 Nippon Musical Instruments Mfg Voicing for a computor organ
DE2523881A1 (de) * 1974-05-31 1975-12-11 Nippon Musical Instruments Mfg Elektronisches musikinstrument mit rauschueberlagerungseffekt
DE2524062A1 (de) * 1974-05-31 1975-12-11 Nippon Musical Instruments Mfg Elektronisches musikinstrument mit vibratoerzeugung
US3956960A (en) * 1974-07-25 1976-05-18 Nippon Gakki Seizo Kabushiki Kaisha Formant filtering in a computor organ
US3951030A (en) * 1974-09-26 1976-04-20 Nippon Gakki Seizo Kabushiki Kaisha Implementation of delayed vibrato in a computor organ
US3972259A (en) * 1974-09-26 1976-08-03 Nippon Gakki Seizo Kabushiki Kaisha Production of pulse width modulation tonal effects in a computor organ
US3952623A (en) * 1974-11-12 1976-04-27 Nippon Gakki Seizo Kabushiki Kaisha Digital timing system for an electronic musical instrument
US4128032A (en) * 1974-11-14 1978-12-05 Matsushita Electric Industrial Co., Ltd. Electronic music instrument
US3992970A (en) * 1974-11-15 1976-11-23 Nippon Gakki Seizo Kabushiki Kaisha Electronic musical instrument
US3992971A (en) * 1974-11-15 1976-11-23 Nippon Gakki Seizo Kabushiki Kaisha Electronic musical instrument
US3994195A (en) * 1974-11-15 1976-11-30 Nippon Gakki Seizo Kabushiki Kaisha Electronic musical instrument
US4048480A (en) * 1975-04-30 1977-09-13 Minot Pierre J M Generators of anharmonic binary sequences
US4108036A (en) * 1975-07-31 1978-08-22 Slaymaker Frank H Method of and apparatus for electronically generating musical tones and the like
US4085644A (en) * 1975-08-11 1978-04-25 Deutsch Research Laboratories, Ltd. Polyphonic tone synthesizer
FR2321161A1 (fr) * 1975-08-11 1977-03-11 Deutsch Res Lab Synthetiseur de sons polyphonique
US4135422A (en) * 1976-02-12 1979-01-23 Nippon Gakki Seizo Kabushiki Kaisha Electronic musical instrument
US4202234A (en) * 1976-04-28 1980-05-13 National Research Development Corporation Digital generator for musical notes
US4177706A (en) * 1976-09-08 1979-12-11 Greenberger Alan J Digital real time music synthesizer
US4150600A (en) * 1977-05-10 1979-04-24 Nippon Gakki Seizo Kabushiki Kaisha Computer organ with extended harmonics
US4178825A (en) * 1977-06-06 1979-12-18 Kawai Musical Instrument Mfg. Co. Ltd. Musical tone synthesizer for generating a marimba effect
US4205577A (en) * 1977-06-06 1980-06-03 Kawai Musical Instrument Mfg. Co. Ltd. Implementation of multiple voices in an electronic musical instrument
USRE31653E (en) * 1978-04-24 1984-08-28 Nippon Gakki Seizo Kabushiki Kaisha Electronic musical instrument of the harmonic synthesis type
US4249448A (en) * 1979-04-09 1981-02-10 Kawai Musical Instrument Mfg. Co. Ltd. Even-odd symmetric computation in a polyphonic tone synthesizer
US4393742A (en) * 1980-09-08 1983-07-19 Nippon Gakki Seizo Kabushiki Kaisha Electronic musical instruments of the type synthesizing a plurality of partial tone signals
US4446770A (en) * 1980-09-25 1984-05-08 Kimball International, Inc. Digital tone generation system utilizing fixed duration time functions
US4351219A (en) * 1980-09-25 1982-09-28 Kimball International, Inc. Digital tone generation system utilizing fixed duration time functions
US4437377A (en) 1981-04-30 1984-03-20 Casio Computer Co., Ltd. Digital electronic musical instrument
EP0823699A1 (de) * 1996-08-05 1998-02-11 Yamaha Corporation Software-Tonerzeuger
US5955691A (en) * 1996-08-05 1999-09-21 Yamaha Corporation Software sound source
US20080229917A1 (en) * 2007-03-22 2008-09-25 Qualcomm Incorporated Musical instrument digital interface hardware instructions
US20080229919A1 (en) * 2007-03-22 2008-09-25 Qualcomm Incorporated Audio processing hardware elements
US7678986B2 (en) * 2007-03-22 2010-03-16 Qualcomm Incorporated Musical instrument digital interface hardware instructions

Also Published As

Publication number Publication date
CA1004886A (en) 1977-02-08
JPS4970618A (de) 1974-07-09
NL166812B (nl) 1981-04-15
NL7314278A (de) 1974-04-19
AU6130873A (en) 1975-04-17
AU471179B2 (en) 1976-04-08
DE2350143B2 (de) 1977-06-30
IT995881B (it) 1975-11-20
DE2350143C3 (de) 1982-11-18
NL166812C (nl) 1981-09-15
JPS5210373B2 (de) 1977-03-23
GB1441776A (en) 1976-07-07
DE2350143A1 (de) 1974-05-02

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