US20220141053A1 - Circular pilot sequences for joint channel and phase noise estimation - Google Patents

Circular pilot sequences for joint channel and phase noise estimation Download PDF

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US20220141053A1
US20220141053A1 US17/433,471 US202017433471A US2022141053A1 US 20220141053 A1 US20220141053 A1 US 20220141053A1 US 202017433471 A US202017433471 A US 202017433471A US 2022141053 A1 US2022141053 A1 US 2022141053A1
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max
reference signals
radio signal
subcarriers
channel estimation
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US12095592B2 (en
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Jean-Christophe SIBEL
Cristina Ciochina
Julien Guillet
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Mitsubishi Electric Corp
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Mitsubishi Electric Corp
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    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L25/00—Baseband systems
    • H04L25/02—Details ; arrangements for supplying electrical power along data transmission lines
    • H04L25/0202—Channel estimation
    • H04L25/022—Channel estimation of frequency response
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L25/00—Baseband systems
    • H04L25/02—Details ; arrangements for supplying electrical power along data transmission lines
    • H04L25/0202—Channel estimation
    • H04L25/0224—Channel estimation using sounding signals
    • H04L25/0226—Channel estimation using sounding signals sounding signals per se
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L25/00—Baseband systems
    • H04L25/02—Details ; arrangements for supplying electrical power along data transmission lines
    • H04L25/0202—Channel estimation
    • H04L25/0224—Channel estimation using sounding signals
    • H04L25/0228—Channel estimation using sounding signals with direct estimation from sounding signals
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L25/00—Baseband systems
    • H04L25/02—Details ; arrangements for supplying electrical power along data transmission lines
    • H04L25/0202—Channel estimation
    • H04L25/024—Channel estimation channel estimation algorithms
    • H04L25/0256—Channel estimation using minimum mean square error criteria
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L25/00—Baseband systems
    • H04L25/02—Details ; arrangements for supplying electrical power along data transmission lines
    • H04L25/0202—Channel estimation
    • H04L25/024—Channel estimation channel estimation algorithms
    • H04L25/0258—Channel estimation using zero-forcing criteria
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L25/00—Baseband systems
    • H04L25/02—Details ; arrangements for supplying electrical power along data transmission lines
    • H04L25/03—Shaping networks in transmitter or receiver, e.g. adaptive shaping networks
    • H04L25/03006—Arrangements for removing intersymbol interference
    • H04L25/03821—Inter-carrier interference cancellation [ICI]
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/26—Systems using multi-frequency codes
    • H04L27/2601—Multicarrier modulation systems
    • H04L27/2602—Signal structure
    • H04L27/261—Details of reference signals
    • H04L27/2613—Structure of the reference signals
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L5/00—Arrangements affording multiple use of the transmission path
    • H04L5/003—Arrangements for allocating sub-channels of the transmission path
    • H04L5/0048—Allocation of pilot signals, i.e. of signals known to the receiver

Definitions

  • the present invention generally relates to the domain of telecommunication system, and more specifically to wireless communication for example wireless OFDM-based communication.
  • the present invention more specifically relates to processing the radio signal received according to the distortion and noise induced on the radio signal by the radio channel.
  • the receivers determine a channel estimation based on the reference signals inserted in the signal by the transmitter. Based on the knowledge of the reference signal (RS), the receiver is able to determine a channel estimation matrix, generally noted H. Each coefficient of this matrix corresponds to an attenuation of the signal between one of the antenna of the transmitter and one of the antenna of the receiver. Based on this matrix the terminal estimates the phase noise of the radio channel. Such a matrix enables to process the radio signal received to reduce the effect of the radio channel on the radio signal.
  • the receiver also implements phase tracking algorithms to deduce the phase noise experienced by the radio signal. Generally, these algorithms assume that the phase noise and the channel (approximated by the channel estimated matrix) are not strongly coupled, which gives good results when the phase noise is small and the channel quasi-static.
  • millimeter-Wave systems which operate in millimeter-Wave bands, for which the new radio standard or 5G currently at normalization aims at, are subject to strong and/or fast phase variations due to different causes such as carrier frequency offset, Doppler effects and especially phase noise.
  • phase variation break the orthogonality property between the subcarriers used for the communication, leading to subcarrier interferences and thus performance loss.
  • subcarrier interferences also called inter-carrier interferences (ICI)
  • ICI inter-carrier interferences
  • the present invention aims at improving the situation.
  • the invention relates to a method for transmitting at least K reference signals in a radio signal to be transmitted over a wireless communication system, said radio signal being intended to be emitted by an emitter comprising at least a transmit antenna configured for emitting on a number M of subcarriers S 1 , . . . , S M amongst which at least a number K of different subcarriers S q+1 , S q+2 , . . . , S q+K are contiguous, the respective frequencies of the contiguous subcarriers S q+1 , S q+2 , . . . , S q+K being ordered, said radio signal being provided by:
  • the reference signals are set according to a specific reference signal pattern.
  • the reference signals are inserted as a block, that is, the reference signals are inserted on contiguous subcarriers of the carrier.
  • the values taken by these references signals meet a specific condition, which is that if K is odd, the values of the reference signals P 1 , . . . , P (K ⁇ 1)/2 are respectively equal to the values of the reference signals P (K+3)/2 , . . . , P K , if K is even, the values of the reference signals P 1 , . . . , P K/2 are respectively equal to the values of the reference signals P K/2+1 , . . . , P K .
  • phase noise and channel estimation This enables to reduce the complexity of the computation of the phase noise and channel estimation at the receiver side, especially when the channel and phase noise are strongly affected by each other, that is, for example when the radio signal suffers from strong phase noise.
  • the attenuation of the radio signal, represented by the channel can be affected if the phase noise is not taken into account in its estimation (since symbols emitted through other subcarriers may add power to the considered subcarrier, thus obstructing a correct determination of the attenuation of radio signal relatively to this considered subcarrier). Therefore, the invention reduces the effects related to strongly coupled phase noise and channel.
  • the invention implements a block of cyclic structured reference signals.
  • This structure enables to receive, at the receiver side, symbols expressed as circular convolution of the phase noise and the reference signals.
  • the specific reference signal pattern due to the block configuration of the reference signals and especially to the size of this block (compared to the spectral occupancy of the phase noise ⁇ PN as it will be described in the followings), enables to receive a block of K 0 (with
  • the invention enables to approximate the received contiguous symbols (Y n min , . . . , Y n max ) as a circular convolution of the phase noise ( ⁇ k min , . . . , ⁇ k max ) and the sequence of reference signals (P 1 , . . . , P K 0 ).
  • the components ⁇ i of the phase noise are considered as null or negligible under k min and above k max , k min to k max corresponds to the spectral occupancy of the phase noise.
  • (Y n min , . . . , Y n max ) may be approximated by:
  • [Y n min , . . . , Y n max ] H[ ⁇ k min , . . . , ⁇ k max ] [P 1 , . . . , P K 0 ]+[Z n min , . . . , Z n max ] with (Z n min , . . . , Z n max ) representing additive white Gaussian noise (AWGN), being the circular convolution operator and H the channel (the channel being assumed constant over the block).
  • AWGN additive white Gaussian noise
  • F K 0 - 1 ⁇ ⁇ ( Y n min , ... ⁇ , Y n max ) ⁇ H .
  • the invention enables to efficiently estimate the channel and of the phase noise even in the case of important phase noise, due to the combination of the fact that the radio signal emitted is at the receiver side known at least for a range of frequency and to the fact that the sequence of reference signals transmitted is repeated.
  • the invention encompasses all symbols that are known by the receiver regarding their values and their positions (in time and in frequency), and on the basis of which the receiver can estimate the impact of the radio channel between the transmitter and the receiver. For example, based on the received version of the reference signals (e.g. corrupted by the radio channel that is corrupted by channel and/or noise and/or phase noise, etc.), the receiver can estimate the channel and/or improve the channel estimation quality.
  • the radio channel encompasses here all effects including propagation and hardware impact such as nonlinearities, attenuations, phase noise, Doppler, carrier frequency offset, etc.
  • the wireless communication system may be a wireless communication system using OFDM (Orthogonal frequency-division multiplexing) like for LTE.
  • OFDM Orthogonal frequency-division multiplexing
  • the symbols transmitted in the other subcarriers S 1 , . . . , S q , S q+K+1 , . . . , S M may be of any type, that is, other reference signals and/or symbols containing user data and/or symbols containing control data.
  • contiguous subcarriers it is here understood that no other subcarrier may be used to transmit symbols between two contiguous subcarriers. Contiguous symbols are symbols transmitted on contiguous subcarriers.
  • the reference signals in the radio signal By inserting the reference signals in the radio signal it is understood setting the values (values which are known by the receiver) in the frequency domain of the symbols to be transmitted through the subcarriers S q+1 , S q+2 , . . . , S q+K as it is usually done to insert the reference signals in the radio signal.
  • the invention is described according to a frequency domain insertion of the reference signals.
  • the K reference signals are inserted to be transmitted together on the K contiguous subcarriers. That is, when the reference signals are inserted in the frequency domain, the symbols which values have been set according to the invention (that is, the symbols transmitted through the subcarriers S q+1 , S q+2 , . . . , S q+K ) are processed together. For example, an IDFT is applied simultaneously to the M subcarriers S 1 , . . . , S M , and thus simultaneously to the K reference signal P 1 , . . . P K transmitted by the K contiguous subcarriers S q+1 , S q+2 , . . . , S q+K .
  • the P 1 , . . . , P K are inserted to be transmitted by the K contiguous subcarriers S q+1 , S q+2 , . . . , S q+K in the same symbol of the transmission scheme, for example, in the same OFDM symbol.
  • q is an integer greater than or equal to zero and smaller than or equal to M-K.
  • the values of P 1 , . . . , P K 0 are respectively a sequence Q 1 , . . . , Q K 0 such that
  • n L 1+mod(n ⁇ 1, L)
  • mod(n ⁇ 1, L) [n ⁇ 1] mod L.
  • the sequence Q 1 , . . . , Q K 0 and therefore P 1 , . . . , P K 0 satisfy an autocorrelation condition.
  • Using such sequences enables to reduce the effects related to strongly coupled phase noise and channel. Indeed, it enables to isolate each frequency component of the phase noise with an advantageous signal-to-noise ratio, for example by computing Y i .
  • the autocorrelation condition of sequence (P 1 , . . . , P K 0 ) enables to apply on Y n min , . . . , Y n max Hadamard products of cyclic permuted sequences (P 1 , . . . , P K 0 ) (as described below), enabling to reduce the complexity of the phase noise and channel estimation.
  • the sequence Q 1 , . . . , Q K 0 may be issued from a CAZAC sequence or advantageously a Zadoff-Chu sequence.
  • At least K+K′ reference signals are transmitted on the M subcarriers S 1 , . . . , S M amongst which at least a number K′ of different subcarriers S q′+1 , S q′+2 , . . . , S q′+K′ are contiguous, the respective frequencies of the contiguous subcarriers S q′+1 , S q′+2 , . . . , S q′+K′ being ordered and q′ strictly superior than q+K, said radio signal being further provided by:
  • groups and blocks of reference signals are synonymous and refer to contiguous reference signals as described by the invention.
  • More than two groups of reference signals may be inserted according to the invention. Therefore, L groups of respectively K 1 , . . . , K L reference signals may be inserted in the radio signal according to the invention, these groups being respectively inserted as blocks on the subcarriers q i +1, . . . , q i +K i , with i from 1 to L and with q 1+1 +1 strictly superior than q i +K i .
  • the groups may be spaced by one or more subcarriers, enabling to transmit other symbols than reference signals between two groups of reference signals and therefore being able to decode these symbols even though they suffered from important channel and phase noise effects.
  • the L groups may be of the same size and with the same sequence of reference signals, therefore, reducing the memory needed to store the reference signal pattern.
  • the transmitter may choose optimized value of the reference signal pattern parameters (q i , ⁇ i , K i , Q i 1 , . . . , Q i K 0 i ) with i from 1 to L and ⁇ 0 , with
  • the transmitter may set a
  • the number of reference signals in each block may be set between a maximum K max and a minimum K min , that is, K min ⁇ K i ⁇ K max .
  • K min may be set according to the spectral occupancy of the phase noise ⁇ PN, that is, such as K min . ⁇ f is greater or equal to 2. ⁇ PN, with ⁇ f being the subcarrier spacing configuration of at least the subcarriers transmitting the reference signals of the L groups of reference signals. This enables to ensure that the circular convolution of the phase noise with the reference signals takes into account all the components of the phase noise that are not negligible.
  • K max may be set such as the channel is constant or can be assimilated as such on scale of K max . ⁇ f. Therefore, the results are better if the channel is constant at least on a scale of 2. ⁇ PN. This enables to have a better approximation with the circular convolution of the symbol received.
  • a second aspect of the invention concerns a method for processing at a receiver a radio signal transmitted over a wireless communication system and received from an emitter comprising at least a transmit antenna configured for emitting on a number M of different subcarriers S 1 , . . . , S M amongst which at least a number K of different subcarriers S q+1 , S q+2 , . . . , S q+K are contiguous, the respective frequencies of the contiguous subcarriers S q+1 , S q+2 , . . . , S q+K being ordered, said radio signal including K reference signals, said radio signal being provided according to the method for transmitting the reference signals as described previously, the method comprising:
  • the channel estimation is function of the phase noise estimation.
  • phase noise estimation and the channel estimation are both determined based on a same group of parameters ( ⁇ 1 , . . . , ⁇ M ). That is, the channel estimation is computed based on the M 0 -th parameter ⁇ M 0 (with
  • determining a channel estimation, said channel estimation being dependent on a phase noise estimation is equivalent to determining a channel estimation and/or a phase noise estimation, said channel estimation and said phase noise estimation being determined based on a same parameter.
  • This parameter ( ⁇ M 0 ) used according to the invention to determine the channel estimation and/or the channel estimation can be obtained either by a linear estimation based on F K 0 ⁇ 1 ⁇ (P 1 , . . . , P K 0 ) ⁇ and F K 0 ⁇ 1 ⁇ (Y n min , . . . , Y n max ) ⁇ or by
  • the channel estimation and/or the phase noise estimation are computed considering the circular convolution of the phase noise with the reference signals as an approximation of received symbols on specific subcarriers as previously described.
  • phase noise estimation by considering the channel and compute the channel estimation by considering the phase noise, therefore, when the radio signal suffers strong phase noise the channel estimation is not erroneously made without taking into account the phase noise.
  • computing channel estimation by estimating the attenuation of the signal on a subcarrier per subcarrier basis only.
  • the determination of the channel estimation comprises:
  • the receiver obtains the symbols in the frequency domain of the received radio signal corresponding to the radio signal emitted according to the method for transmitting the reference signals as described previously. That is, for example, these symbols are obtained from applying a DFT (discrete Fourier transform) on the received radio signal.
  • the received symbols which contain combination of the reference signals with only negligible power related to emitted symbols that are not RS from the pattern specified by the invention are selected. These selected symbols are for example Y n min , . . . , Y n max , that is, the symbols received on the subcarrier S n min , . . . , S n max , with n min and n max as defined above.
  • the channel estimation can be computed through a linear estimation based on F K 0 ⁇ 1 ⁇ (P 1 , . . . , P K 0 ) ⁇ and F K 0 ⁇ 1 ⁇ (Y n min , . . . , Y n max ) ⁇ .
  • (Y n min , . . . , Y n max ) H.
  • the radio channel also known as equivalent channel in the literature, encompasses here all phenomena impacting the radio signal, from the output of OFDM modulation at the emitter to the input of the OFDM demodulation at the receiver, including propagation and hardware impact such as nonlinearities, attenuations, phase noise, Doppler, carrier frequency offset, etc.
  • the channel, for which is done a channel estimation, is the radio channel for which the phase noise is not included.
  • the radio channel encompasses the attenuation represented by the channel and the effects of the phase noise.
  • the determination of the channel estimation further comprises:
  • ⁇ is computed based on
  • ( ⁇ 1 , . . . , ⁇ K 0 ) is the result of the linear estimation based on F K 0 ⁇ 1 ⁇ (P 1 , . . . , P K 0 ) ⁇ and F K 0 ⁇ 1 ⁇ (Y n min , . . . , Y n max ) ⁇ and F K 0 ,j ⁇ u ⁇ is the j-th terme of DFT of order K 0 of the vector u of size K 0 and with
  • ⁇ M 0 F K 0, M 0 ⁇ 1 , . . . , ⁇ K 0 ) ⁇ .
  • the invention further comprises:
  • ( ⁇ 1 , . . . , ⁇ K 0 ) is the result of the linear estimation based on F K 0 ⁇ 1 ⁇ (P 1 , . . . , P K 0 ) ⁇ and F K 0 ⁇ 1 ⁇ (Y n min , . . . , Y n max ) ⁇ and F K 0 ,j ⁇ u ⁇ is the j-th terme of DFT of order K 0 of the vector u of size K 0 .
  • the channel estimation and the phase noise estimation are both based on the same group of parameters ( ⁇ 1 , . . . , ⁇ M ), therefore, strong phase noise variations are considered for the phase noise estimation as well as for the channel estimation.
  • the channel estimation comprises:
  • ⁇ is computed based on
  • the receiver first obtains the symbols in the frequency domain of the received radio signal corresponding to the radio signal emitted according to the method for transmitting the reference signals as described previously. That is, for example, these symbols are obtained from applying a DFT (discrete Fourier transform) on the received radio signal.
  • the received symbols which contain combination of the reference signals with only negligible power related to emitted symbols that are not RS from the pattern specified by the invention are selected. These selected symbols are for example Y n min , . . . , Y n max , that is, the symbols received on the subcarrier S n min , . . . , S n max , with n min and n max as defined above.
  • the group of parameters ( ⁇ 1 , . . . , ⁇ M ) may be set such as each ⁇ j is computed based on
  • K is an odd integer and K/2 is an odd integer
  • the receiver can, due to these estimation, reduce the effects on the radio signal of the radio channel (that is of the channel and of the phase noise). Therefore, the receiver can decode correctly the radio signal to retrieve the symbols emitted by the transmitter.
  • processing the radio signal by the receiver may comprise computing estimated symbols ⁇ circumflex over (X) ⁇ 1 , . . . , ⁇ circumflex over (X) ⁇ M of symbols X 1 , . . . , X M respectively transmitted on the subcarriers S 1 , . . . , S M , said estimated symbols ( ⁇ circumflex over (X) ⁇ 1 , . . . , ⁇ circumflex over (X) ⁇ M ) being obtained by linear equalization based on ⁇ of R, R being a DFT of order M of e ⁇ i ⁇ circumflex over ( ⁇ ) ⁇ ⁇ y with e ⁇ i ⁇ circumflex over ( ⁇ ) ⁇ equal to
  • the symbols X 1 , . . . , X M transmitted on the subcarriers S 1 , . . . , S M are emitted by the emitter.
  • a third aspect of the invention concerns a computer program product comprising code instructions to perform the method as described previously when said instructions are run by a processor.
  • a fourth aspect of the invention concerns an emitter for transmitting at least K reference signals in a radio signal to be transmitted over a wireless communication system, said radio signal being intended to be emitted by the emitter, said emitter comprising:
  • At least a transmit antenna configured for emitting on a number M of subcarriers S 1 , . . . , S M amongst which at least a number K of different subcarriers S q+1 , S q+2 , . . . , S q+K are contiguous, the respective frequencies of the contiguous subcarriers S q+1 , S q+2 , . . . , S q+ K being ordered,
  • a non-transitory computer-readable medium comprising instructions stored thereon, which when executed by the processor configure the emitter to:
  • a fifth aspect of the invention concerns a receiver for processing a radio signal transmitted over a wireless communication system and received from an emitter comprising at least a transmit antenna configured for emitting on a number M of different subcarriers S 1 , . . . , S M amongst which at least a number K of different subcarriers S q+1 , S q+2 , . . . , S q+K are contiguous, the respective frequencies of the contiguous subcarriers S q+1 , S q+2 , . . . , S q+K being ordered, said radio signal including K reference signals, said radio signal being provided according to any one of claims 1 to 4 , said receiver comprising:
  • a non-transitory computer-readable medium comprising instructions stored thereon, which when executed by the processor configure the receiver to:
  • FIG. 1 illustrates a transmitter and receiver according to the invention.
  • FIG. 2 schematizes a block diagram of a transmitter according to the invention.
  • FIG. 3 details an example of a reference signal pattern according to the invention.
  • FIG. 4 schematizes a block diagram of a receiver according to the invention.
  • FIG. 5 illustrates a flowchart representing the steps of radio signal processing according to the invention.
  • FIG. 6 illustrates a flowchart representing the steps of radio signal decoding according to the invention.
  • a transmitter 1 . 1 transmitting a radio signal to a receiver 1 . 2 .
  • the receiver 1 . 1 is in the cell of the transmitter 1 . 2 .
  • This transmission may be an OFDM based transmission.
  • the transmitter 1 . 1 is a fixed station and the receiver 1 . 2 is a mobile terminal.
  • the fixed station and the mobile terminal are respectively referred to as a base station and a user equipment.
  • the transmitter 1 . 1 can as well be the mobile terminal and the receiver 1 . 2 the fixed station.
  • the transmitter 1 . 1 comprises one communication module (COM_trans) 1 . 3 , one processing module (PROC_trans) 1 . 4 and a memory unit (MEMO_trans) 1 . 5 .
  • the MEMO_trans 1 . 5 comprises a non-volatile unit which retrieves the computer program and a volatile unit which retrieves the reference signal pattern parameters, for example the tuple (q i , ⁇ i , K i , Q i 1 , . . . , Q i K 0 i ).
  • the PROC_trans 1 . 4 is configured to insert the reference signals according to the invention.
  • the COM_trans is configured to transmit to the receiver 1 . 2 the radio signal.
  • the processing module 1 . 4 and the memory unit 1 . 5 may constitute the device for inserting the reference signals, as previously described.
  • the processing module 1 . 4 and the memory unit 1 . 5 can be dedicated to this task or also used for other functions of the transmitter like for processing the radio signal
  • the receiver 1 . 2 comprises one communication module (COM_recei) 1 . 6 , one processing module (PROC_recei) 1 . 7 and a memory unit (MEMO_recei) 1 . 8 .
  • the MEMO_recei 1 . 8 comprises a non-volatile unit which retrieves the computer program and a volatile unit which retrieves the reference signal pattern parameters, for example the tuple (q i , ⁇ i , K i , Q i 1 , . . . , Q i K 0 i ).
  • the PROC_recei 1 comprises one communication module (COM_recei) 1 . 6 , one processing module (PROC_recei) 1 . 7 and a memory unit (MEMO_recei) 1 . 8 .
  • the MEMO_recei 1 . 8 comprises a non-volatile unit which retrieves the computer program and a volatile unit which retrieves the reference signal pattern parameters, for example the
  • the processing module 1 . 7 and the memory unit 1 . 8 may be dedicated to these tasks, as previously described. The processing module 1 . 7 and the memory unit 1 . 8 may also be used for other functions of the receiver.
  • FIG. 2 there is shown a block diagram of a transmitter 1 . 1 according to the invention.
  • Such OFDM transmitter 1 . 1 applies an OFDM scheme on a block of N′ symbols to obtain the radio signal.
  • the OFDM transmitter emits a radio signal by emitting on one transmit antenna Tx 2 . 0 , this is none limiting and the OFDM transmitter can as well transmit by using several transmit antennas, for example in a MIMO context.
  • the reference signal pattern may be identical for each antenna or only one antenna transmits the RS according to the invention, the RS of the RS pattern being replaced by zeros for the other antennas.
  • the symbols of the block of symbols may be N′ complex symbols obtained by a QPSK digital modulation scheme or any other digital modulation scheme as QAM, or may be symbols of a sequence with controlled PAPR (e.g. a CAZAC sequence).
  • the parallel symbols are mapped, with a subcarrier mapping module 2 . 2 in the frequency domain to N (>N′) out of M subcarriers (S 1 , . . . S M ).
  • the complex symbols are mapped to the N allocated subcarriers out of M existing subcarriers via subcarrier mapping module 2 . 2 .
  • the subcarrier mapping can be for example localized, that is, the N′ complex symbols are mapped throughout N consecutive subcarriers among the M existing. This subcarrier mapping is done in accordance with the reference signal pattern used by the transmitter 1 . 1 .
  • the N-N′ allocated subcarriers to which none of the N′ complex symbols have been mapped correspond to the subcarriers which transmit the RS according to the RS pattern. Therefore, the RS insertion module 2 . 3 adds to these unused N-N′ subcarriers the RS according to the RS pattern as described in FIG. 3 .
  • M-size inverse DFT module 2 . 4 is then applied to the resulting vector of M symbols X 1 , . . . , X M , the M symbols being the N non-null symbols (comprising the RS of the RS pattern) and M-N null symbols (according to the subcarrier mapping scheme), therefore generating an OFDM symbol which is transmitted via the transmit antenna 2 . 0 .
  • a signal ⁇ tilde over (x) ⁇ is obtained at the output of the IDFT module 2 . 4 a signal ⁇ tilde over (x) ⁇ is obtained. This signal occupies during a time interval corresponding to an OFDM symbol, N allocated subcarriers out of the M existing subcarriers. This time-domains signal ⁇ tilde over (x) ⁇ corresponds to an OFDM symbol.
  • a cyclic prefix can be optionally appended after the IDFT by the CP module 2 . 5 .
  • the digital-to-analog converter (DAC) module 2 . 6 converts the digital signal resulting from the IDFT module 2 . 4 to an analog signal that can be transmitted through the antenna 2 . 0 .
  • FIG. 3 there is shown an example of a reference signal pattern according to the invention.
  • the invention specifies specific positions (that is the subcarriers used to transmit the reference signals) and values for the reference signals.
  • This specific reference signal pattern according to the invention (or simply the reference signal pattern) enables to have specific properties of the radio signal enabling to reduce errors during its decoding.
  • the reference signals are positioned by groups of RS.
  • L groups of RS are configured.
  • the i-th group of RS is transmitted on the subcarriers S qi+1 , . . . , S qi+K i , for i from 1 to L.
  • the position of the first symbol in the group has to be greater than the last position of the previous group, that is, q i +K i ⁇ q i+1 +1 for i from 1 to L ⁇ 1.
  • These positions are among the M positions of the subcarriers used in the bandwidth by the transmitter.
  • Only one group of RS may be set in the RS pattern, then, the group of RS is transmitted on the subcarriers S q+1 , . . . , S q+K .
  • the values in the frequency domain of the reference signals P i 1 , . . . , P i K 0 i ⁇ 1 are respectively equal to the values of the reference signals P i K 0 i +1 , . . . , P i K i (transmitted respectively on the subcarriers S qi+K 0 i +1 , . . . , S K i ), with
  • the group of reference signals P i 1 , . . . , P i K i may be issued from a sequence of Q i 1 , . . . , Q i K 0 i which satisfies an auto-correlation condition, that is, such as
  • sequences may be CAZAC sequences, for example Zadoff-Chu sequences.
  • the size K i of each group of reference signals may be chosen such as described after according to the spectral occupancy of the phase noise, or at least to the spectral occupancy of the modelized phase noise.
  • the size K i of each group may be set such as the channel is constant or can be assimilated as such on a scale of K i . ⁇ f. Therefore, the results are better if the channel is constant at least on a scale of 2. ⁇ PN.
  • the number L of groups of reference signals may be chosen according to the variation of channel in the spectrum. Indeed, if the channel is sensitive to frequency then it may be relevant to have an important density of groups of reference signals through the bandwidth used for the communication. Adventurously these groups of reference signals may be uniformly distributed through the bandwidth (all the ⁇ i are equal or similar). If the channel is not sensitive to frequency then only one or two groups of reference signals may be needed to have good channel and/or phase noise estimation through all the bandwidth.
  • FIG. 4 there is shown a block diagram of a receiver 1 . 2 according to the invention.
  • a receiver is configured to decode a radio signal emitted by a transmitter 1 . 1 as previously described.
  • This example shows a receiver with a unique receive antenna but such receiver can have several receive antennas. When using several antennas, the radio signal received by each antenna differs which introduces receive diversity.
  • said radio signal is received on one antenna Rx 4 . 0 .
  • the results, at the outputs of the DFT 4 . 3 are M symbols Y 1 , . . . , Y M respectively received on the subcarriers S 1 , . . . , S M .
  • the RS extraction module 4 . 4 extracts a block of symbols from the M symbols Y 1 , . . . , Y M . More specifically, the RS extraction module 4 . 4 extracts K 0 i received contiguous symbols Y n min i , . . . , Y n max i on the subcarriers S n min i , . . . , S n max i . n min i and n max i are defined so that each of these extracted symbols are only composed of samples of the reference signals P i 1 , . . . , P i K i of the block of K i reference signals. These received symbols Y n min i , . . . ,
  • Y n max i may also contain samples from other symbols but these samples are of low energy compared to the samples of the reference signals set in block. Indeed, by considering a typical model of phase noise such as a Wiener processed phase noise (also known as a Brownian motion)) it is possible to determine the number of contiguous symbols Y n min i , . . . , Y n max i that do not contain samples of other symbols.
  • the sizes K i of the blocks of reference signals are chosen according to the spectral occupancy of the phase noise ⁇ PN, that is, for each i, K i . ⁇ f is equal or greater than 2 ⁇ PN.
  • the K i are all equal since the spectral occupancy of the phase noise ⁇ PN is the same for each blocks of reference signals. This enables to ensure that a sufficiently important block of symbols Y n min i , . . . , Y n max i only composed of samples of the reference signals P i 1 , . . . , P i K i is received. For instance, if K i is greater than or equal to 2 ⁇ PN/ ⁇ f, then n min and n max can be defined as:
  • H is constant on the bandwidth corresponding to subcarriers S q i to S q i +2K 0 i ⁇ 2 , which are the subcarriers transmitting reference signals P i 1 , . . . , P i K i .
  • this assumption is generally not restrictive.
  • K i may be set greater than or equal to 2 ⁇ PN/ ⁇ f and H may be assumed as constant on the bandwidth corresponding to subcarriers S q i to S q i +2K 0 1 ⁇ 2 .
  • H is not constant and/or 2 ⁇ PN is greater than K i ⁇ f then the invention may still be applied with good results but less accurate than when those conditions are met.
  • the channel and phase noise estimation module 4 . 5 computes channel estimation and a phase noise estimation.
  • Two different algorithms using the specificities of the specific RS pattern may be implemented by the channel and phase noise estimation module 4 . 5 .
  • the channel and phase noise estimation module 4 . 5 computes the linear estimation of F K 0 i ⁇ 1 ⁇ (P 1 i , . . . , P K 0 i i ) ⁇ by F K 0 i ⁇ 1 ⁇ (Y n min i , . . . , Y n max i ) ⁇ with F K 0 i ⁇ 1 ⁇ U ⁇ the inverse DFT of order K 0 i of the vector U of size K 0 i , with
  • the linear estimation may be:
  • ⁇ circumflex over ( ⁇ ) ⁇ ( ⁇ circumflex over ( ⁇ ) ⁇ 1 , . . . , ⁇ circumflex over ( ⁇ ) ⁇ M )
  • ⁇ circumflex over ( ⁇ ) ⁇ j e ⁇ i.arg ⁇ i ⁇ j i .
  • each ⁇ circumflex over ( ⁇ ) ⁇ j can be computed based on an coherent average of the parameters through the RS pattern, that is, for example,
  • channel and phase noise estimation module 4 . 5 computes the frequency domain representation ⁇ of the channel estimation such as ⁇ is computed based on
  • ⁇ is equal to
  • the channel and phase noise estimation module 4 . 5 computes a group of parameters ( ⁇ 1 i , . . . , ⁇ k min i i , . . . , ⁇ k max i i , . . . ⁇ M i ) with
  • ⁇ circumflex over ( ⁇ ) ⁇ ( ⁇ circumflex over ( ⁇ ) ⁇ 1 , . . . , ⁇ circumflex over ( ⁇ ) ⁇ M )
  • ⁇ circumflex over ( ⁇ ) ⁇ (j ⁇ M.) M e ⁇ i.arg H i M 0 ⁇ j i for K min i ⁇ j ⁇ k max i , with
  • K i is an even integer and K i /2 is an even integer
  • K i is an even integer and K i /2 is an odd integer
  • K i is an odd integer and K i /2 is an even integer
  • each ⁇ circumflex over ( ⁇ ) ⁇ (j ⁇ M.) M can be computed based on an average of the parameters through the RS pattern, that is, for example,
  • the equalization module 4 . 6 performs a linear equalization based on ⁇ of R, R being a DFT of order M of e ⁇ i ⁇ circumflex over ( ⁇ ) ⁇ ⁇ y with e ⁇ i ⁇ circumflex over ( ⁇ ) ⁇ equal to
  • ⁇ circumflex over (X) ⁇ M ⁇ circumflex over (X) ⁇ of the symbols X 1 , . . . , X M respectively transmitted through the subcarriers S 1 , . . . , S M .
  • estimated symbols ( ⁇ circumflex over (X) ⁇ 1 , . . . , ⁇ circumflex over (X) ⁇ M ) may be obtained by a minimum mean-squared error (MMSE) equalization, that is:
  • FIG. 5 there is shown a flowchart representing the steps of radio signal processing according to the invention.
  • a RS pattern stored in the memory unit 1 . 5 is selected.
  • the selection may be either static or dynamically.
  • the transmitter 1 . 1 may change, for example for each OFDM symbol or for a number of OFDM symbols, the RS pattern used for the insertion of RS. This selection may be done according to feedbacks from the receiver 1 . 2 through a control channel.
  • the transmitter may choose another configuration upon those saved in the MEMO_trans 1 . 5 .
  • several configurations may be stored in the MEMO_trans 1 . 5 , those configurations can be ordered according to the number of reference signals ( ⁇ K i ) and/or the number of groups of RS the RS pattern provides.
  • a RS pattern may be defined by the number ⁇ K i of reference signals, by the number of groups (L) of RS or by the positions of the RS in the frequency domain.
  • the transmitter 1 . 1 may select a RS pattern based on the communication configuration (subcarrier spacing configuration, carrier frequency range, modulation and coding scheme, carrier frequency, resource allocation unit) and radio channel characteristics (strong phase noise variation, strong sensitivity to the frequency) of the transmission.
  • the communication configuration subcarrier spacing configuration, carrier frequency range, modulation and coding scheme, carrier frequency, resource allocation unit
  • radio channel characteristics strong phase noise variation, strong sensitivity to the frequency
  • the subcarrier mapping module 2 . 2 and the RS insertion module 2 . 3 are configured according to the RS pattern stored in the memory unit 1 . 5 and used for the transmission. Therefofe, the subcarrier mapping module 2 . 2 is configured to map the N′ symbols at its inputs on subcarriers that will not be occupied, according to the RS pattern, by the ⁇ K i reference signals.
  • the other subcarriers are occupied by the N′ symbols to be transmitted and by zeros according to the scheme of the subcarrier mapping.
  • IDFT module 2 . 4 the OFDM scheme
  • CP module 2 . 5 the OFDM scheme
  • DAC module 2 . 6 the OFDM scheme
  • step S 15 the signal is emitted by Tx 2 . 0 .
  • FIG. 6 there is shown a flowchart representing the steps of radio signal decoding according to the invention.
  • the RS extractor module 4 . 4 , the channel and phase noise estimation module 4 . 5 and the equalization module 4 . 6 are configured according to the configuration of the RS insertion module 2 . 3 .
  • the receiver 1 . 2 may receive, for example from the transmitter 1 . 1 , the RS pattern used for the transmission.
  • the same RS pattern stored in the MEMO_trans 1 . 5 may be stored in the MEMO_recei 1 . 8 .
  • the transmitter 1 . 1 can optionally send control information to the receiver 1 . 2 through a control channel, this control information pointing the RS pattern selected for the transmission.
  • step S 23 channel estimation and phase noise estimation is performed based on the symbols extracted as previously described.
  • This is done according to the channel estimation and to the phase noise estimation computed by the channel and phase noise estimation module 4 . 5 as previously described.
  • the estimated symbols ( ⁇ circumflex over (X) ⁇ 1 , . . . , ⁇ circumflex over (X) ⁇ M ) are then processed through the subcarrier demapping module 4 . 7 and the parallel to serial module 4 . 8 to retrieve the N′ symbols previous processed by the transmitter 1 . 1 .

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Cited By (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
WO2024183002A1 (en) * 2023-03-07 2024-09-12 Mediatek Singapore Pte. Ltd. Reference signal design and processing for wireless sensing in integrated sensing and communications system

Families Citing this family (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
EP3599748B1 (en) * 2018-07-26 2020-12-16 Mitsubishi Electric R&D Centre Europe B.V. Symbols incorporation scheme for dft-s-ofdm
WO2022257046A1 (zh) * 2021-06-09 2022-12-15 深圳大学 载波频率、初始相位、相位噪声的估计方法和相关设备
CN114726689B (zh) * 2022-06-06 2022-09-30 新华三技术有限公司 一种信号估计的方法及装置

Citations (9)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US20110116485A1 (en) * 2008-01-15 2011-05-19 Kim Olszewski Methods for superframe/frame overhead reduction within ofdma-based communication systems
US20170005715A1 (en) * 2015-07-01 2017-01-05 Qualcomm Incorporated Joint channel and phase noise estimation in control symbols of a millimeter wave link
US20170279579A1 (en) * 2016-03-22 2017-09-28 Samsung Electronics Co., Ltd. Signal transmitting and receiving methods in a filtering-based carrier modulation system and apparatuses thereof
US20170302352A1 (en) * 2016-04-18 2017-10-19 Qualcomm Incorporated Channel state information estimation and channel information reporting
US20180167237A1 (en) * 2016-12-14 2018-06-14 Intel IP Corporation Data detection in mimo systems with demodulation and tracking reference signals
US20180212733A1 (en) * 2015-08-12 2018-07-26 Intel Corporation Demodulation in wireless communications
US20200153585A1 (en) * 2017-08-01 2020-05-14 Huawei Technologies Co., Ltd. Reference signal transmission method and apparatus
US20200213161A1 (en) * 2017-08-21 2020-07-02 Zte Corporation Reference signal transmission and parameter sending methods, device, terminal and base station
US20200235900A1 (en) * 2019-01-21 2020-07-23 Qualcomm Incorporated Sequence generation to support demodulation reference signal multiplexing for pi over 2 binary phase shift keying modulation

Family Cites Families (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
GB2458418B (en) * 2006-12-19 2011-08-03 Lg Electronics Inc Sequence generating method for efficient detection and method for transmitting and receiving signals using the same
KR100958031B1 (ko) * 2007-05-17 2010-05-19 엘지전자 주식회사 무선통신 시스템에서 동기 신호를 전송하는 방법
US10129052B2 (en) * 2015-08-14 2018-11-13 Qualcomm Incorporated Phase noise estimation
EP3435609B1 (en) * 2017-07-25 2022-12-07 Mitsubishi Electric R&D Centre Europe B.V. Pre-dft reference signal insertion for sc-sfbc
CN109391403B (zh) * 2017-08-10 2021-07-06 上海诺基亚贝尔股份有限公司 用于无线信号的发送和接收的方法和装置

Patent Citations (10)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US20110116485A1 (en) * 2008-01-15 2011-05-19 Kim Olszewski Methods for superframe/frame overhead reduction within ofdma-based communication systems
US20170005715A1 (en) * 2015-07-01 2017-01-05 Qualcomm Incorporated Joint channel and phase noise estimation in control symbols of a millimeter wave link
US20180212733A1 (en) * 2015-08-12 2018-07-26 Intel Corporation Demodulation in wireless communications
US20170279579A1 (en) * 2016-03-22 2017-09-28 Samsung Electronics Co., Ltd. Signal transmitting and receiving methods in a filtering-based carrier modulation system and apparatuses thereof
US20170302352A1 (en) * 2016-04-18 2017-10-19 Qualcomm Incorporated Channel state information estimation and channel information reporting
US20180167237A1 (en) * 2016-12-14 2018-06-14 Intel IP Corporation Data detection in mimo systems with demodulation and tracking reference signals
US20200153585A1 (en) * 2017-08-01 2020-05-14 Huawei Technologies Co., Ltd. Reference signal transmission method and apparatus
US20200213161A1 (en) * 2017-08-21 2020-07-02 Zte Corporation Reference signal transmission and parameter sending methods, device, terminal and base station
US11757680B2 (en) * 2017-08-21 2023-09-12 Zte Corporation Reference signal sending and receiving methods, device and storage medium
US20200235900A1 (en) * 2019-01-21 2020-07-23 Qualcomm Incorporated Sequence generation to support demodulation reference signal multiplexing for pi over 2 binary phase shift keying modulation

Cited By (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
WO2024183002A1 (en) * 2023-03-07 2024-09-12 Mediatek Singapore Pte. Ltd. Reference signal design and processing for wireless sensing in integrated sensing and communications system

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