1376085 六、發明說明： 【發明所屬之技術領域】 本發明是有關於一種升壓轉換裝置，特別是指一種能 將低電壓轉成高電壓的高升壓轉換裝置。 【先前技術】 在許多的應用場合中常常需要將現有的低電壓升壓至 較尚電壓以提供設備之需求，如汽車用之電力電子、具能 量回收之主動式燒機負載，其中以升壓型轉換器（B〇〇st Converter)及升降壓型轉換器（Buck_B〇〇st c〇nverter)在市面 上使用較為普遍，但不論為升壓型轉換器或升降壓型轉換 器均存在一個無法達到高升壓比的缺點。 如圖1所示，升壓型轉換器在連續導通模式（CCM)下， 其升壓比可=jT万，0為責任週期（duty cycle);理論上，雖 然升壓比_沒有上限（如虛線部分），但實際上受限於元件寄 生效應以及控制器之能力，其升壓比達到4至5倍時將下 降（如實線部分），因此不可能無限制的提高升壓比。 以實際的應用而言，通常將升壓比設定於5倍左右， 若需要更高的升壓比，通常會採用兩級的升壓轉換器或是 採用返馳式轉換器（Flyback Converter)、前向式轉換器 (Forward Converter)之隔離式升壓轉換器。 為了使單級的升壓轉換器能達到高升壓比，因此一些 探討高升壓比的論文相繼被提出，其中有F L Lu〇提出的 羅式轉換器（Luo Converter)及其一系列的衍生架構，但其 3 1376085 架構均類似邱克轉換器（Cuk Converter)，以電容作為能量 轉移中繼站對其壽命之影響很大，不適合用於大電流大功 率場合。在 R. Gules, L. L. Pfitscher 及 L· C. Franco 提出之 論文 “An interleaved boost DC-DC converter with large conversion ratio”中提出一種可達到高升壓比之升壓轉換器 架構，以一輸入24V輸出200V/2A實際電路來驗證所提架 構之可行性，此架構乃利用傳統升壓轉換器搭配電荷幫浦 (Charge Pump)以提高輸出電壓，但欲提高升壓比則須將電 荷幫浦量增加，即用更多的二極體和電容，且當電容容量 增加後，電路於能量轉移時將會產生較大之湧浪電流，因 此電容值無法選擇過大且等效串連電阻（Equivalent Series Resistance，ESR)亦要很小；另外，若要達到高電流輸出則 須採用多組並連方式以提高功率。 【發明内容】 有鑒於目前多採用兩級的升壓轉換器，並無一套能有 效提昇升壓比且電路精簡的高升壓轉換裝置，因此本發明 希望能提供一種能有效提昇升壓比且精簡電路的高升壓轉 換裝置。 因此，本發明高升壓轉換裝置包括一電荷幫浦、一耦 合電感、一電壓箝制緩衝器及一輸出側。 該電荷幫浦用以接收一輸入電壓並使該輸入電壓升壓 ，具有一第一開關元件、一串接該第一開關元件之第二開 關元件、一連接該第一開關元件之一端的二極體及一跨接 該第一開關元件及該二極體之升壓電容。 4 該輕合電咸Φ k i 並且有: 連接該升壓電容及該第三開關元件， 制緩衝器電性連丄-:人側電感及-漏感；該電壓箝 開關亓杜曰 > '"輕合電感及該電荷幫浦’具有一第三 輪出二極體及_輪出：開關象跨壓；該輸出側具有-接該㈣制緩衝=:該輸出電容經該輸出二刪 之能量。 用以儲存该耦合電感之漏感所釋放 藉此，該第一pq Bfl - _ 開關疋件與該第三開關元件導通且該第 —開關元件不導诵_ 、 · *亥一次側電感產生一高於該輸入電 ^之激磁電壓，且由該輸出電容輸出該激磁電壓；及該第 -開關元件與該第三開關元件不導通且該第二開關元件導 通時，該二極體因順偏而導通，該升壓電容充電為該輸入 電壓’令先前儲存於該—次側電感的能量被轉移至該二次 側電感並釋出能量對該輸出電容充電。 本發明高升壓轉換裝置是結合包括電荷幫浦、耗合電 感、電壓箝制緩衝器及輸出電容等元件，電路精簡，且能 在全負載範圍達到高效率之能量轉移。 【實施方式】 有關本發明之前述及其他技術内容、特點與功效，在 以下配合參考圖式之較佳實施例的詳細說明中，將可清楚 的呈現。 參閱圖2，本發明高升壓轉換裝置丨之較佳實施例包含 一電荷幫浦11、一耦合電感Π及一電壓箝制緩二二 (Snubber)13 〇 1376085 電何幫浦u用以接收—輸人電壓&並使該輪 升壓，具n開m,(並聯有— ^ 第-開關元件-第二開關元件购”有一二極L、:)串接 連接第一開關元件&之一端的_扠胁 J'~ 件&及二極體仏之升壓電容開關几 耦合電感12電性連接升壓 电谷C〆並具有—一次側電 感％ --人側電感4及-漏感~ ;其中—次側電感0 二次側電感4分別為輕合電感12的-次側自感與二次側自 感’假設圈數比例„ = J，D為音紅 馮貝任週期，則可以得到輸出 電壓K與輪入電壓匕之關係式：奶 f 闷+ 1。 電壓箝制緩衝器13電性連接耗合電感12及電荷幫浦 11，具有一與第二開關元件 稍按之第二開關兀件A (並聯 有一二極體£)3)、一電容 、一 _ ^ ^ _ sn —體^^與一電感，用以 推制第二開關元件4之跨壓。 由於相β電感12存在漏感^，漏感^的能量會累積 ㈤關兀件&的寄生電容上’若此時電壓太高則會擊穿 第^關讀^因此，本發明針對此問題設計將電壓籍制 ,,衝裔13將漏感[认之能量釋放至輸出側，當第三開關元件 $3不導通時’漏感的能量會經由二極體化對電容^充電 ’爾後電容所儲存之能量將經由電感&送至輸出側。 輸出侧具有-輸出二極❹。及一輸出電容〔。，輸出電容 c。經輪出二極體⑽接該電壓箝制緩衝器13，用以儲存輛 合電感12漏感所釋放之之能量。 I S1 6 1376085 需說明的是，當高升壓轉換裝置1採多相（Multi-phase) 交錯控制以提高輸出功率時，例如N相，只須加入N-1個 二極體^即可，電路十分簡潔。 本發明所提架構之相關規格如表一所示。 表一 輸入電壓 5V 輸出電壓G(滿載） 48V 輸出電流t 1A 切換頻率Λ 195kHz 耦合電感 一次側電感& ΙΟμΗ，T106-18 鐵心繞 8 圈 二次側電感4 250μΗ，Τ106-1 8 鐵心繞 40 圈 輸入端電容 1500μΕ 輸出端電容c。 ΙΟΟΟμΡ 升壓電容cb 330μΡ*3+22μΡ MLCC 緩衝電容 琴，MLCC 緩衝二極體/^ 3CTQ100 緩衝電感k ΙΟμΗ 二極體A STPS20L25 輸出二極體A 3CTQ100 功率晶體s, PHD96NQ03LT 功率晶體& PHD96NQ03LT 功率晶體& IRL3705ZS 控制1C Altera FPGA Cyclone 系列 EP1C3T100 1376085 第二開關亓I„ 午4之驅動訊號；（C)為量測流經一次側電咸 之電流；及⑷為量測流經二次側電h之電流。電^ 圖 9反古广 一 马间升壓轉換裝置1操作於滿載情況下，（a)為量 d第/關7L件Sl(第三開關元件&)之驅動訊號；（b)為量測 七元件\之驅動訊號；（C)為量測流經一次側電感1 之電"·<·,及（d)為量測流經二次侧電感&之電流。 如圖10至圖12所示，圖10、圖u及圖12分別 升壓轉換裝置1操作於1G%載、8G%載及%載之情況下 一’各圖的（a)為量測第一開關元件以第三開關元件^之驅動 號（b)為里測第二開關元件&之驅動訊號；⑷為量測第 三開關元件1之跨壓；及⑷為量測電容Q之跨壓。 如圖13所示，為負載電流對效率之關係圖，在滿載時 效率。接近82%，效率最高點則是出現於半載，其效率可達 84.3%°由上述實驗結果可知，所提之新型升壓轉換器可穩 定地操作於所設定之規格。另外，在輕載方面，不像其他 父換式電源架構有效率降低的困擾。 卸納上述，本發明高升壓轉換裝置丄係採用電荷幫浦 11口耗σ電12感所構成，在輸人5V之低壓大電流條件 下’可以達到接近10倍的升壓比，且於輕載時仍具有嶋 轉換效率’整個負載操作範圍下的效率曲線較為平緩可 在全負載範圍達到高效率之能量轉移。 惟以上所述者’僅為本發明之較佳實施例而已，當不 能以此限定本發明實施之範圍，即大凡依本發明申請專利 範圍及發明說明内容所作之簡單的等效變化與修飾，皆仍 I S1 9 1376085 屬本發明專利涵蓋之範圍内。1376085 VI. Description of the Invention: [Technical Field] The present invention relates to a boost converter, and more particularly to a high boost converter capable of converting a low voltage into a high voltage. [Prior Art] In many applications, it is often necessary to boost the existing low voltage to a higher voltage to provide equipment requirements, such as power electronics for automobiles, active burner loads with energy recovery, and boost Type converters (B〇〇st Converter) and buck-boost converters (Buck_B〇〇st c〇nverter) are commonly used in the market, but there is a failure between the boost converter and the buck-boost converter. The disadvantage of achieving a high boost ratio. As shown in Figure 1, in the continuous conduction mode (CCM), the boost converter can have a boost ratio of = jT 10,000 and 0 is the duty cycle; in theory, although the boost ratio _ has no upper limit (such as The dotted line), but actually limited by the component parasitics and the ability of the controller, will drop when the boost ratio is 4 to 5 times (as in the solid line portion), so it is impossible to increase the boost ratio without limitation. In practical applications, the boost ratio is usually set at about 5 times. If a higher boost ratio is required, a two-stage boost converter or a flyback converter (Flyback Converter) is usually used. Isolated Converter Converter for Forward Converter. In order to achieve a high boost ratio for a single-stage boost converter, some papers discussing high boost ratios have been proposed, including FL Lu〇's Luo Converter and its series of derivatives. Architecture, but its 3 1376085 architecture is similar to the Cuk Converter. Capacitance as an energy transfer relay has a great impact on its lifetime and is not suitable for high current and high power applications. In the paper "An interleaved boost DC-DC converter with large conversion ratio" by R. Gules, LL Pfitscher and L. C. Franco, a boost converter architecture with high boost ratio is proposed, with an input 24V output. The actual circuit of 200V/2A is used to verify the feasibility of the proposed architecture. This architecture uses a traditional boost converter with a charge pump to increase the output voltage. However, to increase the boost ratio, the charge pump must be increased. That is, more diodes and capacitors are used, and when the capacitance increases, the circuit will generate a large surge current during energy transfer, so the capacitance value cannot be selected too much and the equivalent series resistance (Equivalent Series Resistance) , ESR) is also small; in addition, to achieve high current output, multiple sets of parallel connections must be used to increase power. SUMMARY OF THE INVENTION In view of the fact that a two-stage boost converter is currently used, there is no high boost converter that can effectively increase the boost ratio and the circuit is simplified. Therefore, the present invention is intended to provide an improved boost ratio. And the high boost converter of the circuit is simplified. Accordingly, the high boost converter of the present invention includes a charge pump, a coupling inductor, a voltage clamp buffer, and an output side. The charge pump is configured to receive an input voltage and boost the input voltage, and has a first switching component, a second switching component connected in series with the first switching component, and a second terminal connected to the first switching component The pole body and a boosting capacitor bridging the first switching element and the diode. 4 The light and electric salt Φ ki and have: connect the boosting capacitor and the third switching element, make the buffer electrical connection -: human side inductance and - leakage inductance; the voltage clamp switch 亓 Du Fu> "Lighting inductance and the charge pump 'has a third round out diode and _ wheel out: switch like cross voltage; the output side has - connected to the (four) system buffer =: the output capacitor is deleted by the output Energy. The leakage inductance for storing the coupled inductor is released, wherein the first pq Bfl − _ switch element is electrically connected to the third switching element and the first switching element is non-conducting _ , · * The excitation voltage is higher than the input voltage, and the excitation voltage is outputted by the output capacitor; and when the first switching element and the third switching element are not turned on and the second switching element is turned on, the diode is biased Turning on, the boost capacitor is charged to the input voltage 'so that the energy previously stored in the secondary side inductor is transferred to the secondary side inductor and the energy is released to charge the output capacitor. The high boost converter of the present invention combines components including charge pump, consuming inductor, voltage clamp buffer and output capacitor, has a simplified circuit, and can achieve high efficiency energy transfer over the full load range. The above and other technical contents, features, and advantages of the present invention will be apparent from the following detailed description of the preferred embodiments of the invention. Referring to FIG. 2, a preferred embodiment of the high boost converter of the present invention comprises a charge pump 11, a coupled inductor, and a voltage clamped Snubber 13 〇 1376085 electrical Hepu u for receiving - input Voltage & and boost the wheel, with n open m, (parallel with - ^ first - switching element - second switching element purchased) has a diode L, :) serially connected to the first switching element & one end The _ 胁 J J '~ piece & and the diode 升压 升压 电容 电容 几 几 几 几 几 几 几 耦合 耦合 耦合 耦合 耦合 耦合 耦合 耦合 耦合 耦合 耦合 耦合 耦合 耦合 耦合 耦合 耦合 耦合 耦合 一次 一次 一次 一次 一次 一次 一次 一次 一次~ ; Among them - the secondary side inductance 0 secondary side inductance 4 is the light-inductive inductance 12 - the secondary side self-inductance and the secondary side self-induction 'assumed the number of turns ratio „ = J, D is the sound red von Bei Ren cycle, then The relationship between the output voltage K and the wheeling voltage 匕 can be obtained: milk f boring + 1. The voltage clamping buffer 13 is electrically connected to the consuming inductor 12 and the charge pump 11 , and has a second switching element A which is slightly pressed with the second switching element (a diode is connected in parallel) 3), a capacitor, and a capacitor _ ^ ^ _ sn — body ^ ^ and an inductor for pushing the voltage across the second switching element 4 . Since the phase β inductor 12 has a leakage inductance ^, the energy of the leakage inductance will accumulate (5) the parasitic capacitance of the off device & 'If the voltage is too high, the breakdown will be read. Therefore, the present invention addresses this problem. The design will be voltage system, and the rushing 13 will leak the sensation [recognize the energy to the output side. When the third switching element $3 is not conducting, the energy of the leakage sensation will charge the capacitor ^ through the diode. The stored energy will be sent to the output side via the inductor & The output side has an - output diode. And an output capacitor [. , output capacitor c. The voltage clamping buffer 13 is connected to the diode (10) for storing the energy released by the leakage inductance of the inductor 12. I S1 6 1376085 It should be noted that when the high boost converter 1 adopts multi-phase interleaving control to increase the output power, for example, the N phase, only N-1 diodes must be added. The circuit is very simple. The relevant specifications of the architecture proposed by the present invention are shown in Table 1. Table 1 input voltage 5V output voltage G (full load) 48V output current t 1A switching frequency Λ 195kHz coupled inductor primary side inductance & ΙΟμΗ, T106-18 core around 8 turns secondary side inductance 4 250μΗ, Τ106-1 8 core around 40 The input terminal capacitance is 1500μΕ and the output terminal capacitance c. ΙΟΟΟμΡ boost capacitor cb 330μΡ*3+22μΡ MLCC buffer capacitor, MLCC buffer diode /^ 3CTQ100 buffer inductor k ΙΟμΗ diode A STPS20L25 output diode A 3CTQ100 power crystal s, PHD96NQ03LT power crystal & PHD96NQ03LT power crystal & IRL3705ZS Control 1C Altera FPGA Cyclone Series EP1C3T100 1376085 The second switch 亓I„ drive signal of noon 4; (C) is the current flowing through the primary side of the measurement; and (4) is the measurement of the secondary side of the current h The current of the electric current is shown in Fig. 9. In the case of full load, the (a) is the driving signal of the amount d/off 7L piece Sl (third switching element &); (b) To measure the driving signal of the seven components\; (C) to measure the current flowing through the primary side inductance 1 "·<·, and (d) to measure the current flowing through the secondary side inductance & 10 to FIG. 12, FIG. 10, FIG. 9 and FIG. 12 respectively show that the boost converter device 1 operates at 1 G% load, 8 G% load and % load, and (a) of each figure is the first measurement. The switching element drives the second switching element & driving with the driving number (b) of the third switching element (4) is to measure the voltage across the third switching element 1; and (4) is to measure the voltage across the capacitor Q. As shown in Figure 13, is the load current versus efficiency diagram, the efficiency at full load. Close to 82%, The highest efficiency is in the half load, and its efficiency can reach 84.3%. From the above experimental results, the new boost converter can be stably operated in the set specifications. In addition, in light load, unlike The other parent-replacement power supply architecture has the problem of reduced efficiency. In the above, the high-boost converter device of the present invention is composed of a charge pump 11 port sigma electric 12 sense, under the condition of low voltage and high current of 5V input' It can achieve nearly 10 times the boost ratio, and still has the enthalpy conversion efficiency at light load. The efficiency curve under the entire load operation range is relatively flat and can achieve high efficiency energy transfer in the full load range. The present invention is not limited by the scope of the invention, and the simple equivalent changes and modifications made by the scope of the invention and the description of the invention are still I S1 9 137608 5 is within the scope of the patent of the present invention.
【圖式簡單說明】 圖1是一示意圖，說明升壓型轉換器在連續導通模式 下的升壓比； 圖2是一電路圖，說明本發明高升壓轉換裝置之較佳 實施例； 圖3是一電路示意圖，說明該較佳實施例中電荷幫浦BRIEF DESCRIPTION OF THE DRAWINGS FIG. 1 is a schematic view showing a step-up ratio of a boost converter in a continuous conduction mode; FIG. 2 is a circuit diagram showing a preferred embodiment of the high boost converter of the present invention; Is a schematic circuit diagram illustrating the charge pump in the preferred embodiment
之第一開關元件與第三開關元件導通且第二開關元件不導 通時各元件的動作； 圖4是一電路示意圖，說明該較佳實施例中電荷幫浦 之第一開關元件與第三開關元件不導通且第二開關元件導 通時各元件的動作； 圖6为別疋一電路示意圖，說明該較佳實施例中 電壓籍制緩衝器保護第三開關元件之工作原理； 八f β圖8及圖9分別是一波形圖，說明該較佳實施例The operation of each element when the first switching element and the third switching element are turned on and the second switching element is not turned on; FIG. 4 is a circuit diagram illustrating the first switching element and the third switch of the charge pump in the preferred embodiment The operation of each component when the component is not conducting and the second switching component is turned on; FIG. 6 is a schematic diagram of another circuit, illustrating the working principle of the voltage switching device protecting the third switching component in the preferred embodiment; And FIG. 9 are respectively a waveform diagram illustrating the preferred embodiment.
4问升Μ轉換裝置操作於輕載、半載及全 之結果； 圖 1 0、1 1 λ 1及圖12分別是一波形圖，說明該較佳實 ::別為高升壓轉換裝置操作於1〇%載、8〇及湖 载之情況下量測之結果；及 圖 13 β - 疋一示意圖，說明為負載電流對效率之關係。 10 1376085 【主要元件符號說明】 1… .......高升壓轉換裝置 Lsn …· · …·電感 11 .· .......電荷幫浦 LP •.… — 次側電感 12·. .......耦合電感 Ls •.… …· ·二次側電感 13·· .......電壓箝制緩衝器 Llk 漏感 cs„ . .......電容 s' ····.. •…第一開關元件 Cb ·· .......升壓電容 A ·…· •…第二開關元件 C0·· .......輸出電容 · ...· ·.··第三開關元件 A、 h、D、、Db、Dsn V〇 ·…_ •…輸入電壓 .......—-tS； ....iA. iIj 一 flS ^ in 叛电歷 D0·· .......輸出一極體 i si 114 ask the upgrade converter to operate on light load, half load and all results; Figure 10, 1 1 λ 1 and Figure 12 are respectively a waveform diagram, indicating that the better:: Do not operate for high boost converter The results measured at 1〇% load, 8〇 and lake load; and Fig. 13 β-疋1 diagram, showing the relationship between load current and efficiency. 10 1376085 [Description of main component symbols] 1... .......High boost converter Lsn ...· ···Inductance 11 .· ....... Charge pump LP •.... — Secondary inductance 12·. .......Coupling inductance Ls •....···Second-side inductance 13·· ....... Voltage clamp buffer Llk leakage inductance cs„ . ....... Capacitor s' ····.. •...first switching element Cb ·· .......boost capacitor A ·...· •...second switching element C0··.......output capacitor · ...· ···· The third switching element A, h, D, Db, Dsn V〇·..._ •...input voltage............—tS; ....iA. iIj a flS ^ in rebel calendar D0·· .......output one pole i si 11