201025808 六、發明說明： 【發明所屬之技術領域】 本發明是有關於一種升壓轉換裝置，特別是指一種能 將低電壓轉成高電壓的高升壓轉換裝置。 【先前技術】 在許多的應用場合中常常需要將現有的低電壓升壓至 較高電壓以提供設備之需求，如汽車用之電力電子、具能 量回收之主動式燒機負載，其中以升壓型轉換器（Boost Converter)及升降壓型轉換器（Buck-Boost Converter)在市面 上使用較為普遍，但不論為升壓型轉換器或升降壓型轉換 器均存在一個無法達到高升壓比的缺點。 如圖1所示，升壓型轉換器在連續導通模式（CCM)下， 其升壓比t = 一]一，D為責任週期（duty cycle);理論上，雖201025808 VI. Description of the Invention: [Technical Field] The present invention relates to a boost converter, and more particularly to a high boost converter capable of converting a low voltage into a high voltage. [Prior Art] In many applications, it is often necessary to boost the existing low voltage to a higher voltage to provide equipment requirements, such as power electronics for automobiles, active burner loads with energy recovery, and boost Boost Converters and Buck-Boost Converters are commonly used in the market, but there is a high boost ratio that cannot be achieved by either a boost converter or a buck-boost converter. Disadvantages. As shown in Figure 1, in the continuous conduction mode (CCM), the boost converter has a boost ratio t = one], and D is the duty cycle; in theory, though
Vi 1 — Z) 然升壓比f沒有上限（如虛線部分），但實際上受限於元件寄 生效應以及控制器之能力，其升壓比達到4至5倍時將下 降（如實線部分），因此不可能無限制的提高升壓比。 以實際的應用而言，通常將升壓比設定於5倍左右， 若需要更高的升壓比，通常會採用兩級的升壓轉換器或是 採用返驰式轉換器（Flyback Converter)、前向式轉換器 (Forward Converter)之隔離式升壓轉換器。 為了使單級的升壓轉換器能達到高升壓比，因此一些 探討高升壓比的論文相繼被提出，其中有F. L. Luo提出的 羅式轉換器（Luo Converter)及其一系列的衍生架構，但其 201025808 架構均類似邱克轉換器（Cuk Converter)，以電容作為能量 轉移中繼站對其壽命之影響很大，不適合用於大電流大功 率場合。在 R_ Gules, L. L. Pfitscher 及 L. C. Franco 提出之 論文 “An interleaved boost DC-DC converter with large conversion ratio”中提出一種可達到高升壓比之升壓轉換器 架構，以一輸入24V輸出200V/2A實際電路來驗證所提架 構之可行性，此架構乃利用傳統升壓轉換器搭配電荷幫浦 (Charge Pump)以提高輸出電壓，但欲提高升壓比則須將電 荷幫浦量增加，即用更多的二極體和電容’且當電容容量® 增加後，電路於能量轉移時將會產生較大之湧浪電流，因 此電容值無法選擇過大且等效串連電阻（Equivalent Series Resistance，ESR)亦要很小；另外，若要達到高電流輸出貝1J 須採用多組並連方式以提高功率。 【發明内容】 有鑒於目前多採用兩級的升壓轉換器，並無一套能有 效提昇升壓比且電路精簡的高升壓轉換裝置，因此本發明 希望能提供一種能有效提昇升壓比且精簡電路的高升壓轉® 換裝置。 因此，本發明高升壓轉換裝置包括一電荷幫浦、一耦 合電感、一電壓箝制緩衝器及一輸出側。 該電荷幫浦用以接收一輸入電壓並使該輸入電壓升壓 ，具有一第一開關元件、一串接該第一開關元件之第二開 關元件、一連接該第一開關元件之一端的二極體及一跨接 該第一開關元件及該二極體之升壓電容。 201025808 該轉合電感電性連接該升壓電容及該第三開關元件， 並具有—一次側電感、一二次側電感及一漏感；該電壓箝 制緩衝器電性連接㈣纟電感a該電荷幫肖，具有一第三 開關7L件且箝制該第三開關元件之跨壓；該輸出側具有一 輸出一極體及一輪出電容，該輸出電容經該輸出二極體耦 接該電壓箝制緩衝器’用以儲存該_合電感之漏感所釋放 之能量。 藉此，該第一開關元件與該第三開關元件導通且該第 開關元件不導通時，該—次側電感產生—高於該輸入電 壓之激磁電壓，且由該輸出電容輸出該激磁電壓；及該第 一開關元件與該第三開關元件不導通且該第二開關元件導 通時’該二極趙因順偏而導通，該升Μ電容充電為該輸入 電壓，令先前儲存於該一次侧電感的能量被轉移至該二次 側電感並釋出能量對該輸出電容充電。 本發明高升屋轉換裝置是結合包括電荷幫浦、麵合電 感、電壓箝制緩衝器及輸出電容等元#，電路精簡，且能 在全負載範圍達到高效率之能量轉移。 【實施方式】 有關本發明之前述及其他技術内容、特點與功效，在 以下配合參考圖式之較佳實施例的詳細說明中，將可清楚 的呈現。 參閱圖2,本發明高升壓轉換裝置1之較佳實施例包含 電荷幫浦11、一耦合電感12及一電壓箝制緩衝器 (Snubber)13。 201025808 電荷幫浦11用以接收一輸入電壓匕並使該輸入電壓匕 升壓’具有一第一開關元件&(並聯有一二極體A)、一串接 第一開關元件孕之第二開關元件&(並聯有一二極體q)、一 連接第開關元件孕之一端的二極體及一跨接第一開關元 件&及二極體A之升壓電容Ci。 耦合電感12電性連接升壓電容Ci，並具有一一次側電 感、一二次側電感A及一漏感~ ;其中一次側電感^與 二次侧電感矣分別為耦合電感12的一次側自感與二次侧自 感，假設圈數比例„ = D為責任週期，則可以得到輸出 電壓與輸入電壓匕之關係式：圣=_^_ K n(l-D) + i 電壓箝制緩衝器13電性連接耦合電感12及電荷幫浦 11，具有一與第二開關元件⑲接之第三開關元件^並聯 有-二極體A)、一電容Q、一二極體4與一電感~ ,用以 箝制第三開關元件晃之跨壓。 由於輕合電感存在漏感&，漏感k的能量會累積 在第三開關元件4的寄生電容上，若此時電壓太高則會擊穿 第三開關it件U此’本發明針對此問題設計將 緩衝器U將漏感、之能量釋放至輸出側，當第三開關元件 3不導通時，漏感心的能量會經由二極體化對電容G充電 爾後電容Q所儲存之能量將經由電感k送至輸出側。 y侧具有-輸出二極體A及—輸出電容Q，輪出電容 合極體⑽接該電壓㈣緩衝器13，用以儲存麵 電感12漏感所釋放之之能量。 201025808 需說明的是，當高升壓轉換裝置1採多相（Multi-phase) 交錯控制以提高輸出功率聘，例如N相，只須加入N-1個 二極體A«即可，電路十分簡潔。 本發明所提架構之相關規格如表一所示。 表一 輸入電壓G 5V 輸出電壓匕（滿載） 48V 輸出電流总 1Α 切換頻率Λ 195kHz 耦合電感 一次侧電感ζρ ΙΟμΗ，T106-18 鐵心繞 8 圈 二次侧電感4 250μΗ，Τ106-18 鐵心繞 40 圈 輸入端電容ς_„ 1500μΡ 輸出端電容c。 ΙΟΟΟμΡ 升壓電容cb 33〇nF*3+22fiF MLCC 緩衝電容ci;I _，MLCC 緩衝二極體 3CTQ100 緩衝電感 ΙΟμΗ 二極體A STPS20L25 輸出二極體 3CTQ100 功率晶體& PHD96NQ03LT 功率晶體A PHD96NQ03LT 功率晶體4 IRL3705ZS 控制1C Altera FPGA Cyclone 系列 EP1C3T100 201025808 參閱圖3及圖4,說明電荷幫浦u之工作原理為方 便說明起見，圖中省略漏感、及電塵箝制緩衝器13的部分 元件（僅顯不第二開關元件&及二極趙〇)。Vi 1 — Z) However, there is no upper limit on the boost ratio f (such as the dotted line), but it is actually limited by the component parasitics and the controller's ability to reduce the boost ratio by 4 to 5 times (as in the solid line). Therefore, it is impossible to increase the boost ratio without limitation. In practical applications, the boost ratio is usually set at about 5 times. If a higher boost ratio is required, a two-stage boost converter or a flyback converter (Flyback Converter) is usually used. Isolated Converter Converter for Forward Converter. In order to achieve a high boost ratio for a single-stage boost converter, some papers discussing high boost ratios have been proposed, including FL Luo's Luo Converter and its series of derivative architectures. However, its 201025808 architecture is similar to the Cuk Converter. Capacitance as an energy transfer relay has a great impact on its lifetime and is not suitable for high current and high power applications. In the paper "An interleaved boost DC-DC converter with large conversion ratio" by R_ Gules, LL Pfitscher and LC Franco, a boost converter architecture with high boost ratio is proposed, with an input 24V output of 200V/2A. The circuit is used to verify the feasibility of the proposed architecture. This architecture uses a conventional boost converter with a charge pump to increase the output voltage. However, to increase the boost ratio, the charge pump must be increased. Multiple diodes and capacitors' and when the capacitance capacity is increased, the circuit will generate a large surge current during energy transfer, so the capacitor value cannot be selected too much and the equivalent series resistance (ESR) It must also be small; in addition, to achieve high current output, the 1J must be connected in multiple groups to increase power. SUMMARY OF THE INVENTION In view of the fact that a two-stage boost converter is currently used, there is no high boost converter that can effectively increase the boost ratio and the circuit is simplified. Therefore, the present invention is intended to provide an improved boost ratio. And the high-boost converter for the circuit is simplified. Accordingly, the high boost converter of the present invention includes a charge pump, a coupling inductor, a voltage clamp buffer, and an output side. The charge pump is configured to receive an input voltage and boost the input voltage, and has a first switching component, a second switching component connected in series with the first switching component, and a second terminal connected to the first switching component The pole body and a boosting capacitor bridging the first switching element and the diode. 201025808 The turn-in inductor is electrically connected to the boost capacitor and the third switching component, and has a primary side inductance, a secondary side inductance and a leakage inductance; the voltage clamping buffer is electrically connected (4) the inductance a The utility model has a third switch 7L and clamps the voltage across the third switching element; the output side has an output one body and a wheel discharging capacitor, and the output capacitor is coupled to the voltage clamping buffer via the output diode The device 'saves the energy released by the leakage inductance of the inductor. Thereby, when the first switching element and the third switching element are turned on and the first switching element is not turned on, the secondary side inductance generates an excitation voltage higher than the input voltage, and the excitation voltage is output by the output capacitor; And when the first switching element and the third switching element are non-conducting and the second switching element is turned on, the diode is turned on by the biasing capacitor, and the rising capacitor is charged to the input voltage, so that the first-side inductor is previously stored. Energy is transferred to the secondary side inductance and energy is released to charge the output capacitor. The high-rise house conversion device of the present invention combines a charge pump, a surface-sensing inductor, a voltage-clamping buffer, and an output capacitor, and the circuit is simplified, and energy transfer can be achieved at a high load range. The above and other technical contents, features, and advantages of the present invention will be apparent from the following detailed description of the preferred embodiments of the invention. Referring to Figure 2, a preferred embodiment of the high boost converter device 1 of the present invention includes a charge pump 11, a coupled inductor 12 and a voltage clamp buffer (Snubber) 13. 201025808 The charge pump 11 is configured to receive an input voltage 匕 and to boost the input voltage 具有 with a first switching element & (parallel with a diode A), a series of first switching element pregnant second The switching element & (parallel with a diode q), a diode connected to one end of the first switching element, and a boosting capacitor Ci connecting the first switching element & The coupled inductor 12 is electrically connected to the boosting capacitor Ci, and has a primary side inductance, a secondary side inductance A and a leakage inductance~; wherein the primary side inductance ^ and the secondary side inductance 矣 are the primary side of the coupled inductor 12, respectively. Self-inductance and secondary side self-inductance. Assuming that the ratio of turns is „ = D is the duty cycle, the relationship between the output voltage and the input voltage 匕 can be obtained: St = _ ^ _ K n (lD) + i Voltage clamp buffer 13 Electrically coupled to the coupled inductor 12 and the charge pump 11, having a third switching element connected to the second switching element 19 in parallel with a diode A), a capacitor Q, a diode 4 and an inductor ~ The voltage of the leakage inductance k is accumulated on the parasitic capacitance of the third switching element 4, and if the voltage is too high, the breakdown is performed. The present invention is directed to the problem that the buffer U is designed to release the leakage inductance and the energy to the output side. When the third switching element 3 is not turned on, the energy of the leakage sensation will pass through the diode to the capacitor. After G charges, the energy stored in capacitor Q will be sent to the output side via inductor k. - output diode A and - output capacitor Q, the output capacitor body (10) is connected to the voltage (four) buffer 13 for storing the energy released by the leakage inductance of the surface inductor 12. 201025808 It should be noted that when the high rise The pressure conversion device 1 adopts multi-phase interleaving control to increase the output power, for example, the N phase, and only needs to add N-1 diodes A«, the circuit is very simple. The architecture of the present invention is related. The specifications are shown in Table 1. Table 1 Input voltage G 5V Output voltage 匕 (full load) 48V Output current total 1Α Switching frequency Λ 195kHz Coupling inductor primary side inductance ζρ ΙΟμΗ, T106-18 core around 8 turns secondary side inductance 4 250μΗ, Τ106-18 The core is wound around 40 input terminals ς „„ 1500μΡ Output capacitor c. ΙΟΟΟμΡ boost capacitor cb 33〇nF*3+22fiF MLCC snubber capacitor ci; I _, MLCC buffer diode 3CTQ100 buffer inductor ΙΟμΗ diode A STPS20L25 output diode 3CTQ100 power crystal & PHD96NQ03LT power crystal A PHD96NQ03LT power crystal 4 IRL3705ZS Control 1C Altera FPGA Cyclone Series EP1C3T100 201025808 Referring to Figure 3 and Figure 4, the operation principle of the charge pump u is explained. For convenience of explanation, the leakage inductance and some components of the electric dust clamp buffer 13 are omitted. Not the second switching element & and the second pole Zhao Wei).
G 如圖3所示，假設此高升壓轉換裝置i工作於連續導 通模式下，於第-開關元轉通時的動作，升壓電容Μ 壓W ’第-開關元件聽第三開關元件、導通且第二開 關元件。不導通時，該一次側電感、產生一高於輸入電Μ 之激磁電壓，且由輸出電容〇。產生輸出電壓厂。。 如圖4所示，第一開關元件轉第三開關元料不導通 且第二開關元件0通時，輸出二極體&因順偏而導通，开 壓電容⑽為輸入電壓匕，令先前儲存於該一次側電感々 :能量被轉移至二次側電感4 ’並釋出能量對輸出電容c。充 電產生輸出電麼厂。。 〇As shown in FIG. 3, it is assumed that the high-boost converter device i operates in the continuous conduction mode, and the boosting capacitor voltage W' the first switching element listens to the third switching element when the first switching element is turned on. The second switching element is turned on. When not conducting, the primary side inductance produces an excitation voltage higher than the input voltage and is output by the output capacitance. Produce an output voltage factory. . As shown in FIG. 4, when the first switching element turns to the third switching element and the second switching element is not turned on, the output diode & is turned on by the forward bias, and the open capacitor (10) is the input voltage 匕, Previously stored in the primary side inductor 々: energy is transferred to the secondary side inductor 4' and the energy is discharged to the output capacitor c. Charging produces output power. . 〇
Q 參閱圖5及圖6,說明電壓箝制緩衝器"用以保護第 :=件…作原理;如圖5所示，當第三開關元件& 接圖漏，的能量會經由二極體對電容。充電； 送至輸出側。所不，電容^的所儲存之能量將經由電仏 測第圖二高升壓轉換裝置1操作於輕載情況下，⑷為量Q Referring to FIG. 5 and FIG. 6, the voltage-clamping buffer is used to protect the first:=... principle; as shown in FIG. 5, when the third switching element & drains, the energy will pass through the diode. For the capacitor. Charging; sent to the output side. No, the stored energy of the capacitor ^ will be operated by the electric high-voltage converter 1 in the case of light load, and (4) is the amount.
/貝J第開關疋件S f笛-pq Μ - AL 第二開關元徠 3)之驅動訊號；（b)為量測 &之驅動訊號；（c)為量測流經一 之電流；及⑷為量測流經二次側電感4之電流。電“ 測第圖二為二升：換於梅 1(第一開關兀件4)之驅動訊號；（b)為量測 $ 201025808 第 胃元件4之驅動訊號；（C)為量測流經一次側電感χ 之電流’及（d)為量測流經二次側電感Α之電流。/ (J) is the driving signal of the second switching element )3); (b) is the driving signal of the measurement & (c) is the current flowing through the measurement; And (4) is to measure the current flowing through the secondary side inductor 4. The electric drive “measures the second drive: the drive signal for the plum 1 (the first switch device 4); (b) the drive signal for the measurement of the $201025808 stomach component 4; (C) for the measurement flow The primary side inductance χ current ' and (d) is the current flowing through the secondary side inductor 量.
…圖9為高升壓轉換裝置1操作於滿載情況下，⑷為量 則第開關元件W第三開關元件&)之驅動訊號；(b)為量測 關元件&之驅動訊號；（c)為量測流經一次側電感z 之電流，及（d)為量測流經二次侧電感&之電流。 P 如圖10至圖12所示，圖10、圖11及圖12分別為高 升壓轉換裝置1操作於1G%載、8G%載及1GG%載之情況下 ’各圖的(a)為量測第一開關元件、(第三開關元件&)之驅動 訊號；(b)為量測第二開關元件&之驅動訊號；⑷為量測第 三開關元件&之跨壓；及（d)為量測電容^之跨壓。 如圖13所示，為負載電流對效率之關係圖，在滿載時 效率接近82%，效率最高點則是出現於半載，其效率可達 84.3%。由上述實驗結果可知，所提之新型升壓轉換器可穩 定地操作於所設定之規格。另外，在輕載方面，不像其他 乂換式電源架構有效率降低的困擾。 歸納上述，本發明高升壓轉換裝置丨係採用電荷幫浦 11結合辆合電12感所構成，在輸入5V之低壓大電流條件 下，可以達到接近10倍的升壓比，且於輕載時仍具有8〇% 轉換效率，整個負載操作範圍下的效率曲線較為平緩可 在全負載範圍達到高效率之能量轉移。 惟以上所述者，僅為本發明之較佳實施例而已，當不 能以此限定本發明實施之範圍，即大凡依本發明申請專利 範圍及發明說明内容所作之簡單的等效變化與修飾，皆仍 201025808 屬本發明專利涵蓋之範圍内。 【圖式簡單說明】 圖1是一示意圖’說明升壓型轉換器在連續導通模式 下的升壓比； ^ 圖2是一電路圖，說明本發明高升壓轉換裝置之較佳 實施例； 圖3是一電路示意圖，說明該較佳實施例中電荷幫浦 之第一開關元件與第三開關元件導通且第二開關元件不導 通時各元件的動作； 圖4疋一電路示意圖，說明該較佳實施例中電荷幫浦 之第一開關元件與第三開關元件不導通且第二開關元件導 通時各元件的動作； 圖5、圖6分別是一電路示意圖，說明該較佳實施例中 電壓箝制緩衝器保護第三開關元件之卫作原理； 圖7圖8及圖9分別是一波形圖，說明該較佳實施例 分別间升壓轉換裝置操作於輕載、半載及全載情況下量測 之結果； 圖10圖11及圖12分別是一波形圖，說明該較佳實 施例分別為高升壓轉換裝置操作於1〇%載、8〇%載及 載之情況下量測之結果；及 圖13是一示意圖’說明為負載電流對效率之關係。 201025808 【主要元件符號說明】 1… .......高升壓轉換裝置 LSn …" …·電感 11 ·· ……電荷幫浦 LP •…· ···· 次側電感 12·· .......耦合電感 Ls ….· …·二次側電感 13.· .......電壓箝制緩衝器 Llk cs„ . .......電容 S'…… •…第一開關元件 cb.. .......升壓電容 A •… •…第二開關元件 c0.. .......輸出電容 …· · •…第三開關元件 A、 D2、Dr Db、Dsn K · ·… •…輸入電壓 .......—-ts； ΛΛ -—蚀篮 ^ in …· W出電歷 D0.. .......輸出二極體 ❿ 11... Figure 9 is a high-boost converter 1 operating at full load, (4) is the driving signal of the third switching element & of the switching element W; (b) is the driving signal of the measuring component & c) to measure the current flowing through the primary side inductance z, and (d) to measure the current flowing through the secondary side inductance & P, as shown in FIG. 10 to FIG. 12, FIG. 10, FIG. 11, and FIG. 12 respectively show that the high-boost converter 1 operates at 1 G% load, 8 G% load, and 1 Gg load, respectively, and (a) of each figure is Measuring the driving signal of the first switching element, (the third switching element &); (b) measuring the driving signal of the second switching element & (4) measuring the voltage across the third switching element & (d) is to measure the voltage across the capacitor ^. As shown in Figure 13, for the load current vs. efficiency diagram, the efficiency is close to 82% at full load, and the highest efficiency is at half load, with an efficiency of 84.3%. It can be seen from the above experimental results that the proposed boost converter can be stably operated to the set specifications. In addition, in terms of light load, it is not as efficient as other 乂-switched power supply architectures. In summary, the high-boost converter device of the present invention is composed of a charge pump 11 combined with a 12-in-one sense of electric power. Under the condition of low-voltage and high-current input of 5V, a boost ratio of nearly 10 times can be achieved, and at a light load. It still has 8转换% conversion efficiency, and the efficiency curve under the entire load operation range is relatively flat, achieving high-efficiency energy transfer in the full load range. The above is only the preferred embodiment of the present invention, and the scope of the invention is not limited thereto, that is, the simple equivalent changes and modifications made by the scope of the invention and the description of the invention are All are still 201025808 within the scope of the invention patent. BRIEF DESCRIPTION OF THE DRAWINGS FIG. 1 is a schematic diagram showing the boosting ratio of a boost converter in a continuous conduction mode; FIG. 2 is a circuit diagram showing a preferred embodiment of the high boost converter of the present invention; 3 is a circuit diagram illustrating the operation of each component when the first switching element and the third switching element of the charge pump are turned on and the second switching element is not turned on in the preferred embodiment; FIG. 4 is a schematic diagram of the circuit, illustrating the comparison In the preferred embodiment, the first switching element and the third switching element of the charge pump are not turned on and the second switching element is turned on. FIG. 5 and FIG. 6 are respectively schematic diagrams showing the voltage in the preferred embodiment. The clamping buffer protects the working principle of the third switching element; FIG. 7 and FIG. 9 are respectively waveform diagrams illustrating the operation of the boost converter in the preferred embodiment under light load, half load and full load The results of the measurement; FIG. 10 and FIG. 12 are respectively a waveform diagram illustrating the preferred embodiment of the high-boost converter device operating at 1〇% load, 8〇% load and load, respectively. Result; and Figure 13 is A schematic diagram 'illustrated as the relationship between the load current efficiency. 201025808 [Description of main component symbols] 1... .......High boost converter LSn ..." ...·Inductance 11 ··...... Charge pump LP •...····· Secondary side inductor 12·· .......Coupling Inductance Ls ..... .... Secondary Side Inductance 13.. . . Voltage Clamping Buffer Llk cs„ . . . Capacitor S'... ...the first switching element cb........the boosting capacitor A •...the...the second switching element c0........the output capacitor...···...the third switching element A, D2, Dr Db, Dsn K · ·... •...Input voltage.......--ts; ΛΛ -—etch basket ^ in ...· W output calendar D0.. .......output two Polar body ❿ 11