TW202002458A - Interleaved wireless high frequency pulsed battery charger - Google Patents

Interleaved wireless high frequency pulsed battery charger Download PDF

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TW202002458A
TW202002458A TW107120247A TW107120247A TW202002458A TW 202002458 A TW202002458 A TW 202002458A TW 107120247 A TW107120247 A TW 107120247A TW 107120247 A TW107120247 A TW 107120247A TW 202002458 A TW202002458 A TW 202002458A
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power switch
current
present
resonance
charging
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TW107120247A
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TWI694656B (en
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莊英俊
張哲魁
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崑山科技大學
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Abstract

The invention relates to an interleaved wireless high frequency pulsed battery charger. Primarily, it has the advantages of simple circuit, low cost, small size and fast charging speed. Furthermore, it can achieve the maximum output current during transmission between coils, reduce the switching loss of a switch and improve the overall efficiency. It can also reduce the switching loss of diodes and achieve the function of interleaved charging, thus the battery module has enough time to fully rest to extend the service life of the battery, so as to increase the practicality and efficiency for the whole implementation.

Description

交錯型無線高頻脈衝式蓄電池充電器Interleaved wireless high-frequency pulse battery charger

本發明係有關於一種交錯型無線高頻脈衝式蓄電池充電器，尤其是指一種具有電路簡單、成本低、體積小與充電速度快等優點，且能讓線圈間傳輸時能夠達到最大輸出電流，並可降低開關的切換損失，提升整體效率，又可以降低二極體的切換損失，同時亦能達到交錯充電的功能，讓蓄電池模組有足夠的時間充分休息，以延長蓄電池的使用壽命，而在其整體施行使用上更增實用功效特性者。The present invention relates to an interleaved wireless high-frequency pulse battery charger, in particular, it has the advantages of simple circuit, low cost, small size and fast charging speed, and can achieve the maximum output current when transmitting between coils. It can reduce the switching loss of the switch, improve the overall efficiency, and reduce the switching loss of the diode. At the same time, it can also achieve the function of interleaved charging, so that the battery module has enough time to rest fully to extend the life of the battery. Those who have more practical functional characteristics in their overall application.

按，電力對於人們在日常生活中的重要性一直形影不離，近年來於人們身邊充滿了各式的電子產品，雖然對人們生活帶來更多便利，卻也更多了各種線材的纏繞；對於電子產品來說電源是不可缺少的動力來源，人們隨時都需要幫各種充電式之電子產品進行充電，如：行動電話，不過卻常會因忘記攜帶充電器或充電線，造成無法順利對該充電式電子產品進行充電之情況發生；使得若是未來所有的充電式產品皆能使用無線充電方式進行充電，使用者則不需要隨身攜帶充電器或充電線，僅需將該充電式產品置於商店內或公共場所中所提供的對應充電處上，或係將該充電式產品置於車輛上之對應充電處上，即可馬上進行充電，不會有因廠牌不同、充電孔規格不同即無法進行充電的現象產生。According to the press, the importance of electricity to people in daily life has been inseparable. In recent years, people have been filled with various types of electronic products. Although it brings more convenience to people’s lives, it also has more winding of various wires; for electronics The power source is an indispensable source of power for products. People need to charge all kinds of rechargeable electronic products at any time, such as mobile phones, but they often fail to carry the charger or charging cable, which makes it impossible to successfully charge the rechargeable electronics. The charging of the product occurs; so that if all future rechargeable products can be charged by wireless charging, users do not need to carry a charger or charging cable with them, just place the rechargeable product in the store or public At the corresponding charging point provided in the place, or by placing the rechargeable product on the corresponding charging point on the vehicle, you can immediately charge it, there will be no charging due to different brands and different charging hole specifications. The phenomenon occurs.

「無線充電」於近幾年快速發展崛起，在無線的時代裡，家裡將不需要插頭和延長線了，插頭的消失也降低了危險的發生，老舊的延長線造成電線走火而發生火災的情況也不再發生，家具的擺設也不再受限於插頭附近，人們行走時再沒有被線材絆倒的情況發生，整體環境上的美觀問題也一併解決。另，廁所、浴室等每個人每天都需要去的地方，因為濕氣重造成觸電的危險也跟著提高，若是以無線充電方式進行充電作業，即可防止觸電的危險情況問題發生，沒有插座將大大降低了觸電的危險，電子產品的防水設計也能提升，由於不需設置充電孔，其防水設計可以做得更加完善完美，無線化將減少充電線的成本和長久使用的消耗，使用上也更具便利性，也因為沒有充電線的限制，使得不小心拉扯線材的問題也解決了，同時亦由於不需設置充電孔，也沒有積灰塵和接觸不良的問題產生，令其在使用上更加的人性化。"Wireless charging" has developed rapidly in recent years. In the era of wireless, there will be no need for plugs and extension cords in the home. The disappearance of plugs also reduces the risk of occurrence. The old extension cords cause the wires to catch fire and cause fires. The situation no longer occurs, and the arrangement of furniture is no longer limited to the vicinity of the plug. When people walk, they no longer trip over the wire, and the aesthetic problems in the overall environment are also solved. In addition, toilets, bathrooms, and other places where everyone needs to go every day, because the risk of electric shock due to heavy moisture also increases, if the charging operation is performed by wireless charging, the problem of dangerous situations of electric shock can be prevented. The risk of electric shock is reduced, and the waterproof design of electronic products can also be improved. Since there is no need to provide a charging hole, the waterproof design can be made more perfect and perfect. Wireless will reduce the cost of the charging cable and the consumption of long-term use, and the use is also more It is convenient, and because there is no restriction on the charging cable, the problem of accidentally pulling the wire is also solved. At the same time, because there is no need to provide charging holes, there is no problem of dust and poor contact, which makes it more in use. Humanize.

又，隨著電動汽機車的時代來臨，若於路邊所設立的各個停車格設置有無線充電裝置，即可輕易的解決電動汽機車電池續航性的問題，也因為係利用無線式進行充電，不需使用者手動進行接線等操作，於使用上更具便利性同時更符合人性化；再，由於醫療方面所使用的人工心臟，其內部所裝設的電池於使用一段時間後，即需再次開刀更換該人工心臟所裝設的電池，對於病人來說係為一大折磨及傷害，亦會對病人的心理造成極大的影響，而有了無線充電後，病人將不需要再次開刀更換人工心臟之電池。Moreover, with the advent of the era of electric steam locomotives, if wireless charging devices are installed in the parking spaces established on the roadside, the problem of battery life of electric steam locomotives can be easily solved, because the wireless charging is used. There is no need for the user to manually perform wiring and other operations, which is more convenient and more humane in use; moreover, due to the artificial heart used in medical treatment, the battery installed inside it needs to be used again after a period of use The operation of replacing the battery installed in the artificial heart is a big torment and injury for the patient, and it will also have a great impact on the patient's psychology. With wireless charging, the patient will not need to operate the artificial heart again to replace the artificial heart Of the battery.

緣是，發明人有鑑於此，秉持多年該相關行業之豐富設計開發及實際製作經驗，針對現有之結構及缺失再予以研究改良，提供一種交錯型無線高頻脈衝式蓄電池充電器，以期達到更佳實用價值性之目的者。The reason is that in view of this, the inventors have maintained years of rich design development and practical production experience in the relevant industry, and then studied and improved the existing structure and deficiencies to provide a staggered wireless high-frequency pulse battery charger in order to achieve more The purpose of good practical value.

本發明之主要目的在於提供一種交錯型無線高頻脈衝式蓄電池充電器，主要係具有電路簡單、成本低、體積小與充電速度快等優點，且能讓線圈間傳輸時能夠達到最大輸出電流，並可降低開關的切換損失，提升整體效率，又可以降低二極體的切換損失，同時亦能達到交錯充電的功能，讓蓄電池模組有足夠的時間充分休息，以延長蓄電池的使用壽命，而在其整體施行使用上更增實用功效特性者。The main purpose of the present invention is to provide an interleaved wireless high-frequency pulse battery charger, which mainly has the advantages of simple circuit, low cost, small size and fast charging speed, and can achieve the maximum output current when transmitting between coils. It can reduce the switching loss of the switch, improve the overall efficiency, and reduce the switching loss of the diode. At the same time, it can also achieve the function of interleaved charging, so that the battery module has enough time to rest fully to extend the life of the battery. Those who have more practical functional characteristics in their overall application.

為令本發明所運用之技術內容、發明目的及其達成之功效有更完整且清楚的揭露，茲於下詳細說明之，並請一併參閱所揭之圖式及圖號：In order to make the technical content, the purpose of the invention and the effect achieved by the invention more complete and clear disclosure, it is described in detail below, and please refer to the drawings and figures disclosed:

首先，請參閱第一圖本發明之電路圖所示，本發明之充電器（１）主要係於所輸入之電壓

Figure 02_image098
正極端分別與濾波電容
Figure 02_image099
之第一端、第一功率開關
Figure 02_image101
之第一端及第三功率開關
Figure 02_image103
之第一端相連接，且令該第一功率開關
Figure 02_image101
之第二端與第四功率開關
Figure 02_image105
之第一端相連接，並令該第三功率開關
Figure 02_image106
之第二端與第二功率開關
Figure 02_image107
之第一端相連接，而輸入之該電壓
Figure 02_image098
負極端則分別與該濾波電容
Figure 02_image108
之第二端、該第四功率開關
Figure 02_image105
之第二端及該第二功率開關
Figure 02_image107
之第二端相連接，另於該第一功率開關
Figure 02_image101
之第二端與該第四功率開關
Figure 02_image105
之第一端之間連接有一次側共振電容之第一端，該一次側共振電容之第二端與一次側共振電感之第一端相連接，而該一次側共振電感之第二端則連接至該第三功率開關
Figure 02_image106
之第二端與該第二功率開關
Figure 02_image107
之第一端之間，對應該一次側共振電感設有二次側共振電感，於該二次側共振電感之第一端連接有二次側共振電容之第一端，該二次側共振電容之第二端分別與第一二極體
Figure 02_image117
之第二端及第二二極體
Figure 02_image119
之第一端相連接，而該第一二極體
Figure 02_image117
之第一端與第一蓄電池模組
Figure 02_image121
之第一端相連接，該第二二極體
Figure 02_image119
之第二端與第二蓄電池模組
Figure 02_image122
之第二端相連接，再令該二次側共振電感之第二端則分別與該第一蓄電池模組
Figure 02_image093
之第二端及該第二蓄電池模組
Figure 02_image124
之第一端相連接。First, please refer to the first figure, the circuit diagram of the present invention shows that the charger (1) of the present invention is mainly based on the input voltage
Figure 02_image098
Positive terminal and filter capacitor
Figure 02_image099
The first end, the first power switch
Figure 02_image101
The first end and the third power switch
Figure 02_image103
Connected to the first end of the first power switch
Figure 02_image101
The second terminal and the fourth power switch
Figure 02_image105
Connected to the first end of the third power switch
Figure 02_image106
The second terminal and the second power switch
Figure 02_image107
The first terminal is connected, and the input voltage
Figure 02_image098
The negative terminal is connected to the filter capacitor
Figure 02_image108
The second terminal and the fourth power switch
Figure 02_image105
The second terminal and the second power switch
Figure 02_image107
Connected to the second end of the first power switch
Figure 02_image101
The second terminal and the fourth power switch
Figure 02_image105
The first end of the primary resonance capacitor is connected between the first ends, the second end of the primary resonance capacitor is connected to the first end of the primary resonance inductor, and the second end of the primary resonance inductor is connected To the third power switch
Figure 02_image106
The second terminal and the second power switch
Figure 02_image107
Between the first ends, a secondary resonance inductor is provided corresponding to the primary resonance inductor. A first end of the secondary resonance capacitor is connected to the first end of the secondary resonance inductor. The secondary resonance capacitor The second end is connected to the first diode
Figure 02_image117
Second end and second diode
Figure 02_image119
The first end is connected, and the first diode
Figure 02_image117
The first end and the first battery module
Figure 02_image121
Connected to the first end, the second diode
Figure 02_image119
The second end and the second battery module
Figure 02_image122
The second end of the secondary side resonance inductor is connected to the first battery module
Figure 02_image093
The second end and the second battery module
Figure 02_image124
The first end is connected.

如此一來，使得本發明於操作使用上，其係輸入該電壓

Figure 02_image098
後，經由該第一功率開關
Figure 02_image101
、該第二功率開關
Figure 02_image107
、該第三功率開關
Figure 02_image103
及該第四功率開關
Figure 02_image105
所組成的全橋式轉換器，讓一次側的該第一功率開關
Figure 02_image101
、該第二功率開關
Figure 02_image107
、該第三功率開關
Figure 02_image103
及該第四功率開關
Figure 02_image105
能夠維持在零電壓切換，且該第一功率開關
Figure 02_image101
、該第二功率開關
Figure 02_image107
、該第三功率開關
Figure 02_image103
及該第四功率開關
Figure 02_image105
分為兩組輪流交替工作；對於由該第一功率開關
Figure 02_image101
、該第二功率開關
Figure 02_image107
、該第三功率開關
Figure 02_image103
及該第四功率開關
Figure 02_image105
所組成的全橋式轉換器來說，平均分擔的功率瓦特數較少，各個功率開關元件承受的功率瓦特數也較少，其轉換效率高。另，該充電器（１）的輸出功率很大，工作效率很高，因為該第一功率開關
Figure 02_image101
、該第二功率開關
Figure 02_image107
、該第三功率開關
Figure 02_image103
及該第四功率開關
Figure 02_image105
分為兩組輪流交替進行工作，一組有兩顆功率開關元件同時進行輸出功率，大約為單顆功率開關元件的兩倍輸出功率。該一次側共振電感與該二次側共振電感的串聯無線共振，係利用該一次側共振電感與該一次側共振電容兩元件特殊的共振特性，使該一次側共振電感與該一次側共振電容阻抗相互抵消，總阻抗Z為最小，讓流過的共振槽電流
Figure 02_image125
能維持最大電流進行無線傳輸，使無線傳輸至二次側依然為最大電流。In this way, the present invention is used for operation and it inputs the voltage
Figure 02_image098
After the first power switch
Figure 02_image101
、The second power switch
Figure 02_image107
3. The third power switch
Figure 02_image103
And the fourth power switch
Figure 02_image105
The full-bridge converter is composed of the first power switch on the primary side
Figure 02_image101
、The second power switch
Figure 02_image107
3. The third power switch
Figure 02_image103
And the fourth power switch
Figure 02_image105
Can be maintained at zero voltage switching, and the first power switch
Figure 02_image101
、The second power switch
Figure 02_image107
3. The third power switch
Figure 02_image103
And the fourth power switch
Figure 02_image105
Divided into two groups to work alternately; for the first power switch
Figure 02_image101
、The second power switch
Figure 02_image107
3. The third power switch
Figure 02_image103
And the fourth power switch
Figure 02_image105
For the composed full-bridge converter, the average shared power wattage is less, the power wattage of each power switching element is also less, and its conversion efficiency is high. In addition, the output power of the charger (1) is very large, and the working efficiency is very high, because the first power switch
Figure 02_image101
、The second power switch
Figure 02_image107
3. The third power switch
Figure 02_image103
And the fourth power switch
Figure 02_image105
It is divided into two groups to work alternately. One group has two power switching elements to output power at the same time, which is about twice the output power of a single power switching element. The series wireless resonance of the primary resonance inductor and the secondary resonance inductor utilizes the special resonance characteristics of the primary resonance inductor and the primary resonance capacitor to make the impedance of the primary resonance inductor and the primary resonance capacitor Mutually cancel each other, the total impedance Z is the smallest, allowing the resonance tank current to flow
Figure 02_image125
Can maintain the maximum current for wireless transmission, so that the wireless transmission to the secondary side is still the maximum current.

而同樣利用該二次側共振電感與該二次側共振電容兩元件串聯共振特性，讓總阻抗Z為最小阻抗，使二次側接收端共振槽電流流經過的

Figure 02_image127
電流為最大電流，進入由該第一二極體
Figure 02_image117
與該第二二極體
Figure 02_image119
所組成之交錯型整流電路，以對該第一蓄電池模組
Figure 02_image093
及該第二蓄電池模組
Figure 02_image124
進行交錯型充電。該交錯型整流電路能讓該第一蓄電池模組
Figure 02_image093
及該第二蓄電池模組
Figure 02_image124
有分時交錯充電的效果，於該第一蓄電池模組
Figure 02_image093
進行充電時，該第二蓄電池模組
Figure 02_image124
進行休息，反之，該第二蓄電池模組
Figure 02_image124
進行充電時，該第一蓄電池模組
Figure 02_image093
進行休息，以達到快速充電且省時的目的。Also, the series resonance characteristics of the secondary resonance inductor and the secondary resonance capacitor are used to make the total impedance Z the minimum impedance, so that the current flowing through the resonance tank of the secondary receiver
Figure 02_image127
The current is the maximum current and enters the first diode
Figure 02_image117
With the second diode
Figure 02_image119
The interleaved rectifier circuit composed of the first battery module
Figure 02_image093
And the second battery module
Figure 02_image124
Perform interleaved charging. The interleaved rectifier circuit enables the first battery module
Figure 02_image093
And the second battery module
Figure 02_image124
It has the effect of time-sharing staggered charging, which is in
Figure 02_image093
When charging, the second battery module
Figure 02_image124
Take a rest, otherwise, the second battery module
Figure 02_image124
When charging, the first battery module
Figure 02_image093
Take a break to achieve fast charging and save time.

請再參閱第二圖本發明之時序圖所示，以下將本發明分為六個工作模式進行分析討論：Please refer to the second diagram of the present invention as shown in the timing chart. The present invention is divided into six working modes for analysis and discussion:

工作模式一［

Figure 02_image129
］：請再一併參閱第三圖本發明之工作模式一示意圖所示，在
Figure 02_image131
期間，該第一功率開關
Figure 02_image101
與該第二功率開關
Figure 02_image107
之驅動訊號
Figure 02_image133
及
Figure 02_image135
為觸發，此時
Figure 02_image137
節點之電流
Figure 02_image139
為負電流，該電流
Figure 02_image140
即為該一次側共振電容、共振電感之電流
Figure 02_image141
，因此一次側之電流路徑為輸入電壓
Figure 02_image098
負極流進該第二功率開關
Figure 02_image107
，再流進該一次側共振電感、該一次側共振電容，由該第一功率開關
Figure 02_image101
流出回到輸入電壓
Figure 02_image098
正極。因為該一次側共振電感、該一次側共振電容與該二次側共振電感、該二次側共振電容產生串聯共振反應，所以可將能量傳送至二次側，而二次側的電流路徑為由該二次側共振電容、該二次側共振電感流進該第二蓄電池模組
Figure 02_image124
進行充電，由該第二二極體
Figure 02_image119
回到該二次側共振電容。當電流
Figure 02_image143
由負上升至零的時候，跳至下一個模式。而請再一併參閱第四圖本發明之工作模式一等效電路示意圖所示，則可得電路狀態方程式：Working mode one [
Figure 02_image129
]: Please refer to the third figure for a schematic diagram of the working mode of the present invention.
Figure 02_image131
During this period, the first power switch
Figure 02_image101
With the second power switch
Figure 02_image107
Drive signal
Figure 02_image133
and
Figure 02_image135
To trigger, at this time
Figure 02_image137
Node current
Figure 02_image139
Is a negative current, the current
Figure 02_image140
It is the current of the primary resonance capacitance and resonance inductance
Figure 02_image141
, So the current path on the primary side is the input voltage
Figure 02_image098
The negative electrode flows into the second power switch
Figure 02_image107
, Then flows into the primary resonance inductor, the primary resonance capacitor, and is switched by the first power switch
Figure 02_image101
Flow back to the input voltage
Figure 02_image098
positive electrode. Because the primary-side resonance inductance, the primary-side resonance capacitance and the secondary-side resonance inductance, and the secondary-side resonance capacitance produce a series resonance reaction, energy can be transferred to the secondary side, and the secondary side current path is due to The secondary side resonance capacitor and the secondary side resonance inductance flow into the second battery module
Figure 02_image124
To be charged by the second diode
Figure 02_image119
Return to the secondary resonance capacitance. Current
Figure 02_image143
When rising from negative to zero, jump to the next mode. And please refer to the fourth diagram of the working mode of the present invention as shown in the schematic diagram of an equivalent circuit, the circuit state equation can be obtained:

Figure 02_image144
Figure 02_image144

工作模式二［

Figure 02_image146
］：請再一併參閱第五圖本發明之工作模式二示意圖所示，在
Figure 02_image148
期間，該第一功率開關
Figure 02_image101
與該第二功率開關
Figure 02_image107
之驅動訊號
Figure 02_image133
及
Figure 02_image135
為觸發，此時
Figure 02_image137
節點之電流
Figure 02_image139
為正電流，該電流
Figure 02_image140
即為該一次側共振電容、共振電感之電流
Figure 02_image141
，因此一次側之電流路徑為輸入電壓
Figure 02_image098
正極流進該第一功率開關
Figure 02_image101
，再流進該一次側共振電容、該一次側共振電感，由該第二功率開關
Figure 02_image107
流出回到輸入電壓
Figure 02_image098
負極。因為該一次側共振電感、該一次側共振電容與該二次側共振電感、該二次側共振電容產生串聯共振反應，所以可將能量傳送至二次側，而二次側的電流路徑為由該二次側共振電感、該二次側共振電容流進該第一二極體
Figure 02_image117
再流進該第一蓄電池模組
Figure 02_image093
進行充電，之後流出到該二次側共振電感。當該第一功率開關
Figure 02_image101
與該第二功率開關
Figure 02_image107
切換的時候，跳至下一個模式。而請再一併參閱第六圖本發明之工作模式二等效電路示意圖所示，則可得電路狀態方程式：Working Mode 2 [
Figure 02_image146
]: Please refer to the fifth diagram of the working mode 2 of the present invention as shown in the schematic diagram.
Figure 02_image148
During this period, the first power switch
Figure 02_image101
With the second power switch
Figure 02_image107
Drive signal
Figure 02_image133
and
Figure 02_image135
To trigger, at this time
Figure 02_image137
Node current
Figure 02_image139
Is a positive current, the current
Figure 02_image140
It is the current of the primary resonance capacitance and resonance inductance
Figure 02_image141
, So the current path on the primary side is the input voltage
Figure 02_image098
The positive electrode flows into the first power switch
Figure 02_image101
, And then flow into the primary resonance capacitor and the primary resonance inductor, by the second power switch
Figure 02_image107
Flow back to the input voltage
Figure 02_image098
negative electrode. Because the primary-side resonance inductance, the primary-side resonance capacitance and the secondary-side resonance inductance, and the secondary-side resonance capacitance produce a series resonance reaction, energy can be transferred to the secondary side, and the secondary side current path is due to The secondary side resonance inductance and the secondary side resonance capacitance flow into the first diode
Figure 02_image117
Then flow into the first battery module
Figure 02_image093
After charging, it flows out to the secondary side resonance inductance. When the first power switch
Figure 02_image101
With the second power switch
Figure 02_image107
When switching, jump to the next mode. Please also refer to the sixth diagram of the working mode 2 equivalent circuit diagram of the present invention to obtain the circuit state equation:

Figure 02_image149
Figure 02_image149

工作模式三［

Figure 02_image151
］：請再一併參閱第七圖本發明之工作模式三示意圖所示，在
Figure 02_image153
期間，該第三功率開關
Figure 02_image106
與該第四功率開關
Figure 02_image105
進行零電壓切換，在驅動訊號
Figure 02_image154
及
Figure 02_image156
為觸發之前，先將該第三功率開關
Figure 02_image106
與該第四功率開關
Figure 02_image105
上的跨壓降為零，來減少開關切換損失，此時
Figure 02_image137
節點之電流
Figure 02_image139
為正電流，該電流
Figure 02_image140
即為該一次側共振電容、共振電感之電流
Figure 02_image141
，因此一次側之電流路徑為輸入電壓
Figure 02_image098
負極流進該第四功率開關
Figure 02_image105
，再流進該一次側共振電容、該一次側共振電感，由該第三功率開關
Figure 02_image106
流出回到輸入電壓
Figure 02_image098
正極。因為該一次側共振電感、該一次側共振電容與該二次側共振電感、該二次側共振電容產生串聯共振反應，所以可將能量傳送至二次側，而二次側的電流路徑為由該二次側共振電感、該二次側共振電容流進該第一二極體
Figure 02_image117
，再流進該第一蓄電池模組
Figure 02_image093
進行充電，之後流出到該二次側共振電感。當驅動訊號
Figure 02_image154
及
Figure 02_image156
觸發時，跳至下一個模式。而請再一併參閱第八圖本發明之工作模式三等效電路示意圖所示，則可得電路狀態方程式：Working Mode Three [
Figure 02_image151
]: Please refer to the seventh diagram of the working mode 3 of the present invention, as shown in
Figure 02_image153
During this period, the third power switch
Figure 02_image106
With the fourth power switch
Figure 02_image105
Perform zero-voltage switching and drive signals
Figure 02_image154
and
Figure 02_image156
Before triggering, the third power switch
Figure 02_image106
With the fourth power switch
Figure 02_image105
The voltage drop across is zero to reduce the switching loss, at this time
Figure 02_image137
Node current
Figure 02_image139
Is a positive current, the current
Figure 02_image140
It is the current of the primary resonance capacitance and resonance inductance
Figure 02_image141
, So the current path on the primary side is the input voltage
Figure 02_image098
The negative electrode flows into the fourth power switch
Figure 02_image105
, And then flow into the primary resonance capacitor and the primary resonance inductor, by the third power switch
Figure 02_image106
Flow back to the input voltage
Figure 02_image098
positive electrode. Because the primary-side resonance inductance, the primary-side resonance capacitance and the secondary-side resonance inductance, and the secondary-side resonance capacitance produce a series resonance reaction, energy can be transferred to the secondary side, and the secondary side current path is due to The secondary side resonance inductance and the secondary side resonance capacitance flow into the first diode
Figure 02_image117
, And then flow into the first battery module
Figure 02_image093
After charging, it flows out to the secondary side resonance inductance. When driving signal
Figure 02_image154
and
Figure 02_image156
When triggered, skip to the next mode. Please refer to the eighth diagram of the working mode three equivalent circuit diagram of the present invention again, then the circuit state equation can be obtained:

Figure 02_image158
Figure 02_image158

工作模式四［

Figure 02_image160
］：請再一併參閱第九圖本發明之工作模式四示意圖所示，在
Figure 02_image162
期間，該第三功率開關
Figure 02_image106
與該第四功率開關
Figure 02_image105
之驅動訊號
Figure 02_image154
及
Figure 02_image156
為觸發，此時
Figure 02_image137
節點之電流
Figure 02_image139
為正電流，該電流
Figure 02_image140
即為該一次側共振電容、共振電感之電流
Figure 02_image141
，因此一次側之電流路徑為輸入電壓
Figure 02_image098
負極流進該第四功率開關
Figure 02_image105
，再流進該一次側共振電容、該一次側共振電感，由該第三功率開關
Figure 02_image106
流出回到輸入電壓
Figure 02_image098
正極。因為該一次側共振電感、該一次側共振電容與該二次側共振電感、該二次側共振電容產生串聯共振反應，所以可將能量傳送至二次側，而二次側的電流路徑為由該二次側共振電感、該二次側共振電容流進該第一二極體
Figure 02_image117
，再流進該第一蓄電池模組
Figure 02_image093
進行充電，之後流出到該二次側共振電感。當電流
Figure 02_image143
由正下降至零的時候，跳至下一個模式。而請再一併參閱第十圖本發明之工作模式四等效電路示意圖所示，則可得電路狀態方程式：Working Mode 4 [
Figure 02_image160
]: Please refer to the ninth figure of the working mode of the present invention as shown in the fourth schematic diagram.
Figure 02_image162
During this period, the third power switch
Figure 02_image106
With the fourth power switch
Figure 02_image105
Drive signal
Figure 02_image154
and
Figure 02_image156
To trigger, at this time
Figure 02_image137
Node current
Figure 02_image139
Is a positive current, the current
Figure 02_image140
It is the current of the primary resonance capacitance and resonance inductance
Figure 02_image141
, So the current path on the primary side is the input voltage
Figure 02_image098
The negative electrode flows into the fourth power switch
Figure 02_image105
, And then flow into the primary resonance capacitor and the primary resonance inductor, by the third power switch
Figure 02_image106
Flow back to the input voltage
Figure 02_image098
positive electrode. Because the primary-side resonance inductance, the primary-side resonance capacitance and the secondary-side resonance inductance, and the secondary-side resonance capacitance produce a series resonance reaction, energy can be transferred to the secondary side, and the secondary side current path is due to The secondary side resonance inductance and the secondary side resonance capacitance flow into the first diode
Figure 02_image117
, And then flow into the first battery module
Figure 02_image093
After charging, it flows out to the secondary side resonance inductance. Current
Figure 02_image143
When it drops from positive to zero, jump to the next mode. And please refer to the tenth picture of the working mode 4 of the present invention as shown in the schematic diagram of the equivalent circuit, the circuit state equation can be obtained:

Figure 02_image163
Figure 02_image163

工作模式五［

Figure 02_image165
］：請再一併參閱第十一圖本發明之工作模式五示意圖所示，在
Figure 02_image167
期間，該第三功率開關
Figure 02_image106
與該第四功率開關
Figure 02_image105
之驅動訊號
Figure 02_image154
及
Figure 02_image156
為觸發，此時
Figure 02_image137
節點之電流
Figure 02_image139
為負電流，該電流
Figure 02_image140
即為該一次側共振電容、共振電感之電流
Figure 02_image141
，因此一次側之電流路徑為輸入電壓
Figure 02_image098
正極流進該第三功率開關
Figure 02_image106
，再流進該一次側共振電容、該一次側共振電感，由該第四功率開關
Figure 02_image105
流出回到輸入電壓
Figure 02_image098
負極。因為該一次側共振電感、該一次側共振電容與該二次側共振電感、該二次側共振電容產生串聯共振反應，所以可將能量傳送至二次側，而二次側的電流路徑為該二次側共振電感、該二次側共振電容流進該第二蓄電池模組
Figure 02_image124
進行充電，由該第二二極體
Figure 02_image119
流出回到該二次側共振電容。當該第三功率開關
Figure 02_image106
與該第四功率開關
Figure 02_image105
進行切換的時候，跳至下一個模式。而請再一併參閱第十二圖本發明之工作模式五等效電路示意圖所示，則可得電路狀態方程式：Working Mode Five [
Figure 02_image165
]: Please refer to the eleventh figure, the schematic diagram of the working mode 5 of the present invention is shown in
Figure 02_image167
During this period, the third power switch
Figure 02_image106
With the fourth power switch
Figure 02_image105
Drive signal
Figure 02_image154
and
Figure 02_image156
To trigger, at this time
Figure 02_image137
Node current
Figure 02_image139
Is a negative current, the current
Figure 02_image140
It is the current of the primary resonance capacitance and resonance inductance
Figure 02_image141
, So the current path on the primary side is the input voltage
Figure 02_image098
The positive electrode flows into the third power switch
Figure 02_image106
, And then flow into the primary resonance capacitor and the primary resonance inductor, by the fourth power switch
Figure 02_image105
Flow back to the input voltage
Figure 02_image098
negative electrode. Because the primary-side resonance inductance, the primary-side resonance capacitance and the secondary-side resonance inductance, and the secondary-side resonance inductance produce a series resonance reaction, energy can be transferred to the secondary side, and the secondary side current path is Secondary side resonance inductance and the secondary side resonance capacitance flow into the second battery module
Figure 02_image124
To be charged by the second diode
Figure 02_image119
It flows back to the secondary side resonance capacitor. When the third power switch
Figure 02_image106
With the fourth power switch
Figure 02_image105
When switching, jump to the next mode. And please refer to the twelfth figure of the working mode 5 equivalent circuit diagram of the present invention, the circuit state equation can be obtained:

Figure 02_image168
Figure 02_image168

工作模式六［

Figure 02_image170
］：請再一併參閱第十三圖本發明之工作模式六示意圖所示，在
Figure 02_image172
期間，該第一功率開關
Figure 02_image101
與該第二功率開關
Figure 02_image107
進行零電壓切換，在驅動訊號
Figure 02_image133
及
Figure 02_image135
為觸發之前，先將該第一功率開關
Figure 02_image101
與該第二功率開關
Figure 02_image107
上的跨壓降為零，來減少開關切換損失，此時
Figure 02_image137
節點之電流
Figure 02_image139
為負電流，該電流
Figure 02_image140
即為該一次側共振電容、共振電感之電流
Figure 02_image141
，因此一次側之電流路徑為輸入電壓
Figure 02_image098
負極流進該第二功率開關
Figure 02_image107
，再流進該一次側共振電容、該一次側共振電感，由該第一功率開關
Figure 02_image101
流出回到輸入電壓
Figure 02_image098
正極。因為該一次側共振電感、該一次側共振電容與該二次側共振電感、該二次側共振電容產生串聯共振反應，所以可將能量傳送至二次側，而二次側的電流路徑為由該二次側共振電感、該二次側共振電容流進該第二蓄電池模組
Figure 02_image124
進行充電，由該第二二極體
Figure 02_image119
流出回到該二次側共振電容。當該第一功率開關
Figure 02_image101
與該第二功率開關
Figure 02_image107
進行觸發時，跳回工作模式一。而請再一併參閱第十四圖本發明之工作模式六等效電路示意圖所示，則可得電路狀態方程式：Working Mode Six [
Figure 02_image170
]: Please refer to the thirteenth picture of the working mode of the present invention.
Figure 02_image172
During this period, the first power switch
Figure 02_image101
With the second power switch
Figure 02_image107
Perform zero-voltage switching and drive signals
Figure 02_image133
and
Figure 02_image135
Before triggering, the first power switch
Figure 02_image101
With the second power switch
Figure 02_image107
The voltage drop across is zero to reduce the switching loss, at this time
Figure 02_image137
Node current
Figure 02_image139
Is a negative current, the current
Figure 02_image140
It is the current of the primary resonance capacitance and resonance inductance
Figure 02_image141
, So the current path on the primary side is the input voltage
Figure 02_image098
The negative electrode flows into the second power switch
Figure 02_image107
, Then flows into the primary resonance capacitor and the primary resonance inductor, and is switched by the first power switch
Figure 02_image101
Flow back to the input voltage
Figure 02_image098
positive electrode. Because the primary-side resonance inductance, the primary-side resonance capacitance and the secondary-side resonance inductance, and the secondary-side resonance capacitance produce a series resonance reaction, energy can be transferred to the secondary side, and the secondary side current path is due to The secondary side resonance inductance and the secondary side resonance capacitance flow into the second battery module
Figure 02_image124
To be charged by the second diode
Figure 02_image119
It flows back to the secondary side resonance capacitor. When the first power switch
Figure 02_image101
With the second power switch
Figure 02_image107
When triggering, jump back to working mode one. And please refer to the fourteenth figure of the present invention, the working mode six equivalent circuit schematic diagram, you can get the circuit state equation:

Figure 02_image174
Figure 02_image174

將本發明利用IsSpice模擬軟體對電路進行模擬與參數分析，最後再配合硬體電路的測試，將實際量測所得的波形與數據，與軟體模擬之波形比對及分析，來比較兩者是否符合。設定各項參數如下：輸入電壓155V，輸入電流9.7A，該第一蓄電池模組

Figure 02_image093
額定電壓48V、額定電流14Ah，該第二蓄電池模組
Figure 02_image124
額定電壓48V、額定電流14Ah，切換頻率fs =40.5kHz，兩線圈距離20cm，一次側共振電感=202.4μH，一次側共振電容=0.1μF，一次側諧振頻率fr1 =35.3kHz，二次側共振電感=134.2μH，二次側共振電容=0.151μF，二次側諧振頻率fr2 =35.3kHz；以下以模擬波形與實作結果檢驗：The invention uses IsSpice simulation software to simulate and analyze the circuit, and finally cooperates with the hardware circuit test to compare and analyze the waveform and data obtained by the actual measurement with the waveform simulated by the software to compare whether the two meet . Set the parameters as follows: input voltage 155V, input current 9.7A, the first battery module
Figure 02_image093
Rated voltage 48V, rated current 14Ah, the second battery module
Figure 02_image124
Rated voltage of 48V, the rated current of 14Ah, the switching frequency f s = 40.5kHz, two-coil distance 20cm, the primary-side resonant inductor = 202.4μH, the primary-side resonant capacitor = 0.1μF, the primary-side resonant frequency f r1 = 35.3kHz, secondary side resonant inductor = 134.2μH, the secondary-side resonant capacitor = 0.151μF, the secondary side resonance frequency f r2 = 35.3kHz; the implementation of analog waveforms with the test results:

請再一併參閱第十五圖本發明之輸入電壓

Figure 02_image001
與輸入電流
Figure 02_image003
模擬波形圖、第十六圖本發明之輸入電壓
Figure 02_image005
與濾波電容電流
Figure 02_image006
模擬波形圖、第十七圖本發明之輸入電壓
Figure 02_image008
與電流
Figure 02_image009
模擬波形圖、第十八圖本發明之PWM驅動電路的方波信號
Figure 02_image011
,
Figure 02_image013
與
Figure 02_image015
,
Figure 02_image017
模擬波形圖、第十九圖本發明之PWM驅動電路的方波信號
Figure 02_image019
,
Figure 02_image020
與功率開關
Figure 02_image021
，
Figure 02_image023
上電壓
Figure 02_image025
,
Figure 02_image027
模擬波形圖、第二十圖本發明之PWM驅動電路的方波信號
Figure 02_image029
,
Figure 02_image030
與功率開關
Figure 02_image031
，
Figure 02_image033
上電壓
Figure 02_image035
,
Figure 02_image037
模擬波形圖所示，其皆可在接受範圍內。請再一併參閱第二十一圖本發明之功率開關
Figure 02_image039
上電壓
Figure 02_image041
與功率開關
Figure 02_image043
上電流
Figure 02_image044
模擬波形圖所示，可得知該第一功率開關
Figure 02_image176
與該第二功率開關
Figure 02_image177
確實是操作在零電壓切換導通狀態。請再一併參閱第二十二圖本發明之功率開關
Figure 02_image046
上電壓
Figure 02_image048
與開關
Figure 02_image050
上電流
Figure 02_image051
模擬波形圖所示，同樣可得知該第三功率開關
Figure 02_image178
與該第四功率開關
Figure 02_image179
確實也是操作在零電壓切換導通狀態。請再一併參閱第二十三圖本發明之電壓
Figure 02_image053
與電流
Figure 02_image055
模擬波形圖、第二十四圖本發明之一次測共振電容電壓
Figure 02_image057
與電流
Figure 02_image059
模擬波形圖、第二十五圖本發明之一次測共振電感電壓
Figure 02_image061
與電流
Figure 02_image063
模擬波形圖、第二十六圖本發明之二次測共振電感電壓
Figure 02_image064
與電流
Figure 02_image066
模擬波形圖、第二十七圖本發明之二次測共振電容電壓
Figure 02_image068
與電流
Figure 02_image070
模擬波形圖所示，其皆可在接受範圍內。請再一併參閱第二十八圖本發明之二極體電壓
Figure 02_image071
與電流
Figure 02_image073
模擬波形圖所示，可得知該第一二極體
Figure 02_image181
是操作在零電流切換狀態。請再一併參閱第二十九圖本發明之二極體電壓
Figure 02_image075
與電流
Figure 02_image077
模擬波形圖所示，可得知該第二二極體
Figure 02_image183
也是操作在零電流切換狀態。請再一併參閱第三十圖本發明之電壓
Figure 02_image079
與電流
Figure 02_image081
模擬波形圖、第三十一圖本發明之蓄電池充電電壓
Figure 02_image082
與蓄電池充電電流
Figure 02_image084
模擬波形圖、第三十二圖本發明之蓄電池充電電壓
Figure 02_image085
與蓄電池充電電流
Figure 02_image087
模擬波形圖、第三十三圖本發明之電壓
Figure 02_image088
與電壓
Figure 02_image089
模擬波形圖所示，其皆可在接受範圍內。請再一併參閱第三十四圖本發明之二次測共振電流
Figure 02_image090
與蓄電池充電電流
Figure 02_image091
、
Figure 02_image092
模擬波形圖所示，可得知充電器確實能產生交錯型脈衝式充電電流的功能。請再一併參閱第三十五圖本發明之蓄電池模組
Figure 02_image093
充電期間電壓曲線圖所示，該第一蓄電池模組
Figure 02_image093
充電期間端電壓由46.47V歷經1小時又40分鐘上升至60.99V，在此同時間該第一蓄電池模組
Figure 02_image093
的充電電流由8A下降至5A［請再一併參閱第三十六圖本發明之蓄電池模組
Figure 02_image093
充電期間電流曲線圖所示］。請再一併參閱第三十七圖本發明之蓄電池模組
Figure 02_image095
充電期間電壓曲線圖所示，該第二蓄電池模組
Figure 02_image185
充電期間端電壓由46.79V歷經1小時又40分鐘上升至60.24V，在此同時間該第二蓄電池模組
Figure 02_image186
的充電電流由8.1A下降至5.2A［請再一併參閱第三十八圖本發明之蓄電池模組
Figure 02_image097
充電期間電流曲線圖所示］。請再一併參閱第三十九圖本發明之蓄電池模組充電期間轉換效率曲線圖所示，可得知蓄電池模組於充電期間的最高充電效率為69%。Please also refer to the fifteenth figure of the input voltage of the present invention
Figure 02_image001
And input current
Figure 02_image003
Analog Waveform, Figure 16 The input voltage of the invention
Figure 02_image005
And filter capacitor current
Figure 02_image006
Analog Waveform, Figure 17 The input voltage of the invention
Figure 02_image008
With current
Figure 02_image009
Analog waveform diagram, the eighteenth figure of the square wave signal of the PWM drive circuit of the present invention
Figure 02_image011
,
Figure 02_image013
versus
Figure 02_image015
,
Figure 02_image017
Analog Waveform, Figure 19 Square Wave Signal of PWM Drive Circuit of the Present Invention
Figure 02_image019
,
Figure 02_image020
With power switch
Figure 02_image021
,
Figure 02_image023
Upper voltage
Figure 02_image025
,
Figure 02_image027
Analog waveform diagram, twentieth figure square wave signal of the PWM drive circuit of the present invention
Figure 02_image029
,
Figure 02_image030
With power switch
Figure 02_image031
,
Figure 02_image033
Upper voltage
Figure 02_image035
,
Figure 02_image037
As shown in the analog waveform diagram, they are all within the acceptable range. Please refer to Figure 21 for the power switch of the present invention
Figure 02_image039
Upper voltage
Figure 02_image041
With power switch
Figure 02_image043
Up current
Figure 02_image044
The simulation waveform diagram shows that the first power switch
Figure 02_image176
With the second power switch
Figure 02_image177
It is indeed operating at zero voltage to switch on state. Please also refer to the twenty-second figure of the power switch of the present invention
Figure 02_image046
Upper voltage
Figure 02_image048
With switch
Figure 02_image050
Up current
Figure 02_image051
As shown in the analog waveform diagram, the third power switch can also be known
Figure 02_image178
With the fourth power switch
Figure 02_image179
It is indeed operating in the zero-voltage switching conduction state. Please refer to Figure 23 for the voltage of the present invention
Figure 02_image053
With current
Figure 02_image055
Simulated waveform diagram, twenty-fourth diagram The primary measurement of the resonant capacitor voltage of the present invention
Figure 02_image057
With current
Figure 02_image059
Simulated waveform diagram, the twenty-fifth picture of the present invention, the primary measurement of resonance inductance voltage
Figure 02_image061
With current
Figure 02_image063
Simulated waveform diagram, the twenty-sixth figure of the present invention is the second measurement of resonance inductance voltage
Figure 02_image064
With current
Figure 02_image066
Analog waveform diagram, the twenty-seventh diagram of the present invention, the second measurement of the resonance capacitor voltage
Figure 02_image068
With current
Figure 02_image070
As shown in the analog waveform diagram, they are all within the acceptable range. Please also refer to the twenty-eighth figure for the diode voltage of the present invention
Figure 02_image071
With current
Figure 02_image073
The analog waveform shows that the first diode
Figure 02_image181
Is operating in the zero current switching state. Please also refer to Figure 29 for the diode voltage of the present invention
Figure 02_image075
With current
Figure 02_image077
The analog waveform shows that the second diode
Figure 02_image183
It is also operated in the zero current switching state. Please refer to Figure 30 for the voltage of the present invention
Figure 02_image079
With current
Figure 02_image081
Analog waveform diagram, the thirty-first diagram of the battery charging voltage of the present invention
Figure 02_image082
Charging current with battery
Figure 02_image084
Analog waveform diagram, the thirty-second picture of the battery charging voltage of the present invention
Figure 02_image085
Charging current with battery
Figure 02_image087
Analog waveform diagram, 33rd diagram of the voltage of the present invention
Figure 02_image088
With voltage
Figure 02_image089
As shown in the analog waveform diagram, they are all within the acceptable range. Please refer to the 34th picture again for the second measurement of the resonance current of the present invention
Figure 02_image090
Charging current with battery
Figure 02_image091
,
Figure 02_image092
As shown in the analog waveform diagram, it can be known that the charger can indeed generate the function of interleaved pulse charging current. Please also refer to the thirty-fifth figure of the battery module of the present invention
Figure 02_image093
The voltage curve during charging shows that the first battery module
Figure 02_image093
During charging, the terminal voltage rose from 46.47V to 60.99V after 1 hour and 40 minutes. At the same time, the first battery module
Figure 02_image093
The charging current of the battery is reduced from 8A to 5A
Figure 02_image093
Current graph during charging]. Please also refer to the thirty-seventh figure of the battery module of the present invention
Figure 02_image095
As shown in the voltage curve during charging, the second battery module
Figure 02_image185
During charging, the terminal voltage rose from 46.79V to 60.24V after 1 hour and 40 minutes, at the same time the second battery module
Figure 02_image186
The charging current of the battery is reduced from 8.1A to 5.2A [please refer to Figure 38 for the battery module of the present invention
Figure 02_image097
Current graph during charging]. Please also refer to the thirty-ninth figure as shown in the conversion efficiency curve diagram of the battery module of the present invention during charging. It can be known that the maximum charging efficiency of the battery module during charging is 69%.

藉由以上所述，本發明之使用實施說明可知，本發明與現有技術手段相較之下，本發明主要係具有電路簡單、成本低、體積小與充電速度快等優點，且能讓線圈間傳輸時能夠達到最大輸出電流，且功率開關操作於零電壓切換導通狀態，可降低開關的切換損失，提升整體效率，又可以降低二極體的切換損失；且利用弦波脈衝式電流對蓄電池模組進行快速充電，當一組蓄電池模組於充電期間另一組蓄電池模組則處於休息狀態，達到交錯充電的功能，讓蓄電池模組有足夠的時間充分休息，以延長蓄電池的使用壽命，而在其整體施行使用上更增實用功效特性者。According to the above description of the use and implementation of the present invention, compared with the prior art means, the present invention mainly has the advantages of simple circuit, low cost, small size and fast charging speed, etc. The maximum output current can be reached during transmission, and the power switch is operated in the zero-voltage switching conduction state, which can reduce the switching loss of the switch, improve the overall efficiency, and can also reduce the switching loss of the diode; and use the sine wave pulse current to the battery mode The group is charged quickly. When one group of battery modules is at rest during charging, the other group of battery modules is at rest to achieve the function of interleaved charging, so that the battery modules have enough time to rest fully to extend the life of the battery. Those who have more practical functional characteristics in their overall application.

然而前述之實施例或圖式並非限定本發明之產品結構或使用方式，任何所屬技術領域中具有通常知識者之適當變化或修飾，皆應視為不脫離本發明之專利範疇。However, the foregoing embodiments or drawings do not limit the product structure or usage of the present invention. Any appropriate changes or modifications by those with ordinary knowledge in the technical field should be regarded as not departing from the patent scope of the present invention.

綜上所述，本發明實施例確能達到所預期之使用功效，又其所揭露之具體構造，不僅未曾見諸於同類產品中，亦未曾公開於申請前，誠已完全符合專利法之規定與要求，爰依法提出發明專利之申請，懇請惠予審查，並賜准專利，則實感德便。In summary, the embodiments of the present invention can indeed achieve the expected use effect, and the specific structure disclosed by it has not only not been seen in similar products, nor has it been disclosed before application, and has fully complied with the provisions of the Patent Law To meet the requirements, I filed an application for a patent for invention according to law, and pleaded for the review, and granted the patent.

（１）‧‧‧充電器(1) Charger

第一圖：本發明之電路圖Figure 1: The circuit diagram of the present invention

第二圖：本發明之時序圖Figure 2: The timing diagram of the present invention

第三圖：本發明之工作模式一示意圖Figure 3: A schematic diagram of the working mode of the present invention

第四圖：本發明之工作模式一等效電路示意圖Figure 4: Schematic diagram of an equivalent circuit of the working mode of the present invention

第五圖：本發明之工作模式二示意圖Figure 5: Schematic diagram of the second working mode of the present invention

第六圖：本發明之工作模式二等效電路示意圖Figure 6: Schematic diagram of the equivalent circuit of working mode 2 of the present invention

第七圖：本發明之工作模式三示意圖Figure 7: Schematic diagram of the third working mode of the present invention

第八圖：本發明之工作模式三等效電路示意圖Figure 8: Schematic diagram of the equivalent mode of the working mode 3 of the present invention

第九圖：本發明之工作模式四示意圖Ninth figure: Four schematic diagrams of the working mode of the present invention

第十圖：本發明之工作模式四等效電路示意圖Figure 10: Schematic diagram of the equivalent circuit of the working mode 4 of the present invention

第十一圖：本發明之工作模式五示意圖Figure 11: Schematic diagram of the working mode 5 of the present invention

第十二圖：本發明之工作模式五等效電路示意圖Figure 12: Schematic diagram of the equivalent mode of the working mode 5 of the present invention

第十三圖：本發明之工作模式六示意圖Figure 13: Six schematic diagrams of the working mode of the present invention

第十四圖：本發明之工作模式六等效電路示意圖Figure 14: Schematic diagram of six equivalent circuits of the working mode of the present invention

第十五圖：本發明之輸入電壓

Figure 02_image001
與輸入電流
Figure 02_image003
模擬波形圖Figure 15: Input voltage of the present invention
Figure 02_image001
And input current
Figure 02_image003
Analog waveform

第十六圖：本發明之輸入電壓

Figure 02_image005
與濾波電容電流
Figure 02_image006
模擬波形圖Figure 16: Input voltage of the present invention
Figure 02_image005
And filter capacitor current
Figure 02_image006
Analog waveform

第十七圖：本發明之輸入電壓

Figure 02_image008
與電流
Figure 02_image009
模擬波形圖Figure 17: Input voltage of the present invention
Figure 02_image008
With current
Figure 02_image009
Analog waveform

第十八圖：本發明之PWM驅動電路的方波信號

Figure 02_image011
,
Figure 02_image013
與
Figure 02_image015
,
Figure 02_image017
模擬波形圖Figure 18: Square wave signal of the PWM drive circuit of the present invention
Figure 02_image011
,
Figure 02_image013
versus
Figure 02_image015
,
Figure 02_image017
Analog waveform

第十九圖：本發明之PWM驅動電路的方波信號

Figure 02_image019
,
Figure 02_image020
與功率開關
Figure 02_image021
，
Figure 02_image023
上電壓
Figure 02_image025
,
Figure 02_image027
模擬波形圖Figure 19: Square wave signal of the PWM drive circuit of the present invention
Figure 02_image019
,
Figure 02_image020
With power switch
Figure 02_image021
,
Figure 02_image023
Upper voltage
Figure 02_image025
,
Figure 02_image027
Analog waveform

第二十圖：本發明之PWM驅動電路的方波信號

Figure 02_image029
,
Figure 02_image030
與功率開關
Figure 02_image031
，
Figure 02_image033
上電壓
Figure 02_image035
,
Figure 02_image037
模擬波形圖Figure 20: Square wave signal of the PWM drive circuit of the present invention
Figure 02_image029
,
Figure 02_image030
With power switch
Figure 02_image031
,
Figure 02_image033
Upper voltage
Figure 02_image035
,
Figure 02_image037
Analog waveform

第二十一圖：本發明之功率開關

Figure 02_image039
上電壓
Figure 02_image041
與功率開關
Figure 02_image043
上電流
Figure 02_image044
模擬波形圖Figure 21: Power switch of the present invention
Figure 02_image039
Upper voltage
Figure 02_image041
With power switch
Figure 02_image043
Up current
Figure 02_image044
Analog waveform

第二十二圖：本發明之功率開關

Figure 02_image046
上電壓
Figure 02_image048
與開關
Figure 02_image050
上電流
Figure 02_image051
模擬波形圖Figure 22: The power switch of the present invention
Figure 02_image046
Upper voltage
Figure 02_image048
With switch
Figure 02_image050
Up current
Figure 02_image051
Analog waveform

第二十三圖：本發明之電壓

Figure 02_image053
與電流
Figure 02_image055
模擬波形圖Figure 23: The voltage of the present invention
Figure 02_image053
With current
Figure 02_image055
Analog waveform

第二十四圖：本發明之一次測共振電容電壓

Figure 02_image057
與電流
Figure 02_image059
模擬波形圖Figure 24: The primary measurement of the resonance capacitor voltage of the present invention
Figure 02_image057
With current
Figure 02_image059
Analog waveform

第二十五圖：本發明之一次測共振電感電壓

Figure 02_image061
與電流
Figure 02_image063
模擬波形圖Twenty-fifth picture: the primary measurement of the resonance inductor voltage of the present invention
Figure 02_image061
With current
Figure 02_image063
Analog waveform

第二十六圖：本發明之二次測共振電感電壓

Figure 02_image064
與電流
Figure 02_image066
模擬波形圖Figure 26: Secondary resonance inductor voltage measured by the present invention
Figure 02_image064
With current
Figure 02_image066
Analog waveform

第二十七圖：本發明之二次測共振電容電壓

Figure 02_image068
與電流
Figure 02_image070
模擬波形圖Figure 27: The secondary measurement of the resonant capacitor voltage of the present invention
Figure 02_image068
With current
Figure 02_image070
Analog waveform

第二十八圖：本發明之二極體電壓

Figure 02_image071
與電流
Figure 02_image073
模擬波形圖Figure 28: Diode voltage of the present invention
Figure 02_image071
With current
Figure 02_image073
Analog waveform

第二十九圖：本發明之二極體電壓

Figure 02_image075
與電流
Figure 02_image077
模擬波形圖Figure 29: Diode voltage of the present invention
Figure 02_image075
With current
Figure 02_image077
Analog waveform

第三十圖：本發明之電壓

Figure 02_image079
與電流
Figure 02_image081
模擬波形圖Figure 30: The voltage of the present invention
Figure 02_image079
With current
Figure 02_image081
Analog waveform

第三十一圖：本發明之蓄電池充電電壓

Figure 02_image082
與蓄電池充電電流
Figure 02_image084
模擬波形圖Figure 31: Battery charging voltage of the present invention
Figure 02_image082
Charging current with battery
Figure 02_image084
Analog waveform

第三十二圖：本發明之蓄電池充電電壓

Figure 02_image085
與蓄電池充電電流
Figure 02_image087
模擬波形圖Figure 32: Battery charging voltage of the present invention
Figure 02_image085
Charging current with battery
Figure 02_image087
Analog waveform

第三十三圖：本發明之電壓

Figure 02_image088
與電壓
Figure 02_image089
模擬波形圖Figure 33: Voltage of the invention
Figure 02_image088
With voltage
Figure 02_image089
Analog waveform

第三十四圖：本發明之二次測共振電流

Figure 02_image090
與蓄電池充電電流
Figure 02_image091
、
Figure 02_image092
模擬波形圖Figure 34: The secondary resonance current of the present invention
Figure 02_image090
Charging current with battery
Figure 02_image091
,
Figure 02_image092
Analog waveform

第三十五圖：本發明之蓄電池模組

Figure 02_image093
充電期間電壓曲線圖Figure 35: Battery module of the present invention
Figure 02_image093
Voltage curve during charging

第三十六圖：本發明之蓄電池模組

Figure 02_image093
充電期間電流曲線圖Figure 36: Battery module of the present invention
Figure 02_image093
Current curve during charging

第三十七圖：本發明之蓄電池模組

Figure 02_image095
充電期間電壓曲線圖Figure 37: Battery module of the present invention
Figure 02_image095
Voltage curve during charging

第三十八圖：本發明之蓄電池模組

Figure 02_image097
充電期間電流曲線圖Figure 38: Battery module of the present invention
Figure 02_image097
Current curve during charging

第三十九圖：本發明之蓄電池模組充電期間轉換效率曲線圖Figure 39: Conversion efficiency curve diagram of the battery module of the present invention during charging

(1)‧‧‧充電器 (1)‧‧‧Charger

Claims (1)

一種交錯型無線高頻脈衝式蓄電池充電器，其主要係令充電器於所輸入之電壓
Figure 03_image098
正極端分別與濾波電容
Figure 03_image099
之第一端、第一功率開關
Figure 03_image101
之第一端及第三功率開關
Figure 03_image103
之第一端相連接，且令該第一功率開關
Figure 03_image101
之第二端與第四功率開關
Figure 03_image105
之第一端相連接，並令該第三功率開關
Figure 03_image106
之第二端與第二功率開關
Figure 03_image107
之第一端相連接，而輸入之該電壓
Figure 03_image098
負極端則分別與該濾波電容
Figure 03_image108
之第二端、該第四功率開關
Figure 03_image105
之第二端及該第二功率開關
Figure 03_image107
之第二端相連接，另於該第一功率開關
Figure 03_image101
之第二端與該第四功率開關
Figure 03_image105
之第一端之間連接有一次側共振電容之第一端，該一次側共振電容之第二端與一次側共振電感之第一端相連接，而該一次側共振電感之第二端則連接至該第三功率開關
Figure 03_image106
之第二端與該第二功率開關
Figure 03_image107
之第一端之間，對應該一次側共振電感設有二次側共振電感，於該二次側共振電感之第一端連接有二次側共振電容之第一端，該二次側共振電容之第二端分別與第一二極體
Figure 03_image117
之第二端及第二二極體
Figure 03_image119
之第一端相連接，而該第一二極體
Figure 03_image117
之第一端與第一蓄電池模組
Figure 03_image121
之第一端相連接，該第二二極體
Figure 03_image119
之第二端與第二蓄電池模組
Figure 03_image122
之第二端相連接，再令該二次側共振電感之第二端則分別與該第一蓄電池模組
Figure 03_image093
之第二端及該第二蓄電池模組
Figure 03_image124
之第一端相連接。A staggered wireless high-frequency pulse battery charger, which mainly makes the charger input the voltage
Figure 03_image098
Positive terminal and filter capacitor
Figure 03_image099
The first end, the first power switch
Figure 03_image101
The first end and the third power switch
Figure 03_image103
Connected to the first end of the first power switch
Figure 03_image101
The second terminal and the fourth power switch
Figure 03_image105
Connected to the first end of the third power switch
Figure 03_image106
The second terminal and the second power switch
Figure 03_image107
The first terminal is connected, and the input voltage
Figure 03_image098
The negative terminal is connected to the filter capacitor
Figure 03_image108
The second terminal and the fourth power switch
Figure 03_image105
The second terminal and the second power switch
Figure 03_image107
Connected to the second end of the first power switch
Figure 03_image101
The second terminal and the fourth power switch
Figure 03_image105
The first end of the primary resonance capacitor is connected between the first ends, the second end of the primary resonance capacitor is connected to the first end of the primary resonance inductor, and the second end of the primary resonance inductor is connected To the third power switch
Figure 03_image106
The second terminal and the second power switch
Figure 03_image107
Between the first ends, a secondary resonance inductor is provided corresponding to the primary resonance inductor. A first end of the secondary resonance capacitor is connected to the first end of the secondary resonance inductor. The secondary resonance capacitor The second end is connected to the first diode
Figure 03_image117
Second end and second diode
Figure 03_image119
The first end is connected, and the first diode
Figure 03_image117
The first end and the first battery module
Figure 03_image121
Connected to the first end, the second diode
Figure 03_image119
The second end and the second battery module
Figure 03_image122
The second end of the secondary side resonance inductor is connected to the first battery module
Figure 03_image093
The second end and the second battery module
Figure 03_image124
The first end is connected.
TW107120247A 2018-06-12 2018-06-12 Interleaved wireless high frequency pulsed battery charger TWI694656B (en)

Priority Applications (1)

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Cited By (2)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
TWI736260B (en) * 2020-05-14 2021-08-11 崑山科技大學 Single switch with zero voltage switching wireless charger with interleaved high-frequency sine-wave pulse-charging methodology used in dual-battery energy storage systems for light electric vehicles
TWI789783B (en) * 2021-06-09 2023-01-11 崑山科技大學 High-efficiency dual-sided llc resonant wireless charger for electric vehicles

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CN206353727U (en) * 2016-03-04 2017-07-25 中惠创智无线供电技术有限公司 Point-to-point wireless power coil coupling model and point-to-point wireless power supply system
TWI568130B (en) * 2016-03-08 2017-01-21 Staggered high frequency chord pulse electric vehicle charger

Cited By (2)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
TWI736260B (en) * 2020-05-14 2021-08-11 崑山科技大學 Single switch with zero voltage switching wireless charger with interleaved high-frequency sine-wave pulse-charging methodology used in dual-battery energy storage systems for light electric vehicles
TWI789783B (en) * 2021-06-09 2023-01-11 崑山科技大學 High-efficiency dual-sided llc resonant wireless charger for electric vehicles

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