TWI736260B - Single switch with zero voltage switching wireless charger with interleaved high-frequency sine-wave pulse-charging methodology used in dual-battery energy storage systems for light electric vehicles - Google Patents

Single switch with zero voltage switching wireless charger with interleaved high-frequency sine-wave pulse-charging methodology used in dual-battery energy storage systems for light electric vehicles Download PDF

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TWI736260B
TWI736260B TW109116037A TW109116037A TWI736260B TW I736260 B TWI736260 B TW I736260B TW 109116037 A TW109116037 A TW 109116037A TW 109116037 A TW109116037 A TW 109116037A TW I736260 B TWI736260 B TW I736260B
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battery
primary side
capacitor
side resonance
current
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TW109116037A
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TW202143621A (en
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莊英俊
潘建良
范淑媛
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崑山科技大學
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Abstract

The invention discloses single switch with zero voltage switching wireless charger with interleaved high-frequency sine-wave pulse-charging methodology used in dual-battery energy storage systems for light electric vehicle, which has advantages of simple circuit, low cost and small volume, the switch operates with zero voltage switching through choosing adequate device parameter, switching frequency and resonant frequency, the loss during switching can also be reduced on account of the operation of zero voltage switching. Further, the dual-battery has sufficient time to break because of the dual-battery charges in rotation during charging and thus enhance performance of the battery.

Description

輕型電動載具雙蓄電池組之單開關零電壓切換無線交錯式高頻弦波脈衝式充電器Single-switch zero-voltage switching wireless interleaved high-frequency sine wave pulse charger for light electric vehicles with dual battery packs

本發明係有關於一種輕型電動載具雙蓄電池組之單開關零電壓切換無線交錯式高頻弦波脈衝式充電器，尤其是指一種具有電路簡單、成本低、體積小等優點，且經由選擇適當的元件參數、切換頻率以及共振頻率，使切換開關操作於零電壓切換，由於操作在於零電壓切換的關係，減少切換開關切換過程的損失，提升整體效率，並由於在對蓄電池充電過程中，係為一組充電一組休息之輪流充電的方式，讓蓄電池有足夠的時間休息，來增加蓄電池的使用壽命，而在其整體施行使用上更增實用功效特性者。The present invention relates to a single-switch zero-voltage switching wireless interleaved high-frequency sine wave pulse type charger for light-duty electric vehicles with dual battery packs, in particular, it refers to a simple circuit, low cost, small size, etc., and through selection Appropriate component parameters, switching frequency and resonance frequency enable the switch to operate at zero voltage switching. Since the operation is based on zero voltage switching, the loss of the switching process of the switch is reduced, the overall efficiency is improved, and because the battery is charged, It is a charging method that is a group of charging and a group of rest, so that the battery has enough time to rest, to increase the service life of the battery, and it is more practical and functional in its overall implementation.

按，現今科技的日新月異，提高了人類生活的品質，但也因為快速的發展，帶給人類更多負面的傷害及危害；由於科技的進步與世界人口快速成長，因此能源的消耗與環境污染問題一直是現今社會的重點議題，而石油是目前使用最為廣泛的代表性能源，但石油開採及加工卻是非常昂貴與汙染的，大量開採石油，不僅加速地球環境汙染，且更造成地球的氣候改變，使得全球溫度不斷提高，不斷地侵蝕危害著地球上所居住的所有生物。By the way, today’s rapid advances in science and technology have improved the quality of human life, but because of the rapid development, it has brought more negative harm and harm to mankind. Due to the advancement of science and technology and the rapid growth of the world’s population, energy consumption and environmental pollution problems It has always been a key issue in today’s society. Petroleum is currently the most widely used representative energy source, but oil extraction and processing are very expensive and polluting. Large-scale extraction of oil will not only accelerate the pollution of the earth’s environment, but also cause changes in the earth’s climate. , Which makes the global temperature continue to rise, and continues to erode and endanger all living creatures on the earth.

在這樣的危害地球環境下，使得人類環保意識抬頭，也不斷的開發新型態的能源，以用來替代石油燃料開採過程與製造時所產生的危害與污染；其中，電能不僅可以做任何型態的方式儲存，也是一種可以替代石油的能源，且其可以在不破壞環境的方式下的產生，同時不會像石油燃燒時會產生廢氣造成負面影響，讓電能具有更佳的環保及安全性，使得電能若能在生產後加以好好保存，其將會是一種取之不盡的能源，所以電能的使用與保存將是一大課題，同時在電力電子相關領域方面中，該如何提升電力轉換效率且又同時降低成本和損失，已成為現今科學家及各大科技產業中所重視的其中一個環節。Under such a hazard to the earth environment, human environmental awareness has risen, and new types of energy are constantly being developed to replace the hazards and pollution generated during the extraction and manufacturing of petroleum fuels; among them, electric energy can not only be used in any type. It is also a kind of energy that can replace petroleum, and it can be produced in a way that does not damage the environment. At the same time, it will not produce negative effects like waste gas when petroleum is burned, so that electric energy has better environmental protection and safety. , So that if electric energy can be well preserved after production, it will be an inexhaustible energy source. Therefore, the use and preservation of electric energy will be a major issue. At the same time, in the field of power electronics, how to improve power conversion Efficiency while reducing costs and losses at the same time has become one of the links that today's scientists and major science and technology industries attach importance to.

緣是，發明人有鑑於此，秉持多年該相關行業之豐富設計開發及實際製作經驗，針對現有之結構及缺失再予以研究改良，提供一種輕型電動載具雙蓄電池組之單開關零電壓切換無線交錯式高頻弦波脈衝式充電器，以期達到更佳實用價值性之目的者。In view of this, the inventor, with years of rich experience in design, development and actual production in the related industry, researched and improved the existing structure and deficiencies, and provided a single-switch zero-voltage switching wireless for light-duty electric vehicles with dual battery packs. Interleaved high frequency sine wave pulse type charger, in order to achieve the purpose of better practical value.

本發明之主要目的在於提供一種輕型電動載具雙蓄電池組之單開關零電壓切換無線交錯式高頻弦波脈衝式充電器，主要係具有電路簡單、成本低、體積小等優點，且經由選擇適當的元件參數、切換頻率以及共振頻率，使切換開關操作於零電壓切換，由於操作在於零電壓切換的關係，減少切換開關切換過程的損失，提升整體效率，並由於在對蓄電池充電過程中，係為一組充電一組休息之輪流充電的方式，讓蓄電池有足夠的時間休息，來增加蓄電池的使用壽命，而在其整體施行使用上更增實用功效特性者。The main purpose of the present invention is to provide a single-switch zero-voltage switching wireless interleaved high-frequency sine wave pulse charger for light-duty electric vehicles with dual battery packs, which mainly has the advantages of simple circuit, low cost, and small size. Appropriate component parameters, switching frequency and resonance frequency enable the switch to operate at zero voltage switching. Since the operation is based on zero voltage switching, the loss of the switching process of the switch is reduced, the overall efficiency is improved, and because the battery is charged, It is a charging method that is a group of charging and a group of rest, so that the battery has enough time to rest, to increase the service life of the battery, and it is more practical and functional in its overall implementation.

為令本發明所運用之技術內容、發明目的及其達成之功效有更完整且清楚的揭露，茲於下詳細說明之，並請一併參閱所揭之圖式及圖號：In order to make the technical content, the purpose of the invention and the effects achieved by the present invention more complete and clear, the following detailed descriptions are given, and please refer to the disclosed drawings and figure numbers together:

首先，請參閱第一圖本發明之電路圖及第二圖本發明之電路方塊示意圖所示，本發明之充電器(1)主要係於輸入電源

Figure 02_image094
之正極分別連接濾波電容
Figure 02_image096
之第一端及扼流電感
Figure 02_image009
之第一端，該扼流電感
Figure 02_image009
之第二端分別連接有切換開關
Figure 02_image015
之第一端、分流電容
Figure 02_image019
之第一端及一次側共振電容
Figure 02_image025
之第一端，該一次側共振電容
Figure 02_image025
之第二端連接有一次側共振電感
Figure 02_image031
之第一端，而於該輸入電源
Figure 02_image098
之負極則分別連接濾波電容
Figure 02_image096
之第二端、切換開關
Figure 02_image015
之第二端、分流電容
Figure 02_image019
之第二端及一次側共振電感
Figure 02_image031
之第二端，而對應該一次側共振電感
Figure 02_image031
設有二次側共振電感
Figure 02_image099
，該二次側共振電感
Figure 02_image100
之第一端連接二次側共振電容
Figure 02_image101
之第一端，該二次側共振電容
Figure 02_image101
之第二端分別連接第一整流二極體
Figure 02_image049
之正極、第二整流二極體
Figure 02_image103
之負極，該第一整流二極體
Figure 02_image049
之負極連接第一蓄電池
Figure 02_image061
之正極，該第二整流二極體
Figure 02_image103
之正極連接第二蓄電池
Figure 02_image080
之負極，該二次側共振電感
Figure 02_image100
之第二端則與該第一蓄電池
Figure 02_image061
之負極及該第二蓄電池
Figure 02_image104
之正極相連接。 First of all, please refer to the first diagram of the circuit diagram of the present invention and the second diagram of the circuit block diagram of the present invention. The charger (1) of the present invention is mainly based on the input power supply.
Figure 02_image094
The positive poles are respectively connected to the filter capacitor
Figure 02_image096
The first terminal and choke inductor
Figure 02_image009
The first end, the choke inductor
Figure 02_image009
The second end is connected with a switch
Figure 02_image015
The first terminal, shunt capacitor
Figure 02_image019
The first end and primary side resonant capacitor
Figure 02_image025
The first terminal, the primary side resonant capacitor
Figure 02_image025
The second end is connected to the primary side resonance inductance
Figure 02_image031
The first end, and the input power
Figure 02_image098
The negative pole is connected to the filter capacitor
Figure 02_image096
The second terminal, switch
Figure 02_image015
The second terminal, shunt capacitor
Figure 02_image019
The second end and primary side resonance inductance
Figure 02_image031
The second end corresponds to the primary side resonance inductance
Figure 02_image031
Equipped with secondary side resonance inductance
Figure 02_image099
, The secondary side resonance inductance
Figure 02_image100
The first terminal is connected to the secondary side resonant capacitor
Figure 02_image101
The first terminal, the secondary side resonant capacitor
Figure 02_image101
The second ends are respectively connected to the first rectifier diode
Figure 02_image049
The positive pole, the second rectifier diode
Figure 02_image103
The negative pole, the first rectifier diode
Figure 02_image049
The negative pole is connected to the first battery
Figure 02_image061
The positive pole, the second rectifier diode
Figure 02_image103
The positive terminal is connected to the second battery
Figure 02_image080
The negative pole of the secondary side resonance inductance
Figure 02_image100
The second end is connected to the first battery
Figure 02_image061
The negative electrode and the second battery
Figure 02_image104
The positive pole is connected.

如此一來，使得該充電器(1)於操作使用上，其係於一次側將該一次側共振電容

Figure 02_image025
與該一次側共振電感
Figure 02_image031
串聯成為共振槽，使得該一次側共振電容
Figure 02_image025
與該一次側共振電感
Figure 02_image031
阻抗互相抵消，令總阻抗為最小，讓流過該一次側共振電容
Figure 02_image025
之電流
Figure 02_image105
能維持最大電流進行無線電力轉換，使無線轉換至二次側依然為最大電流；而該二次側共振電感
Figure 02_image100
同樣與該二次側共振電容
Figure 02_image101
串聯成為共振槽，令總阻抗為最小，讓流過該二次側共振電容
Figure 02_image101
之電流
Figure 02_image106
為最大電流，進入由該第一整流二極體
Figure 02_image049
與該第二整流二極體
Figure 02_image103
兩組半波整流所組成之倍壓整流電路，使得具有兩倍壓之輸出效果，以對該第一蓄電池
Figure 02_image107
及該第二蓄電池
Figure 02_image108
進行充電，而半波整流會將正弦波的負半週截掉，只有正半週工作，讓蓄電池在正半週時以大電流充電，負半週時不充電進行休息，而該充電器(1)於輸出端係由該第一蓄電池
Figure 02_image107
及該第二蓄電池
Figure 02_image108
串聯組成，使得利用該切換開關
Figure 02_image015
進行切換，當該第一蓄電池
Figure 02_image107
充電時，該第二蓄電池
Figure 02_image108
進行休息，該第二蓄電池
Figure 02_image108
充電時，則該第一蓄電池
Figure 02_image107
進行休息，以達到快速充電且省時的目的。 In this way, the charger (1) is used in operation, and it is connected to the primary side and the primary side resonant capacitor
Figure 02_image025
Resonant inductance with the primary side
Figure 02_image031
Connected in series to become a resonant tank, so that the primary side resonant capacitor
Figure 02_image025
Resonant inductance with the primary side
Figure 02_image031
The impedances cancel each other out, so that the total impedance is minimized, so that the primary side resonant capacitor flows through
Figure 02_image025
The current
Figure 02_image105
Can maintain the maximum current for wireless power conversion, so that the wireless conversion to the secondary side is still the maximum current; and the secondary side resonance inductance
Figure 02_image100
Same with the secondary side resonant capacitor
Figure 02_image101
Connected in series to form a resonance tank to minimize the total impedance and allow the secondary side resonance capacitor to flow
Figure 02_image101
The current
Figure 02_image106
Is the maximum current that enters the first rectifier diode
Figure 02_image049
With the second rectifier diode
Figure 02_image103
The voltage doubler rectifier circuit composed of two sets of half-wave rectifiers has a double voltage output effect to the first battery
Figure 02_image107
And the second battery
Figure 02_image108
For charging, half-wave rectification will cut off the negative half of the sine wave, and only the positive half of the cycle will work, allowing the battery to be charged with high current during the positive half of the cycle, and rest without charging during the negative half of the cycle, and the charger ( 1) The first battery at the output
Figure 02_image107
And the second battery
Figure 02_image108
Series composition, making use of the switch
Figure 02_image015
Switch, when the first battery
Figure 02_image107
When charging, the second battery
Figure 02_image108
Take a break, the second battery
Figure 02_image108
When charging, the first battery
Figure 02_image107
Take a break to achieve fast charging and save time.

另，該充電器(1)之該扼流電感

Figure 02_image009
的電感值要足夠大，以將輸入電源
Figure 02_image098
轉換成直流電流源
Figure 02_image013
，且電流漣波很小；又，該充電器(1)由於需操作在高頻的環境下，使得該第一整流二極體
Figure 02_image049
及該第二整流二極體
Figure 02_image103
所需要的逆向恢復時間必須相當快，令該第一整流二極體
Figure 02_image049
及該第二整流二極體
Figure 02_image103
可以選擇蕭特基［Schittky］二極體或是快速恢復［Fast Recovery］二極體來因應。 In addition, the choke inductor of the charger (1)
Figure 02_image009
The inductance value should be large enough to transfer the input power
Figure 02_image098
Convert to DC current source
Figure 02_image013
, And the current ripple is very small; In addition, the charger (1) needs to operate in a high-frequency environment, so that the first rectifier diode
Figure 02_image049
And the second rectifier diode
Figure 02_image103
The required reverse recovery time must be quite fast so that the first rectifier diode
Figure 02_image049
And the second rectifier diode
Figure 02_image103
You can choose Schittky [Schittky] diode or fast recovery [Fast Recovery] diode to respond.

而依據該切換開關

Figure 02_image015
及該第一整流二極體
Figure 02_image049
、該第二整流二極體
Figure 02_image103
的ON/OFF狀態，與
Figure 02_image109
之大小，可以將該充電器(1)在一個切換週期
Figure 02_image111
的動作，分成六個工作模式，於分析此電路前，先做以下三項理想設置： And according to the switch
Figure 02_image015
And the first rectifier diode
Figure 02_image049
, The second rectifier diode
Figure 02_image103
The ON/OFF state of
Figure 02_image109
The size of the charger (1) can be used in a switching cycle
Figure 02_image111
The action is divided into six working modes. Before analyzing this circuit, make the following three ideal settings:

1.電路操作在穩壓狀態下。1. The circuit is operating in a regulated state.

2.該切換開關

Figure 02_image015
及該第一整流二極體
Figure 02_image049
、該第二整流二極體
Figure 02_image103
設為理想元件，即不考慮該該切換開關
Figure 02_image015
之順向導通電壓和該第一整流二極體
Figure 02_image049
、該第二整流二極體
Figure 02_image103
的反向恢復特性。 2. The switch
Figure 02_image015
And the first rectifier diode
Figure 02_image049
, The second rectifier diode
Figure 02_image103
Set as an ideal component, that is, the switch is not considered
Figure 02_image015
The forward conduction voltage and the first rectifier diode
Figure 02_image049
, The second rectifier diode
Figure 02_image103
The reverse recovery characteristics.

3.該扼流電感

Figure 02_image009
的電感值足夠大，使該輸入電源
Figure 02_image098
可視為理想直流電流源。 3. The choke inductor
Figure 02_image009
The inductance value is large enough to make the input power
Figure 02_image098
It can be regarded as an ideal DC current source.

該充電器(1)各工作模式等效線性電路以及主要元件時序波形如下，請再一併參閱第三圖本發明之主要元件時序波形圖所示，其中，一次側共振電容電流

Figure 02_image113
等於一次側共振電感電流
Figure 02_image114
，且二次側共振電容電流
Figure 02_image115
等於二次側共振電感電流
Figure 02_image117
： The equivalent linear circuit of each working mode of the charger (1) and the timing waveforms of the main components are as follows. Please refer to the third diagram as shown in the timing waveform diagram of the main components of the present invention. Among them, the primary side resonance capacitor current
Figure 02_image113
Equal to the primary side resonance inductor current
Figure 02_image114
, And the secondary side resonance capacitor current
Figure 02_image115
Equal to the secondary side resonance inductor current
Figure 02_image117
:

工作模式一［

Figure 02_image119
］：請再一併參閱第四圖本發明之工作模式一等效線性電路圖所示，在
Figure 02_image121
時，該切換開關
Figure 02_image015
之驅動訊號
Figure 02_image005
由低電位轉換為高電位，此時該切換開關
Figure 02_image015
切換導通，因為一次側共振電感電流
Figure 02_image114
大於扼流電感電流
Figure 02_image013
，
Figure 02_image109
小於零，所以電流反向流經該切換開關
Figure 02_image015
，切換開關電流
Figure 02_image123
小於零，而該分流電容
Figure 02_image019
無電流通過，該一次側共振電感電流
Figure 02_image114
為正值，流經該一次側共振電容
Figure 02_image025
對其進行充電，一次側共振電容電壓
Figure 02_image125
上升，當
Figure 02_image109
等於零的同時，該切換開關電流
Figure 02_image123
也上升至等於零，此時該一次側共振電感電流
Figure 02_image114
大於零，與二次側進行共振，該第一整流二極體
Figure 02_image049
導通，並且對該第一蓄電池
Figure 02_image107
充電，當該切換開關
Figure 02_image015
升至大於零時進入工作模式二。 Working mode one [
Figure 02_image119
]: Please also refer to the fourth figure as shown in the equivalent linear circuit diagram of the working mode of the present invention.
Figure 02_image121
When the toggle switch
Figure 02_image015
Drive signal
Figure 02_image005
From low potential to high potential, at this time the switch
Figure 02_image015
Switching on, because the primary side resonant inductor current
Figure 02_image114
Greater than choke inductor current
Figure 02_image013
,
Figure 02_image109
Less than zero, so the current flows through the switch in the reverse direction
Figure 02_image015
, Switch current
Figure 02_image123
Less than zero, and the shunt capacitor
Figure 02_image019
No current flows, the primary side resonance inductor current
Figure 02_image114
Positive value, flowing through the primary side resonant capacitor
Figure 02_image025
Charge it, the primary side resonance capacitor voltage
Figure 02_image125
Rise when
Figure 02_image109
At the same time as zero, the switch current
Figure 02_image123
Also rises to equal to zero, at this time the primary side resonance inductor current
Figure 02_image114
Greater than zero, resonates with the secondary side, the first rectifier diode
Figure 02_image049
Turn on, and the first battery
Figure 02_image107
Charging, when the toggle switch
Figure 02_image015
When it rises to greater than zero, it enters working mode two.

工作模式二［

Figure 02_image126
］：請再一併參閱第五圖本發明之工作模式二等效線性電路圖所示，在
Figure 02_image128
時，該切換開關
Figure 02_image015
仍為導通，此時
Figure 02_image109
大於零，電流流經該切換開關
Figure 02_image015
，該切換開關電流
Figure 02_image123
為大於零，該分流電容
Figure 02_image019
仍無電流通過，該一次側共振電感電流
Figure 02_image114
仍為正值且持續下降，在流經該一次側共振電容
Figure 02_image025
對其進行充電，該一次側共振電容電壓
Figure 02_image125
上升，當該一次側共振電容電壓
Figure 02_image125
上升到達峰值時，該一次側共振電感電流
Figure 02_image114
降至零點，此時該一次側共振電感電流
Figure 02_image114
大於零，與二次側進行共振，該第一整流二極體
Figure 02_image049
導通，並且對該第一蓄電池
Figure 02_image107
充電，當該一次側共振電感電流
Figure 02_image114
降至零時，進入工作模式三。 Working mode two [
Figure 02_image126
]: Please also refer to the fifth figure as shown in the equivalent linear circuit diagram of the second working mode of the present invention.
Figure 02_image128
When the toggle switch
Figure 02_image015
Is still on, at this time
Figure 02_image109
Greater than zero, current flows through the switch
Figure 02_image015
, The current of the switch
Figure 02_image123
Is greater than zero, the shunt capacitor
Figure 02_image019
Still no current flows, the primary side resonance inductor current
Figure 02_image114
Is still positive and continues to decrease, and the resonant capacitor flows through the primary side
Figure 02_image025
Charge it, the primary side resonance capacitor voltage
Figure 02_image125
Rise, when the primary side resonance capacitor voltage
Figure 02_image125
When it rises to the peak value, the primary side resonance inductor current
Figure 02_image114
Down to zero, at this time the primary side resonance inductor current
Figure 02_image114
Greater than zero, resonates with the secondary side, the first rectifier diode
Figure 02_image049
Turn on, and the first battery
Figure 02_image107
Charging, when the primary side resonance inductor current
Figure 02_image114
When it drops to zero, it enters working mode three.

工作模式三［

Figure 02_image130
］：請再一併參閱第六圖本發明之工作模式三等效線性電路圖所示，在
Figure 02_image132
時，該切換開關
Figure 02_image015
仍為導通，此時該一次側共振電感電流
Figure 02_image114
由零開始下降，該一次側共振電容電壓
Figure 02_image125
由峰值開始下降，因該一次側共振電感電流
Figure 02_image114
電流小於該扼流電感電流
Figure 02_image013
，
Figure 02_image109
仍維持大於零，所以電流流經該切換開關
Figure 02_image015
，該切換開關電流
Figure 02_image123
為正值且漸漸上升，該分流電容
Figure 02_image019
上仍無電流通過，由於該一次側共振電感電流
Figure 02_image114
小於零，與二次側進行共振，該第二整流二極體
Figure 02_image103
導通，並且對該第二蓄電池
Figure 02_image108
充電，當該切換開關
Figure 02_image015
之驅動訊號
Figure 02_image005
由高電位變為低電位時，進入工作模式四。 Working Mode Three [
Figure 02_image130
]: Please also refer to the sixth figure as shown in the three equivalent linear circuit diagram of the working mode of the present invention.
Figure 02_image132
When the toggle switch
Figure 02_image015
Is still on, at this time the primary side resonance inductor current
Figure 02_image114
Decline from zero, the primary side resonance capacitor voltage
Figure 02_image125
It starts to decrease from the peak value, because the primary side resonance inductor current
Figure 02_image114
The current is less than the choke inductor current
Figure 02_image013
,
Figure 02_image109
Remains greater than zero, so the current flows through the switch
Figure 02_image015
, The current of the switch
Figure 02_image123
Is positive and gradually rises, the shunt capacitor
Figure 02_image019
There is still no current passing through, due to the resonant inductor current on the primary side
Figure 02_image114
Less than zero, resonating with the secondary side, the second rectifier diode
Figure 02_image103
Turn on, and the second battery
Figure 02_image108
Charging, when the toggle switch
Figure 02_image015
Drive signal
Figure 02_image005
When changing from high potential to low potential, it enters into working mode four.

工作模式四［

Figure 02_image134
］：請再一併參閱第七圖本發明之工作模式四等效線性電路圖所示，在
Figure 02_image136
時，該切換開關
Figure 02_image015
之驅動訊號
Figure 02_image005
由高電位變為低電位，該一次側共振電感電流
Figure 02_image114
仍小於該扼流電感電流
Figure 02_image013
，
Figure 02_image109
仍維持大於零，因此該切換開關
Figure 02_image015
截止，所以電流流經該分流電容
Figure 02_image019
，所以分流電容電流
Figure 02_image138
仍為正值，該一次側共振電容電壓
Figure 02_image125
由正值降至負值，該一次側共振電感電流
Figure 02_image114
由負開始上升，由於該一次側共振電感電流
Figure 02_image114
小於零，與二次側進行共振，該第二整流二極體
Figure 02_image103
導通，並且對該第二蓄電池
Figure 02_image108
充電，當該一次側共振電感電流
Figure 02_image114
上升至零點時，進入工作模式五。 Working Mode Four [
Figure 02_image134
]: Please also refer to the seventh figure shown in the working mode four equivalent linear circuit diagram of the present invention.
Figure 02_image136
When the toggle switch
Figure 02_image015
Drive signal
Figure 02_image005
From high potential to low potential, the primary side resonance inductor current
Figure 02_image114
Still less than the choke inductor current
Figure 02_image013
,
Figure 02_image109
Remains greater than zero, so the toggle switch
Figure 02_image015
Cut off, so the current flows through the shunt capacitor
Figure 02_image019
, So the shunt capacitor current
Figure 02_image138
Is still positive, the primary side resonance capacitor voltage
Figure 02_image125
From the positive value to the negative value, the primary side resonance inductor current
Figure 02_image114
Starting from negative to rise, due to the primary side resonance inductance current
Figure 02_image114
Less than zero, resonating with the secondary side, the second rectifier diode
Figure 02_image103
Turn on, and the second battery
Figure 02_image108
Charging, when the primary side resonance inductor current
Figure 02_image114
When it rises to zero, it enters working mode 5.

工作模式五［

Figure 02_image140
］：請再一併參閱第八圖本發明之工作模式五等效線性電路圖所示，在
Figure 02_image142
時，該切換開關
Figure 02_image015
仍為截止，該一次側共振電感電流
Figure 02_image114
仍小於該扼流電感電流
Figure 02_image013
，
Figure 02_image109
仍大於零，電流流經該分流電容
Figure 02_image019
，所以該分流電容電流
Figure 02_image138
仍為正值，該一次側共振電容電壓
Figure 02_image125
由負上升至正值，該一次側共振電感電流
Figure 02_image114
由零開始上升，由於該一次側共振電感電流
Figure 02_image114
大於零，與二次側進行共振，該第一整流二極體
Figure 02_image049
導通，並且對該第一蓄電池
Figure 02_image107
充電，當該一次側共振電感電流
Figure 02_image114
上升至等於該扼流電感電流
Figure 02_image013
，
Figure 02_image109
等於零時，進入工作模式六。 Working mode five [
Figure 02_image140
]: Please also refer to the eighth figure as shown in the fifth equivalent linear circuit diagram of the working mode of the present invention.
Figure 02_image142
When the toggle switch
Figure 02_image015
Still cut off, the primary side resonance inductor current
Figure 02_image114
Still less than the choke inductor current
Figure 02_image013
,
Figure 02_image109
Is still greater than zero, the current flows through the shunt capacitor
Figure 02_image019
, So the shunt capacitor current
Figure 02_image138
Is still positive, the primary side resonance capacitor voltage
Figure 02_image125
Rising from negative to positive, the primary side resonance inductor current
Figure 02_image114
It starts to rise from zero, because the primary side resonance inductor current
Figure 02_image114
Greater than zero, resonates with the secondary side, the first rectifier diode
Figure 02_image049
Turn on, and the first battery
Figure 02_image107
Charging, when the primary side resonance inductor current
Figure 02_image114
Rise to be equal to the choke inductor current
Figure 02_image013
,
Figure 02_image109
When equal to zero, enter working mode 6.

工作模式六［

Figure 02_image144
］：請再一併參閱第九圖本發明之工作模式六等效線性電路圖所示，在
Figure 02_image146
時，該切換開關
Figure 02_image015
仍為截止，該一次側共振電感電流
Figure 02_image114
大於該扼流電感電流
Figure 02_image013
，
Figure 02_image109
小於零，電流反向流經該分流電容
Figure 02_image019
，所以該分流電容電流
Figure 02_image138
為負值，該一次側共振電感電流
Figure 02_image114
為正值，對該一次側共振電容
Figure 02_image025
充電，該一次側共振電容電壓
Figure 02_image125
上升，由負值轉為正值，與二次側進行共振，該第一整流二極體
Figure 02_image049
仍為導通，並且對該第一蓄電池
Figure 02_image107
充電，當切換開關跨壓
Figure 02_image007
降至為零時，該切換開關
Figure 02_image015
切換為導通，電路動作重新進入工作模式一。 Working mode six
Figure 02_image144
]: Please also refer to the ninth figure shown in the sixth equivalent linear circuit diagram of the working mode of the present invention.
Figure 02_image146
When the toggle switch
Figure 02_image015
Still cut off, the primary side resonance inductor current
Figure 02_image114
Greater than the choke inductor current
Figure 02_image013
,
Figure 02_image109
Less than zero, the current flows through the shunt capacitor in the reverse direction
Figure 02_image019
, So the shunt capacitor current
Figure 02_image138
Is a negative value, the primary side resonance inductor current
Figure 02_image114
Is a positive value, the primary side resonant capacitor
Figure 02_image025
Charging, the primary side resonance capacitor voltage
Figure 02_image125
Rise, change from a negative value to a positive value, and resonate with the secondary side, the first rectifier diode
Figure 02_image049
Is still on, and the first battery
Figure 02_image107
Charging, when the switch is pressed across
Figure 02_image007
When it drops to zero, the toggle switch
Figure 02_image015
Switching to conduction, the circuit action re-enters working mode one.

將該充電器(1)之電氣規格與元件參數設定如下表所示： 電源側 輸入電源

Figure 02_image148
155V 切換頻率
Figure 02_image149
 45.49kHz 責任週期D 0.66 扼流電感
Figure 02_image009
 24.96mH 分流電容
Figure 02_image019
 0.01μF 一次側共振槽 一次側共振電感
Figure 02_image031
 一次側共振電容
Figure 02_image025
 匝數 367μH 0.0547μF 23 二次側共振槽 二次側共振電感
Figure 02_image100
 二次側共振電容
Figure 02_image101
 匝數 227μF 0.07μF 20 無線傳輸的距離 10cm Set the electrical specifications and component parameters of the charger (1) as shown in the table below: Power side Input power
Figure 02_image148
Figure 02_image148
 155V Switching frequency
Figure 02_image149
 45.49kHz Duty cycle D 0.66 Choke inductance
Figure 02_image009
 24.96mH Shunt capacitor
Figure 02_image019
 0.01μF Primary side resonance groove Primary side resonance inductance
Figure 02_image031
 Primary side resonance capacitance
Figure 02_image025
 Number of turns 367μH 0.0547μF twenty three Secondary side resonance tank Secondary side resonance inductance
Figure 02_image100
 Secondary side resonance capacitor
Figure 02_image101
 Number of turns 227μF 0.07μF 20 Wireless transmission distance 10cm

該充電器(1)經由適當的選擇參數，可以使該切換開關

Figure 02_image015
操作於零電壓切換，降低該切換開關
Figure 02_image015
切換損失，因此提高電路整體效率，而該切換開關
Figure 02_image015
與該第一整流二極體
Figure 02_image049
、該第二整流二極體
Figure 02_image103
之元件規格則如下表所示： 元件型號 元件規格 切換開關：IXFN38N100P
Figure 02_image151
＝1000V
Figure 02_image152
＝210mΩ
Figure 02_image003
＝38A 整流二極體：IQBD60E60A1
Figure 02_image154
＝600V
Figure 02_image156
＝60A The charger (1) can make the switch
Figure 02_image015
Operate at zero voltage switch, lower the switch
Figure 02_image015
Switching loss, so improve the overall efficiency of the circuit, and the switch
Figure 02_image015
With the first rectifier diode
Figure 02_image049
, The second rectifier diode
Figure 02_image103
The component specifications are shown in the following table: Component model Component specifications Switch: IXFN38N100P
Figure 02_image151
＝1000V
Figure 02_image152
＝210mΩ
Figure 02_image003
＝38A Rectifier diode: IQBD60E60A1
Figure 02_image154
＝600V
Figure 02_image156
＝60A

請再一併參閱第十圖本發明之輸入電壓與電流實際量測波形圖所示，該充電器之輸入電壓V DC為155V，輸入電流I DC為8.4A；請再一併參閱第十一圖本發明之輸入電壓V DC與濾波電容電流

Figure 02_image001
實際量測波形圖所示；請再一併參閱第十二圖本發明之輸入電壓V DC與切換開關電流
Figure 02_image003
實際量測波形圖所示，上述各實際量測波形圖皆與模擬結果相當吻合。 Please also refer to Figure 10 as shown in the actual measurement waveforms of the input voltage and current of the present invention. The input voltage V DC of the charger is 155V, and the input current I DC is 8.4A; please refer to the eleventh. Figure The input voltage V DC and filter capacitor current of the present invention
Figure 02_image001
The actual measurement waveform is shown in the figure; please refer to Figure 12 for the input voltage V DC and the switch current of the present invention
Figure 02_image003
As shown in the actual measurement waveform diagram, the above-mentioned actual measurement waveform diagrams are quite consistent with the simulation results.

請再一併參閱第十三圖本發明之切換開關驅動訊號

Figure 02_image005
與切換開關跨壓
Figure 02_image007
實際量測波形圖所示，在切換開關驅動訊號
Figure 02_image005
於高電位時，該切換開關
Figure 02_image015
為導通，該切換開關
Figure 02_image015
上的電壓
Figure 02_image007
為零，切換開關驅動訊號
Figure 02_image005
為低電位時，該切換開關跨壓
Figure 02_image007
由零開始上升，在切換開關驅動訊號
Figure 02_image005
由低電位轉為高電位時，該切換開關跨壓
Figure 02_image007
降至為零，由此可知該切換開關
Figure 02_image015
操作於零電壓切換，其與模擬的結果相當吻合。 Please also refer to Figure 13 for the drive signal of the switch of the present invention
Figure 02_image005
Cross voltage with toggle switch
Figure 02_image007
As shown in the actual measurement waveform, the switch drive signal
Figure 02_image005
At high potential, the switch
Figure 02_image015
To turn on, the switch
Figure 02_image015
Voltage on
Figure 02_image007
Is zero, switch drive signal
Figure 02_image005
When the voltage is low, the switch across the voltage
Figure 02_image007
Starting from zero to rise, the signal is driven by the switch
Figure 02_image005
When changing from a low potential to a high potential, the switch is over-voltage
Figure 02_image007
Drop to zero, which shows that the switch
Figure 02_image015
It operates at zero voltage switching, which is in good agreement with the simulation results.

請再一併參閱第十四圖本發明之扼流電感

Figure 02_image009
電壓
Figure 02_image011
與電流
Figure 02_image013
實際量測波形圖所示，當該切換開關
Figure 02_image015
導通時，該扼流電感
Figure 02_image009
上跨一正電壓，該扼流電感
Figure 02_image009
儲存能量，該扼流電感電流
Figure 02_image013
上升，當該切換開關
Figure 02_image015
截止時，該扼流電感
Figure 02_image009
釋放能量，該扼流電感電流
Figure 02_image013
下降，其與模擬的結果相吻合。 Please also refer to Figure 14 for the choke inductor of the present invention
Figure 02_image009
Voltage
Figure 02_image011
With current
Figure 02_image013
As shown in the actual measurement waveform, when the switch
Figure 02_image015
When turned on, the choke inductance
Figure 02_image009
There is a positive voltage across the choke inductor
Figure 02_image009
Store energy, the choke inductor current
Figure 02_image013
Rise when the toggle switch
Figure 02_image015
When cut off, the choke inductance
Figure 02_image009
Release energy, the choke inductor current
Figure 02_image013
Decline, which is consistent with the simulation results.

請再一併參閱第十五圖本發明之切換開關

Figure 02_image015
電壓
Figure 02_image017
與電流
Figure 02_image018
實際量測波形圖所示，於該切換開關
Figure 02_image015
導通瞬間，因該一次側共振電感電流
Figure 02_image114
大於扼流電感電流
Figure 02_image013
電流反向流經該切換開關
Figure 02_image015
，故該切換開關
Figure 02_image015
於切換開關電流
Figure 02_image018
為負值時切換導通，當該切換開關
Figure 02_image015
截止時，切換開關電流
Figure 02_image018
為零，其與模擬的結果相吻合。 Please also refer to Figure 15 for the toggle switch of the present invention
Figure 02_image015
Voltage
Figure 02_image017
With current
Figure 02_image018
The actual measurement waveform is shown in the toggle switch
Figure 02_image015
At the moment of turn-on, due to the primary side resonance inductor current
Figure 02_image114
Greater than choke inductor current
Figure 02_image013
The current flows through the switch in the reverse direction
Figure 02_image015
, So the switch
Figure 02_image015
Switch current
Figure 02_image018
When the value is negative, the switch is turned on, when the switch
Figure 02_image015
When cut off, switch current
Figure 02_image018
It is zero, which is consistent with the simulation result.

請再一併參閱第十六圖本發明之分流電容

Figure 02_image019
電壓
Figure 02_image021
與電流
Figure 02_image023
實際量測波形圖所示，當該切換開關
Figure 02_image015
截止時，分流電容
Figure 02_image019
電壓
Figure 02_image158
上升，上升至最高點時，該一次側共振電感電流
Figure 02_image114
大於扼流電感電流
Figure 02_image013
，電流反向流經分流電容
Figure 02_image019
，該切換開關
Figure 02_image015
導通時，
Figure 02_image109
流經該切換開關
Figure 02_image015
，分流電容
Figure 02_image019
上並無電流流經，其與模擬的結果吻合。 Please also refer to Figure 16 The shunt capacitor of the present invention
Figure 02_image019
Voltage
Figure 02_image021
With current
Figure 02_image023
As shown in the actual measurement waveform, when the switch
Figure 02_image015
When cut off, the shunt capacitor
Figure 02_image019
Voltage
Figure 02_image158
When rising to the highest point, the primary side resonance inductor current
Figure 02_image114
Greater than choke inductor current
Figure 02_image013
, The current flows through the shunt capacitor in the reverse direction
Figure 02_image019
, The switch
Figure 02_image015
When turned on,
Figure 02_image109
Flow through the switch
Figure 02_image015
, Shunt capacitor
Figure 02_image019
There is no current flowing through it, which is consistent with the simulation results.

請再一併參閱第十七圖本發明之一次側共振電容

Figure 02_image025
電壓
Figure 02_image027
與電流
Figure 02_image029
實際量測波形圖所示，當一次側共振電容電流
Figure 02_image113
大於零時，一次側共振電容
Figure 02_image025
開始儲存能量，一次側共振電容電壓
Figure 02_image159
上升，反之一次側共振電容電流
Figure 02_image113
小於零時，一次側共振電容
Figure 02_image025
釋放能量，一次側共振電容電壓
Figure 02_image159
下降，其與模擬的結果相當吻合。 Please also refer to Figure 17 for the primary side resonance capacitor of the present invention
Figure 02_image025
Voltage
Figure 02_image027
With current
Figure 02_image029
As shown in the actual measurement waveform, when the primary side resonance capacitor current
Figure 02_image113
When greater than zero, the primary side resonance capacitance
Figure 02_image025
Start to store energy, primary side resonance capacitor voltage
Figure 02_image159
Rising, conversely, the primary side resonance capacitor current
Figure 02_image113
When less than zero, the primary side resonance capacitance
Figure 02_image025
Release energy, primary side resonance capacitor voltage
Figure 02_image159
Decline, which is in good agreement with the simulation results.

請再一併參閱第十八圖本發明之一次側共振電感

Figure 02_image031
電壓
Figure 02_image033
與電流
Figure 02_image035
實際量測波形圖所示，當一次側共振電感電壓
Figure 02_image160
大於零時，一次側共振電感
Figure 02_image031
開始儲存能量，一次側共振電感電流
Figure 02_image161
上升，當一次側共振電感電壓
Figure 02_image160
小於零時，一次側共振電感
Figure 02_image031
釋放能量，一次側共振電感電流
Figure 02_image161
下降，而一次側共振電感電壓
Figure 02_image160
上的突波，是因為二次側輸出端第一整流二極體
Figure 02_image049
、第二整流二極體
Figure 02_image103
在切換時所造成的現象，其與模擬的結果相吻合。 Please also refer to Figure 18, the primary side resonance inductance of the present invention
Figure 02_image031
Voltage
Figure 02_image033
With current
Figure 02_image035
As shown in the actual measurement waveform, when the primary side resonance inductance voltage
Figure 02_image160
When greater than zero, the primary side resonance inductance
Figure 02_image031
Start to store energy, primary side resonance inductor current
Figure 02_image161
Rise, when the primary side resonance inductor voltage
Figure 02_image160
When less than zero, the primary side resonance inductance
Figure 02_image031
Release energy, primary side resonant inductor current
Figure 02_image161
Drop, and the primary side resonant inductor voltage
Figure 02_image160
The surge is caused by the first rectifier diode at the secondary side output
Figure 02_image049
, The second rectifier diode
Figure 02_image103
The phenomenon caused by the switch is consistent with the simulation result.

請再一併參閱第十九圖本發明之二次側共振電感

Figure 02_image037
電壓
Figure 02_image039
與電流
Figure 02_image041
實際量測波形圖所示，當二次側共振電感電壓
Figure 02_image162
大於零時，二次側共振電感
Figure 02_image163
開始儲存能量，二次側共振電感電流
Figure 02_image164
上升，當二次側共振電感電壓
Figure 02_image162
小於零時，二次側共振電感
Figure 02_image165
釋放能量，二次側共振電感電流
Figure 02_image164
下降，而二次側共振電感電壓
Figure 02_image162
上的突波，是因為二次側輸出端第一整流二極體
Figure 02_image049
、第二整流二極體
Figure 02_image103
在切換時所造成的現象，其與模擬的結果相吻合。 Please also refer to the nineteenth figure of the secondary side resonance inductance of the present invention
Figure 02_image037
Voltage
Figure 02_image039
With current
Figure 02_image041
As shown in the actual measurement waveform, when the secondary side resonant inductor voltage
Figure 02_image162
When greater than zero, the secondary side resonance inductance
Figure 02_image163
Start to store energy, secondary side resonant inductor current
Figure 02_image164
Rise, when the secondary side resonant inductor voltage
Figure 02_image162
When less than zero, the secondary side resonance inductance
Figure 02_image165
Release energy, resonant inductor current on the secondary side
Figure 02_image164
Drop, and the secondary side resonant inductor voltage
Figure 02_image162
The surge is caused by the first rectifier diode at the secondary side output
Figure 02_image049
, The second rectifier diode
Figure 02_image103
The phenomenon caused by the switch is consistent with the simulation result.

請再一併參閱第二十圖本發明之二次側共振電容

Figure 02_image043
電壓
Figure 02_image045
與電流
Figure 02_image047
實際量測波形圖所示，當二次側共振電容電流
Figure 02_image166
大於零時，二次側共振電容
Figure 02_image167
開始儲存能量，二次側共振電容電壓
Figure 02_image168
上升，反之二次側共振電容電流
Figure 02_image166
小於零時，二次側共振電容
Figure 02_image169
釋放能量，二次側共振電容電壓
Figure 02_image168
下降，其與模擬的結果相當吻合。 Please also refer to Figure 20 of the secondary side resonance capacitor of the present invention
Figure 02_image043
Voltage
Figure 02_image045
With current
Figure 02_image047
As shown in the actual measurement waveform, when the secondary side resonance capacitor current
Figure 02_image166
When greater than zero, the secondary side resonance capacitance
Figure 02_image167
Start to store energy, secondary side resonant capacitor voltage
Figure 02_image168
Rising, on the contrary, the secondary side resonance capacitor current
Figure 02_image166
When less than zero, the secondary side resonance capacitance
Figure 02_image169
Release energy, secondary side resonance capacitor voltage
Figure 02_image168
Decline, which is in good agreement with the simulation results.

請再一併參閱第二十一圖本發明之第一整流二極體

Figure 02_image049
電壓
Figure 02_image051
與電流
Figure 02_image053
實際量測波形圖所示，第一整流二極體
Figure 02_image049
導通時，第一整流二極體
Figure 02_image049
有電流
Figure 02_image079
通過，其大小為一次側共振電感電流
Figure 02_image161
之半週，第一整流二極體
Figure 02_image049
截止時，第一整流二極體
Figure 02_image049
上的電流
Figure 02_image079
為零，其與模擬的結果相吻合。 Please also refer to the first rectifier diode of the present invention in Figure 21
Figure 02_image049
Voltage
Figure 02_image051
With current
Figure 02_image053
As shown in the actual measurement waveform, the first rectifier diode
Figure 02_image049
When turned on, the first rectifier diode
Figure 02_image049
Current
Figure 02_image079
Pass, its magnitude is the primary side resonance inductor current
Figure 02_image161
Half of the cycle, the first rectifier diode
Figure 02_image049
When cut off, the first rectifier diode
Figure 02_image049
Current on
Figure 02_image079
It is zero, which is consistent with the simulation result.

請再一併參閱第二十二圖本發明之第二整流二極體

Figure 02_image055
電壓
Figure 02_image057
與電流
Figure 02_image059
實際量測波形圖所示，第二整流二極體
Figure 02_image170
導通時，第二整流二極體
Figure 02_image170
有電流
Figure 02_image171
通過，其大小為一次側共振電感電流
Figure 02_image161
之負半週，第二整流二極體
Figure 02_image170
截止時，第二整流二極體
Figure 02_image170
上的電流
Figure 02_image171
為零，其與模擬的結果相吻合。 Please also refer to the second rectifier diode of the present invention in Figure 22
Figure 02_image055
Voltage
Figure 02_image057
With current
Figure 02_image059
As shown in the actual measurement waveform, the second rectifier diode
Figure 02_image170
When turned on, the second rectifier diode
Figure 02_image170
Current
Figure 02_image171
Pass, its magnitude is the primary side resonance inductor current
Figure 02_image161
The negative half cycle, the second rectifier diode
Figure 02_image170
When cut off, the second rectifier diode
Figure 02_image170
Current on
Figure 02_image171
It is zero, which is consistent with the simulation result.

請再一併參閱第二十三圖本發明之第一蓄電池

Figure 02_image061
電壓
Figure 02_image063
與電流
Figure 02_image065
實際量測波形圖及第二十四圖本發明之第二蓄電池
Figure 02_image067
電壓
Figure 02_image069
與電流
Figure 02_image071
實際量測波形圖所示，請再一併參閱第二十五圖本發明之一次側共振槽電壓
Figure 02_image073
與電流
Figure 02_image075
實際量測波形圖、第二十六圖本發明之二次側共振槽電壓
Figure 02_image076
與電流
Figure 02_image078
實際量測波形圖、第二十七圖本發明之二次側共振電容電流
Figure 02_image078
與第一整流二極體電流
Figure 02_image079
及第二整流二極體電流
Figure 02_image059
實際量測波形圖、第二十八圖本發明之第一蓄電池
Figure 02_image061
、第二蓄電池
Figure 02_image080
串聯電壓
Figure 02_image172
與第一蓄電池電壓
Figure 02_image173
及第二蓄電池電壓
Figure 02_image174
實際量測波形圖所示，上述各實際量測波形圖皆與模擬結果相當吻合。 Please also refer to Figure 23. The first battery of the present invention
Figure 02_image061
Voltage
Figure 02_image063
With current
Figure 02_image065
Actual measurement waveform diagram and twenty-fourth diagram The second battery of the present invention
Figure 02_image067
Voltage
Figure 02_image069
With current
Figure 02_image071
The actual measurement waveform is shown in the figure, please refer to Figure 25. The voltage of the primary side resonance tank of the present invention
Figure 02_image073
With current
Figure 02_image075
The actual measurement waveform, the twenty-sixth graph The voltage of the secondary side resonance tank of the present invention
Figure 02_image076
With current
Figure 02_image078
The actual measurement waveform diagram, the twenty-seventh diagram The secondary side resonance capacitor current of the present invention
Figure 02_image078
With the first rectifier diode current
Figure 02_image079
And the second rectifier diode current
Figure 02_image059
Actual measurement waveform diagram, twenty-eighth diagram The first battery of the present invention
Figure 02_image061
, The second battery
Figure 02_image080
Series voltage
Figure 02_image172
With the first battery voltage
Figure 02_image173
And the second battery voltage
Figure 02_image174
As shown in the actual measurement waveform diagram, the above-mentioned actual measurement waveform diagrams are quite consistent with the simulation results.

請再一併參閱第二十九圖本發明之第一蓄電池

Figure 02_image061
充電期間［2h20min］電壓曲線圖、第三十圖本發明之第一蓄電池
Figure 02_image061
充電期間［2h20min］電流曲線圖、第三十一圖本發明之第二蓄電池
Figure 02_image086
充電期間［2h20min］電壓曲線圖、第三十二圖本發明之第二蓄電池
Figure 02_image087
充電期間［2h20min］電流曲線圖、第三十三圖本發明之第一蓄電池
Figure 02_image061
充電期間［2h20min］-靜置［1h］電壓曲線圖、第三十四圖本發明之第二蓄電池
Figure 02_image088
充電期間［2h20min］-靜置［1h］電壓曲線圖、第三十五圖本發明之第一蓄電池
Figure 02_image061
充電期間Ah曲線圖、第三十六圖本發明之第二蓄電池
Figure 02_image089
充電期間Ah曲線圖、第三十七圖本發明之第一蓄電池
Figure 02_image061
加上第二蓄電池
Figure 02_image090
充電期間Ah曲線圖、第三十八圖本發明之第一蓄電池
Figure 02_image061
充電電壓與充電容量曲線圖、第三十九圖本發明之第二蓄電池
Figure 02_image091
充電電壓與充電容量曲線圖、第四十圖本發明之第一蓄電池
Figure 02_image061
加上第二蓄電池
Figure 02_image092
充電電壓與充電容量曲線圖、第四十一圖本發明之第一蓄電池
Figure 02_image061
充電電壓與充電容量百分比曲線圖、第四十二圖本發明之第二蓄電池
Figure 02_image091
充電電壓與充電容量百分比曲線圖、第四十三圖本發明之第一蓄電池
Figure 02_image061
加上第二蓄電池
Figure 02_image092
充電電壓與充電容量百分比曲線圖、第四十四圖本發明之輸入電壓曲線圖、第四十五圖本發明之輸入電流曲線圖、第四十六圖本發明之蓄電池輸入功率曲線圖、第四十七圖本發明之蓄電池輸出功率曲線圖、第四十八圖本發明之第一蓄電池
Figure 02_image061
功率曲線圖、第四十九圖本發明之第二蓄電池
Figure 02_image093
功率曲線圖、第五十圖本發明之蓄電池充電期間［2h20min］轉換效率曲線圖所示，該第一蓄電池
Figure 02_image061
及該第二蓄電池
Figure 02_image080
快速充電完成後，該第一蓄電池
Figure 02_image061
共充進14.32Ah，該第二蓄電池
Figure 02_image080
共充進14.15Ah，充電最低效率：65％，充電最高效率：77％。 Please also refer to the first battery of the present invention in Figure 29
Figure 02_image061
During the charging period [2h20min] voltage curve diagram, the thirtieth figure The first battery of the present invention
Figure 02_image061
During the charging period [2h20min] current curve diagram, the thirty-first diagram The second battery of the present invention
Figure 02_image086
During the charging period [2h20min] voltage curve diagram, the thirty-second diagram The second battery of the present invention
Figure 02_image087
During the charging period [2h20min] the current curve diagram, the thirty-third diagram The first battery of the present invention
Figure 02_image061
During the charging period [2h20min]-standstill [1h] voltage curve graph, thirty-fourth graph The second battery of the present invention
Figure 02_image088
During the charging period [2h20min]-standstill [1h] voltage curve graph, thirty-fifth graph The first battery of the present invention
Figure 02_image061
Ah curve diagram and thirty-sixth diagram during charging The second battery of the present invention
Figure 02_image089
Ah curve diagram and thirty-seventh diagram during charging The first battery of the present invention
Figure 02_image061
Plus the second battery
Figure 02_image090
Ah curve diagram and thirty-eighth diagram during charging The first battery of the present invention
Figure 02_image061
Graph of charging voltage and charging capacity, the thirty-ninth graph The second battery of the present invention
Figure 02_image091
Graph of charging voltage and charging capacity, the fortieth graph The first battery of the present invention
Figure 02_image061
Plus the second battery
Figure 02_image092
Graph of charging voltage and charging capacity, figure 41 The first battery of the present invention
Figure 02_image061
Charging voltage and charging capacity percentage curve diagram, forty-second diagram The second battery of the present invention
Figure 02_image091
Charging voltage and charging capacity percentage graph, forty-third graph The first battery of the present invention
Figure 02_image061
Plus the second battery
Figure 02_image092
Charging voltage and charging capacity percentage curve graph, the forty-fourth graph the input voltage graph of the present invention, the forty-fifth graph the input current graph of the present invention, the forty-sixth graph the battery input power graph of the present invention, the fourth graph Forty-seventh figure the output power curve of the battery of the present invention, and figure forty-eighth the first battery of the present invention
Figure 02_image061
Power curve diagram, forty-ninth diagram The second battery of the present invention
Figure 02_image093
The power curve and the fiftieth graph show the conversion efficiency curve of the battery during charging of the present invention [2h20min], the first battery
Figure 02_image061
And the second battery
Figure 02_image080
After the quick charge is completed, the first battery
Figure 02_image061
A total of 14.32Ah is charged, the second battery
Figure 02_image080
A total of 14.15Ah is charged, the lowest charging efficiency: 65%, the highest charging efficiency: 77%.

藉由以上所述，本發明之使用實施說明可知，本發明與現有技術手段相較之下，本發明主要係具有電路簡單、成本低、體積小等優點，且經由選擇適當的元件參數、切換頻率以及共振頻率，使切換開關操作於零電壓切換，由於操作在於零電壓切換的關係，減少切換開關切換過程的損失，提升整體效率，並由於在對蓄電池充電過程中，係為一組充電一組休息之輪流充電的方式，讓蓄電池有足夠的時間休息，來增加蓄電池的使用壽命，而在其整體施行使用上更增實用功效特性者。Based on the above, the description of the implementation of the present invention shows that, compared with the prior art, the present invention mainly has the advantages of simple circuit, low cost, small size, etc., and by selecting appropriate component parameters and switching The frequency and resonance frequency make the switch operate at zero voltage switching. Because the operation is based on zero voltage switching, the loss during the switching process of the switch is reduced, and the overall efficiency is improved. The alternate charging method of the group rest allows the battery to have enough time to rest, to increase the service life of the battery, and to increase the practical performance characteristics in its overall implementation.

1:充電器1: charger

第一圖：本發明之電路圖Figure 1: Circuit diagram of the present invention

第二圖：本發明之電路方塊示意圖Figure 2: Block diagram of the circuit of the present invention

第三圖：本發明之主要元件時序波形圖Figure 3: Timing waveform diagram of main components of the present invention

第四圖：本發明之工作模式一等效線性電路圖Figure 4: The equivalent linear circuit diagram of the working mode of the present invention

第五圖：本發明之工作模式二等效線性電路圖Figure 5: Equivalent linear circuit diagram of working mode 2 of the present invention

第六圖：本發明之工作模式三等效線性電路圖Figure 6: Three equivalent linear circuit diagrams of the working mode of the present invention

第七圖：本發明之工作模式四等效線性電路圖The seventh figure: the equivalent linear circuit diagram of the working mode four of the present invention

第八圖：本發明之工作模式五等效線性電路圖Figure 8: Equivalent linear circuit diagram of working mode 5 of the present invention

第九圖：本發明之工作模式六等效線性電路圖Figure Ninth: Six equivalent linear circuit diagram of the working mode of the present invention

第十圖：本發明之輸入電壓與電流實際量測波形圖Figure 10: The actual measurement waveform of the input voltage and current of the present invention

第十一圖：本發明之輸入電壓V DC與濾波電容電流

Figure 02_image001
實際量測波形圖 Figure 11: Input voltage V DC and filter capacitor current of the present invention
Figure 02_image001
Actual measurement waveform

第十二圖：本發明之輸入電壓V DC與切換開關電流

Figure 02_image003
實際量測波形圖 Figure 12: Input voltage V DC and switch current of the present invention
Figure 02_image003
Actual measurement waveform

第十三圖：本發明之切換開關驅動訊號

Figure 02_image005
與切換開關跨壓
Figure 02_image007
實際量測波形圖 Figure 13: The switch drive signal of the present invention
Figure 02_image005
Cross voltage with toggle switch
Figure 02_image007
Actual measurement waveform

第十四圖：本發明之扼流電感

Figure 02_image009
電壓
Figure 02_image011
與電流
Figure 02_image013
實際量測波形圖 Figure 14: Choke inductor of the present invention
Figure 02_image009
Voltage
Figure 02_image011
With current
Figure 02_image013
Actual measurement waveform

第十五圖：本發明之切換開關

Figure 02_image015
電壓
Figure 02_image017
與電流
Figure 02_image018
實際量測波形圖 Figure 15: The switch of the present invention
Figure 02_image015
Voltage
Figure 02_image017
With current
Figure 02_image018
Actual measurement waveform

第十六圖：本發明之分流電容

Figure 02_image019
電壓
Figure 02_image021
與電流
Figure 02_image023
實際量測波形圖 Figure 16: Shunt capacitor of the present invention
Figure 02_image019
Voltage
Figure 02_image021
With current
Figure 02_image023
Actual measurement waveform

第十七圖：本發明之一次側共振電容

Figure 02_image025
電壓
Figure 02_image027
與電流
Figure 02_image029
實際量測波形圖 Figure 17: Primary side resonance capacitor of the present invention
Figure 02_image025
Voltage
Figure 02_image027
With current
Figure 02_image029
Actual measurement waveform

第十八圖：本發明之一次側共振電感

Figure 02_image031
電壓
Figure 02_image033
與電流
Figure 02_image035
實際量測波形圖 Figure 18: Primary side resonance inductor of the present invention
Figure 02_image031
Voltage
Figure 02_image033
With current
Figure 02_image035
Actual measurement waveform

第十九圖：本發明之二次側共振電感

Figure 02_image037
電壓
Figure 02_image039
與電流
Figure 02_image041
實際量測波形圖 Figure 19: The secondary side resonance inductor of the present invention
Figure 02_image037
Voltage
Figure 02_image039
With current
Figure 02_image041
Actual measurement waveform

第二十圖：本發明之二次側共振電容

Figure 02_image043
電壓
Figure 02_image045
與電流
Figure 02_image047
實際量測波形圖 Figure 20: The secondary side resonant capacitor of the present invention
Figure 02_image043
Voltage
Figure 02_image045
With current
Figure 02_image047
Actual measurement waveform

第二十一圖：本發明之第一整流二極體

Figure 02_image049
電壓
Figure 02_image051
與電流
Figure 02_image053
實際量測波形圖 Figure 21: The first rectifier diode of the present invention
Figure 02_image049
Voltage
Figure 02_image051
With current
Figure 02_image053
Actual measurement waveform

第二十二圖：本發明之第二整流二極體

Figure 02_image055
電壓
Figure 02_image057
與電流
Figure 02_image059
實際量測波形圖 Figure 22: The second rectifier diode of the present invention
Figure 02_image055
Voltage
Figure 02_image057
With current
Figure 02_image059
Actual measurement waveform

第二十三圖：本發明之第一蓄電池

Figure 02_image061
電壓
Figure 02_image063
與電流
Figure 02_image065
實際量測波形圖 Figure 23: The first battery of the present invention
Figure 02_image061
Voltage
Figure 02_image063
With current
Figure 02_image065
Actual measurement waveform

第二十四圖：本發明之第二蓄電池

Figure 02_image067
電壓
Figure 02_image069
與電流
Figure 02_image071
實際量測波形圖 Figure 24: The second battery of the present invention
Figure 02_image067
Voltage
Figure 02_image069
With current
Figure 02_image071
Actual measurement waveform

第二十五圖：本發明之一次側共振槽電壓

Figure 02_image073
與電流
Figure 02_image075
實際量測波形圖 Figure 25: The primary side resonance tank voltage of the present invention
Figure 02_image073
With current
Figure 02_image075
Actual measurement waveform

第二十六圖：本發明之二次側共振槽電壓

Figure 02_image076
與電流
Figure 02_image078
實際量測波形圖 Figure 26: The voltage of the secondary side resonance tank of the present invention
Figure 02_image076
With current
Figure 02_image078
Actual measurement waveform

第二十七圖：本發明之二次側共振電容電流

Figure 02_image078
與第一整流二極體電流
Figure 02_image079
及第二整流二極體電流
Figure 02_image059
實際量測波形圖 Figure 27: Secondary side resonance capacitor current of the present invention
Figure 02_image078
With the first rectifier diode current
Figure 02_image079
And the second rectifier diode current
Figure 02_image059
Actual measurement waveform

第二十八圖：本發明之第一蓄電池

Figure 02_image061
、第二蓄電池
Figure 02_image080
串聯電壓
Figure 02_image082
與第一蓄電池電壓
Figure 02_image084
及第二蓄電池電壓
Figure 02_image085
實際量測波形圖 Figure 28: The first battery of the present invention
Figure 02_image061
, The second battery
Figure 02_image080
Series voltage
Figure 02_image082
With the first battery voltage
Figure 02_image084
And the second battery voltage
Figure 02_image085
Actual measurement waveform

第二十九圖：本發明之第一蓄電池

Figure 02_image061
充電期間［2h20min］電壓曲線圖 Figure 29: The first battery of the present invention
Figure 02_image061
During charging [2h20min] voltage curve

第三十圖：本發明之第一蓄電池

Figure 02_image061
充電期間［2h20min］電流曲線圖 Figure 30: The first battery of the present invention
Figure 02_image061
[2h20min] current curve during charging

第三十一圖：本發明之第二蓄電池

Figure 02_image086
充電期間［2h20min］電壓曲線圖 Figure 31: The second battery of the present invention
Figure 02_image086
During charging [2h20min] voltage curve

第三十二圖：本發明之第二蓄電池

Figure 02_image087
充電期間［2h20min］電流曲線圖 Figure 32: The second battery of the present invention
Figure 02_image087
[2h20min] current curve during charging

第三十三圖：本發明之第一蓄電池

Figure 02_image061
充電期間［2h20min］-靜置［1h］電壓曲線圖 Figure 33: The first battery of the present invention
Figure 02_image061
During charging [2h20min]-standstill [1h] voltage curve

第三十四圖：本發明之第二蓄電池

Figure 02_image088
充電期間［2h20min］-靜置［1h］電壓曲線圖 Figure 34: The second battery of the present invention
Figure 02_image088
During charging [2h20min]-standstill [1h] voltage curve

第三十五圖：本發明之第一蓄電池

Figure 02_image061
充電期間Ah曲線圖 Figure 35: The first battery of the present invention
Figure 02_image061
Ah curve during charging

第三十六圖：本發明之第二蓄電池

Figure 02_image089
充電期間Ah曲線圖 Figure 36: The second battery of the present invention
Figure 02_image089
Ah curve during charging

第三十七圖：本發明之第一蓄電池

Figure 02_image061
加上第二蓄電池
Figure 02_image090
充電期間Ah曲線圖 Figure 37: The first battery of the present invention
Figure 02_image061
Plus the second battery
Figure 02_image090
Ah curve during charging

第三十八圖：本發明之第一蓄電池

Figure 02_image061
充電電壓與充電容量曲線圖 Figure 38: The first battery of the present invention
Figure 02_image061
Graph of charging voltage and charging capacity

第三十九圖：本發明之第二蓄電池

Figure 02_image091
充電電壓與充電容量曲線圖 Figure 39: The second battery of the present invention
Figure 02_image091
Graph of charging voltage and charging capacity

第四十圖：本發明之第一蓄電池

Figure 02_image061
加上第二蓄電池
Figure 02_image092
充電電壓與充電容量曲線圖 Figure 40: The first battery of the present invention
Figure 02_image061
Plus the second battery
Figure 02_image092
Graph of charging voltage and charging capacity

第四十一圖：本發明之第一蓄電池

Figure 02_image061
充電電壓與充電容量百分比曲線圖 Figure 41: The first battery of the present invention
Figure 02_image061
Charging voltage and charging capacity percentage curve

第四十二圖：本發明之第二蓄電池

Figure 02_image091
充電電壓與充電容量百分比曲線圖 Figure 42: The second battery of the present invention
Figure 02_image091
Charging voltage and charging capacity percentage curve

第四十三圖：本發明之第一蓄電池

Figure 02_image061
加上第二蓄電池
Figure 02_image092
充電電壓與充電容量百分比曲線圖 Figure 43: The first battery of the present invention
Figure 02_image061
Plus the second battery
Figure 02_image092
Charging voltage and charging capacity percentage curve

第四十四圖：本發明之輸入電壓曲線圖Figure 44: Input voltage curve diagram of the present invention

第四十五圖：本發明之輸入電流曲線圖Figure 45: The input current curve of the present invention

第四十六圖：本發明之蓄電池輸入功率曲線圖Figure 46: The battery input power curve diagram of the present invention

第四十七圖：本發明之蓄電池輸出功率曲線圖Figure 47: The battery output power curve diagram of the present invention

第四十八圖：本發明之第一蓄電池

Figure 02_image061
功率曲線圖 Figure 48: The first battery of the present invention
Figure 02_image061
Power curve

第四十九圖：本發明之第二蓄電池

Figure 02_image093
功率曲線圖 Figure 49: The second battery of the present invention
Figure 02_image093
Power curve

第五十圖：本發明之蓄電池充電期間［2h20min］轉換效率曲線圖Figure 50: The conversion efficiency curve of the battery charging period [2h20min] of the present invention

1:充電器 1: charger

Claims (5)

一種輕型電動載具雙蓄電池組之單開關零電壓切換無線交錯式高頻弦波脈衝式充電器，其主要係令充電器於輸入電源之正極分別連接濾波電容之第一端及扼流電感之第一端，該扼流電感之第二端分別連接有切換開關之第一端、分流電容之第一端及一次側共振電容之第一端，該一次側共振電容之第二端連接有一次側共振電感之第一端，而於該輸入電源之負極則分別連接濾波電容之第二端、切換開關之第二端、分流電容之第二端及一次側共振電感之第二端，而對應該一次側共振電感設有二次側共振電感，該二次側共振電感之第一端連接二次側共振電容之第一端，該二次側共振電容之第二端分別連接第一整流二極體之正極、第二整流二極體之負極，該第一整流二極體之負極連接第一蓄電池之正極，該第二整流二極體之正極連接第二蓄電池之負極，該二次側共振電感之第二端則與該第一蓄電池之負極及該第二蓄電池之正極相連接，令該輸入電源係為155V，使得其切換頻率係為45.49kHz，該扼流電感係為24.96mH，該分流電容係為0.01Mf。 A single-switch zero-voltage switching wireless interleaved high-frequency sine wave pulse charger for light-duty electric vehicles with dual battery packs. The charger is mainly connected to the first end of the filter capacitor and the choke inductor at the positive pole of the input power supply. At the first end, the second end of the choke inductor is respectively connected to the first end of the switch, the first end of the shunt capacitor, and the first end of the primary side resonant capacitor. The second end of the primary side resonant capacitor is connected to the first end of the primary side resonant capacitor. The first terminal of the side resonance inductor, and the negative terminal of the input power supply is connected to the second terminal of the filter capacitor, the second terminal of the switch, the second terminal of the shunt capacitor, and the second terminal of the primary side resonance inductance. The primary side resonant inductor should be equipped with a secondary side resonant inductor, the first end of the secondary side resonant inductor is connected to the first end of the secondary side resonant capacitor, and the second end of the secondary side resonant capacitor is respectively connected to the first rectifier two The positive pole of the polar body, the negative pole of the second rectifier diode, the negative pole of the first rectifier diode is connected to the positive pole of the first battery, and the positive pole of the second rectifier diode is connected to the negative pole of the second battery. The secondary side The second end of the resonance inductance is connected to the negative electrode of the first battery and the positive electrode of the second battery, so that the input power is 155V, the switching frequency is 45.49kHz, and the choke inductance is 24.96mH, The shunt capacitance is 0.01Mf. 如請求項1所述輕型電動載具雙蓄電池組之單開關零電壓切換無線交錯式高頻弦波脈衝式充電器，其中，該充電器之該第一整流二極體及該第二整流二極體係為蕭特基〔 Schittky〕二極體、快速恢復〔Fast Recovery〕二極體任一種。 The single-switch zero-voltage switching wireless interleaved high-frequency sine wave pulse-type charger of the light-duty electric vehicle dual-battery pack according to claim 1, wherein the first rectifier diode and the second rectifier diode of the charger The polar system is Schottky ( Schittky] diode, fast recovery [Fast Recovery] diode either. 如請求項1所述輕型電動載具雙蓄電池組之單開關零電壓切換無線交錯式高頻弦波脈衝式充電器，其中，該一次側共振電感係為367μH，該一次側共振電容係為0.0547μF，該一次側共振電容與該一次側共振電感串聯成為一次側共振槽，匝數為23匝。 The single-switch zero-voltage switching wireless interleaved high-frequency sine wave pulse charger for light-duty electric vehicles with dual battery packs as described in claim 1, wherein the primary resonance inductance is 367μH, and the primary resonance capacitance is 0.0547 μF, the primary side resonant capacitor and the primary side resonant inductance are connected in series to form a primary side resonant tank, and the number of turns is 23 turns. 如請求項1所述輕型電動載具雙蓄電池組之單開關零電壓切換無線交錯式高頻弦波脈衝式充電器，其中，該二次側共振電感係為227μF，該二次側共振電容係為0.07μF，該二次側共振電感與該二次側共振電容串聯成為二次側共振槽，匝數為20匝。 The single-switch zero-voltage switching wireless interleaved high-frequency sine wave pulse charger for light-duty electric vehicles with dual battery packs as described in claim 1, wherein the secondary side resonance inductance is 227μF, and the secondary side resonance capacitor is It is 0.07μF, the secondary side resonant inductance and the secondary side resonant capacitor are connected in series to form a secondary side resonant tank, and the number of turns is 20 turns. 如請求項1所述輕型電動載具雙蓄電池組之單開關零電壓切換無線交錯式高頻弦波脈衝式充電器，該一次側共振電容與該一次側共振電感串聯成為一次側共振槽，該二次側共振電感與該二次側共振電容串聯成為二次側共振槽，該一次側共振槽與該二次側共振槽間的傳輸距離為10cm。 The single-switch zero-voltage switching wireless interleaved high-frequency sinusoidal pulse type charger for the light-duty electric vehicle dual battery pack described in claim 1, the primary side resonance capacitor and the primary side resonance inductance are connected in series to form a primary side resonance tank, the The secondary-side resonance inductance and the secondary-side resonance capacitor are connected in series to form a secondary-side resonance tank, and the transmission distance between the primary-side resonance tank and the secondary-side resonance tank is 10 cm.
TW109116037A 2020-05-14 2020-05-14 Single switch with zero voltage switching wireless charger with interleaved high-frequency sine-wave pulse-charging methodology used in dual-battery energy storage systems for light electric vehicles TWI736260B (en)

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Citations (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US20150207334A1 (en) * 2012-08-24 2015-07-23 Drayson Wireless Limited Inductive Power Transfer System
US20170326995A1 (en) * 2016-05-12 2017-11-16 Daihen Corporation Vehicle system
TW202002458A (en) * 2018-06-12 2020-01-01 崑山科技大學 Interleaved wireless high frequency pulsed battery charger

Patent Citations (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US20150207334A1 (en) * 2012-08-24 2015-07-23 Drayson Wireless Limited Inductive Power Transfer System
US20170326995A1 (en) * 2016-05-12 2017-11-16 Daihen Corporation Vehicle system
TW202002458A (en) * 2018-06-12 2020-01-01 崑山科技大學 Interleaved wireless high frequency pulsed battery charger

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