TWI524643B - High step-up converter - Google Patents
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本發明是有關於一種升壓轉換器，特別是指一種高升壓型轉換器。 The present invention relates to a boost converter, and more particularly to a high boost converter.
分散式發電主要分成幾種類型，例如：廢熱發電、太陽能發電、電動車對電網供電、風力發電等。然而，上述的發電方式所產生出來的電壓皆不高且不夠穩定，此外，輸出電壓易隨著負載的變動而跟著變動，為了解決這個問題，故於分散式能源後端接一升壓型轉換器(Step-Up Converter)，以提供相對穩定的高電壓給後端設備使用，或提供給市電並聯系統之變頻器所需之輸入電源，例如：熱電產生器(Thermo Electrical Generator,TEG)、獨立型太陽能供電系統、市電並聯型太陽能供電系統，在所述系統中皆需要升壓型轉換器將熱電模組或太陽能板所產生的低電壓升至高電壓，以提供變頻器或負載端所需之電源。 Decentralized power generation is mainly divided into several types, such as: waste heat power generation, solar power generation, electric vehicle power supply to the grid, and wind power generation. However, the voltage generated by the above-mentioned power generation method is not high and is not stable enough. In addition, the output voltage tends to fluctuate with changes in the load. To solve this problem, a boost-type conversion is connected to the back end of the distributed energy source. Step-Up Converter, which provides a relatively stable high voltage for the back-end equipment, or the input power required for the inverter of the mains parallel system, for example: Thermo Electrical Generator (TEG), independent Type solar power supply system, commercial power parallel solar power supply system, in which the boost converter is required to raise the low voltage generated by the thermoelectric module or the solar panel to a high voltage to provide the inverter or the load terminal. power supply.
為了達到更高的電壓轉換比，現有的技術採用多組的倍壓電路，使得二極體及電容的數量增加，進而導致成本提高，且電路元件過多易造成設計複雜。 In order to achieve a higher voltage conversion ratio, the prior art adopts multiple sets of voltage doubler circuits, which increases the number of diodes and capacitors, which leads to an increase in cost, and too many circuit components are likely to cause complicated design.
本發明之目的，即在提供一種改善先前技術的高升壓型轉換器。 It is an object of the present invention to provide a high boost converter that improves upon the prior art.
本發明的高升壓型轉換器電連接於一電源及一輸出電路之間，包含一第一開關元件、一第二開關元件、一接地電容、一順向導通元件、一儲能電容、一初級繞組、一次級繞組及一輸出電路。 The high step-up converter of the present invention is electrically connected between a power source and an output circuit, and includes a first switching component, a second switching component, a grounding capacitor, a forward conducting component, a storage capacitor, and a Primary winding, primary winding and an output circuit.
該第一開關元件具有一第一控制端、一第一連接端及一第一驅動端，該第一連接端接地，該第一控制端接受一脈波控制信號以調控該第一開關元件。該第二開關元件具有一第二控制端、一第二連接端及一第二驅動端，該第二連接端電性連接於該第一驅動端，該第二控制端接受一與該脈波控制信號反相的脈波控制信號以調控該第二開關元件。 The first switching element has a first control end, a first connecting end and a first driving end. The first connecting end is grounded, and the first control end receives a pulse wave control signal to regulate the first switching element. The second switching element has a second control end, a second connecting end and a second driving end. The second connecting end is electrically connected to the first driving end, and the second control end receives a pulse wave A pulse wave control signal that inverts the signal is controlled to regulate the second switching element.
該接地電容具有兩端，一端接地及另一端電性連接於該第二驅動端。該順向導通元件具有一電性連接於該第二驅動端的第一端，及一第二端；該儲能電容具有兩端，一端電性連接於該順向導通元件的第二端及另一端電性連接於該第一驅動端。該初級繞組的一端電性連接於該電源，及另一端電性連接於該儲能電容的另一端。該次級繞組的一端電性連接於該順向導通元件的第二端，及另一端電性連接於該輸出電路。 The grounding capacitor has two ends, one end is grounded and the other end is electrically connected to the second driving end. The forward conducting component has a first end electrically connected to the second driving end, and a second end; the storage capacitor has two ends, one end is electrically connected to the second end of the forward conducting component, and the other end One end is electrically connected to the first driving end. One end of the primary winding is electrically connected to the power source, and the other end is electrically connected to the other end of the storage capacitor. One end of the secondary winding is electrically connected to the second end of the forward conducting component, and the other end is electrically connected to the output circuit.
在一些實施態樣中，該輸出電路具有一輸出二極體、一輸出電容及一輸出電阻，該輸出二極體之陽極電 性連接該次級繞組的另一端，該輸出二極體之陰極電性連接該輸出電容的一端及該輸出電阻的一端，該輸出電容的另一端及該輸出電阻的另一端皆為接地。 In some implementations, the output circuit has an output diode, an output capacitor, and an output resistor, and the anode of the output diode The other end of the output winding is electrically connected to one end of the output capacitor and one end of the output resistor, and the other end of the output capacitor and the other end of the output resistor are grounded.
在一些實施態樣中，該電源提供一輸入電壓V i ，經該高升壓型轉換器的轉換後產生一輸出電壓V o ，D為該第一開關元件及該第二開關元件的責任週期，n為該次級繞組及該初級繞組的匝數比，且該次級繞組的匝數大於該初級繞組的匝數，該高升壓型轉換器的電壓轉換比為 In some aspects of the embodiments, the power source provides an input voltage V i, for generating an output voltage V o after converting the high boost converter, D for the duty cycle of the first switching element and the second switching element , n is the turns ratio of the secondary winding and the primary winding, and the number of turns of the secondary winding is greater than the number of turns of the primary winding, and the voltage conversion ratio of the high boost converter is
本發明之功效在於：相較於現有的升壓型轉換器，本發明之高升壓型轉換器可使用相對較少的元件數。此外，本發明之高升壓型轉換器對應的電壓轉換比相較於現有的升壓型轉換器更易於設計。 The effect of the present invention is that the high boost converter of the present invention can use a relatively small number of components compared to existing boost converters. In addition, the voltage conversion ratio of the high boost converter of the present invention is easier to design than the conventional boost converter.
100‧‧‧高升壓型轉換器 100‧‧‧High boost converter
2‧‧‧輸出電路 2‧‧‧Output circuit
S 1‧‧‧第一開關元件 S 1 ‧‧‧first switching element
S 2‧‧‧第二開關元件 S 2 ‧‧‧Second switching element
C 1‧‧‧儲能電容 C 1 ‧‧‧ storage capacitor
C 2‧‧‧接地電容 C 2 ‧‧‧ Grounding capacitor
C o ‧‧‧輸出電容 C o ‧‧‧output capacitor
D 1‧‧‧順向導通元件 D 1 ‧‧‧ 顺通通元件
D o ‧‧‧輸出二極體 D o ‧‧‧ output diode
L k1、L k2‧‧‧漏感 L k 1 , L k 2 ‧‧‧ leakage
L m ‧‧‧激磁電感 L m ‧‧‧Magnetic inductance
N p ‧‧‧初級繞組 N p ‧‧‧Primary winding
N s ‧‧‧次級繞組 N s ‧‧‧secondary winding
R o ‧‧‧輸出電阻 R o ‧‧‧ output resistance
V i ‧‧‧輸入電壓 V i ‧‧‧ input voltage
V o ‧‧‧輸出電壓 V o ‧‧‧output voltage
本發明之其他的特徵及功效，將於參照圖式的實施例詳細說明中清楚地呈現，其中：圖1是一電路圖，說明本發明高升壓型轉換器之實施例；圖2是一波形圖，說明本發明高升壓型轉換器之各元件的電壓及電流；圖3至圖7是電路圖，說明本實施例的五種操作狀態的電流流向；圖8是一曲線圖，說明激磁電感操作模式之分界；圖9是一波形圖，說明本發明高升壓型轉換器之各元件 不考慮漏感影響的電壓及電流；圖10至圖13是預定規格元件於滿載時之量測波形。 Other features and advantages of the present invention will be apparent from the following detailed description of embodiments referring to the accompanying drawings in which: FIG. 1 is a circuit diagram illustrating an embodiment of a high boost converter of the present invention; The figure shows the voltage and current of each component of the high-boost converter of the present invention; FIG. 3 to FIG. 7 are circuit diagrams illustrating the current flow directions of the five operating states of the embodiment; FIG. 8 is a graph illustrating the magnetizing inductance. Figure 5 is a waveform diagram illustrating the components of the high boost converter of the present invention The voltage and current affected by the leakage inductance are not considered; FIG. 10 to FIG. 13 are measurement waveforms of the predetermined specification component at full load.
參閱圖1與圖2，本發明的高升壓型轉換器100電連接於一提供一輸入電壓V i 的電源，包含一第一開關元件S 1、一第二開關元件S 2、一儲能電容C 1、一接地電容C 2、一順向導通元件D 1、一初級繞組N p 、一次級繞組N s 及一輸出電路2。 Referring to FIG. 1 and FIG. 2, the high-boost converter 100 of the present invention is electrically connected to a power supply for providing an input voltage V i , including a first switching element S 1 , a second switching element S 2 , and an energy storage device A capacitor C 1 , a grounding capacitor C 2 , a forward conducting component D 1 , a primary winding N p , a primary winding N s and an output circuit 2 are provided.
第一開關元件S 1具有一第一控制端、一第一連接端及一第一驅動端，第一連接端接地。第二開關元件S 2具有一第二控制端、一第二連接端及一第二驅動端，第二連接端電性連接於第一驅動端。接地電容C 2具有兩端，一端接地及另一端電性連接於第二驅動端。順向導通元件D 1具有一電性連接於第二驅動端的第一端，及一第二端。儲能電容C 1具有兩端，一端電性連接於順向導通元件D 1的第二端及另一端電性連接於第一驅動端。初級繞組N p 的一端電性連接於電源，及另一端電性連接於儲能電容C 1的另一端。次級繞組N s 的一端電性連接於順向導通元件D 1的第二端，及另一端電性連接於輸出電路2。 The first switching element S 1 has a first control end, a first connecting end and a first driving end, and the first connecting end is grounded. The second switching element S 2 has a second control end, a second connecting end and a second driving end. The second connecting end is electrically connected to the first driving end. The grounding capacitor C 2 has two ends, one end is grounded and the other end is electrically connected to the second driving end. The forward conducting component D 1 has a first end electrically connected to the second driving end, and a second end. Storage capacitor C 1 has two ends, one end connected to the electrically conducting element along the second end D 1 of the first drive and at the other end is electrically connected to the. One end of the primary winding N p is electrically connected to the power source, and the other end is electrically connected to the other end of the storage capacitor C 1 . One end of the secondary winding N s is electrically connected to the second end of the forward conducting element D 1 , and the other end is electrically connected to the output circuit 2 .
輸出電路2具有一輸出二極體D o 、一輸出電容C o 及一輸出電阻R o ，輸出二極體D o 之陽極電性連接次級繞組N s 的另一端，輸出二極體D o 之陰極電性連接輸出電容C o 的一端及輸出電阻R o 的一端，輸出電容C o 的另一端及輸出電阻R o 的另一端皆為接地。 The output circuit 2 has an output diode D o , an output capacitor C o and an output resistor R o . The anode of the output diode D o is electrically connected to the other end of the secondary winding N s , and the output diode D o . One end of the cathode connected to one end of the output capacitor C o and an output resistor R o, the other ends of the output capacitor C o and the output resistance R o are all grounded.
本實施例中，電源提供的輸入電壓V i 經高升壓型轉換器100的轉換後產生一輸出電壓V o ，且第一開關元件S 1及第二開關元件S 2的責任週期D，次級繞組N s 及初級繞組N p 的匝數比n，且次級繞組N s 的匝數大於初級繞組N p 的匝數，高升壓型轉換器100的電壓轉換比為 In this embodiment, the input voltage V i provided by the power supply is converted by the high-boost converter 100 to generate an output voltage V o , and the duty cycle D of the first switching element S 1 and the second switching element S 2 is The turns ratio of the stage winding N s and the primary winding N p is n, and the number of turns of the secondary winding N s is greater than the number of turns of the primary winding N p , and the voltage conversion ratio of the high step-up converter 100 is
本實施例之相關符號定義：(i)輸入電壓V i 、輸出電壓V o ；(ii)儲能電容C 1、接地電容C 2之容值足夠大，使其跨壓為某一定值；(iii)T s 為切換週期；(iv)次級繞組N s 、初級繞組N p 之匝數比為n；(v)所有開關、二極體及電容均視為理想元件；(vi)第一開關元件S 1之第一控制端接受的驅動訊號與第二開關元件S 2之之第二控制端接受的驅動訊號兩者為反相；(vii)電路均操作於連續導通模式(Continuous Conduction Mode,CCM)，於一切換週期內共有五個操作狀態。各操作狀態分別說明如下。 The relevant symbol definitions in this embodiment are: (i) the input voltage V i and the output voltage V o ; (ii) the capacitance of the storage capacitor C 1 and the ground capacitor C 2 are sufficiently large to make the voltage across the certain value; Iii) T s is the switching period; (iv) the turns ratio of the secondary winding N s , the primary winding N p is n; (v) all switches, diodes and capacitors are considered ideal components; (vi) first switching element S 1 of a first control terminal receiving both the second signal and driving the switching element S 2 of the second control terminal receiving a driving signal for the inverter; (VII) circuits are operating in a continuous conduction mode (continuous conduction mode , CCM), there are five operating states in one switching cycle. The respective operational states are described below.
狀態一[ t 0 t t 1 ]：參閱圖3，第一開關元件S 1導通、第二開關元件S 2截止，順向導通元件D 1導通，輸出二極體D o 導通，此時，負載所需之能量由輸入電壓V i 、儲能電容C 1、接地電容C 2以及儲存於漏感L k2之能量提供。當於時刻t 1時，儲能電容C 1停止放電，結束狀態一。 State one [ t 0 t t 1 ]: Referring to FIG. 3, the first switching element S 1 is turned on, the second switching element S 2 is turned off, the forward conducting element D 1 is turned on, and the output diode D 0 is turned on. At this time, the energy required for the load is input. The voltage V i , the storage capacitor C 1 , the ground capacitance C 2 , and the energy stored in the leakage inductance L k 2 are supplied. When at time t 1, to stop discharging the storage capacitor C 1, an end state.
狀態二[ t 1 t t 2 ]：參閱圖4，第一開關元件S 1導通、第二開關元件S 2截止，順向導通元件D 1導通，輸出二極體D o 導通，此時，接地電容C 2對儲能電容C 1充電，儲存於漏感L k2之能量持續對負載釋能。當於時刻t 2時，耦合電感之二次側電流i Ns 降至零，結束狀態二。 State two [ t 1 t t 2 ]: Referring to FIG. 4, the first switching element S 1 is turned on, the second switching element S 2 is turned off, the forward conducting element D 1 is turned on, and the output diode D 0 is turned on. At this time, the grounding capacitor C 2 is opposite to the energy storage. Capacitor C 1 is charged, and the energy stored in the leakage inductance L k 2 continues to release energy to the load. At time t 2 , the secondary side current i Ns of the coupled inductor drops to zero, ending state two.
狀態三[ t 2 t t 3 ]：參閱圖5，第一開關元件S 1導通、第二開關元件S 2截止，順向導通元件D 1導通，輸出二極體D o 截止，此時，跨於激磁電感L m 與漏感L k1之電壓為輸入電壓V i ，故激磁電感L m 與漏感L k1皆處於激磁狀態。同時，接地電容C 2對儲能電容C 1充電，而輸出電容C o 提供負載所需的能量。當於時刻t 3時，第一開關元件S 1截止、第二開關元件S 2導通，結束狀態三。 State three [ t 2 t t 3 ]: Referring to FIG. 5, the first switching element S 1 is turned on, the second switching element S 2 is turned off, the forward conducting element D 1 is turned on, and the output diode D o is turned off, at this time, across the exciting inductance L m and Since the voltage of the leakage inductance L k 1 is the input voltage V i , both the magnetizing inductance L m and the leakage inductance L k 1 are in an excited state. Meanwhile, the ground capacitance C 2 charge the energy storage capacitor C 1, and the output capacitor C o to provide energy required by the load. When at time t 3, the first switching element S 1 is turned off, the second switching element S 2 is turned on, the end of the third state.
狀態四[ t 3 t t 4 ]：參閱圖6，第一開關元件S 1截止、第二開關元件S 2導通，順向導通元件D 1截止，輸出二極體D o 導通，此時，跨於激磁電感L m 與漏感L k1之電壓為輸入電壓V i 減去接地電容C 2上之跨壓V C2，故激磁電感L m 與漏感L k1皆處於去磁狀態。同時，輸入電壓V i 、激磁電感L m 與漏感L k1對接地電容C 2充電，並與儲能電容C 1來提供負載所需的能量。當於時刻t 4時，接地電容C 2停止充電，結束狀態四。 State four [ t 3 t t 4 ]: Referring to FIG. 6 , the first switching element S 1 is turned off, the second switching element S 2 is turned on, the forward conducting element D 1 is turned off, and the output diode D 0 is turned on, at this time, across the exciting inductance L m and The voltage of the leakage inductance L k 1 is the input voltage V i minus the voltage across the ground capacitor C 2 , V C 2 , so the magnetizing inductance L m and the leakage inductance L k 1 are in a demagnetized state. At the same time, the input voltage V i , the magnetizing inductance L m and the leakage inductance L k 1 charge the grounding capacitor C 2 and provide the energy required for the load with the storage capacitor C 1 . When at time t 4, the ground stops charging the capacitor C 2, four end state.
狀態五[ t 4 t t 0+T s ]：參閱圖7，第一開關元件S 1截止、第二開關元件S 2導通，順向導通元件D 1截止，輸出二極體D o 導通，此時，除了狀態四中所言之對負載提供能量的路徑外，接地電容C 2亦對負載提供能量。當於時刻t 0+T s 時，開關S 1導通、S 2截止，則狀態五結束，回到狀態一，完成一週期的循環。 State five [ t 4 t t 0 + T s ]: Referring to FIG. 7, the first switching element S 1 is turned off, the second switching element S 2 is turned on, the forward conducting element D 1 is turned off, and the output diode D 0 is turned on, at this time, except for the state four said path provides the energy to the load, the capacitor C 2 is grounded also provide energy load. At time t 0 + T s , switch S 1 is turned on and S 2 is turned off, state 5 ends, and state 1 is returned to complete a cycle of one cycle.
為了簡化分析，以下的電壓轉換比計算不考慮漏感L k1、L k2，並忽略狀態一及狀態二之區間。 In order to simplify the analysis, the following voltage conversion ratio calculation does not consider the leakage inductances L k 1 , L k 2 , and ignores the interval of state one and state two.
參閱圖5，可得知於狀態三下所對應的方程式為公式(1)。 Referring to FIG. 5, it can be seen that the equation corresponding to the state three is the formula (1).
參閱圖6與圖7，可得知於狀態四、狀態五下所對應的方程式為公式(2)。 Referring to FIG. 6 and FIG. 7, it can be seen that the equation corresponding to state four and state five is formula (2).
將公式(3)代入公式(1)，公式(1)可改寫為公式(4)。 Substituting equation (3) into equation (1), equation (1) can be rewritten as equation (4).
藉由激磁電感上之跨壓於穩態下需符合伏秒平衡，可得公式(5)及(6)。 Equations (5) and (6) are obtained by the volt-second balance of the cross-voltage on the magnetizing inductance in the steady state.
V i D+(V i -V C1)(1-D)=0 (5) V i D +( V i - V C 1 )(1- D )=0 (5)
將公式(5)整理後，可得公式(7)。 After formula (5) is sorted out, formula (7) is obtained.
再將公式(7)代入公式(6)，即可得電壓轉換比如公式(8)。 Substituting equation (7) into equation (6), the voltage conversion is obtained, for example, equation (8).
激磁電感之邊界條件，假設此轉換器於功率轉換時沒有任何損失，即P i =P o 。再藉由公式(8)可得公式(9)及(10)。 Magnetizing inductance of the boundary conditions, this converter is assumed without any loss at the time of power conversion, i.e., P i = P o. Equations (9) and (10) are obtained by equation (8).
因此，公式(9)可以改寫為公式(11)。 Therefore, the formula (9) can be rewritten as the formula (11).
I Lm =I i +I Np (12) I Lm = I i + I Np (12)
初級繞組N p 之平均電流I Np 為次級繞組N s 之平均電流I Ns 的n倍，而次級繞組N s 之平均電流I Ns 等於輸出電流I o ，即公式(13)。 Average current of the primary winding N p I Np n times the average of the current in the secondary winding N s I Ns, and the average current I Ns of the secondary winding N s is equal to the output current I o, i.e. formula (13).
因此，公式(12)可以改寫為公式(14)。 Therefore, the formula (12) can be rewritten as the formula (14).
I Lm =I i +nI o (14) I Lm = I i + nI o (14)
最後將公式(10)及公式(11)代入公式(14)可得公式(15)。 Finally, formula (10) and formula (11) are substituted into formula (14) to obtain formula (15).
經整理後可得公式(16)。 After finishing, formula (16) can be obtained.
由於流經激磁電感L m 的電流漣波△i Lm 可表示為公式(17)。 Since the current chopping Δi Lm flowing through the magnetizing inductance L m can be expressed as the formula (17).
因此，當2I Lm △i Lm 時，激磁電感L m 將操作於連續導通模式下，即公式(18)。 So when 2 I Lm At Δi Lm , the magnetizing inductance L m will operate in continuous conduction mode, equation (18).
參閱圖8，由公式(18)可知，次級繞組N s 及初級繞組N p 的匝數比n=2，且當K K crit (D)時，激磁電感L m 操作於連續導通模式(CCM)下；否則，將操作於不連續導通模式(DCM)。因此，可以畫出激磁電感L m 操作模式之分界曲線。 Referring to FIG. 8, it can be seen from the formula (18) that the turns ratio of the secondary winding N s and the primary winding N p is n=2, and when K For K crit (D), the magnetizing inductance L m operates in continuous conduction mode (CCM); otherwise, it will operate in discontinuous conduction mode (DCM). Therefore, the boundary curve of the operating mode of the magnetizing inductance L m can be drawn.
本實施例之元件設計規格為：(i)輸入電壓為20伏；(ii)輸出電壓為200伏；(iii)額定輸出電流為1安培，輸出最小電流為0.1安培；(iv)切換頻率為100kHz；(v)第一開關元件S 1及第二開關元件S 2的型號分別為AP70T15GP-HF及STP120NF10；(vi)順向導通元件D 1的型號為V20120C；(vii)輸出二極體D o 的型號為MUR860；(viii)儲能電容C 1的容值為220μF及接地電容C 2的容值為220μF並聯22μF；(ix)輸出電容C o 的容值為100μF；(x)FPGA(Field Programmable Gate Array，場效可程式邏輯閘陣列)控制器的型號是EP1C3T100。參閱圖10至13，為依據所述規格的元件於滿載時之量測波形。 The component design specifications of this embodiment are: (i) the input voltage is 20 volts; (ii) the output voltage is 200 volts; (iii) the rated output current is 1 amp, the output minimum current is 0.1 amp; (iv) the switching frequency is 100 kHz; (v) the first switching element S 1 and the second switching element S 2 are respectively modeled as AP70T15GP-HF and STP120NF10; (vi) the forward-conducting element D 1 is of the type V20120C; (vii) the output diode D o The model number is MUR860; (viii) The storage capacitor C 1 has a capacitance of 220 μF and the ground capacitor C 2 has a capacitance of 220 μF in parallel with 22 μF; (ix) the output capacitor C o has a capacitance of 100 μF; (x) FPGA ( Field Programmable Gate Array, the model number of the controller is EP1C3T100. Referring to Figures 10 through 13, the measured waveforms of the components according to the specifications at full load.
綜上所述，透過本發明高升壓型轉換器100，其相較於現有的升壓型轉換器，高升壓型轉換器100使用相對較少的元件數。此外，藉由初級繞組N p 及次級繞組N s 搭配儲能電容C 1及接地電容C 2來達到較高的電壓轉換比，且電壓轉換比更易於設計，故確實能達成本發明之目的。 As described above, the high-boost converter 100 of the present invention uses a relatively small number of components compared to the conventional boost converter. In addition, the primary winding N p and the secondary winding N s are combined with the storage capacitor C 1 and the grounding capacitor C 2 to achieve a higher voltage conversion ratio, and the voltage conversion ratio is easier to design, so the object of the present invention can be achieved. .
惟以上所述者，僅為本發明之實施例而已，當不能以此限定本發明實施之範圍，即大凡依本發明申請專利範圍及專利說明書內容所作之簡單的等效變化與修飾，皆仍屬本發明專利涵蓋之範圍內。 However, the above is only the embodiment of the present invention, and the scope of the present invention is not limited thereto, that is, the simple equivalent changes and modifications made by the patent application scope and the patent specification of the present invention are still It is within the scope of the patent of the present invention.
100‧‧‧高升壓型轉換器 100‧‧‧High boost converter
2‧‧‧輸出電路 2‧‧‧Output circuit
S 1‧‧‧第一開關元件 S 1 ‧‧‧first switching element
S 2‧‧‧第二開關元件 S 2 ‧‧‧Second switching element
C 1‧‧‧儲能電容 C 1 ‧‧‧ storage capacitor
C 2‧‧‧接地電容 C 2 ‧‧‧ Grounding capacitor
C o ‧‧‧輸出電容 C o ‧‧‧output capacitor
D 1‧‧‧順向導通元件 D 1 ‧‧‧ 顺通通元件
D o ‧‧‧輸出二極體 D o ‧‧‧ output diode
L k1、L k2‧‧‧漏感 L k 1 , L k 2 ‧‧‧ leakage
L m ‧‧‧激磁電感 L m ‧‧‧Magnetic inductance
N p ‧‧‧初級繞組 N p ‧‧‧Primary winding
N s ‧‧‧次級繞組 N s ‧‧‧secondary winding
R o ‧‧‧輸出電阻 R o ‧‧‧ output resistance
V i ‧‧‧輸入電壓 V i ‧‧‧ input voltage
V o ‧‧‧輸出電壓 V o ‧‧‧output voltage
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