KR20030090238A - Non Radiative Dielectric Waveguide Mixer with Mode Conversion Reflector - Google Patents

Abstract

PURPOSE: A non-radiative dielectric line mixer using a mode conversion reflector is provided to reduce a total size and obtain a broadband characteristic by using a structure of an H-coupler including a mode conversion reflector. CONSTITUTION: A non-radiative dielectric line mixer using a mode conversion reflector includes a parallel conductive plate housing, an H-coupler(100), an intermediate frequency substrate, the first mixer diode mount, and the second mixer diode mount. The H-coupler(100) is installed on the parallel conductive plate housing. The H-coupler(100) includes the first and the second ports(105,106), the third and the fourth ports(109a,109b), and a plurality of mode conversion reflectors(107a-107d). The first and the second ports(105,106) are connected to a connection portion of a side portion of the parallel conductive plate housing. The third and the fourth ports(109a,109b) are installed within the parallel conductive plate housing to provide four signal input/output ports. The mode conversion reflectors(107a-107d) are formed by cutting each edge of the H-coupler as much as 45 degrees. A T-connection circuit is formed on the intermediate frequency substrate. The first mixer diode mount is inserted between the third port(109a) and a dielectric line block. The second mixer diode mount is inserted between the fourth port(109b) and the dielectric line block.

Description

Non Radiative Dielectric Waveguide Mixer with Mode Conversion Reflector

The present invention relates to a non-radial dielectric waveguide mixer using a mode conversion reflector, and more specifically, to a millimeter wave band implemented using the principle of a mode-converting reflector having a simple configuration using a non-radial dielectric waveguide. To a non-radioelectric waveguide mixer.

Recently, efforts have been made to implement wireless communication through a transceiver in the millimeter wave region for high-capacity high-speed wireless communication. Wireless communication systems used in the millimeter wave range are mainly dominated by waveguide systems, and recently, with the development of semiconductor technology, a monolithic single chip called MMIC (Monolithic Microwave Integrated Circuit) has been developed. The waveguide method, which is a hybrid method, is lower than MMIC in mass production and price, but is advantageous in small quantity production.

Since non-radiation dielectric waveguides, which have lower transmission loss than the waveguide method, were introduced in the early 1980s, commercialization efforts and transceivers using them have been actively developed. Non-radial dielectric waveguides transmit signals with low loss through LSM mode, and the non-radio dielectric waveguides can be used to make circuits utilizing the advantages while being easily compatible with existing waveguides.

1 and 2 show the structure of a receiver using a conventional multilayer non-radial dielectric waveguide. This receiving device basically arranges non-radial dielectric lines 3 and 4 including the target frequency between two parallel metal plates of the upper plate 1 and the lower plate 2, and in the case of the receiver through the arranged lines, Local oscillation signal is input.

While the carrier is introduced by attaching the horn antenna to the 10 part of FIG. 1, the bias is applied to the gun diode in the diode mount 7 to generate the LSM mode to generate the local oscillation signal, which is generated in this process. The LSE mode is suppressed through the mode compressor 8.

The passed signal increases the transmission gain of a specific frequency band through the high dielectric resonator 9 and the like, and extracts the intermediate frequency to both ports 16 and 17 through a 3-dB coupler in band form. .

The signal from ports 16 and 17 is then introduced into the Schottky barrier diode from balanced mixer mounts 5 and 6 and passed to IF stage 12. Here, the Schottky barrier diode enters a bias voltage 13 of constant voltage and is grounded to form a closed circuit.

The structure of Fig. 1 is a typical structure of a receiver using a non-radial dielectric waveguide. Here, the coupler is designed by bending the dielectric line to bend using the principle of the parallel dielectric line coupler to construct data about the line width of the appropriate dielectric line for each bend angle. However, in the dielectric coupler, the bend cannot be reduced when it is made small, and if the bend is bent, the line width of the bend part is lost because the line width of the dielectric line is not reduced to different widths according to the corresponding frequencies. This should be reduced, but it is difficult when applied to actual production. In addition, when the parallel dielectric line coupler is applied to mass production, it is difficult to obtain accurate dielectric line spacing or bending angle, and there is a disadvantage in that isolation between ports is inferior. In addition, in order to achieve a smaller size and to reduce the size, in order to increase the bending angle, the line width of the bend portion should be reduced. However, since it is difficult to precisely reduce the line width of dielectric lines made of Teflon or the like, it is difficult to realize in actual implementation.

In view of this point, the present invention is advantageous in miniaturization by adopting a mode conversion reflector and an H-coupler designed using the principle that the transmission mode is converted with low loss when the radio signal is incident on the inclined cutting plane of the non-radial dielectric line. It is an object of the present invention to provide a non-radioelectric waveguide mixer having the advantages of easy fabrication and line arrangement.

DETAILED DESCRIPTION OF THE INVENTION The present invention will be described in detail with reference to the accompanying drawings, wherein the accompanying drawings and reference numerals representing the components are as follows.

1 is a perspective view showing the principle of a conventional parallel non-radioactive line coupler and the overall structure of a receiver using a balanced mixer.

2 is a plan view of FIG. 1.

3 is a perspective view of a non-radioactive dielectric line having a mode conversion reflector according to an embodiment of the present invention.

4 is a perspective view showing the structure of an H-coupler using a mode conversion reflector according to an embodiment of the present invention.

5 is a plan view showing the structure of an H-coupler using a mode conversion reflector having an improved structure.

6 is an exploded perspective view of a non-radial dielectric mixer using a mode conversion reflector according to the present invention.

7 is a top view of the mixer of FIG. 6.

8 is a perspective view showing the structure of a mixer diode mount used in a balanced mixer.

Fig. 9 is an equivalent circuit of the mixer constituted when the non-radial line mixer using the mode conversion reflector is applied to the receiver.

FIG. 10 is an equivalent circuit of a mixer configured when a non-radioelectric line mixer using a mode conversion reflector is applied to a transmitter. FIG.

FIG. 11 is a perspective view illustrating another embodiment of a mode conversion reflector having a structure combined with an LSM mode suppressor installed on a non-radial dielectric line.

12 is a perspective view showing another embodiment of a mode conversion reflector having a structure combined with an LSE mode suppressor installed on a non-radial dielectric line.

<Description of each part of the drawing>

100: H-Coupler

101: upper conductor plate 102: lower conductor plate

105: first port

106: second port

107: mode conversion reflector

108: coupling section

109a: third port (IF input / output port)

109b: 4th port (IF In / Out port)

110: first mixer diode mount

111: dielectric line

112: EMI filter for bias supply

113: ground pin

114: IF stage T-type junction (T-Junction)

115: IF stage substrate

116: connector for connecting IF terminal

117: ground terminal

118a ~ 118d: screw hole

119 dielectric line

120: second mixer diode mount

121: Chamfer

122: round

123: High dielectric constant sheet

124: Schottky Mixer Diodes

125: Teflon substrate

126: patch antenna

127: λ / 4 choke

128: Input port to receive signal in LSM mode

129: Output port to output signal in LSM mode

130: LSM mode suppressor

131: Input port for incoming signal in LSE mode

132: Output port for signal output in LSE mode

133: LSE mode suppressor

According to the present invention for achieving the above object,

Parallel conductor plate housings facing in parallel; And

Mounted in the parallel conductor plate housing,

The first and second non-linear dielectric lines having the same shape as the 'c'-shape are coupled to be mutually spaced apart at predetermined intervals while being at the center of each other and connected to one side of the center portion. Ports respectively extend to the connection port on the side of the housing, and the third and fourth ports connected to the other side of the center portion are located in the housing to provide four signal input / output ports while forming an H-coupling, wherein each dielectric Two orthogonally bent corners on the track have an H-coupler configured to act as a mode conversion reflector by cutting the outer portion approximately 45 degrees;

An intermediate frequency (IF) substrate on which a T-connection circuit is formed;

A patch antenna is formed on the dielectric substrate and a Schottky mixer diode is mounted across the gap of the patch antenna, and is inserted between the third port and a predetermined length of the dielectric line block, and both sides of the patch antenna A first mixer diode mount connected to a bias power supply and the T-connection circuit, respectively; And

The second mixer diode mount has the same structure as the first mixer diode mount, and is inserted between the fourth port and a predetermined length of the dielectric line block, and both sides of the patch antenna are connected to ground and the T-connection circuit, respectively. Non-dielectric waveguide mixer using an H-coupler is provided to act as a receiver or transmitter.

Preferably, a series choke and a parallel capacitor for preventing leakage of the intermediate frequency signal can be further connected between the supply side of the DC bias power supply and the ground side of the Schottky mixer diode to prevent leakage of the carrier signal and reposition the resonance pole. To provide the functionality.

Other features and advantages of the present invention will become more apparent with reference to the following detailed description and accompanying drawings that illustrate the features of various embodiments of the invention.

Hereinafter, exemplary embodiments of the present invention will be described in detail with reference to the accompanying drawings.

3 is a perspective view of a non-radioactive dielectric line having a mode conversion reflector according to an embodiment of the present invention. The mode conversion reflector 56 is a structure in which the outside of the center edge of the non-radial dielectric line bent at approximately right angles is cut out at an angle of about 45 degrees. When the wireless signal is applied to the mode conversion reflector 56 through the first port 52, the wireless signal is converted to the transmission mode and output to the second port 54 as well as the power according to the mode conversion The new feature is that the degree of loss is also very small. Previously, metal plates were added to the cut edges for reflection of the transmission signal, which caused a lot of power loss.

Based on the concept of the present invention as described above, it is possible to make an H-bonding group. 4 is a perspective view showing the H-coupler 100 according to the first embodiment. This H-coupler is constructed using the principles of the mode-converting reflector mentioned above. That is, in the case of the non-radial dielectric line, when the radio signal propagating along the line meets the inclined reflecting surface, the transmission mode is changed at the boundary surface. The present invention uses these properties to construct H-bonding groups.

The structure of the H-coupler 100 is described in detail as follows. The first and second non-radial dielectric lines having the same structure having a 'c' shape are coupled to each other by being spaced apart from each other by a predetermined distance (G1) while the middle of the coupling sections 108a and 108b are lifted from each other. On one side of these coupling sections 108a, 108b there is a transition between the input / output port of the local oscillation signal and the input / output port of the radio signal and the waveguide of the first port 105 which functions as a transition part with the waveguide. The second port 106 which is responsible for the function of the part is extended, respectively, and the third port 109a and the fourth port 109b are respectively extended to the other side. These four ports 105, 106, 109a, and 109b function as input / output ports for radio signals. The two corners that are bent at right angles on each of the dielectric lines are cut out of the outer portion by approximately 45 degrees. And nothing is attached to each cut. The portion including the cut surface of the corner of the non-radial dielectric line that is bent at right angles is the mode conversion reflector 107 mentioned in FIG. 3.

The signal transmitted in the straight section connected to each port of the non-radial dielectric line is converted to another mode while passing through the mode conversion reflectors 107a, 107b, 107c, and 107d. That is, the non-radial dielectric line transmits a signal in a low loss LSM mode. For example, when the LSM mode wireless signal input to the first port encounters the first mode conversion reflector 107a, the signal is converted into the LSE mode. . On the contrary, when the transmission mode of the applied radio signal is the LSE mode, the transmission mode of the signal propagated through the mode conversion reflector 107a and propagated to the coupling section 108a is converted into the LSM mode. Therefore, if a radio signal passes sequentially through two mode conversion reflectors, eg, first and second mode conversion reflectors 107a and 107b or sequentially through the third and fourth mode conversion reflectors 107c and 107d, The transmission mode of the radio signal is output in the original mode as when it is first applied. In addition, since a member such as a metal plate, which causes a large power loss, is not attached to the mode conversion reflector, the insertion loss also appears very small in relation to the mode conversion.

The present invention can design an H-coupler using this principle, and furthermore, implements a non-radioelectric line mixer in the millimeter wave using this H-coupler. As shown in FIG. 4, when the coupling sections 108a and 108b of the first and second non-radial dielectric lines are spaced apart by a predetermined gap G1, a coupling occurs between these two non-radial dielectric lines. It is divided into 3dB, which is half of the power, and delivered to the output port. The diagonal length L1 of each of the mode conversion reflectors 107a, 107b, 107c, and 107d is a variable directly related to the insertion loss and the reflection coefficient of the mode conversion reflector. Therefore, in order to obtain the best result in the desired frequency band, it is necessary to optimize the diagonal length L1. Many factors affect the optimization of the diagonal length (L1), which can be optimized using a tool that can analyze 3D electromagnetic waves. The length L2 of the coupling sections 108a and 108b in which mutual induction of electromagnetic waves between the two non-radial dielectric lines occurs is related to the coupling band. The shorter the length (L2), the wider the coupling band is.

5 shows the structure of the improved mode conversion reflector 100-1. 4 is a configuration in which a chamfer 121 is further added to a dielectric having the same dielectric constant as that of the non-radiative dielectric line at the inner edge portion of the mode conversion reflector 100-1. By adding the chamfer 121, the characteristics of the mode conversion reflector can be further improved. The same effect can also be obtained by the method of giving round 122. It is easy to process when manufacturing the H-coupler (100-1) made of a non-radial dielectric line in one body.

As described above, the H-coupler 100 or 100-1 made of a non-radial dielectric line can be used to make a mixer that can act as a millimeter wave radio transmitter or a radio receiver device. FIG. 6 is a perspective view illustrating a structure of a non-radioelectric waveguide mixer according to an embodiment of the present invention, in which the upper conductor plate 101 is separated from the lower conductor plate 102. 7 is a plan view of the state in which the upper conductor plate 101 of the non-radioelectric waveguide mixer of FIG. 6 is removed.

The main feature of the mixer configuration of the present invention is that it employs an H-combiner 100 or 100-1 using mode conversion reflectors 107a, 107b, 107c, 107d. In the mixer configuration of the present invention, the local oscillation unit is applied by an external local oscillation module. When connecting the waveguide type local oscillator, the first port 105 functions as a waveguide-non-dielectric dielectric transition unit so as to be connected well. In addition, if the local oscillator of the non-radial dielectric type dielectric line can be aligned and connected as it is.

The H-coupler 100 or 100-1 and each of the components connected thereto are mounted on the lower conductor plate 102 and covered and fixed by the upper conductor plate 101 facing in parallel thereto. Therefore, the H-coupler 100 or 100-1 is inserted between the upper conductor plate 101 and the lower conductor plate 102. Four corresponding corners of the upper conductor plate 101 and the lower conductor plate 102 respectively have coupling holes 104a, 104b, 104c, 104d and 104a ', 104b', 104c ', 104d' for screwing. They are each formed and assembled with screws 103a, 103b, 103c, and 103d. In the upper conductor plate 101 and the lower conductor plate 102, screw holes 118c and 118d and 118a and 118b for connecting with the standard waveguide are formed, respectively. The upper conductor plate 101 and the lower conductor plate 102 constitute a housing that is parallel to and face each other while the H-coupler 100 or 100-1 is incorporated therein. The size of the parallel plate housing may be arbitrarily determined and may vary depending on the frequency band or application of the transmitter, receiver or transceiver. The upper and lower conductor plates 101 and 102 are made of metal, for example, preferably made of aluminum so as to satisfy both conductivity and weight reduction.

In addition, an IF terminal substrate 115 for T-junction is attached to the lower conductor plate 102 at one end of each of the first mixer diode mount 110 and the second mixer diode mount 120. The signal power from the first mixer diode mount 110 and the second mixer diode mount 120 is combined through the T-Junction 114 pattern generated above. Although not shown as a different scheme from such a configuration, first IF terminal inlet holes and DC bias inlet holes are formed on both sides of the first mixer diode mount 110 and the second mixer diode mount 120, and the second mixer diode. A second IF stage inlet hole and a mixer diode mount ground hole are formed at both ends of the mount 120 to mount an EMI filter, a feed through, etc., in the inlet hole, and then the T-power under the lower conductor plate 102. The IF terminal substrate provided with the combiner 114 pattern may be attached.

8 shows the structure of the mixer diode mount constituting the mixer. A high dielectric constant sheet 123 is attached to each of the third and fourth ports 109a and 109b, and a mixer diode mount 110 or 120 and a dielectric line block 111 or 119 are added thereto. The mixer diode mount 110 or 120 shows a patch antenna 126 having a number of λ / 4 choke circuits 127 serving as a low pass filter by etching copper foil stacked on a dielectric substrate 125 made of Teflon, for example. And a Schottky mixer diode 124 coupled across the gap of the patch antenna 126. The dielectric line block 111 or 119 not only protects the attachment state of the Schottky mixer diode 124, but also serves as a so-called backshort that achieves impedance matching by allowing it to have an appropriate length according to signal wavelengths. . Since the optimum length of the dielectric line block 111 or 119 to obtain impedance matching depends on various factors such as the wavelength and frequency of the transmission signal and the size of the dielectric line, it will generally be obtained by experiment.

The bias applied from the external EMI filter 112 is connected to the left side of the first mixer diode mount 110 by a lead wire, and creates an IF signal through the Schottky mixer diode 124 of the first mixer diode mount 110. Sent to T-coupler 114. In addition, the IF signal from the second mixer diode mount 120 is connected to the T-coupler 114 on the right side, and the applied bias is connected to the ground port 117 through a lead wire connected to the left side of the second mixer diode mount 120. Ground). The ground pin 113 shown in FIG. 7 serves as a grounding function, and the conductor plates 101 and 102 may be made of aluminum, and may be mounted anywhere on the lower conductor plate 102.

Means may be further provided to enable leakage prevention of the carrier signal and position shift of the resonant pole. This means, as shown by " A " in FIG. 6, forms a grounding through hole 146 on the substrate 140 for bias application or grounding, and also prevents IF signal leakage on the substrate 140. The capacitor 144 is connected in parallel with the choke 142. This means is provided between the EMI filter 112 and the mixer diode mount 110 and the ground terminal 117 and the mixer diode mount 120 for providing a bias power, respectively, to perform the above functions.

A mixer having such a configuration may serve as a receiver or a transmitter of a wireless communication device.

First, the case of acting as a receiver will be described.

The DC bias power source provided from the bias supply EMI filter 112 is provided to the mixer diode mount 110, and the high frequency component of the DC bias power source is cut off by the bias choke 127 of the mixer diode mount 110 and the remaining low frequency component. Only is supplied to the Schottky mixer diodes 124a and 124b so that the mixer can operate.

On the other hand, suppose that the oscillation signal is introduced into the LSM mode, which is a representative mode of the non-radiative dielectric transmission mode, for example, through the first port 105. The oscillation signal of the applied LSM mode is inputted to and reflected from the mode conversion reflector 107 while traveling along the dielectric line of the H-coupler 100 or 100-1 to be converted into the LSE mode. The reflected LSE mode signal passes through the coupling sections 108a and 108b of the H-coupler 100 or 100-1, causing coupling, that is, mutual induction of electromagnetic waves, and coupling with the coupling section 108a. In each section 108b, a signal of LSE mode divided by 3 dB is delivered. These LSE mode signals, which are divided into two paths and advanced, are once again converted through the mode conversion reflectors 107b and 107d to the LSM mode, which is the original transmission mode, and along the dielectric line. Each is applied to four ports 109b.

Also in the same manner, the received radio signal is applied through the second port 106, passing through the H-coupler 100 or 100-1, and the mode conversion and coupling section 108a in the mode conversion reflector 107c. , And are transferred to the third port 109a and the fourth port 109b through another mode conversion in both mode conversion reflectors 107b and 107d.

The local oscillation signal and the received signal transmitted through the above process are mixed with each other to form an intermediate frequency signal or a baseband frequency signal which is a sum signal and a difference signal of these two signals. For example, when a 59 GHz local oscillation signal is transmitted to the first port 105 and a received signal of 60 to 61 GHz is introduced into the second port 106, the first port 105 and the fourth port 109b are respectively connected to the first port 109a and the fourth port 109b. A difference signal and a sum signal having a frequency of 2 GHz and 119 to 120 GHz are derived. At this time, the signal of the high frequency band and harmonic components effectively utilize the signal of the 1 ~ 2GHz band ignored.

9 shows an equivalent circuit of a mixer applied in a receiver. In FIG. 9, the portion labeled RF Hybrid is an H-combiner 100, and the present invention shows an example in which a 90-degree hybrid single balanced mixer is adopted. As described above, in the receiver, the Schottky mixer diodes 124a and 124b mounted to the first and second mixer diode mounts 110 and 120 are arranged in opposite directions.

The case where the mixer of the present invention acts as a transmitter is the opposite of the case where the mixer acts as a receiver.

The intermediate frequency signal required for transmission is transmitted through the connector 116 to the first mixer diode mount 110 and the second mixer diode mount 120 via the T-junction 114 on the IF terminal substrate 115. . And it is delivered to the Schottky mixer diodes (124c, 124d) inside each of the mixer diode mounts (110, 120). Meanwhile, the local oscillation signal introduced through the first port 105 passes through the mode conversion reflector 107a as described above through the H-combiner 100 to cause mode conversion and passes through the coupling sections 108a and 108b. While being divided by the reversal force, the mode is converted back to the original transmission mode through the mode conversion reflectors 107b and 107d and transmitted to the third and fourth ports 109a and 109b. Then, the two oscillating local oscillation signals are introduced into the first mixer diode mount 110 and the second mixer diode mount 120 respectively inserted at both ports and mixed with the intermediate frequency signal. The sum signal of the intermediate frequency signal and the local oscillation signal obtained by mixing the two signals is passed through the H-coupler 100 or 100-1 through the third port 109a and the fourth port 109b. Is output to 106.

The configuration of the mixer applied as a transmitter is that the Schottky mixer diode 124d mounted on the second mixer diode mount 120 is attached in a direction opposite to that at the receiver as compared with the receiver described above. That is, the direction of the Schottky mixer diodes 124c and 124d mounted to the first and second mixer dood mounts 110 and 120 when looking at the IF substrate 115 from the H-coupler 100 or 100-1. Since this is the same, it is called Same Direction Singly Balanced Mixer.

10 shows an equivalent circuit of the mixer when the mixer of the present invention is applied as a transmitter. In the transmitter, since the IF signals are introduced in the same direction, the Schottky mixer diodes 124c and 124d of the first and second mixer diode mounts 110 and 120 do not need to be changed in different directions. Only the Group Delay due to this is increased.

11 shows the structure of another embodiment of the mode conversion reflector. If you want to configure the circuit with non-radial dielectric lines, if you want to use it as a port bent vertically 90 degrees without changing the mode, change the direction of the line by blocking it with a metal plate at the 90-degree angled part 107 of the non-radiative dielectric line. You can do it. However, this method not only generates a lot of dielectric loss but can also affect other circuits as much as the width of the metal plate being blocked. Therefore, when the LSM mode suppressor 130 is inserted therein in the form of vertically cutting the non-radial dielectric line as shown in the arrangement of FIG. 11, the direction of the circuit is changed to the minimum area without reducing the dielectric loss and affecting other circuits. May be considered as an alternative.

In the structure in which the LSM mode suppressor 130 is inserted into the input port 128 as shown in FIG. 11, when the LSE mode and LSM mode wireless signals are applied to the input port 128, the LSM mode suppressor 130 is applied. Over 99% of the LSM mode is reflected and only LSE mode passes. The LSE mode signal passing through the LSM mode suppressor 130 is converted back to the LSM mode with a relatively small loss while passing through the mode conversion reflector 107. Therefore, the output port 129 outputs an LSM mode signal almost equal to the power applied from the input port 128. This method is applied to the input port 128 in the LSM mode is less loss and easier to implement than the method of outputting in the LSM mode using a bend or a corner mode conversion reflector. The LSM mode suppressor 130 is made of a structure in which a copper foil pattern is formed on a Teflon substrate in a shape of a horizontal length. By this structure, the LSE mode passes well through the LSM mode suppressor 130, but the LSM mode is well blocked.

FIG. 12 illustrates a structure in which the traveling direction of the line is bent vertically by 90 degrees without causing a mode change of an input signal when the LSE mode is applied to the non-radioactive dielectric line in the same manner as in FIG. 11. Illustrated. The LSE mode suppressor 133 is inserted into the non-radiative dielectric line between the input port 131 and the mode conversion reflector 107 in the longitudinal direction thereof. In this structure, when the signals of the transmission mode of the LSM mode and the LSE mode are applied to the input port 131, the signals of the LSE mode are all reflected by 99% or more while passing through the LSE mode suppressor 133 and pass only the LSM mode. . At this time, since the mode conversion reflector 107 is converted back to the LSE mode with a relatively small loss, the output port 132 outputs the LSE mode almost equal to the power applied from the input port 131.

11 and 12, as well as other mode conversion reflectors can be used to configure more circuits. In a circuit using non-radial dielectric lines, a mode conversion reflector may be able to construct a more efficient and miniaturized transceiver.

The mode conversion reflector described in the present invention can not only be designed vertically of 90 degrees, but also can be applied to various angles, including 135 degrees, which is a relatively popular angle.

As described above, the conventional non-radioactive line coupler is a structure that has various difficulties in miniaturization and processing. On the contrary, the present invention adopts the H-coupler structure using the mode conversion reflector, which exhibits broadband characteristics while occupying less space than the gently curved bend coupler using the parallel dielectric line coupler. It can be realized at the same time. Therefore, the broadband characteristics required in the millimeter wave range can be obtained.

In addition, since the port is formed at a right angle as compared with the conventional bend coupler, it is advantageous to machine processing or port arrangement. In addition, it is easy to arbitrarily adjust the frequency band in which coupling occurs by adjusting the length of the coupling section of the H-coupler.

However, the greatest effect of the present invention is a mode conversion reflector. By using the mode conversion reflector developed in the present invention, a directional coupler or a power divider of a specific size, as well as a 3dB coupler, can be variously configured in a non-radial dielectric line. In addition, more circuit structures can be applied in addition to mode suppressors in circuits using non-radio dielectrics.

The mode conversion reflector, the H-coupler, and the mixer using the H-coupler of the present invention can be variously modified or applied as necessary.

Although described above with reference to a preferred embodiment of the present invention, those skilled in the art various modifications and changes to the present invention without departing from the spirit and scope of the invention described in the claims below You can. Accordingly, all changes that come within the meaning or range of equivalency of the claims are to be embraced within their scope.

Claims (9)

Parallel conductor plate housings facing in parallel; And Mounted in the parallel conductor plate housing, The first and second non-linear dielectric lines having the same structure as the 'c' shape are coupled to each other by being spaced apart from each other at a predetermined interval to induce mutual induction and connected to one side of the center portion. Ports respectively extend to the connection port on the side of the housing, and the third and fourth ports connected to the other side of the center portion are located in the housing to provide four signal input / output ports while forming an H-coupling, wherein each dielectric Two orthogonally bent corners on the track have an H-coupler configured to act as a mode conversion reflector by cutting the outer portion approximately 45 degrees; An intermediate frequency (IF) substrate on which a T-connection circuit is formed; A patch antenna is formed on the dielectric substrate and a Schottky mixer diode is mounted across the gap of the patch antenna, and is inserted between the third port and a predetermined length of the dielectric line block, and both sides of the patch antenna A first mixer diode mount connected to a bias power supply and the T-connection circuit, respectively; And The second mixer diode mount has the same structure as the first mixer diode mount, and is inserted between the fourth port and a predetermined length of the dielectric line block, and both sides of the patch antenna are connected to ground and the T-connection circuit, respectively. Non-dielectric waveguide mixer using an H-coupler, characterized in that acts as a receiver or transmitter. The schottky mixer diode mounted on the first mixer diode mount and the schottky mixer diode mounted on the second mixer diode mount are disposed in opposite directions. The wireless signal and the oscillation signal introduced through the first port and the second port are mutually induced while passing through the coupling section of the H-coupler and transmitted to the third port and the fourth port, respectively, and the Schottky mixer. A non-dielectric waveguide mixer using an H-coupler, characterized in that a mixture of diodes is made of a sum signal and a difference signal to obtain an intermediate frequency signal through the T-connection circuit. The schottky mixer diode mounted on the first mixer diode mount and the schottky mixer diode mounted on the second mixer diode mount are disposed in the same direction. The intermediate frequency signal is transmitted to the Schottky mixer diode through the first and second mixer diode mounts, and the local oscillation signal applied through the first port is mutually induced while passing through the coupling section of the H-coupler. An H-coupler coupled to the first and second mixer diode mounts to be mixed with the intermediate frequency signal to form a sum signal, and the sum signal is output through the second port through the coupling section. A nonradioactive waveguide mixer. The non-dielectric waveguide mixer of claim 1, wherein the mode conversion reflector converts and outputs the LSE mode when the incident signal is in the LSM mode, and converts and outputs the LSM mode when the incident signal is the LSE mode. The non-radioelectric waveguide mixer according to claim 1, wherein a chamfer or round member is further added to an inner edge of each mode conversion reflector of the H-coupler. The slug of claim 1, further comprising a high dielectric constant sheet disposed between the third port and the dielectric substrate of the first mixer diode mount or between the fourth port and the dielectric substrate of the second mixer diode mount. Dielectric waveguide mixer. 2. The apparatus according to claim 1, further comprising a series choke for preventing leakage of an IF signal on a side of the DC bias power supply and a ground side of the Schottky mixer diode to prevent leakage of a carrier signal and shift a position of a resonance pole. A non-radioelectric waveguide mixer, characterized in that the parallel capacitor is further connected. The LSM mode suppressor according to claim 1, further comprising an LSM mode suppressor inserted between the port of the first and / or second non-radiative dielectric line and a mode conversion reflector to block passage of a radio signal in an LSM mode. Nonradioactive waveguide mixer. The LSE mode suppressor according to claim 1, further comprising an LSE mode suppressor inserted between the port of the first and / or second non-radiating dielectric line and a mode conversion reflector to block passage of an LSE mode radio signal. Nonradioactive waveguide mixer.