JPS6037665B2 - Phase synchronization method - Google Patents
Phase synchronization methodInfo
- Publication number
- JPS6037665B2 JPS6037665B2 JP55148147A JP14814780A JPS6037665B2 JP S6037665 B2 JPS6037665 B2 JP S6037665B2 JP 55148147 A JP55148147 A JP 55148147A JP 14814780 A JP14814780 A JP 14814780A JP S6037665 B2 JPS6037665 B2 JP S6037665B2
- Authority
- JP
- Japan
- Prior art keywords
- phase
- frequency
- reference signal
- circuit
- signal
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Expired
Links
Classifications
-
- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
- H04L7/00—Arrangements for synchronising receiver with transmitter
- H04L7/02—Speed or phase control by the received code signals, the signals containing no special synchronisation information
- H04L7/033—Speed or phase control by the received code signals, the signals containing no special synchronisation information using the transitions of the received signal to control the phase of the synchronising-signal-generating means, e.g. using a phase-locked loop
- H04L7/0331—Speed or phase control by the received code signals, the signals containing no special synchronisation information using the transitions of the received signal to control the phase of the synchronising-signal-generating means, e.g. using a phase-locked loop with a digital phase-locked loop [PLL] processing binary samples, e.g. add/subtract logic for correction of receiver clock
Description
【発明の詳細な説明】
本発明はデータ伝送の信号処理における位相同期方式に
関し、例えば、電話回線を使用してデータ伝送を行うデ
ータモデム等における位相同期方式に関する。DETAILED DESCRIPTION OF THE INVENTION The present invention relates to a phase synchronization method in signal processing for data transmission, and for example, to a phase synchronization method in a data modem or the like that transmits data using a telephone line.
一般にデータモデムは、その送信部でデータ端末装置か
らの送信ヱレメント同期信号に同期してデータを取込み
、取込んだデータを変調して送信する。Generally, a data modem captures data in its transmitter in synchronization with a transmission element synchronization signal from a data terminal device, modulates the captured data, and transmits the modulated data.
また、データモデムの受信部では受信信号から変調速度
成分を抽出し、抽出された変調速度成分に同期して受信
信号を復調する。送信部および受信部におけるこれらの
同期精度は、CCITTV27やV29の勧告によれば
、±0.01%と規定されている。Further, the receiving section of the data modem extracts the modulation rate component from the received signal and demodulates the received signal in synchronization with the extracted modulation rate component. According to the recommendations of CCITTV27 and V29, the synchronization accuracy in the transmitter and receiver is defined as ±0.01%.
この同期精度を達成するために、従来は低域フィル夕、
電圧制御発振器(VCO)等のアナログ装置を用いてい
たが、アナログ装置は外乱に弱いという欠点を有する。
本発明の目的は、前述の如き送信ヱレメント同期信号や
抽出された変調速度成分の如き基準信号の位相と、デー
タの取込みや復調等の処理の位相とをディジタル的に同
期させることにより、データ伝送の信号処理において安
定かつ高い同期精度を達成することにある。To achieve this synchronization accuracy, conventional low-pass filters,
Analog devices such as voltage controlled oscillators (VCOs) have been used, but analog devices have the disadvantage of being susceptible to external disturbances.
An object of the present invention is to digitally synchronize the phase of a reference signal such as a transmission element synchronization signal or an extracted modulation rate component as described above with the phase of processing such as data acquisition and demodulation, thereby improving data transmission. The aim is to achieve stable and high synchronization accuracy in signal processing.
上述の目的を達成するために、本発明においては、命令
の繰返し実行処理周波数が既知である計算回路で基準信
号を読み込み、読み込んだ該基準信号の位相と該計算回
路の繰返し実行処理の位相とを比較して、該比較の結果
、該繰返し実行処理の位相が該基準信号の位相より早い
場合は特定の命令を実行させて該繰返し実行処理周波数
を減少させ、該繰返し実行処理の位相が該基準信号の位
相より遅い場合は特定の命令の実行を省略して該繰返し
実行処理周波数を増大させるようにした事を特徴とする
位相同期方式が提案される。In order to achieve the above object, in the present invention, a reference signal is read in a calculation circuit whose instruction repetition execution processing frequency is known, and the phase of the read reference signal and the phase of the repetition execution processing of the calculation circuit are calculated. As a result of the comparison, if the phase of the repetitive execution process is earlier than the phase of the reference signal, a specific instruction is executed to decrease the frequency of the repetitive execution process, and the phase of the repetitive execution process is A phase synchronization method is proposed in which the execution of a specific command is omitted when the phase is slower than that of the reference signal, and the repeat execution processing frequency is increased.
以下、添附の図面に基づき、本発明による位相同期方式
の1実施例を従来方式と対比しながら説明する。Hereinafter, one embodiment of the phase synchronization method according to the present invention will be described in comparison with a conventional method based on the accompanying drawings.
第1図は従来の位相同期回路を示すブロック図であって
、周知のPLL回路構成となっている。FIG. 1 is a block diagram showing a conventional phase synchronization circuit, which has a well-known PLL circuit configuration.
第1図において、周波数fRの基準信号の位相と周波数
fvの追従信号の位相とが位相比較器1によつて比較さ
れ、この比較結果から得られた位相差信号に含まれる高
周波成分は低域フィル夕2によって除去され、低域フィ
ル夕2の出力電圧でVC03を制御する。VC03の出
力周波数をカウンタ4で1/N‘こしたものが追従信号
の周波数fvとなって、位相比較器1に帰還される。こ
うして追従信号は基準信号にアナログ的に同期させられ
るが、前述の如く、低域フィル夕2やVC03は外部雑
音による影響を受けやすいので、同期動作は不安定であ
り、VC03の調整をいまいま必要とするので操作が煩
雑であり、高い同期精度が得られない。第2図は本発明
による位相同期方式を概略的に説明するためのディジタ
ル形位相同期回路を示すフロック図である。In FIG. 1, the phase of the reference signal of frequency fR and the phase of the follow-up signal of frequency fv are compared by phase comparator 1, and the high frequency components contained in the phase difference signal obtained from this comparison result are low frequency components. It is removed by filter 2, and the output voltage of low-pass filter 2 controls VC03. The output frequency of the VC03 is divided by 1/N' by the counter 4 and becomes the frequency fv of the follow-up signal, which is fed back to the phase comparator 1. In this way, the follow-up signal is analog-synchronized with the reference signal, but as mentioned above, the low-pass filter 2 and VC03 are easily affected by external noise, so the synchronization operation is unstable, so it is difficult to adjust VC03. The operation is complicated, and high synchronization accuracy cannot be obtained. FIG. 2 is a block diagram showing a digital phase synchronization circuit for schematically explaining the phase synchronization method according to the present invention.
第2図において、発振器(OSC)1 1の出力周波数
は基準信号の周波数fRのN倍より少し高い。発振器1
1からの出力信号は歯抜回路(RMT)12を介してカ
ウンタ13に入力される。カウンタ13はその入力信号
周波数を1/Nに分周して出力する。カウンタの出力信
号の周波数fvは位相比較器11によって基準信号の周
波数fRと比較され、この比較の結果の位相差信号は歯
抜回路12の制御信号としてその制御入力に帰還される
。周波数fvが周波数fRより高い場合、その周波数差
に応じた数のパルスが歯抜回路によって発振器11の出
力信号から除去されるので、周波数fvは低くなる。こ
のループを繰返す事によりカウン夕の出力信号と基準信
号との位相同期がとれる。第3図は本発明による位相同
期方式の一実施例を説明するための更に詳細なブロック
図である。In FIG. 2, the output frequency of the oscillator (OSC) 11 is slightly higher than N times the frequency fR of the reference signal. Oscillator 1
The output signal from 1 is input to a counter 13 via a tooth extraction circuit (RMT) 12. The counter 13 divides the input signal frequency into 1/N and outputs the divided signal. The frequency fv of the output signal of the counter is compared with the frequency fR of the reference signal by a phase comparator 11, and the phase difference signal resulting from this comparison is fed back to the control input of the tooth extraction circuit 12 as a control signal. When the frequency fv is higher than the frequency fR, the number of pulses corresponding to the frequency difference is removed from the output signal of the oscillator 11 by the tooth extraction circuit, so the frequency fv becomes lower. By repeating this loop, phase synchronization can be achieved between the output signal of the counter and the reference signal. FIG. 3 is a more detailed block diagram for explaining one embodiment of the phase synchronization method according to the present invention.
第2図と第3図において、第2図のカウンタ13は第3
図の遅延回路D.,D2,D3,・・・,Dnからなる
カウンタ13に対応している。遅延回路D.ないしDn
の各遅延回路tDは実質的に一定である。第2図の歯
抜回路12は第3図のスイッチ21、遅延回路Doおよ
びオアゲート22からなる歯抜回路12に対応している
。第2図の位相比較器14は第3図の読取回路23およ
びスイッチ切換回路24に対応している。第3図におい
て、読取回路23は外部から周波数fRの基準クロツク
信号を受取り、これを遅延回路Dnからの周波数fvの
信号と比較する。この比較の結果、読取回路に接続され
たスイッチ切換回路24はスイッチ21を駆動してfR
がfvより大の場合は遅延回路Dnの出力をスイッチ2
1の接点26に接続させ、fRがfvより小の場合は遅
延回路Dnの出力をスイッチ21の接点27に接続させ
る。前者の場合には繰返し実行処理の周波数fvは遅延
回路D,,D2.・・・,Dnの一周総遅延時間nt。
の逆数に等しくなり、後者の場合には周波数fvは遅延
回路Do,D,,D2,…,Dnの一周総遅延時間(n
十1)t。の逆数に等しくなる。従って遅延回路Dnの
出力には、周波数1/nらを上限とし周波数1/(n十
1)toを下限とする可変周波数の信号が得られる。す
なわち、第3図の回路は可変周波数発振器(VFO)と
して動作する。シフトレジスタで遅延回路を構成する場
合の様に、遅延時間toとクロック周期が同じとき各遅
延回路を駆動させるクロック発振器(OSC)28の出
力周期は基準信号の周波数fRが1/nt。と1/(n
+1)toのほぼ中間値となるように遅延時間tDを決
定する。第3図の回路の上記の動作によって、基準信号
の立上りに遅延回路Dnの出力信号の立上りが同期する
。2 and 3, the counter 13 in FIG.
Delay circuit D. , D2, D3, . . . , Dn. Delay circuit D. Or Dn
Each delay circuit tD is substantially constant. The tooth extraction circuit 12 in FIG. 2 corresponds to the tooth extraction circuit 12 shown in FIG. 3, which includes the switch 21, the delay circuit Do, and the OR gate 22. The phase comparator 14 in FIG. 2 corresponds to the reading circuit 23 and switch changeover circuit 24 in FIG. 3. In FIG. 3, reading circuit 23 receives an external reference clock signal of frequency fR and compares it with a signal of frequency fv from delay circuit Dn. As a result of this comparison, the switch changeover circuit 24 connected to the reading circuit drives the switch 21 so that fR
is larger than fv, the output of the delay circuit Dn is switched to switch 2.
If fR is smaller than fv, the output of the delay circuit Dn is connected to the contact 27 of the switch 21. In the former case, the frequency fv of the repetitive execution process is determined by the delay circuits D, , D2 . ..., one round total delay time nt of Dn.
In the latter case, the frequency fv is the total delay time (n
11)t. is equal to the reciprocal of Therefore, a variable frequency signal having an upper limit of frequency 1/n and a lower limit of frequency 1/(n+1)to is obtained as the output of the delay circuit Dn. That is, the circuit of FIG. 3 operates as a variable frequency oscillator (VFO). When the delay time to and the clock cycle are the same, as in the case of constructing a delay circuit using a shift register, the output cycle of the clock oscillator (OSC) 28 that drives each delay circuit is such that the frequency fR of the reference signal is 1/nt. and 1/(n
+1) Determine the delay time tD so that it is approximately the intermediate value of to. By the above operation of the circuit shown in FIG. 3, the rise of the output signal of the delay circuit Dn is synchronized with the rise of the reference signal.
すなわち、第4図aの基準信号の立上りに対して第4図
bの遅延回路Dnの出力信号の立上りが時間ちだけ進ん
でいる場合はfRがfvより小であるので前述の如くf
vの周波数は減少させられて遅延回路Doの遅延時間t
oだけ遅延回路Dnの出力信号の位相が遅れる。また、
基準信号の立上りに対して遅延回路Dnの出力信号の立
上りが時間t2だけ遅れている場合には逆に遅延回路D
nの出力信号の位相が早められる。このようにして遅延
回路Dnの出力信号の位相を早めたり遅めたりする事に
より、同期がとられる。基準信号の立上りと遅延回路の
出力の立上りで位相同期させる場合は、スイッチ21の
接点26および27への接続を前述と反対にすればよい
。第3図の回路は実際的には、例えば富士通株式会社製
のMB8881またはインテルi8048シリーズとい
った、マイクロコンピュータによって実現できる。That is, if the rise of the output signal of the delay circuit Dn of FIG. 4B is ahead of the rise of the reference signal of FIG.
The frequency of v is decreased and the delay time t of the delay circuit Do
The phase of the output signal of the delay circuit Dn is delayed by o. Also,
Conversely, when the rise of the output signal of the delay circuit Dn is delayed by the time t2 with respect to the rise of the reference signal, the delay circuit D
The phase of the output signal of n is advanced. Synchronization is achieved by advancing or delaying the phase of the output signal of the delay circuit Dn in this manner. If phase synchronization is to be achieved between the rising edge of the reference signal and the rising edge of the output of the delay circuit, the connection of the switch 21 to the contacts 26 and 27 may be reversed to that described above. The circuit of FIG. 3 can actually be realized by a microcomputer such as the MB8881 manufactured by Fujitsu Limited or the Intel i8048 series.
この場合は遅延回路D,,D2,…,Dn‐2の各々は
任意の処理命令で置きかえられ、遅延回路Doは例えば
無効命令(NOOPE−RATION)等の特定命令で
置き替えられる。遅延回路Dn‐,は基準信号の読取命
令に、そして遅延回路Dnは位相比較のために条件分岐
命令に置き替えられる。マイクロコンピュ−夕で位相同
期回路を実現する場合の動作のフローチャートの1例を
第5図に示す。第5図において、第1ステップで、マイ
クロコンピュータの外部から入力された基準信号の周波
数fRとマイクロコンピュータの繰返し実行処理の周波
数fvの位相比較を行い、この比較の結果、fvが進ん
でいれば第2ステップへ、遅れていれば第3ステップに
飛ぶ。第3ステップ以降第nステップまでは任意の処理
ができるが実行時間の合計はD,からDn‐2の合計と
等しくする。第n+1ステップでは基準信号の議取りを
も行う。第n+1ステップの次は再び第1ステップに戻
る。第1ステップにおける比較の結果に従って、第2ス
テップのDoの処理を行ったり行わなかったりすること
により繰返し実行処理の周波数の増減を行い、それによ
り位相同期が達成される。基準信号の論取りは第n十1
ステップ以外の他のステップで行ってもよい。なお、第
3図および第5図において、基準信号周波数と繰返し実
行処理周波数との比較の結果、省略することがある処理
をDoのみとしたが更に他の無効命令を設けて同期精度
を高くすることも可能である。In this case, each of the delay circuits D, D2, . The delay circuit Dn-, is replaced by a reference signal read instruction, and the delay circuit Dn is replaced by a conditional branch instruction for phase comparison. FIG. 5 shows an example of a flowchart of the operation when realizing a phase-locked circuit in a microcomputer. In FIG. 5, in the first step, a phase comparison is made between the frequency fR of the reference signal input from the outside of the microcomputer and the frequency fv of the repetitive execution process of the microcomputer, and as a result of this comparison, if fv is advanced, then Go to the second step, and if you are behind, jump to the third step. Any processing can be performed from the third step to the n-th step, but the total execution time is made equal to the sum of D to Dn-2. At the (n+1)th step, a reference signal is also negotiated. After the (n+1)th step, the process returns to the first step again. According to the comparison result in the first step, the frequency of the repetitive execution process is increased or decreased by performing or not performing the Do process in the second step, thereby achieving phase synchronization. The discussion of the reference signal is the nth eleventh.
It may be performed in steps other than step. In addition, in FIGS. 3 and 5, as a result of the comparison between the reference signal frequency and the repetitive execution processing frequency, only "Do" is considered as the process that may be omitted, but other invalid commands are also provided to increase the synchronization accuracy. It is also possible.
以上の説明から明らかなように、本発明によれば基準信
号の位相とデータ処理の繰返し処理の位相とをディジタ
ル装置を用いて同期させることができるので、データ伝
送の信号処理において安定かつ高い同期精度が達成され
る。As is clear from the above description, according to the present invention, it is possible to synchronize the phase of the reference signal and the phase of repetitive data processing using a digital device, thereby achieving stable and high synchronization in signal processing for data transmission. Accuracy is achieved.
また、マイクロコンピュータによるソフトウェアにて位
相同期を確立することにより、同じマイクロコンピュー
タに他の機能、例えば変調やスクランブラ等の機能を含
める事もできる。Further, by establishing phase synchronization using software by a microcomputer, other functions such as modulation and scrambler functions can be included in the same microcomputer.
第1図は従来の位相同期回路を示すブロック図、第2図
は本発明による位相同期方式を概略的に説明するための
ディジタル形位相同期回路を示すブロック図、第3図は
本発明による位相同期方式の一実施例を説明するための
更に詳細なブロック図、第4図aは基準信号の1例を示
す波形図、第4図bは遅延回路Dnの出力信号の1例を
示す波形図、第5図は第3図の回路をマイクロコンピュ
ータで実現した場合の動作の1実施例のフローチャート
である。
1:位相比較器、2:低域フィル夕、3:電圧制御発振
器、4:カウンタ、11:発振器、12:歯抜回路、1
3:カウント、14:位相比較器、21:スイッチ、2
3:論取回路、24:スイッチ切換回路、26,27:
スイッチ21の接点、28:クロック発振器、Do,D
,,…,Dn:遅延回路。
第1図
第2図
第3図
第4図
第5図FIG. 1 is a block diagram showing a conventional phase locking circuit, FIG. 2 is a block diagram showing a digital phase locking circuit for schematically explaining the phase locking method according to the present invention, and FIG. 3 is a block diagram showing a phase locking circuit according to the present invention. A more detailed block diagram for explaining one embodiment of the synchronization method, FIG. 4a is a waveform diagram showing an example of a reference signal, and FIG. 4b is a waveform diagram showing an example of the output signal of the delay circuit Dn. , FIG. 5 is a flowchart of one embodiment of the operation when the circuit of FIG. 3 is implemented by a microcomputer. 1: Phase comparator, 2: Low-pass filter, 3: Voltage controlled oscillator, 4: Counter, 11: Oscillator, 12: Tooth extraction circuit, 1
3: Count, 14: Phase comparator, 21: Switch, 2
3: Discussion circuit, 24: Switch switching circuit, 26, 27:
Contact of switch 21, 28: Clock oscillator, Do, D
,,...,Dn: delay circuit. Figure 1 Figure 2 Figure 3 Figure 4 Figure 5
Claims (1)
で基準信号を読み込み、読み込んだ該基準信号の位相と
該計算回路の繰返し実行処理の位相とを比較して、該比
較の結果、該繰返し実行処理の位相が該基準信号の位相
より早い場合は特定の命令を実行させて該繰返し実行処
理周波数を減少させ、該繰返し実行処理の位相が該基準
信号の位相より遅い場合は特定の命令の実行を省略して
該繰返し実行処理周波数を増大させるようにした事を特
徴とする位相同期方式。1 A reference signal is read in a calculation circuit whose repetitive execution processing frequency of the instruction is known, the phase of the read reference signal is compared with the phase of the repetitive execution processing of the calculation circuit, and as a result of the comparison, the repetition execution processing frequency of the instruction is known. If the phase of the process is faster than the phase of the reference signal, execute a specific instruction to reduce the repetitive execution processing frequency, and if the phase of the repetitive execution process is slower than the phase of the reference signal, execute the specific instruction. A phase synchronization method characterized in that the repeat execution processing frequency is increased by omitting the above.
Priority Applications (1)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
JP55148147A JPS6037665B2 (en) | 1980-10-24 | 1980-10-24 | Phase synchronization method |
Applications Claiming Priority (1)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
JP55148147A JPS6037665B2 (en) | 1980-10-24 | 1980-10-24 | Phase synchronization method |
Publications (2)
Publication Number | Publication Date |
---|---|
JPS5773545A JPS5773545A (en) | 1982-05-08 |
JPS6037665B2 true JPS6037665B2 (en) | 1985-08-27 |
Family
ID=15446310
Family Applications (1)
Application Number | Title | Priority Date | Filing Date |
---|---|---|---|
JP55148147A Expired JPS6037665B2 (en) | 1980-10-24 | 1980-10-24 | Phase synchronization method |
Country Status (1)
Country | Link |
---|---|
JP (1) | JPS6037665B2 (en) |
Cited By (2)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
JPS6330691A (en) * | 1986-07-23 | 1988-02-09 | 堀井 清之 | Flow-path changeable bent pipe |
JPS6353961U (en) * | 1986-09-29 | 1988-04-11 |
Families Citing this family (2)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
JPS60142623A (en) * | 1983-12-28 | 1985-07-27 | Matsushita Graphic Commun Syst Inc | Digital pll circuit |
JPH01293039A (en) * | 1988-05-20 | 1989-11-27 | Nitsuko Corp | Synchronizing system |
-
1980
- 1980-10-24 JP JP55148147A patent/JPS6037665B2/en not_active Expired
Cited By (2)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
JPS6330691A (en) * | 1986-07-23 | 1988-02-09 | 堀井 清之 | Flow-path changeable bent pipe |
JPS6353961U (en) * | 1986-09-29 | 1988-04-11 |
Also Published As
Publication number | Publication date |
---|---|
JPS5773545A (en) | 1982-05-08 |
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