JPH0219025A - Phase locked loop circuit - Google Patents
Phase locked loop circuitInfo
- Publication number
- JPH0219025A JPH0219025A JP63168299A JP16829988A JPH0219025A JP H0219025 A JPH0219025 A JP H0219025A JP 63168299 A JP63168299 A JP 63168299A JP 16829988 A JP16829988 A JP 16829988A JP H0219025 A JPH0219025 A JP H0219025A
- Authority
- JP
- Japan
- Prior art keywords
- output
- phase
- frequency
- circuit
- locked loop
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Pending
Links
- 230000004069 differentiation Effects 0.000 abstract description 3
- 238000006243 chemical reaction Methods 0.000 abstract description 2
- 238000010586 diagram Methods 0.000 description 5
- 230000000694 effects Effects 0.000 description 2
- 238000000034 method Methods 0.000 description 1
- 230000000630 rising effect Effects 0.000 description 1
Landscapes
- Stabilization Of Oscillater, Synchronisation, Frequency Synthesizers (AREA)
Abstract
Description
【発明の詳細な説明】
イ、[発明の目的J
〔産業上の利用分野〕
本発明は、主として周波数シンセサイザに使用する高分
解能PLI、(phase 1ocked 1oop
)回路の、特性の改良に関するものである。Detailed Description of the Invention A. Objective of the Invention [Field of Industrial Application] The present invention provides a high-resolution PLI (phase 1ocked 1oop
) relates to improvements in the characteristics of circuits.
第5図に従来の位相同期ループ回路の例を示す。 FIG. 5 shows an example of a conventional phase-locked loop circuit.
電圧制御発振器(Voltaae Controlle
d 0scillat。Voltae Control Oscillator
d 0scillat.
r=以下VCOと呼ぶ)21の出力を分周器22で整数
分周(整数分の1の周波数に分周すること)した信号を
基準発振器23からの基準信号と位相比較器24におい
て比較し、低域フィルタ25を介してその位相差に応じ
た制御電圧をVCO21に帰還することにより、VCO
21の出力周波数roを基準周波数frに位相ロックす
る。r = hereinafter referred to as VCO) 21 is divided by an integer frequency by a frequency divider 22 (dividing the frequency by a fraction of an integer), and a signal is compared with a reference signal from a reference oscillator 23 by a phase comparator 24. , by feeding back a control voltage corresponding to the phase difference to the VCO 21 via the low-pass filter 25, the VCO
The output frequency ro of 21 is phase-locked to the reference frequency fr.
しかしながら、上記の方式では出力の周波数fOを基準
周波数frの整数倍以外の値とすることはできない、基
準発振器23の周波数を低くして分周回路22の分周比
を大きくすれば、分解能を向上できるが、位相ロックに
必要な時間が長くなり、応答速度が遅くなる。However, in the above method, it is not possible to set the output frequency fO to a value other than an integral multiple of the reference frequency fr.If the frequency of the reference oscillator 23 is lowered and the division ratio of the frequency divider circuit 22 is increased, the resolution can be improved. Although this can be improved, the time required for phase locking becomes longer and the response speed becomes slower.
本発明は、上記のような問題点を解決するためになされ
たもので、基準周波数を低くすることなく基準周波数の
整数倍より高分解能の位相同期ルプ回路を実現すること
を目的とする。The present invention has been made to solve the above-mentioned problems, and an object of the present invention is to realize a phase-locked loop circuit with higher resolution than an integral multiple of the reference frequency without lowering the reference frequency.
口、「発明の構成」
〔問題点を解決するための手段〕
本発明は電圧制御発振器の出力を分周回路で分周しこの
分周器の出力と基準信号との位相差を位相比較器で検出
し位相比較器の出力に対応する信号で電圧制御発振器の
出力周波数を制御する位相同期ループ回路に係るもので
、その特徴とするところは位相比較器から出力される位
相差信号の単位時間当たりの変化量が一定となるように
電圧制御発振器を制御する制御手段を備える点にある。``Structure of the Invention'' [Means for Solving Problems] The present invention divides the output of a voltage controlled oscillator using a frequency dividing circuit, and calculates the phase difference between the output of the frequency divider and a reference signal using a phase comparator. This circuit is related to a phase-locked loop circuit that controls the output frequency of a voltage-controlled oscillator using a signal that is detected by a signal that corresponds to the output of a phase comparator. The present invention is characterized in that it includes a control means for controlling the voltage controlled oscillator so that the amount of change in winning is constant.
基準信号と分周回路出力の周波数の差は位相差信号の単
位時間当たりの変化量に対応するので、変化量を制御す
ることにより周波数を連続的に変えることができる。Since the difference in frequency between the reference signal and the frequency dividing circuit output corresponds to the amount of change in the phase difference signal per unit time, the frequency can be changed continuously by controlling the amount of change.
以下、図面を用いて本発明の詳細な説明する。 Hereinafter, the present invention will be explained in detail using the drawings.
第1図は、本発明に係る位相同期ループ回路の一実施例
を示した図である。1はVCO52はVColの出力周
波数を整数分周する分周回路、3は周波数frの基準信
号を出力する基準発振器、4は基準信号と分周回路2の
出力の位相差を電圧出力する位相比較器、5は位相比較
器4の出力をA/D変換するA/D変換器、6はA/D
変換器5のデジタル出力を入力してVCOIを制御する
制御回路である。A/D変換器5および制御回路6は位
相比較器4の出力に等測的な微分動作を行う微分回路7
を構成する。FIG. 1 is a diagram showing an embodiment of a phase-locked loop circuit according to the present invention. 1 is a frequency dividing circuit in which the VCO 52 divides the output frequency of the VCol by an integer, 3 is a reference oscillator that outputs a reference signal of frequency fr, and 4 is a phase comparison circuit that outputs the phase difference between the reference signal and the output of the frequency dividing circuit 2 as a voltage. 5 is an A/D converter that A/D converts the output of the phase comparator 4; 6 is an A/D converter;
This is a control circuit that inputs the digital output of the converter 5 and controls the VCOI. The A/D converter 5 and the control circuit 6 include a differentiation circuit 7 that performs an isometric differentiation operation on the output of the phase comparator 4.
Configure.
VCOIの出力周波数f、が基準信号の周波数frの整
数倍でないときは、位相比較器4の出力は第2図に示す
ような鋸歯状波となる。これは基準信号と分周回路2の
出力の位相のずれが2πとなる度に再び位相比軸器4の
出力が0に戻るためである。第2図の鋸歯状波において
傾きθと周期Tは位相比較器4に入力する2つの信号の
周波数の差の大きさによって決まるから、微分回路7に
よりこの鋸歯状波の微分値が一定になるようにVCOl
に帰還をかければ、出力周波数foが基準信号の周波数
frの整数倍でないときにも位相ロックをかけることが
できる。19&分回路7において、A/D変換器は第2
図の鋸歯状波を適当な時間間隔でサンプリングしてA/
D変換し、各サンプル毎のデジタル出力の差分が一定と
なるように制御回路6がvcotに制御電圧を出力する
。したがって上述の差分の目標値を変化することにより
、基準周波数frを変えることなしに出力周波数fOを
高分解能に変化することができる。出力周波数foが基
準信号の周波数ffの整数倍であるときは位相比較器の
位相差出力、制御回路6の出力の変化はOとなり、従来
の場合と同様に適当な分周比で位相ロックする。When the output frequency f of the VCOI is not an integral multiple of the frequency fr of the reference signal, the output of the phase comparator 4 becomes a sawtooth wave as shown in FIG. This is because the output of the phase ratio axis device 4 returns to 0 again every time the phase difference between the reference signal and the output of the frequency dividing circuit 2 becomes 2π. Since the slope θ and period T of the sawtooth wave shown in FIG. 2 are determined by the magnitude of the difference in frequency between the two signals input to the phase comparator 4, the differential value of this sawtooth wave is made constant by the differentiating circuit 7. Like VCOl
By applying feedback to , phase lock can be applied even when the output frequency fo is not an integral multiple of the frequency fr of the reference signal. 19 & branch circuit 7, the A/D converter is connected to the second
Sample the sawtooth wave in the figure at appropriate time intervals and use A/
After D conversion, the control circuit 6 outputs a control voltage to vcot so that the difference in digital output for each sample is constant. Therefore, by changing the target value of the above-mentioned difference, the output frequency fO can be changed with high resolution without changing the reference frequency fr. When the output frequency fo is an integral multiple of the frequency ff of the reference signal, the change in the phase difference output of the phase comparator and the output of the control circuit 6 becomes O, and the phase is locked at an appropriate frequency division ratio as in the conventional case. .
このような構成の位相同期ループ回路によれば、基準周
波数を低くすることなしに高分解能のPLL回路を実現
でき、高分解能と短いロック時間とを両立させることが
できる。According to the phase-locked loop circuit having such a configuration, a high-resolution PLL circuit can be realized without lowering the reference frequency, and high resolution and short lock time can be achieved at the same time.
第3図は本発明に係る位相同期ループ回路の第2の実施
例を示す構成ブロック図である。第1図と同じ部分は同
一の記号を付して説明を省略する。FIG. 3 is a block diagram showing a second embodiment of the phase-locked loop circuit according to the present invention. The same parts as in FIG. 1 are given the same symbols and the explanation is omitted.
第1図の場合と異なり位相比較器14が例えばエツジト
リガ形のように、位相差に対応したパルス幅を出力する
場合を示し、パルス幅測定回路15でこのパルス幅を測
定している。パルス幅測定回路15において、位相比較
器14からのパルス幅信号と短周期のクロック発生器1
51の出力とをANDlff回路152に入力し、パル
ス幅信号か生じている間のクロックがカウンタ153で
計数される。カウンタ153の内容はパルス幅信号の立
上りで各周期の初めにリセットされている。第4図は位
相比較器14のパルス幅出力とAND回路152の出力
との関係を示すタイムチャートである。Unlike the case in FIG. 1, the phase comparator 14 outputs a pulse width corresponding to the phase difference, such as an edge trigger type, and this pulse width is measured by a pulse width measuring circuit 15. In the pulse width measuring circuit 15, the pulse width signal from the phase comparator 14 and the short period clock generator 1 are connected to each other.
51 is input to an ANDlff circuit 152, and a counter 153 counts the clocks while the pulse width signal is being generated. The contents of counter 153 are reset at the beginning of each cycle at the rising edge of the pulse width signal. FIG. 4 is a time chart showing the relationship between the pulse width output of the phase comparator 14 and the output of the AND circuit 152.
各周期の計数出力の差分が一定となるように制御回路6
で制御する点は第1図の場合と同様で、パルス幅測定回
路15と制御回路6とが近似的な微分回路を構成してい
る。The control circuit 6
The point of control is the same as in the case of FIG. 1, and the pulse width measuring circuit 15 and the control circuit 6 constitute an approximate differentiating circuit.
なお上記の各実施例では微分回路をデジタル回路で実現
しているが、A/D変換器を用いずにアナログ的な微分
回路を用いることもできる。Note that in each of the above embodiments, the differentiating circuit is implemented by a digital circuit, but an analog differentiating circuit can also be used without using an A/D converter.
ハ、r本発明の効果J
以上述べたように、本発明によれば、基準周波数を低く
することなく高速応答で、基準周波数の整数倍より高分
解能の位相同期ループ回路を簡単な構成で実現すること
ができる。C. Effects of the present invention J As described above, according to the present invention, a phase-locked loop circuit with a high-speed response and a resolution higher than an integer multiple of the reference frequency can be realized with a simple configuration without lowering the reference frequency. can do.
第1図は本発明に係る位相同期ループ回路の一実施例を
示す構成ブロック図、第2図は第1図装置の動作を示す
タイムチャート、第3図は本発明に係る位相同期ループ
回路の第2の実施例を示す構成ブロック図、第4図は第
3図装置の動作の一部を示すタイムチャート、第5図は
従来の位相同期ループ回路を示す構成ブロック図である
。FIG. 1 is a configuration block diagram showing an embodiment of the phase-locked loop circuit according to the present invention, FIG. 2 is a time chart showing the operation of the device shown in FIG. 1, and FIG. 3 is a block diagram of the phase-locked loop circuit according to the present invention. FIG. 4 is a time chart showing a part of the operation of the device shown in FIG. 3, and FIG. 5 is a block diagram showing a conventional phase locked loop circuit.
Claims (1)
出力と基準信号との位相差を位相比較器で検出し位相比
較器の出力に対応する信号で電圧制御発振器の出力周波
数を制御する位相同期ループ回路において、位相比較器
から出力される位相差信号の単位時間当たりの変化量が
一定となるように電圧制御発振器を制御する制御手段を
備えることを特徴とする位相同期ループ回路。The output of the voltage controlled oscillator is divided by a frequency dividing circuit, the phase difference between the output of this frequency divider and the reference signal is detected by a phase comparator, and the output frequency of the voltage controlled oscillator is determined by the signal corresponding to the output of the phase comparator. A phase-locked loop circuit to be controlled, comprising a control means for controlling a voltage-controlled oscillator so that the amount of change per unit time of the phase difference signal output from the phase comparator is constant. .
Priority Applications (1)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
JP63168299A JPH0219025A (en) | 1988-07-06 | 1988-07-06 | Phase locked loop circuit |
Applications Claiming Priority (1)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
JP63168299A JPH0219025A (en) | 1988-07-06 | 1988-07-06 | Phase locked loop circuit |
Publications (1)
Publication Number | Publication Date |
---|---|
JPH0219025A true JPH0219025A (en) | 1990-01-23 |
Family
ID=15865443
Family Applications (1)
Application Number | Title | Priority Date | Filing Date |
---|---|---|---|
JP63168299A Pending JPH0219025A (en) | 1988-07-06 | 1988-07-06 | Phase locked loop circuit |
Country Status (1)
Country | Link |
---|---|
JP (1) | JPH0219025A (en) |
Cited By (2)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
WO2006074847A1 (en) * | 2005-01-14 | 2006-07-20 | Robert Bosch Gmbh | Analog-digital converter |
JP2009027581A (en) * | 2007-07-23 | 2009-02-05 | Renesas Technology Corp | Semiconductor integrated circuit |
-
1988
- 1988-07-06 JP JP63168299A patent/JPH0219025A/en active Pending
Cited By (3)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
WO2006074847A1 (en) * | 2005-01-14 | 2006-07-20 | Robert Bosch Gmbh | Analog-digital converter |
US8188900B2 (en) | 2005-01-14 | 2012-05-29 | Robert Bosch Gmbh | Analog-digital converter |
JP2009027581A (en) * | 2007-07-23 | 2009-02-05 | Renesas Technology Corp | Semiconductor integrated circuit |
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