JPH02125508A - Input circuit - Google Patents
Input circuitInfo
- Publication number
- JPH02125508A JPH02125508A JP63279794A JP27979488A JPH02125508A JP H02125508 A JPH02125508 A JP H02125508A JP 63279794 A JP63279794 A JP 63279794A JP 27979488 A JP27979488 A JP 27979488A JP H02125508 A JPH02125508 A JP H02125508A
- Authority
- JP
- Japan
- Prior art keywords
- operational amplifier
- input
- output
- amplifier circuit
- signal
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Pending
Links
- 230000005540 biological transmission Effects 0.000 abstract description 5
- 230000005669 field effect Effects 0.000 description 12
- 238000010586 diagram Methods 0.000 description 3
- 239000000470 constituent Substances 0.000 description 1
- 230000007423 decrease Effects 0.000 description 1
- 238000005516 engineering process Methods 0.000 description 1
Abstract
Description
【発明の詳細な説明】
〔産業上の利用分野〕
本発明は、入力回路に関し、特に2線式通信方式におけ
る受信器の様に、同相入力電圧範囲が広く2線間の電位
差が微小な信号を用いる用途に適した入力回路に関する
。[Detailed Description of the Invention] [Industrial Application Field] The present invention relates to an input circuit, and in particular, the present invention relates to an input circuit, and in particular, to a receiver in a two-wire communication system, a signal having a wide common-mode input voltage range and a small potential difference between two wires is used. This invention relates to an input circuit suitable for applications using.
従来この種の入力回路は、第2図の回路が用いられてい
た。第2図の構成としては第3図又は第4図の様であっ
た。まず第3図について説明する。Conventionally, the circuit shown in FIG. 2 has been used as this type of input circuit. The configuration of FIG. 2 was similar to that of FIG. 3 or 4. First, FIG. 3 will be explained.
1は反転入力端子、2は非反転入力端子、3は電圧出力
端子であり、抵抗12と電界効果トランジスタ4はバイ
アス回路を構成しており電界゛効果トランジスタ5,6
,7,8.9は差動増幅回路を構成し、電界効果トラン
ジスタ10.11は電圧出力回路を構成している。1 is an inverting input terminal, 2 is a non-inverting input terminal, and 3 is a voltage output terminal. A resistor 12 and a field effect transistor 4 constitute a bias circuit, and field effect transistors 5 and 6
, 7, 8.9 constitute a differential amplifier circuit, and field effect transistors 10.11 constitute a voltage output circuit.
この回路は、抵抗12と電界効果トランジスタ4でバイ
アス電流が決まり、電界効果トランジスタ4と9がカレ
ントミラーを構成している為、バイアス電流は、差動増
幅回路にも流れる。In this circuit, the bias current is determined by the resistor 12 and the field effect transistor 4, and since the field effect transistors 4 and 9 constitute a current mirror, the bias current also flows to the differential amplifier circuit.
反転入力端子1と非反転入力端子2の端子間電圧は差動
増幅回路で増幅され、さらに、電界効果トランジスタ1
0.11で構成している電圧出力回路で増幅されて電圧
出力端子3に出力される。The voltage between the inverting input terminal 1 and the non-inverting input terminal 2 is amplified by a differential amplifier circuit, and the field effect transistor 1
The voltage is amplified by a voltage output circuit configured with a voltage of 0.11, and is output to the voltage output terminal 3.
第4図についても同様である。第3図と第4図の違いは
、構成しているトランジスタの違いであり、それぞれ同
相入力電圧範囲が第3図の構成の場合では、グランド電
位(以下GNDと称す)+αから電源電圧(以下VDD
と称す)までであり、第5図の51の範囲となり、第4
図の構成の場合ではGNDからVDD−αまでであり、
第5図の52の範囲となる。The same applies to FIG. The difference between Fig. 3 and Fig. 4 is the difference in the constituent transistors. In the case of the configuration shown in Fig. 3, the common-mode input voltage range ranges from ground potential (hereinafter referred to as GND) +α to power supply voltage (hereinafter referred to as GND). VDD
), which corresponds to the range 51 in Figure 5, and the fourth
In the case of the configuration shown in the figure, it is from GND to VDD-α,
This is the range 52 in FIG.
従来の入力回路は、差動増幅回路の出力を電圧出力回路
を介して出力する構成になっている為、次の様な欠点を
持っていた。Conventional input circuits have the following drawbacks because they are configured to output the output of a differential amplifier circuit via a voltage output circuit.
第3図を例に説明すると、反転入力端子1及び非反転入
力端子2の電位を下げてくると、これに伴なって電界効
果トランジスタ9のドレイン電位も下ってくる。Taking FIG. 3 as an example, when the potentials of the inverting input terminal 1 and the non-inverting input terminal 2 are lowered, the drain potential of the field effect transistor 9 is also lowered accordingly.
電界効果トランジスタ9において、ゲート。In field effect transistor 9, the gate.
ソース間電圧V。3とドレイン、ソース間を圧vnsの
関係が
Van<Vos VT
(ただし、■、は電界効果トランジスタ7.8゜9のし
きい値電FE)
になると、電界効果ト・ランジスタ9のドレイン電流は
減少してゆき、
V[<V T
(ただしVtNは入力端子1.2の電圧)では、電界効
果トランジスタ9のドレイン電流はゼロにたり、入力回
路として動作しなくなる。Source-to-source voltage V. When the relationship between the voltage vns between 3 and the drain and source is Van<Vos VT (where ■ is the threshold voltage FE of the field effect transistor 7.8°9), the drain current of the field effect transistor 9 is When V[<V T (however, VtN is the voltage at the input terminal 1.2), the drain current of the field effect transistor 9 becomes zero and it no longer operates as an input circuit.
従ってこの様な入力回路を2線式通信方式の受信用増幅
器として用いた場合、同相入力電圧が低下すると受信信
号を受は付けなくなり、通信が不能となる欠点があった
。Therefore, when such an input circuit is used as a receiving amplifier in a two-wire communication system, there is a drawback that when the common mode input voltage decreases, the receiving signal is no longer received, making communication impossible.
また、第4図についても同様であり、第4図の場合、同
相入力電圧が高くなると、受信信号を受は付けなくなる
欠点があった。Further, the same applies to FIG. 4, and in the case of FIG. 4, there is a drawback that when the common mode input voltage becomes high, the received signal cannot be received.
以上の欠点は、広い入力電圧範囲を要求され、かつ、入
力端子の電位差が小さい2線式通信方式の受信器用入力
回路等では重大な欠点であった。The above drawbacks are serious in input circuits for receivers using two-wire communication systems, which require a wide input voltage range and have a small potential difference between input terminals.
本発明の入力回路は、異なる導電型の素子で構成された
第1及び第2の演算増幅回路を有し、各々の非反転入力
及び反転入力を並列に接続し、それぞ、れの出力を信号
選択回路のデータ入力とし、選択信号に一人力を任意の
定電圧源に接続し、他方の入力を入力端子に接、続した
第3の演算増幅回路の出力を接続して、信号選択回路の
出力を出力端子とした構成をしている。The input circuit of the present invention has first and second operational amplifier circuits configured with elements of different conductivity types, each of which has its non-inverting input and inverting input connected in parallel, and its output. The data input of the signal selection circuit is connected to the selection signal, one input is connected to an arbitrary constant voltage source, the other input is connected to the input terminal, and the output of the third operational amplifier circuit is connected to the signal selection circuit. The configuration is such that the output of is used as the output terminal.
次に本発明の一実施例について説明する。 Next, one embodiment of the present invention will be described.
異なる導電型素子で構成された演算増幅回路31及び3
2のそれぞれの非反転入力には入力端子21反転入力に
は入力端子1を接続している。Operational amplifier circuits 31 and 3 configured with elements of different conductivity types
Input terminal 21 is connected to each non-inverting input of 2, and input terminal 1 is connected to the inverting input.
ここで、演算増幅回路31は、第3図の構成の様になっ
ている。Here, the operational amplifier circuit 31 has a configuration as shown in FIG.
同相入力電圧範囲は、第5図の51の範囲となる。また
、演算増幅回路32は、第4図の構成の様になっている
。The common mode input voltage range is the range 51 in FIG. Further, the operational amplifier circuit 32 has a configuration as shown in FIG.
同相入力電圧範囲は、第5図の52の範囲となる。The common mode input voltage range is the range 52 in FIG.
次に、演算増幅回路33の非反転入力には、入力端子2
を接続し、反転入力端子には定電圧源35(以後VRと
称す)を接続する。VRの設定電圧範囲は、演算増幅回
路31の同相入力電圧範囲の下限値以上、演算増幅回路
32の同相入力電圧範囲の上限以下つまり、第5図の5
3の範囲に設定する。Next, the non-inverting input of the operational amplifier circuit 33 is connected to the input terminal 2.
A constant voltage source 35 (hereinafter referred to as VR) is connected to the inverting input terminal. The set voltage range of VR is greater than or equal to the lower limit of the common-mode input voltage range of the operational amplifier circuit 31 and less than or equal to the upper limit of the common-mode input voltage range of the operational amplifier circuit 32, that is, 5 in FIG.
Set to a range of 3.
以上により、入力端子2に入力される信号とVRとを演
算増幅回路33で比較し、VRより高い電圧の場合演算
増幅回路33の出力は、VDDとなりトラスミッション
ゲート21がONし、演算増幅回路31の出力信号が出
力端子3に現われる。As described above, the signal input to the input terminal 2 and VR are compared by the operational amplifier circuit 33, and if the voltage is higher than VR, the output of the operational amplifier circuit 33 becomes VDD, the transmission gate 21 is turned on, and the operational amplifier circuit 31 output signals appear at output terminal 3.
また反対にVRより低い電圧の場合、演算増幅回路33
の出力は、GNDとなりトラスミッションゲート22が
ONt、演算増幅回路32の出力信号が出力端子3に現
われる。Conversely, if the voltage is lower than VR, the operational amplifier circuit 33
The output becomes GND, the transmission gate 22 is turned on, and the output signal of the operational amplifier circuit 32 appears at the output terminal 3.
また、入力端子1及び2に入力される信号の振幅が微小
である為、この実施例の他に、演算増幅回路33の非反
転入力には、入力端子1でも可能である。Furthermore, since the amplitudes of the signals input to the input terminals 1 and 2 are minute, the input terminal 1 may be used as the non-inverting input of the operational amplifier circuit 33 in addition to this embodiment.
以上説明したように、本発明は、導電型の異なる素子で
構成した2つの演算増幅回路の出力の内、適切な動作範
囲に入っている方の出力を選択する事により、グランド
電位から電源電位までの広い入力範囲にわたって増幅器
として動作する為2線式通信方式の受信器用入力回路で
の従来の可動を解決でき、同相入力電圧がグランド電位
から電源電位まで受信信号を受は付けるので、安定に通
信できる効果がある。As explained above, the present invention can change the power supply voltage from the ground potential to the power supply voltage by selecting the output of two operational amplifier circuits composed of elements of different conductivity types, which is within the appropriate operating range. Because it operates as an amplifier over a wide input range up to It has the effect of communicating.
第1図は、本発明の一実施例の回路図、第2図は、従来
の回路図、第3図、第4図は、演算増幅回路の一構成例
である。
第5図は、第3図、第4図の動作範囲を示す説明図であ
る。
第1図〜第5図において
1.2・・・・・・入力端子、3・・・・・・出力端子
、4〜11・・・・・・電界効果トランジスタ、12・
・・・・・抵抗、21.22・・・・・・トランスミッ
ションゲート、25・・・・・・電源ffDD)、26
・・・・・・グランド(GND)、31〜33.35・
・・・・・演算増幅回路、34・・・・・・定電圧源(
V R)、51.52・・・・・・同相入力電圧範囲、
53・・・・・・定電圧源の設定範囲。
代理人 弁理士 内 原 晋
箭乙回
消3図
第4図FIG. 1 is a circuit diagram of an embodiment of the present invention, FIG. 2 is a conventional circuit diagram, and FIGS. 3 and 4 are examples of the configuration of an operational amplifier circuit. FIG. 5 is an explanatory diagram showing the operating range of FIGS. 3 and 4. FIG. 1 to 5, 1.2...input terminal, 3...output terminal, 4-11...field effect transistor, 12...
... Resistor, 21.22 ... Transmission gate, 25 ... Power supply ffDD), 26
・・・・・・Ground (GND), 31~33.35・
...Operation amplifier circuit, 34... Constant voltage source (
V R), 51.52...Common mode input voltage range,
53... Setting range of constant voltage source. Agent: Patent Attorney Uchihara Shinjutsu Figure 3 Figure 4
Claims (1)
幅回路のそれぞれの非反転入力に入力端子1、反転入力
に入力端子2を並列に接続し、第1及び第2の演算増幅
回路の出力信号をデータ入力とし、選択信号入力として
、入力端子1又は入力端子2を非反転入力又は反転入力
に接続し、残りの入力に任意の定電圧源を接続した第3
の演算増幅回路の出力を接続した信号選択回路により該
データ入力の内いずれかを一方を出力とする選択回路の
出力を出力端子とする事を特徴とする入力回路。The input terminal 1 is connected in parallel to the non-inverting input of each of the first and second operational amplifier circuits, which are configured with elements of different conductivity types, and the input terminal 2 is connected to the inverting input in parallel, so that the first and second operational amplifier circuits are connected in parallel. The output signal of is used as a data input, input terminal 1 or input terminal 2 is connected to a non-inverting input or an inverting input as a selection signal input, and an arbitrary constant voltage source is connected to the remaining inputs.
An input circuit characterized in that a signal selection circuit connected to an output of an operational amplifier circuit has an output terminal as an output terminal of the selection circuit which outputs one of the data inputs.
Priority Applications (1)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
JP63279794A JPH02125508A (en) | 1988-11-04 | 1988-11-04 | Input circuit |
Applications Claiming Priority (1)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
JP63279794A JPH02125508A (en) | 1988-11-04 | 1988-11-04 | Input circuit |
Publications (1)
Publication Number | Publication Date |
---|---|
JPH02125508A true JPH02125508A (en) | 1990-05-14 |
Family
ID=17616001
Family Applications (1)
Application Number | Title | Priority Date | Filing Date |
---|---|---|---|
JP63279794A Pending JPH02125508A (en) | 1988-11-04 | 1988-11-04 | Input circuit |
Country Status (1)
Country | Link |
---|---|
JP (1) | JPH02125508A (en) |
Cited By (1)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
CN102910192A (en) * | 2012-10-25 | 2013-02-06 | 北京铁路信号有限公司 | Security input isolating circuit and track circuit receiver provided with same |
Citations (2)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
JPS55140310A (en) * | 1979-04-18 | 1980-11-01 | Mitsubishi Electric Corp | Voltage follower circuit |
JPS6361810B2 (en) * | 1983-10-11 | 1988-11-30 |
-
1988
- 1988-11-04 JP JP63279794A patent/JPH02125508A/en active Pending
Patent Citations (2)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
JPS55140310A (en) * | 1979-04-18 | 1980-11-01 | Mitsubishi Electric Corp | Voltage follower circuit |
JPS6361810B2 (en) * | 1983-10-11 | 1988-11-30 |
Cited By (2)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
CN102910192A (en) * | 2012-10-25 | 2013-02-06 | 北京铁路信号有限公司 | Security input isolating circuit and track circuit receiver provided with same |
CN102910192B (en) * | 2012-10-25 | 2015-11-25 | 北京铁路信号有限公司 | A kind of safe input isolation circuit and there is the track circuit receiver of this circuit |
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